WO2017215170A1 - 一种非接触传感器电路 - Google Patents

一种非接触传感器电路 Download PDF

Info

Publication number
WO2017215170A1
WO2017215170A1 PCT/CN2016/102682 CN2016102682W WO2017215170A1 WO 2017215170 A1 WO2017215170 A1 WO 2017215170A1 CN 2016102682 W CN2016102682 W CN 2016102682W WO 2017215170 A1 WO2017215170 A1 WO 2017215170A1
Authority
WO
WIPO (PCT)
Prior art keywords
capacitor
operational amplifier
circuit
contact sensor
inverting input
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2016/102682
Other languages
English (en)
French (fr)
Inventor
张丽敏
唐跃
吴绒绒
闫锋
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Nanjing University
Nanjing Tech University
Original Assignee
Nanjing University
Nanjing Tech University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nanjing University, Nanjing Tech University filed Critical Nanjing University
Publication of WO2017215170A1 publication Critical patent/WO2017215170A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

Links

Images

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R1/00—Details of instruments or arrangements of the types included in groups G01R5/00 - G01R13/00 and G01R31/00
    • G01R1/20—Modifications of basic electric elements for use in electric measuring instruments; Structural combinations of such elements with such instruments
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof

Definitions

  • non-contact detection there are two types of low-frequency electrical signal detection methods: contact and non-contact.
  • capacitive coupling is usually used for measurement.
  • an extremely high input impedance circuit is usually required.
  • this leakage current will continuously charge the coupling capacitor, increase the input offset voltage of the circuit, and cause the DC output of the operational amplifier to drift greatly, and even tend to saturate, resulting in the circuit.
  • the dynamic operating range is limited and affects the operational stability of the op amp.
  • an appropriate input bias circuit design is performed to reduce output drift, such as a high-impedance input bias circuit such as a bootstrap and a diode.
  • a high-impedance input bias circuit such as a bootstrap and a diode.
  • the effect of the input bias circuit bleed-through coupling capacitor to accumulate charge is contradictory to the implementation of the input impedance.
  • the invention aims at the deficiencies in the prior art, and proposes a non-contact sensor circuit, which has a simple structure, can realize near-DC signal detection under the condition of skin-size non-contact coupling capacitance, and has the characteristics of adjustable gain and bandwidth.
  • the present invention provides the following technical solutions:
  • a non-contact sensor circuit comprising a capacitor C 2 , a resistor R 1 , a resistor R 2 and an operational amplifier A; one end of the capacitor C 2 is connected to the non-inverting input terminal of the operational amplifier A, and the other end thereof is grounded; One end of R 1 is connected to the inverting input terminal of the operational amplifier A, and the other end thereof is grounded; one end of the resistor R 2 is connected to the inverting input terminal of the operational amplifier A, and the other end thereof is connected to the output end of the operational amplifier A.
  • the circuit further comprises a capacitor C 1, the capacitor C 1 as a non-contact coupling capacitor having one end connected to the signal, the detection electrode and the other end is connected with the operational amplifier A to the inverting input terminal.
  • the value of the capacitance C 2 is less than the value of the capacitance C 1 .
  • the circuit further includes a capacitor C 6 , one end of the capacitor C 6 is connected to the non-inverting input terminal of the operational amplifier A, and the other end of the capacitor C 6 is connected to the output end of the operational amplifier A.
  • the circuit further comprises a capacitor C 3, one end of the capacitor C 3 is connected to an electrical terminal of the capacitor C 1 is detected, with the other end of the capacitor C 3 of the operational amplifier A is connected to the inverting input terminal.
  • the circuit further includes a capacitor C 4 , one end of the capacitor C 4 is connected to the inverting input end of the operational amplifier A, and the other end of the capacitor C 4 is connected to the output end of the operational amplifier A.
  • the operational amplifier A is set as a buffer, that is, the inverting input terminal and the output terminal of the operational amplifier A are directly connected. .
  • a capacitance C 5 is added between the inverting input terminal and the output terminal of the operational amplifier A.
  • the value of the capacitor C 5 is of the same order of magnitude as the value of the capacitor C 2 .
  • the gain of the circuit can be adjusted by adjusting the ratio of the resistors R 2 and R 1 .
  • the circuit structure is simple, the filtering characteristics can be appropriately increased, and the physical achievability is good.
  • Figure 1 is a circuit diagram of Embodiment 1 of the present invention.
  • FIG. 2 is a circuit diagram of Embodiment 2 of the present invention.
  • Figure 3 is a circuit diagram of Embodiment 3 of the present invention.
  • Figure 4 is a circuit diagram of Embodiment 4 of the present invention.
  • Figure 5 is a circuit diagram of Embodiment 5 of the present invention.
  • Figure 6 is a circuit diagram of Embodiment 6 of the present invention.
  • the method includes: a detecting component, a capacitive coupling device, configured to generate a measurement signal from the signal to be tested; a basic part of the circuit, configured to receive the measurement signal as an input and provide a detection signal of the amplified feature as an output; To limit the detection signal bandwidth.
  • the detecting part is realized by a capacitive coupling method, and the capacitive coupling device commonly used in the prior art can be used as a detecting component to detect the measured signal Vs, and the measuring signal is transmitted to the circuit input terminal Vi, and the equivalent circuit diagram is shown in FIG. 1 part.
  • the basic part of the circuit includes a capacitor C 2 , a resistor R 1 , a resistor R 2 and an operational amplifier A.
  • One end of the capacitor C 2 is connected to the detection signal and the non-inverting input terminal of the operational amplifier A, and the other end thereof is grounded; one end of the resistor R 1 is connected to the operational amplifier A The inverting input terminal is grounded at the other end; one end of the resistor R 2 is connected to the inverting input terminal of the operational amplifier A, and the other end thereof is connected to the output terminal of the operational amplifier A.
  • the capacitance value of C 2 is smaller than the capacitance value of C 1 , and the measurement signal can be obtained by means of capacitive voltage division.
  • the circuit theoretically has no low-frequency cutoff frequency and has the capability of detecting a near-DC signal.
  • the gain of the circuit can be adjusted by adjusting the ratio of the resistors R 2 and R 1 .
  • the capacitor C 2 acts to accumulate charge discharge to the coupling capacitor C 1 .
  • the leakage current at the input of the operational amplifier will inevitably charge the capacitor C 1 , causing the charge of the capacitor C 1 to accumulate. If there is no corresponding bleeder circuit in the circuit, the output current of the operational amplifier A will drift greatly, and the output will be close to saturation.
  • the dynamic input range is very limited and can cause operational amplifier A to be unstable.
  • the charge accumulated on the capacitor C 1 is discharged to the ground through the capacitor C 2 , which significantly reduces the output drift of the operational amplifier A, allowing the operational amplifier A to operate at a high gain without output saturation, thereby improving the dynamic input of the signal. Range and operational stability of operational amplifier A.
  • a detection portion and a circuit portion are included.
  • Change detecting section the circuit portion of the circuit on the basis of FIG. 1, the capacitance C 1 between the non-inverting input terminal of the operational amplifier A is connected in series circuit of capacitor C 3, C 3 of the capacitor can be large in the case of the input coupling capacitor Reduce circuit output drift.
  • a detection portion and a circuit portion are included.
  • the detection part is unchanged, and the circuit part is based on the circuit of FIG. 1, and the capacitor C 4 is connected at both ends of the resistor R 2 to realize low-pass filtering, limit the detection signal bandwidth, and reduce the noise floor of the circuit.
  • a detection portion and a circuit portion are included.
  • the detection part is unchanged, and the circuit part is based on the circuit of Fig. 1, the resistance R1 is infinite, and the resistance R2 is 0.
  • the inverting input terminal and the output terminal of the operational amplifier A are connected and set as a buffer.
  • a detection portion and a circuit portion are included.
  • the detection part is unchanged, and the circuit part is based on the circuit of FIG. 4, and a capacitor C 5 is added between the inverting input terminal and the output terminal of the operational amplifier A, and the capacitor C 5 as a balanced capacitor can further reduce the two inputs of the operational amplifier A.
  • the input offset current between the terminals increases the dynamic input range of the signal.
  • the value of capacitor C 5 should be of the same order of magnitude as capacitor C 2 .
  • a detecting portion and a circuit portion are included.
  • Change detecting section the sensor circuit portion of the circuit on the basis of FIG. 1, the operational amplifier A between the inverting input terminal and the output terminal of the series capacitor C 6, to further reduce the play from the operational amplifier noninverting input terminal to ground capacitance effect.
  • the scheme for increasing the capacitance C6 is equally applicable to the circuits of Figures 2, 3, 4 and 5.

Landscapes

  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Measurement Of Resistance Or Impedance (AREA)
  • Amplifiers (AREA)

Abstract

一种非接触传感器电路，该电路包括电容C 2、电阻R 1、电阻R 2和运算放大器A；电容C 2的一端连接运算放大器A的同相输入端，其另一端接地；电阻R 1的一端连接运算放大器A的反相输入端，其另一端接地；电阻R 2的一端连接运算放大器A的反相输入端，其另一端连接运算放大器A的输出端。该电路结构简单，实现了皮法大小非接触耦合电容情况下的近直流信号检测，且具有增益和带宽可调特征。

Description

一种非接触传感器电路 技术领域
本发明涉及一种非接触传感器电路，具体地说是一种电容耦合式非接触传感器电路，属于电容耦合机理的传感技术领域。
背景技术
低频电信号检测方式有接触式和非接触式两大类。在非接触检测中，通常采用电容耦合方式进行测量，为了实现较低的频率检测性能，通常需要极高输入阻抗电路。另一方面，由于运算放大器输入级存在输入漏电流，此漏电流会给耦合电容不断地充电，增大电路输入失调电压，使得运算放大器输出很大的直流漂移，甚至趋于饱和，导致电路的动态工作范围受到限制，且影响运算放大器的工作稳定性。为此，通常电容耦合方式的检测电路中，会进行适当的输入偏置电路设计，降低输出漂移，如自举和二极管等高阻抗输入偏置电路。然而，输入偏置电路泄放耦合电容积累电荷的效果和输入阻抗实现是相矛盾的，实现的输入阻抗越高越不利于泄放耦合电容的积累电荷。因此，已有方法很难实现大于20GΩ输入阻抗，进而难以实现非接触电容为皮法大小时小于1Hz的近直流低频信号的有效检测。
中国专利CN201420252432.7的技术中，通过采取有源屏蔽能实现较好地非接触测量，然而该电路结构相对复杂，且由于没有合适的输入偏置电路，存在着输出直流漂移较大的问题，不利于检测电路的长时间稳定工作。
发明内容
本发明针对现有技术中存在的不足，提出一种非接触传感器电路，结构简单，可实现皮法大小非接触耦合电容情况下的近直流信号检测，且具有增益和带宽可调特征。
为了达到以上目的，本发明提供如下技术方案：
一种非接触传感器电路，该电路包括电容C2、电阻R1、电阻R2和运算放大器A；所述电容C2的一端连接运算放大器A的同相输入端，其另一端接地；所述电阻R1的一端连接运算放大器A的反相输入端，其另一端接地；所述电阻R2的一端连接运算放大器A的反相输入端，其另一端连接运算放大器A的输出端。
进一步地，所述电路还包括电容C1，所述电容C1作为非接触耦合电容，其一端连接被测信号，另一端为检测电极，连接到所述运算放大器A的同相输入端。
优选地，所述电容C2的值小于电容C1的值。
进一步地，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
进一步地，所述电路还包括电容C3，所述电容C3的一端连接所述电容C1的检测电极端，所述电容C3的另一端连接所述运算放大器A的同相输入端。
进一步地，所述电路还包括电容C4，所述电容C4的一端连接所述运算放大器A的反相输入端，所述电容C4的另一端连接所述运算放大器A的输出端。
进一步地，所述电路中，电阻R1的值为无穷大，电阻R2的值为0，这时所述运算放大器A设置为缓冲器，即所述运算放大器A的反相输入端和输出端直接相连。
进一步地，所述电路中，在运算放大器A的反相输入端和输出端之间增加电容C5。
优选地，所述电容C5的值与电容C2的值为同一数量级。
本发明提出的非接触传感器电路的显著优点在于：
(1)适当的选择电容C2的值，可以减小电路的输出漂移。
(2)电路理论上没有低频截止频率，可以实现皮法大小非接触耦合电容情况下的近直流信号检测。
(3)可以通过调整电阻R2和R1的比值调整电路的增益。
(4)电路结构简单，可以适当增加滤波特性，物理可实现性好。
附图说明
图1是本发明实施例1的电路图；
图2是本发明实施例2的电路图；
图3是本发明实施例3的电路图；
图4是本发明实施例4的电路图；
图5是本发明实施例5的电路图；
图6是本发明实施例6的电路图。
具体实施方式
下面结合附图对本发明作进一步的描述和介绍。
本发明实施例中，包括：检测部件，电容耦合装置，用于从被测信号产生测量信号；电路基本部分，用以接受测量信号作为输入以及提供被放大特征的检测信号作为输出；电路滤波部分，用以限制检测信号带宽。
实施例1：
参见图1，仅包括检测部分和电路基本部分。该检测部分采用电容耦合方式实现，可以采用现有技术中常用的电容耦合装置作为检测部件检测被测信号Vs，产生测量信号传输给电路输入端Vi，等效电路图如图1所示的电容C1部分。该电路基本部分包括电容C2，电阻R1，电阻R2和运算放大器A，电容C2一端连接检测信号和运算放大器A同相输入端，其另一端接地；电阻R1的一端连接运算放大器A的反相输入端，其另一端接地；电阻R2的一端连接运算放大器A的反相输入端，其另一端连接运算放大器A的输出端。
此处，一般取C2的容值小于C1的容值，可实现通过电容分压的方式获得测量信号，电路理论上没有低频截止频率，具有检测近直流信号的能力。同时，可以通过调整电阻R2和R1的比值调整电路的增益。
同时，电容C2起到对耦合电容C1累积电荷泄放的作用。运算放大器输入端的漏电流不可避免地会给电容C1充电，造成电容C1电荷累积，若电路中没有相应的泄放回路，将使得运算放大器A输出直流漂移很大，输出接近饱和，信号的动态输入范围受到很大限制，且会导致运算放大器A工作不稳定。在该发明中，电容C1上累积的电荷通过电容C2泄放到地，显著降低运算放大器A的输出漂移，允许运算放大器A在高增益下工作不会输出饱和，进而提高信号的动态输入范围和运算放大器A的工作稳定性。
实施例2：
参见图2，包括检测部分、电路部分。检测部分不变，电路部分为在图1电路基础上，在电容C1与运算放大器A同相输入端的连接电路之间串接电容C3，所述电容C3在输入耦合电容较大情况下能够减小电路输出漂移。
实施例3：
参见图3，包括检测部分、电路部分。检测部分不变，电路部分为在图1电路基础上，在电阻R2的两端并接电容C4，实现低通滤波，限制检测信号带宽，同时降低电路的本底噪声。
实施例4：
参见图4，包括检测部分、电路部分。检测部分不变，电路部分为在图1电路基础上，电阻R1值为无穷大，电阻R2值为0，这时运算放大器A的反相输入端和输出端相连，设置为缓冲器。
实施例5：
参见图5，包括检测部分、电路部分。检测部分不变，电路部分为在图4电路基础上，在运算放大器A的反相输入端和输出端之间增加电容C5，电容C5作为平衡电容能够进一步减小运算放大器A的两输入端之间的输入失调电流，提高信号动态输入范围。电容C5的值应与电容C2的值为同一数量级。
实施例6：
参见图6，包括检测部分、电路部分。检测部分不变，传感器电路部分为在图1电路基础上，在运算放大器A的同相输入端和输出端之间串联电容C6，起到进一步降低从运算放大器同相输入端到地电容的作用。增加电容C6的方案同样适用于图2、3、4和5的电路。
需要说明的是上所述实施例，并非用来限定本发明的保护范围。即凡依本技术方案的基础上所作的等同变换或替代及修饰，皆应落入本发明权利要求所保护的范围。

Claims (13)

  1. 一种非接触传感器电路，其特征在于，该电路包括电容C2、电阻R1、电阻R2和运算放大器A；所述电容C2的一端连接运算放大器A的同相输入端，其另一端接地；所述电阻R1的一端连接运算放大器A的反相输入端，其另一端接地；所述电阻R2的一端连接运算放大器A的反相输入端，其另一端连接运算放大器A的输出端。
  2. 根据权利要求1所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C1，所述电容C1作为非接触耦合电容，其一端连接被测信号，另一端为检测电极，连接到所述运算放大器A的同相输入端。
  3. 根据权利要求2所述的一种非接触传感器电路，其特征在于，所述电容C2的值小于电容C1的值。
  4. 根据权利要求1、2或3所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
  5. 根据权利要求1、2或3所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C3，所述电容C3的一端连接所述电容C1的检测电极端，所述电容C3的另一端连接所述运算放大器A的同相输入端。
  6. 根据权利要求5所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
  7. 根据权利要求1、2或3所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C4，所述电容C4的一端连接所述运算放大器A的反相输入端，所述电容C4的另一端连接所述运算放大器A的输出端。
  8. 根据权利要求7所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
  9. 根据权利要求1、2或3所述的一种非接触传感器电路，其特征在于，所述电路中，电阻R1的值为无穷大，电阻R2的值为0，这时所述运算放大器A设置为缓冲器，即所述运算放大器A的反相输入端和输出端直接相连。
  10. 根据权利要求9所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
  11. 根据权利要求9所述的一种非接触传感器电路，其特征在于，所述电路中，在运算放大器A的反相输入端和输出端之间增加电容C5。
  12. 根据权利要求11所述的一种非接触传感器电路，其特征在于，所述电路还包括电容C6，所述电容C6的一端连接所述运算放大器A的同相输入端，所述电容C6的另一端连接运算放大器A的输出端。
  13. 根据权利要求11所述的一种非接触传感器电路，其特征在于，所述电容C5的值与电容C2的值为同一数量级。
PCT/CN2016/102682 2016-06-15 2016-10-20 一种非接触传感器电路 Ceased WO2017215170A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201610423617.3A CN107632213B (zh) 2016-06-15 2016-06-15 一种非接触传感器电路
CN201610423617.3 2016-06-15

Publications (1)

Publication Number Publication Date
WO2017215170A1 true WO2017215170A1 (zh) 2017-12-21

Family

ID=60663418

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2016/102682 Ceased WO2017215170A1 (zh) 2016-06-15 2016-10-20 一种非接触传感器电路

Country Status (2)

Country Link
CN (1) CN107632213B (zh)
WO (1) WO2017215170A1 (zh)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114036880B (zh) * 2021-11-09 2025-09-26 南京大学 一种低噪声高带宽的电流传感芯片设计

Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4757263A (en) * 1987-05-01 1988-07-12 Tennessee Valley Authority Insulation power factor alarm monitor
US4914382A (en) * 1987-10-14 1990-04-03 Hydro-Quebec High voltage measuring circuit coupled to the capacitive grounding tap bushing of an HV device
CN1053684A (zh) * 1989-12-07 1991-08-07 Gec阿尔斯托姆公司 电压测量电路
US20030160602A1 (en) * 2002-02-27 2003-08-28 Anand Ramesh K. Power factor/tan delta testing of high voltage bushings on power transformers, current transformers, and circuit breakers
CN101490564A (zh) * 2006-07-18 2009-07-22 苏塞克斯大学 电位传感器
CN101556306A (zh) * 2009-05-07 2009-10-14 西安交通大学 开关电器弧后介质恢复强度纳秒连续脉冲测量装置及方法
CN102971636A (zh) * 2010-06-29 2013-03-13 特英普科技有限公司 用于测量绝缘体的损耗因数的装置和方法
CN105049070A (zh) * 2015-07-27 2015-11-11 北京理工大学 用于植入式医疗仪器的上行近场通信接收机

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10332312A (ja) * 1997-06-05 1998-12-18 Tokyo Seimitsu Co Ltd 非接触センサ及び静電容量センサ
JP4385825B2 (ja) * 2004-03-31 2009-12-16 オムロン株式会社 近接センサ
US7256588B2 (en) * 2004-04-16 2007-08-14 General Electric Company Capacitive sensor and method for non-contacting gap and dielectric medium measurement
CN201811999U (zh) * 2010-09-01 2011-04-27 辽宁工程技术大学 非接触式静电感应传感器

Patent Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4757263A (en) * 1987-05-01 1988-07-12 Tennessee Valley Authority Insulation power factor alarm monitor
US4914382A (en) * 1987-10-14 1990-04-03 Hydro-Quebec High voltage measuring circuit coupled to the capacitive grounding tap bushing of an HV device
CN1053684A (zh) * 1989-12-07 1991-08-07 Gec阿尔斯托姆公司 电压测量电路
US20030160602A1 (en) * 2002-02-27 2003-08-28 Anand Ramesh K. Power factor/tan delta testing of high voltage bushings on power transformers, current transformers, and circuit breakers
CN101490564A (zh) * 2006-07-18 2009-07-22 苏塞克斯大学 电位传感器
CN101556306A (zh) * 2009-05-07 2009-10-14 西安交通大学 开关电器弧后介质恢复强度纳秒连续脉冲测量装置及方法
CN102971636A (zh) * 2010-06-29 2013-03-13 特英普科技有限公司 用于测量绝缘体的损耗因数的装置和方法
CN105049070A (zh) * 2015-07-27 2015-11-11 北京理工大学 用于植入式医疗仪器的上行近场通信接收机

Also Published As

Publication number Publication date
CN107632213B (zh) 2020-08-11
CN107632213A (zh) 2018-01-26

Similar Documents

Publication Publication Date Title
JP5777082B2 (ja) 電位センサ
US6714070B1 (en) Differential charge amplifier with built-in testing for rotation rate sensor
JP6744695B2 (ja) アクティブ・シャント電流計
CN102545793A (zh) 一种pA-μA量程的微弱电流放大器
WO2017166058A1 (zh) 便携式电子设备、电容触摸屏和电容检测电路
US8228054B2 (en) Method and apparatus for amplifying a signal and test device using same
CN204347174U (zh) 一种基于磁调制的直流漏电流传感器
CN104515931A (zh) 一种基于磁调制的直流漏电流传感器
JP5588413B2 (ja) 広帯域低雑音センサ増幅回路
US9112455B2 (en) Signal amplifying circuit for electromagnetic flow meter
WO2017215170A1 (zh) 一种非接触传感器电路
CN112217480A (zh) 一种基于电容器反馈的跨阻放大器及光电传感器
CN106788327B (zh) 一种接触与非接触检测兼用的传感器电路
KR20100101062A (ko) 센서 회로
CN114910857A (zh) 电容式传感器中的电气故障的诊断
CN112737517A (zh) 适用于电池内阻测量的交流小信号差分放大滤波电路
WO2015083604A1 (ja) 信号増幅装置及びセンサー装置
KR101001865B1 (ko) 비접촉식 센서 회로
JPWO2025225039A5 (zh)
CN210380775U (zh) 一种电荷灵敏前置放大器
CN113125832B (zh) 全频段电流传感器
KR101001863B1 (ko) 비접촉식 센서 회로
CN100466474C (zh) 电压至电流转换电路装置
RU2703671C1 (ru) Усилитель бесконтактного электрометра и цепь обратной связи
CN114859134A (zh) 一种基于差分运放的电容检测电路

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 16905282

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 16905282

Country of ref document: EP

Kind code of ref document: A1