WO2017049596A1 - 发射机相位自适应调整的方法以及发射机 - Google Patents

发射机相位自适应调整的方法以及发射机 Download PDF

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Publication number
WO2017049596A1
WO2017049596A1 PCT/CN2015/090748 CN2015090748W WO2017049596A1 WO 2017049596 A1 WO2017049596 A1 WO 2017049596A1 CN 2015090748 W CN2015090748 W CN 2015090748W WO 2017049596 A1 WO2017049596 A1 WO 2017049596A1
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Prior art keywords
baseband signal
signal
transmitter
vector
baseband
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Ceased
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PCT/CN2015/090748
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English (en)
French (fr)
Inventor
张宜成
邢志刚
刘勇
郭晓乐
杨宝锋
李云华
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Hytera Communications Corp Ltd
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Hytera Communications Corp Ltd
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Priority to PCT/CN2015/090748 priority Critical patent/WO2017049596A1/zh
Publication of WO2017049596A1 publication Critical patent/WO2017049596A1/zh
Anticipated expiration legal-status Critical
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits

Definitions

  • the present invention relates to the field of wireless communication technologies, and in particular, to a method for transmitter phase adaptive adjustment and a transmitter.
  • FIG. 1 is a schematic diagram of a simulation principle of a Cartesian ring transmitter in the prior art.
  • Iin and Qin are orthogonal baseband signals, that is, baseband signals I1 and Q1.
  • the baseband signals I1 and Q1 are orthogonally modulated by the low pass filter LPF1, the multiplier MIX1, and the low pass filter LPF2 and the multiplier MIX2, respectively, to obtain a modulated radio frequency signal, and the modulated radio frequency signal is transmitted from the antenna port RF_out.
  • the directional coupler Couple of the transmission channel couples the partially modulated signal into the feedback channel, and modulates the coupled portion in the feedback channel.
  • the latter signal is subjected to quadrature demodulation through the low pass filter LPF3, the multiplier MIX3, and the low pass filter LPF4 and the multiplier MIX4 to obtain demodulated baseband signals I2 and Q2.
  • Comparators U1 and U2 compare the initial baseband signal (Iin, Qin) and the demodulated baseband signal (I2, Q2), and subtractively obtain the error signal generated by the initial baseband signal during transmission. And according to the above error signal, the signal transmission channel is compensated, that is, the distortion of the transmission channel power amplifier is compensated.
  • the error signal between the baseband signal (Iin, Qin) and the demodulated baseband signal (I2, Q2) It must be controlled within a certain range, that is, the phase difference between the vector (I1, Q1) and the vector (I2, Q2) must be controlled within a limited range.
  • the baseband signal (Iin, Qin) produces a phase shift value of D from the signal path between the modulator and the demodulator, represented by a phase shifter PS4.
  • the phase difference is A, which is represented by the phase shifter PS2.
  • the phase of the demodulated baseband signal (I2, Q2) is to be the same as the phase of the baseband signal (I1, Q1) before modulation, the correlation of the baseband signal is achieved.
  • the value of the shift parameter of the phase shifter PS2 is generally compensated to the same value as that of the PS4 by the compensation measure, and then the shift value A is saved in the fixed ROM of the transmitter, and in use. No adjustments are needed.
  • the improved method is simpler, the above scheme can only perform open-loop compensation on the phase, and there is no adaptive mechanism.
  • the calibration obtains the value of A, and the fixed value is not changed.
  • the feedback loop will oscillate.
  • the Cartesian ring can work normally, wherein the input signals are as shown in FIGS. 3A-3B.
  • the large phase deviation caused by factors such as environment, temperature or component aging cannot be compensated.
  • the technical problem to be solved by the present invention is to provide a method for transmitter phase adaptive adjustment and a transmitter, which can effectively realize phase adaptive adjustment of the transmitter, improve the adaptability of the transmitter to environmental changes and component aging, and ensure The signal in the transmit channel is stable.
  • a first aspect of the present invention provides a method for phase adjustment of a transmitter, including:
  • the first baseband signal and the second baseband signal are respectively compensated according to the sine value and the cosine value.
  • the step of compensating the first baseband signal and the second baseband signal according to the sine value and the cosine value respectively includes :
  • the first baseband signal and the second baseband signal are separately compensated in real time based on the sine value and the cosine value.
  • the step of compensating the first baseband signal and the second baseband signal according to the sine value and the cosine value respectively comprises :
  • the first baseband signal and the second baseband signal are respectively compensated according to the stored sine value and the cosine value in a predetermined period.
  • the sinusoidal value and the cosine value respectively correspond to the first
  • the step of compensating the baseband signal and the second baseband signal further includes:
  • the compensated first baseband signal and the second baseband signal are modulated and amplified, and then transmitted through the antenna.
  • the first demodulated signal and the second demodulated signal are orthogonal to the first baseband signal and the second baseband signal Demodulated signal.
  • a second aspect of the present invention provides a transmitter, where the transmitter has a phase adaptive adjustment function, including: an acquisition unit, an operation unit, and a compensation unit.
  • the collecting unit is configured to acquire a first baseband signal, a second baseband signal, and a first demodulated signal and a second demodulated signal in the feedback channel of the forward channel of the transmitter, where the first baseband signal And the second baseband signal is a quadrature signal; the first demodulated signal corresponds to the first baseband information, and the second demodulated signal corresponds to the second baseband signal;
  • the operation unit is configured to form a first vector by the first baseband signal and the second baseband signal, and the first demodulated signal and the second demodulated signal form a second vector to determine the first a sine and cosine of a phase difference between the vector and the second vector;
  • the compensation unit is configured to compensate the first baseband signal and the second baseband signal according to the sine value and the cosine value, respectively.
  • the compensation unit is specifically configured to perform the first baseband signal and the second according to the sine value and the cosine value respectively in real time.
  • the baseband signal is compensated.
  • the transmitter further includes a storage unit
  • the storage unit is configured to collect and store the sine value and the cosine value in a predetermined period
  • the compensation unit is specifically configured to compensate the first baseband signal and the second baseband signal according to the stored sine value and the cosine value respectively during the predetermined period.
  • the transmitter further includes a transmitting unit, where the transmitting unit is configured to compensate The first baseband signal and the second baseband signal are modulated and amplified, and then transmitted through an antenna.
  • the computing unit and the compensation unit are located in a forward channel, a feedback channel, a local oscillator channel of a forward RF channel, and a feedback of the transmitter Anywhere in the local oscillator channel of the channel.
  • a third aspect of the present invention provides a transmitter, the transmitter having a phase adaptive adjustment function, including: a processor and a memory,
  • the processor is configured to acquire a first baseband signal, a second baseband signal, and a first demodulated signal and a second demodulated signal in the feedback channel of the forward channel of the transmitter, where the first baseband signal is The second baseband signal is a quadrature signal; the first demodulated signal corresponds to the first baseband information, and the second demodulated signal corresponds to the second baseband signal;
  • the processor is further configured to form a first vector by the first baseband signal and the second baseband signal, and form a second vector by the first demodulated signal and the second demodulated signal to determine the a sine value and a cosine value of a phase difference between the first vector and the second vector; respectively compensating the first baseband signal and the second baseband signal according to the sine value and the cosine value;
  • the memory is configured to store a program running in the processor and data generated during the running of the program.
  • the processor is specifically configured to perform the first baseband signal and the second according to the sine value and the cosine value respectively in real time.
  • the baseband signal is compensated.
  • the processor is specifically configured to collect and store the sine value and the cosine value in a predetermined period; and in the predetermined period, according to The stored sinusoidal value and the cosine value compensate for the first baseband signal and the second baseband signal, respectively.
  • the processor is located in a forward channel, a feedback channel, a local oscillator channel of a forward RF channel, and a local oscillator channel of the feedback channel Anywhere.
  • the utility model has the beneficial effects that the transmitter of the embodiment forms a first vector and acquires a feedback channel by collecting the orthogonal first baseband signal and the second baseband signal of the forward channel of the transmitter, which are different from the prior art.
  • the first demodulated signal and the second demodulated signal form a second vector, and the sine and cosine values of the phase deviation generated by the transmitter in the signal transmission are determined according to the phase difference between the first vector and the second vector, and
  • the first baseband signal and the second baseband signal are compensated according to the sine value and the cosine value, and then transmitted.
  • the compensated first baseband signal and the second baseband signal corresponding to the aging components can be obtained, and the baseband signal and demodulation are ensured without interrupting the communication of the transmitter.
  • the error between the baseband signals is controlled within the effective range, and the influence of unfavorable factors such as aging on the transmitter is overcome, thereby ensuring the basic stability of the transmitter signal transmission and enhancing the practicality of the transmitter.
  • FIG. 1 is a schematic diagram of a simulation principle of a working mode of a prior art Cartesian ring transmitter
  • 2A is a first comparative diagram of a prior art before and after modulation when the phase deviation of the prior art Cartesian ring transmitter is 0 degrees;
  • 2B is a second comparative diagram of the prior art before and after modulation when the phase deviation of the prior art Cartesian ring transmitter is 0 degrees;
  • 2C is a schematic diagram of a waveform of a transmitted signal when the phase deviation of the prior art Cartesian ring transmitter is 0 degrees;
  • 3A is a schematic diagram of a waveform of a first baseband signal Iin before phase modulation of a prior art Cartesian ring transmitter
  • 3B is a schematic diagram of a second baseband signal Qin waveform before phase modulation of a prior art Cartesian ring transmitter
  • 4A is a first comparative diagram of signals before and after modulation when the phase deviation of the prior art Cartesian ring transmitter is 60 degrees;
  • 4B is a second comparison diagram of signals before and after modulation when the phase deviation of the prior art Cartesian ring transmitter is 60 degrees;
  • 4C is a schematic diagram of a waveform of a transmitted signal when the phase deviation of the prior art Cartesian ring transmitter is 60 degrees;
  • FIG. 5 is a schematic diagram of a simulation principle of a first embodiment of an adaptive adjustment transmitter of the present invention.
  • FIG. 6 is a schematic flow chart of an implementation manner of a transmitter adaptive adjustment method according to the present invention.
  • FIG. 7 is a schematic diagram of a simulation principle of the integral comparison circuit of the present invention.
  • FIG. 8 is a schematic diagram of a mathematical principle for determining phase offset according to the present invention.
  • FIG. 9 is a schematic diagram of a simulation principle for determining a phase difference sine value and a cosine value according to the present invention.
  • FIG. 10 is a schematic diagram showing the simulation principle of clock compensation of the first baseband signal and the second baseband signal in the present invention
  • FIG. 11 is a schematic diagram of a simulation principle of a second embodiment of the adaptive adjustment transmitter of the present invention.
  • FIG. 12 is a schematic diagram of a simulation principle of a third embodiment of the adaptive adjustment transmitter of the present invention.
  • FIG. 13 is a schematic diagram of a simulation principle of a fourth embodiment of the adaptive adjustment transmitter of the present invention.
  • 14A is a first comparative diagram of signals before and after modulation when the phase deviation of the Cartesian ring transmitter of the present invention is 60 degrees;
  • 14B is a second comparative diagram of signals before and after modulation when the phase deviation of the Cartesian ring transmitter of the present invention is 60 degrees;
  • 14C is a waveform diagram of a transmitted signal when the phase deviation of the Cartesian ring transmitter of the present invention is 60 degrees;
  • 15 is a schematic flow chart of another embodiment of a transmitter adaptive adjustment method according to the present invention.
  • 16 is a schematic diagram of a simulation principle of a fifth embodiment of the adaptive adjustment transmitter of the present invention.
  • FIG. 17 is a schematic structural view of an embodiment of a transmitter of the present invention.
  • FIG. 18 is a schematic structural view of another embodiment of a transmitter of the present invention.
  • FIG. 19 is a block diagram showing still another embodiment of the transmitter of the present invention.
  • FIG. 5 is a schematic diagram of a simulation principle of an embodiment of the adaptive adjustment transmitter of the present invention, and simulates the working process of the transmitter through a simulation diagram.
  • the transmitter of the present invention is a Cartesian ring transmitter.
  • the Cartesian ring transmitter of the present embodiment includes a forward channel for orthogonally demodulating orthogonal baseband signals, and the forward channel includes a low pass filter LPF1, a multiplier MIX1, and a low pass filter.
  • the multiplier MIX3, the low pass filter LPF4, and the multiplier MIX4, the Cartesian ring transmitter further includes a signal acquisition circuit U102 for comparing the baseband signal and the demodulated signal, and a compensation circuit U101 for phase compensation of the baseband signal.
  • the orthogonal first baseband signal Iin and the second baseband signal Qin are orthogonally modulated by the low pass filter LPF1, the multiplier MIX1, and the low pass filter LPF2 and the multiplier MIX2 to obtain a modulated signal.
  • the directional coupler of the feedback channel couples the partially modulated signal into the feedback channel.
  • the partially modulated signal passes through the low pass filter LPF3, the multiplier MIX3, and the low pass filter LPF4, multiplier.
  • MIX4 realizes quadrature demodulation, and obtains the demodulated first demodulated signal I2 and the second demodulated signal Q2, and the signal collecting circuit U102 collects the first baseband signal Iin, the second baseband signal Qin, and the feedback channel of the transmitter respectively.
  • the demodulated signal Q2 determines a sine value and a cosine value of a phase difference between a vector composed of the first baseband signal Iin and the second baseband signal Qin and a vector composed of the first demodulated signal I2 and the second demodulated signal Q2, and the compensation circuit U101 Compensating the first baseband signal Iin and the second baseband signal Qin according to the sine value and the cosine value, respectively, and passing the compensated first baseband signal and the second baseband signal through a low pass filter
  • the LPF 1, the multiplier MIX1, and the low pass filter LPF2 and the multiplier MIX2 are orthogonally modulated, and the amplifier AMP1 is amplified and transmitted through the antenna RF_out.
  • the comparison circuit U102 and the compensation circuit U101 can be directly integrated in the controller of the Cartesian ring transmitter, or can be implemented by adding additional hardware, which is not limited herein.
  • FIG. 6 is a schematic flowchart of an embodiment of a method for phase adaptive adjustment of a transmitter according to the present invention.
  • the method for transmitter phase adaptive adjustment of this embodiment includes the following steps:
  • the orthogonal first baseband signal Iin and the second baseband signal Qin pass through the integral comparison circuits U1 and U2 and the low pass filter LPF1, the multiplier MIX1, and the low pass filter LPF2, the multiplier MIX2 implements quadrature modulation to obtain a modulated signal.
  • U1 and U2 work as shown in Figure 7.
  • the baseband signal in the present embodiment records the first baseband signal Iin as I1 and the second baseband signal as Q1.
  • the modulated signal is amplified by the amplifier AMP1 to obtain a radio frequency signal.
  • the transmitter can transmit the radio frequency signal from the antenna port RF_out.
  • the directional coupler of the feedback channel couples the partially modulated signal into the feedback channel, and
  • the feedback channel performs the orthogonal demodulation of the coupled partially modulated signal through the low pass filter LPF3, the multiplier MIX3, and the low pass filter LPF4 and the multiplier MIX4 to obtain the demodulated first demodulated signal I2 and the second.
  • Demodulation signal Q2 the demodulated first demodulated signal I2 and the second.
  • the transmitter separately acquires the first baseband signal I1, the second baseband signal Q1, the first demodulated signal I2 corresponding to the first baseband signal I1, and the second baseband The second demodulated signal Q2 corresponding to the signal.
  • the component that completes this step in the simulation diagram 5 is the signal acquisition circuit U102. In the actual transmitter can be directly implemented by the control chip.
  • 602 Form a first vector by the first baseband signal and the second baseband signal, where the first demodulated signal and the second demodulated signal form a second vector, determining the first vector and the The sine and cosine values of the phase difference of the second vector.
  • the first demodulated signal I2 and the second demodulated signal Q2 collected in the feedback channel are obtained by orthogonal mediation. If there is no phase offset in the signal transmission, the demodulated The phases of the first demodulated signal I2 and the second demodulated signal Q2 are the same as those of the first baseband signal I1 and the second baseband signal Q1 before modulation. Therefore, to compensate for the phase, the phase offset is first determined.
  • the phase offset is determined by combining the first baseband signal I1 and the second baseband signal Q1 into a first vector 1 (I1, Q1), and forming the first demodulated signal I2 and the second demodulated signal Q2 into a second
  • the vector 2 (I2, Q2) then calculates the sine and cosine values of the phase difference of the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2).
  • FIG. 8 is a schematic diagram of the mathematical principle of determining the phase offset of the present invention.
  • R1 is the amplitude of the first vector 1 (I1, Q1)
  • r2 is the amplitude of the second vector 2 (I2, Q2)
  • x represents the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2)
  • the phase angle between the two corresponds to the first baseband signal I1 and the second baseband signal Q1, respectively the first baseband signal I1, and the second baseband signal Q1 corresponds to the first demodulated signal I2 and the second solution. Adjust the phase deviation x of the signal Q2.
  • the first demodulated signal I2 and the second demodulated signal Q2 are exemplified by a counterclockwise phase shift x with respect to the first baseband signal I1 and the second baseband signal Q1.
  • the first baseband signal I1 and the second baseband signal Q1 perform clockwise compensation x,
  • the first vector 1 (I1, Q1) is represented by the second vector 2 (I2, Q2) as follows:
  • the second vector 2 (I2, Q2) can be represented by the first vector 1 (I1, Q1):
  • I2 I1*cos(x) - Q1*sin(x),
  • the sine value sin(x) and the cosine value cos(x) of the phase deviation can be expressed by the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2):
  • this step can be implemented by the signal acquisition circuit U102.
  • this step can be directly integrated into the controller of the transmitter, or can be adjusted by adding additional additions.
  • the device and the multiplier are implemented, and the corresponding simulation diagrams of the adder and the multiplier are shown in FIG. 9.
  • 603 Compensating the first baseband signal and the second baseband signal according to the sine value and the cosine value, respectively.
  • the Cartesian ring transmitter After determining the sine and cosine values of the phase deviation, the Cartesian ring transmitter compensates the first baseband signal I1 and the second baseband signal Q1 in real time according to the sine and cosine values of the phase deviation.
  • the second vector 2 (I2, Q2) composed of the first demodulated signal I2 and the second demodulated signal Q2 is opposite to the first baseband signal I1 and the second baseband signal Q1
  • a vector 1 (I1, Q1) exhibits a counterclockwise phase deviation
  • the first baseband signal I1 is based on the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the two baseband signals Q1 are clockwise compensated, and the compensated first baseband signal I1 and the second baseband signal Q1 are obtained as follows:
  • this step can be implemented by the compensation circuit U101, and corresponding to the actual hardware circuit, this step can be directly integrated into the controller of the transmitter, or can be adjusted by adding an additional adder.
  • the multiplier is implemented, and the corresponding simulation diagram of the working principle of the adder and the multiplier is as shown in FIG.
  • the first baseband signal I1 and the second baseband signal Q1 are counterclockwise compensated according to the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the compensated first baseband signal I1 and the second baseband signal Q1 are as follows:
  • I1 I2*cos(x) – Q2*sin(x),
  • the two sets of calculation formulas in the present embodiment are merely exemplified by a method of introducing a vector by a mathematical method under the idea of the present invention, and are not limited.
  • the compensation idea is to compensate the first baseband signal I1 and the second baseband signal Q1 by other calculation methods. Any manner of compensating for phase deviation by the compensation idea of the present invention is within the scope of the present invention.
  • the present invention is not limited to only compensating the first baseband signal I1 and the second baseband signal Q1 in the forward channel.
  • the first baseband signal I1 may also be implemented on the feedback channel.
  • the second baseband signal Q1 is compensated, and the simulation principle diagram of the working mode is shown in FIG. 11. The compensation idea and the calculation method are the same as those in this embodiment, and are not described herein.
  • the Cartesian ring transmitter can compensate the first baseband signal I1 and the second baseband signal Q1 in the forward channel or the feedback channel.
  • the local oscillator channel or feedback in the forward channel can also be used.
  • the local oscillator channel of the channel performs phase compensation, performs phase compensation on the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel, and directly performs the first baseband signal I1 and the second baseband signal Q1 on the forward channel or the feedback channel.
  • the idea of compensation is the same, but since the first baseband signal I1 and the second baseband signal I1 are low frequency signals, when the phase compensation of the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel is performed, it is required to operate in the high frequency signal region.
  • the simulation diagram of the specific working principle is shown in Figure 12 and Figure 13.
  • 12 is a schematic diagram of the simulation principle of phase compensation of the local oscillator channel of the forward channel.
  • 13 is a schematic diagram of the simulation principle of phase compensation for the local oscillator channel of the feedback channel.
  • the embodiment further includes the step of transmitting the compensated first baseband signal and the second baseband signal by modulation and amplification, and then transmitting through the antenna.
  • the compensated first baseband signal is modulated by the low pass filter LPF1 and the multiplier MIX1 to obtain a compensated first modulated signal
  • the compensated second baseband signal passes through the low pass filter LPF2.
  • the multiplier MIX2 performs modulation to obtain the compensated second modulated signal, and the first modulated signal and the second modulated signal are orthogonally modulated, and then the modulated first modulated signal and the second modulated signal are amplified by the amplifier AMP1. It is sent out through the antenna RF_out.
  • the transmitted signals are as shown in Figs. 14A to 14C, wherein the first baseband signal and the second baseband signal are input in the same manner as in the prior art in order to compare the difference between the present invention and the prior art, as shown in Figs. 3A to 3B.
  • the transmitter of the embodiment forms a first vector by collecting the orthogonal first baseband signal and the second baseband signal of the forward channel of the transmitter, and acquires the first demodulated signal and the first in the feedback channel. Demodulating the signal to form a second vector, determining a sine value and a cosine value of the phase deviation generated by the transmitter in the signal transmission according to the phase difference between the first vector and the second vector, and according to the sine and cosine values The first baseband signal and the second baseband signal are compensated and transmitted.
  • the compensated first baseband signal and the second baseband signal corresponding to the aging components can be obtained, and the baseband signal and demodulation are ensured without interrupting the communication of the transmitter.
  • the error between the baseband signals is controlled within the effective range, and the influence of unfavorable factors such as aging on the transmitter is overcome, thereby ensuring the basic stability of the transmitter signal transmission and enhancing the practicality of the transmitter.
  • the phase deviation generally does not change greatly in a short time, and the first baseband signal and the second baseband signal need not be collected in real time to save the transmitter controller resources.
  • FIG. 15 is a schematic flowchart diagram of another embodiment of a method for phase adaptive adjustment of a transmitter according to the present invention.
  • the present embodiment is different from the previous embodiment in that the transmitter consists of the first baseband signal and the second baseband signal to form a first vector, which is composed of the first demodulated signal and the second demodulated signal.
  • a second vector after the step of determining a sine value and a cosine value of a phase difference between the first vector and the second vector, further comprising:
  • Step 1503 Acquire and store sine and cosine values in a predetermined period.
  • the present embodiment sets a predetermined period within a predetermined period. Collecting the sine and cosine values of the phase difference, and storing the collected sine and cosine values. In this cycle, the first baseband signal and the second baseband signal are compensated by the stored sine and cosine values. When the next cycle arrives, the acquisition and storage are resumed, and the first baseband signal and the second baseband signal of the current cycle are compensated by the sine and cosine values of the newly acquired phase.
  • FIG. 16 is a schematic diagram of a simulation principle of a fifth embodiment of the adaptive adjustment transmitter of the present invention.
  • the simulation schematic diagram of the present embodiment is different from the simulation schematic diagrams of the previous embodiments in that a sampling and holding circuit U103 and a sample and hold circuit U103 are further included between the acquisition circuit U102 and the compensation circuit U101, and are enabled by an additional one.
  • the signal is triggered.
  • the sample and hold circuit U103 acquires a signal and saves the current signal for compensation of the first baseband signal and the second baseband signal in the current cycle.
  • this step can also be directly integrated into the controller of the transmitter, or can be realized by adding additional acquisition memory.
  • the added acquisition memory can be placed not only in the middle of the acquisition circuit and the compensation circuit, but also in the middle. At both ends of the acquisition circuit and the compensation circuit, three circuits can be directly integrated into one circuit. As a whole, as long as the functions of acquisition, storage, and compensation can be completed, there is no limitation here.
  • the transmitter uses the feedback of the first baseband signal and the second baseband signal in the feedback channel, or compensates the phase on the local oscillator channel of the forward channel, or performs phase on the local oscillator channel of the feedback channel.
  • the above steps can be added to the compensation, and are not limited herein.
  • the transmitter of the embodiment forms a first vector by collecting the orthogonal first baseband signal and the second baseband signal of the forward channel of the transmitter, and acquires the first demodulated signal and the first in the feedback channel. Demodulating the signal to form a second vector, determining a sine value and a cosine value of the phase deviation generated by the transmitter in the signal transmission according to the phase difference between the first vector and the second vector, and according to the sine and cosine values The first baseband signal and the second baseband signal are compensated and transmitted.
  • the compensated first baseband signal and the second baseband signal corresponding to the aging components can be obtained, and the baseband signal and demodulation are ensured without interrupting the communication of the transmitter.
  • the error between the baseband signals is controlled within the effective range, and the influence of unfavorable factors such as aging on the transmitter is overcome, thereby ensuring the basic stability of the transmitter signal transmission and enhancing the practicality of the transmitter.
  • the Cartesian ring transmitter of the present embodiment acquires and stores the sine and cosine values of the phase difference in a predetermined period after acquiring the sine and cosine values of the phase, and in this cycle. Compensating the first baseband signal and the second baseband signal according to the stored sine value and the cosine value can further save the transmitter resources, improve the working efficiency of the transmitter, and enhance the practicability of the transmitter while ensuring the stability of the transmitted signal.
  • Figure 17 is a block diagram showing an embodiment of a transmitter of the present invention.
  • the transmitter of the embodiment is a Cartesian ring transmitter.
  • the transmitter of the present embodiment includes an acquisition unit 1701, an operation unit 1702, and a compensation unit 1703.
  • the acquiring unit 1701 is configured to collect a first baseband signal, a second baseband signal, and a first demodulated signal and a second demodulated signal in the feedback channel, where the first baseband signal is collected.
  • the second baseband signal is a quadrature signal; the first demodulated signal corresponds to the first baseband information, and the second demodulated signal corresponds to the second baseband signal.
  • the acquisition unit 1701 respectively acquires the first baseband signal I1, the second baseband signal Q1, the first demodulated signal I2 corresponding to the first baseband signal I1, and the second The second demodulated signal Q2 corresponding to the baseband signal.
  • the operation unit 1702 is configured to form a first vector by the first baseband signal and the second baseband signal, where the first demodulated signal and the second demodulated signal form a second vector, and the first vector is determined A sine and cosine of the phase difference from the second vector.
  • the first demodulated signal I2 and the second demodulated signal Q2 collected in the feedback channel are obtained by orthogonal mediation. If there is no phase offset in the signal transmission, the demodulated The phases of the first demodulated signal I2 and the second demodulated signal Q2 are the same as those of the first baseband signal I1 and the second baseband signal Q1 before modulation. Therefore, to compensate for the phase, the phase offset is first determined.
  • the operation unit 1702 determines the phase offset by forming the first baseband signal I1 and the second baseband signal Q1 into the first vector 1 (I1, Q1), and forming the first demodulated signal I2 and the second demodulated signal Q2 into the second
  • the vector 2 (I2, Q2) then calculates the sine and cosine values of the phase difference of the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2).
  • r1 is the amplitude of 1 (I1, Q1)
  • r2 is the amplitude of the second vector 2 (I2, Q2)
  • x represents the first vector 1 (I1, Q1) and the second vector 2 (I2,
  • the phase angle between Q2) corresponds to the phase deviation x between the first baseband signal I1 and the second baseband signal Q1 and the first demodulated signal I2 and the second demodulated signal Q2.
  • the operation unit 1702 exemplifies a counterclockwise phase shift x with respect to the first baseband signal I1 and the second baseband signal Q1, and correspondingly, the compensation unit 1703
  • the first baseband signal I1 and the second baseband signal Q1 need to be clockwise compensated x,
  • the calculation process of the arithmetic unit 1702 is as follows,
  • the first vector 1 (I1, Q1) is represented by the second vector 2 (I2, Q2) as follows:
  • the second vector 2 (I2, Q2) can be represented by the first vector 1 (I1, Q1):
  • I2 I1*cos(x) - Q1*sin(x),
  • the sine value sin(x) and the cosine value cos(x) of the phase deviation may be represented by the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2):
  • the compensation unit 1703 is configured to compensate the first baseband signal and the second baseband signal according to the sine value and the cosine value, respectively.
  • the compensation unit 1703 compensates the first baseband signal I1 and the second baseband signal Q1 in real time according to the sine and cosine values of the phase deviation.
  • the compensation unit 1703 pairs the first baseband signal I1 and the second baseband signal Q1 according to the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the compensated first baseband signal I1 and the second baseband signal Q1 are as follows:
  • the first baseband signal I1 and the second baseband signal Q1 are counterclockwise compensated according to the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the compensated first baseband signal I1 and the second baseband signal Q1 are as follows:
  • I1 I2*cos(x) – Q2*sin(x),
  • the two sets of calculation formulas used by the compensation circuit 1703 in the present embodiment are merely exemplified by a method of introducing a vector by a mathematical method under the idea of the present invention, and are not limited.
  • the first baseband signal I1 and the second baseband signal Q1 can be compensated by other calculation methods according to the compensation idea of the present embodiment. Any manner of compensating for phase deviation by the compensation idea of the present invention is within the scope of the present invention.
  • the compensation unit 1703 is not limited to the first baseband signal I1 and the second baseband signal Q1 in the forward channel. In other embodiments, the compensation unit 1703 can also implement the pair on the feedback channel. A baseband signal I1 and a second baseband signal Q1 are compensated, and the compensation idea and the calculation method are the same as those in this embodiment, and are not described herein.
  • the compensation unit 1703 can compensate the first baseband signal I1 and the second baseband signal Q1 in the forward channel or the feedback channel.
  • the compensation channel 1703 can also be in the local channel or the feedback channel of the forward channel.
  • the local oscillator channel performs phase compensation, performs phase compensation on the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel, and directly compensates the first baseband signal I1 and the second baseband signal Q1 in the forward channel or the feedback channel.
  • first baseband signal I1 and the second baseband signal I1 are low frequency signals, when the phase compensation of the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel is performed, it is required to operate in the high frequency signal region. Not limited.
  • the transmitter of the embodiment further includes a transmitting unit 1704, and the transmitting unit 1704 is configured to use the compensated first baseband signal and the first The two baseband signals are modulated and amplified and transmitted through the antenna.
  • the transmitting unit 1704 amplifies the first modulated signal and the second modulated signal obtained by respectively modulating the compensated first baseband signal and the second baseband signal with respective low-pass filters and multipliers through an amplifier. Send out through the antenna.
  • the phase can be automatically adjusted in real time without interrupting the normal communication, and the adaptability of the product to the phase deviation caused by adverse effects such as environmental factors and aging factors can be enhanced, and even if the phase deviation is large, the phase can be obtained more stably. transmit a signal.
  • the transmitter of the embodiment collects the first baseband signal and the second baseband signal of the forward channel of the transmitter through the collecting unit to form a first vector, and collects the first demodulated signal in the feedback channel. And the second demodulated signal, forming a second vector, the operation unit determining a sine value and a cosine value of the phase deviation generated by the transmitter in the signal transmission according to the phase difference between the first vector and the second vector, the compensation unit according to the sine The value and the cosine value are compensated for the first baseband signal and the second baseband signal are transmitted.
  • the compensated first baseband signal and the second baseband signal corresponding to the aging components can be obtained, and the baseband signal and demodulation are ensured without interrupting the communication of the transmitter.
  • the error between the baseband signals is controlled within the effective range, and the influence of unfavorable factors such as aging on the transmitter is overcome, thereby ensuring the basic stability of the transmitter signal transmission and enhancing the practicality of the transmitter.
  • the phase deviation generally does not change greatly in a short time, and the first baseband signal and the second baseband signal need not be collected in real time to save the transmitter controller resources.
  • the transmitter of the present embodiment includes, in addition to the acquisition unit 1801, the operation unit 1802, the compensation unit 1803, and the transmission unit 1804, and a storage unit 1805.
  • the storage unit is configured to acquire and store sine and cosine values for a predetermined period.
  • the present embodiment sets a predetermined period, and the storage unit 1805 is The sine and cosine values of the phase difference are acquired in a predetermined period, and the sine and cosine values are collected, and in this period, the compensation unit 1803 passes the stored sine and cosine values to the first baseband signal and The two baseband signals are compensated.
  • the storage unit 1804 re-acquires and stores, and the compensation unit 1803 passes the newly acquired phase sine and cosine values to the first baseband signal and the second baseband of the current cycle. The signal is compensated.
  • the transmitter triggers the storage unit 1805 by using an additional enable signal.
  • the storage unit 1805 collects the signal once and saves the current signal for the compensation unit 1803.
  • the first baseband signal and the second baseband signal are compensated internally.
  • the compensation unit 1803 compensates the first baseband signal and the second baseband signal in the feedback channel, or compensates the phase on the local oscillator channel of the forward channel, or compensates the phase on the local oscillator channel of the feedback channel.
  • a compensation unit 1805 can be added, and the sine and cosine values are collected and stored by the storage unit 1805 for a predetermined period, and the compensation unit 1803 compensates the first baseband signal and the second baseband signal in the current period. I will not go into details here.
  • the storage unit acquires and stores the sine and cosine values of the phase difference in a predetermined period, and the compensation unit In the current cycle, the first baseband signal and the second baseband signal are compensated according to the stored sine and cosine values, which can further save the transmitter resources, improve the transmitter working efficiency, and enhance the transmission while ensuring the stability of the transmitted signal. The practicality of the machine.
  • FIG. 19 is a schematic structural diagram of still another embodiment of the transmitter of the present invention.
  • the transmitter of the embodiment is a Cartesian ring transmitter.
  • the 1900 transmitter of the present embodiment includes a processor 1901 and a memory 1902.
  • the processor 1901 and the memory 1902 of the transmitter 1900 are coupled together by a bus 1903.
  • the bus 1903 may include a power bus, a control bus, a status signal bus, and the like in addition to the data bus.
  • various buses are labeled as bus 1903 in the figure.
  • the processor 1901 is configured to acquire a first baseband signal, a second baseband signal, and a first demodulated signal and a second demodulated signal in the feedback channel of the forward channel of the transmitter, where the first baseband signal is The second baseband signal is a quadrature signal; the first demodulated signal corresponds to the first baseband information, and the second demodulated signal corresponds to the second baseband signal;
  • the processor 190 is further configured to form a first vector by the first baseband signal and the second baseband signal, and form a second vector from the first demodulated signal and the second demodulated signal to determine a sine value and a cosine value of a phase difference between the first vector and the second vector; and the first baseband signal and the second baseband signal are respectively compensated according to the sine value and the cosine value.
  • the compensated first baseband signal and the second baseband signal are amplified by modulation and transmitted through the antenna.
  • the orthogonal first baseband signal Iin and the second baseband signal Qin of the transmitter are orthogonally modulated by an integral comparison circuit and a low pass filter and a multiplier, respectively, to obtain a modulated signal.
  • the baseband signal in the present embodiment records the first baseband signal Iin as I1 and the second baseband signal as Q1.
  • the modulated signal is amplified by an amplifier to obtain a radio frequency signal.
  • the transmitter can transmit the radio frequency signal from the antenna port.
  • the transmitter feedback channel couples the partially modulated signal to the feedback channel through the directional coupler, and
  • the modulated signal corresponding to the first baseband signal and the second baseband signal, which are modulated by the coupled channel, is orthogonally demodulated by a low pass filter and a multiplier, respectively, to obtain a demodulated first baseband signal I1.
  • the processor 1901 respectively acquires the first baseband signal I1, the second baseband signal Q1, the first demodulated signal I2 corresponding to the first baseband signal I1, and the second The second demodulated signal Q2 corresponding to the baseband signal.
  • the first demodulated signal I2 and the second demodulated signal Q2 collected in the feedback channel are obtained by orthogonal mediation. If there is no phase offset in the signal transmission, the demodulated The phases of the first demodulated signal I2 and the second demodulated signal Q2 are the same as those of the first baseband signal I1 and the second baseband signal Q1 before modulation. Therefore, to compensate for the phase, the phase offset is first determined.
  • the processor 1901 determines the phase offset by forming the first baseband signal I1 and the second baseband signal Q1 into a first vector 1 (I1, Q1), and forming the first demodulated signal I2 and the second demodulated signal Q2 into a second
  • the vector 2 (I2, Q2) then calculates the sine and cosine values of the phase difference of the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2).
  • r1 be the magnitude of 1 (I1, Q1)
  • r2 be the magnitude of the second vector 2 (I2, Q2)
  • x between the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2)
  • the phase angle corresponds to the phase deviation x between the first baseband signal I1 and the second baseband signal Q1 and the first demodulated signal I2 and the second demodulated signal Q2.
  • the counterclockwise phase shift x angle is exemplified by a vector in which the first demodulated signal I2 and the second demodulated signal Q2 are opposite to the first baseband signal I1 and the second baseband signal Q1.
  • the processor 1901 performs clockwise compensation of the x-angle of the vector consisting of the first baseband signal I1 and the second baseband signal Q1.
  • the first vector 1 (I1, Q1) is represented by the second vector 2 (I2, Q2) as follows:
  • the second vector 2 (I2, Q2) can be represented by the first vector 1 (I1, Q1):
  • I2 I1*cos(x) - Q1*sin(x),
  • the sine value sin(x) and the cosine value cos(x) of the phase deviation may be represented by the first vector 1 (I1, Q1) and the second vector 2 (I2, Q2):
  • the compensation unit 1703 compensates the first baseband signal I1 and the second baseband signal Q1 in real time according to the sine and cosine values of the phase deviation.
  • the processor 1901 pairs the first baseband signal I1 and the second baseband signal Q1 according to the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the compensated first baseband signal I1 and the second baseband signal Q1 are as follows:
  • the processor 1901 counterclockwise the first baseband signal I1 and the second baseband signal Q1 according to the first demodulated signal I2 and the second demodulated signal Q2 and the sine and cosine values of the phase deviation.
  • the compensated first baseband signal I1 and the second baseband signal Q1 are as follows:
  • I1 I2*cos(x) – Q2*sin(x),
  • the two sets of calculation formulas used by the processor 1901 to implement phase compensation are merely exemplified by a method of introducing a vector by a mathematical method under the idea of the present invention, and not limited thereto.
  • the first baseband signal I1 and the second baseband signal Q1 may be compensated by other calculation methods according to the compensation idea of the present embodiment. Any manner of compensating for phase deviation by the compensation idea of the present invention is within the scope of the present invention.
  • the processor 1901 is not limited to only compensating the first baseband signal I1 and the second baseband signal Q1 in the forward channel. In other embodiments, the processor 1901 may also implement the pair on the feedback channel. A baseband signal I1 and a second baseband signal Q1 are compensated, and the compensation idea and the calculation method are the same as those in this embodiment, and are not described herein.
  • the processor can compensate the first baseband signal I1 and the second baseband signal Q1 in the forward channel or the feedback channel.
  • the local oscillator channel or the feedback channel of the forward channel can also be used. Phase compensation of the vibration channel, phase compensation on the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel, and compensation of the first baseband signal I1 and the second baseband signal Q1 directly in the forward channel or the feedback channel Consistent, but since the first baseband signal I1 and the second baseband signal Q1 are low frequency signals, when phase compensation is performed on the local oscillator channel of the forward channel or the local oscillator channel of the feedback channel, it is required to operate in the high frequency signal region, and Make a limit.
  • the processor 1901 completes the compensation of the first baseband signal I1 and the second baseband signal Q1
  • the compensated first baseband signal and the second baseband signal are respectively modulated by the corresponding low pass filter and the multiplier.
  • the first modulated signal and the second modulated signal are amplified by an amplifier and transmitted through an antenna.
  • the phase can be automatically adjusted in real time without interrupting the normal communication, and the adaptability of the product to the phase deviation caused by adverse effects such as environmental factors and aging factors can be enhanced, and even if the phase deviation is large, the phase can be obtained more stably. transmit a signal.
  • the memory 1902 is configured to store a program running in the processor and data generated during the running of the program. Read-only memory and random access memory may be included and instructions and data may be provided to processor 1901. A portion of the memory 1902 may also include non-volatile random access memory (NVRAM).
  • NVRAM non-volatile random access memory
  • the memory 1902 stores the following elements, executable units or data structures, or a subset thereof, or an extended set thereof:
  • Operation instructions include various operation instructions for implementing various operations.
  • Operating system Includes a variety of system programs for implementing various basic services and handling hardware-based tasks.
  • the processor 1901 performs the above operation by calling an operation instruction stored in the memory 1902 (which can be stored in the operating system).
  • the processor 1901 can also be called a CPU (Central Processing) Unit, central processing unit).
  • Memory 1902 can include read only memory and random access memory and provides instructions and data to processor 901. A portion of the memory 1902 may also include non-volatile random access memory (NVRAM).
  • NVRAM non-volatile random access memory
  • the method disclosed in the foregoing embodiments of the present invention may be applied to the processor 1901 or implemented by the processor 1901.
  • the processor 1901 may be an integrated circuit chip with signal processing capabilities.
  • the processor 1901 can also be integrated with a chip that generates a first baseband signal and a second baseband signal, and can integrate a comparator and a phase shifting function for the first baseband and the second baseband.
  • each step of the above method may be completed by an integrated logic circuit of hardware in the processor 1901 or an instruction in a form of software.
  • the processor 1901 described above may be a general purpose processor, a digital signal processor (DSP), an application specific integrated circuit (ASIC), an off-the-shelf programmable gate array (FPGA) or other programmable logic device, a discrete gate or transistor logic device, or discrete hardware. Component.
  • the methods, steps, and logical block diagrams disclosed in the embodiments of the present invention may be implemented or carried out.
  • the general purpose processor may be a microprocessor or the processor or any conventional processor or the like.
  • the steps of the method disclosed in the embodiments of the present invention may be directly implemented by the hardware decoding processor, or may be performed by a combination of hardware and software units in the decoding processor.
  • the software unit can be located in a conventional storage medium such as random access memory, flash memory, read only memory, programmable read only memory or electrically erasable programmable memory, registers, and the like.
  • the storage medium is located in the memory 1902, and the processor 1901 reads the information in the memory 1902 and completes the steps of the above method in combination with its hardware.
  • the processor of the embodiment forms a first vector by collecting the orthogonal first baseband signal and the second baseband signal of the forward channel of the transmitter, and acquires the first demodulated signal and the first in the feedback channel. Demodulating the signal to form a second vector, determining a sine value and a cosine value of the phase deviation generated by the transmitter in the signal transmission according to the phase difference between the first vector and the second vector, and according to the sine and cosine values The first baseband signal and the second baseband signal are compensated and transmitted.
  • the compensated first baseband signal and the second baseband signal corresponding to the aging components can be obtained, and the baseband signal and demodulation are ensured without interrupting the communication of the transmitter.
  • the error between the baseband signals is controlled within the effective range, and the influence of unfavorable factors such as aging on the transmitter is overcome, thereby ensuring the basic stability of the transmitter signal transmission and enhancing the practicality of the transmitter.
  • phase deviation generally does not change greatly in a short time, and the first baseband signal and the second baseband signal are not required to be collected in real time to save the transmitter controller resources.
  • the processor 1901 acquires the sine and cosine values of the phase difference in a predetermined period, and stores the collected sine and cosine values, and stores them in the current cycle.
  • the sine and cosine values compensate the first baseband signal and the second baseband signal.
  • the acquisition and storage are repeated, and the sine and cosine values of the newly acquired phase are compared to the current period.
  • the first baseband signal and the second baseband signal are compensated.
  • the transmitter triggers the storage function of the processor 1901 by using an additional enable signal.
  • the enable signal is triggered once, the processor 1901 re-collects the signal and saves the current signal for the processor.
  • the first baseband signal and the second baseband signal are compensated in this cycle.
  • the processor 1901 compensates the first baseband signal and the second baseband signal in the feedback channel, or compensates the phase on the local oscillator channel of the forward channel, or compensates the phase on the local oscillator channel of the feedback channel.
  • the above functions can be implemented by compensating for the first baseband signal and the second baseband signal in the current period by collecting and storing the sine and cosine values in a predetermined period. I will not go into details here.
  • the Cartesian ring transmitter processor of the present embodiment further acquires and stores the sine and cosine values of the phase difference in a predetermined period after acquiring the sine and cosine values of the phase, and The first baseband signal and the second baseband signal are compensated according to the stored sine and cosine values in the sub-period, which can further save the transmitter resources, improve the working efficiency of the transmitter, and enhance the transmitter while ensuring the stability of the transmitted signal. Practicality.

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Abstract

本发明公开了一种发射机相位自适应调整的方法以及发射机，所述方法包括：采集发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，第一基带信号与第二基带信号为正交信号；所第一解调信号与第一基带信号对应，第二解调信号与所述第二基带信号对应；由第一基带信号与第二基带信号组成第一向量，由第一解调信号与第二解调信号组成第二向量，确定第一向量与第二向量的相位差的正弦值和余弦值；根据正弦值与余弦值分别对第一基带信号和第二基带信号进行补偿。通过上述方式，本发明能够提高发射机对环境变化和元器件老化的适应性，保证发射通道中信号的稳定。

Description

发射机相位自适应调整的方法以及发射机
【技术领域】
本发明涉及无线通信技术领域，特别是涉及一种发射机相位自适应调整的方法以及发射机。
【背景技术】
在现有的窄带通信系统的应用中，信号传输的过程中不可避免的会出现非线性失真的问题，目前，解决非线性失真的方法有很多，其中，利用笛卡尔环发射机来实现功放线性化是一种很常见的方法，其中，笛卡尔环发射机是以负反馈为理论基础的，通过负反馈来实现线性失真后的相位补偿。如图1所示，图1为现有技术中笛卡尔环发射机的仿真原理示意图。
其中，Iin和Qin为正交基带信号，即基带信号I1和Q1。基带信号I1和Q1分别通过低通滤波器LPF1、乘法器MIX1，以及低通滤波器LPF2、乘法器MIX2实现正交调制，得到调制后的射频信号，并将调制后的射频信号从天线端口RF_out发射出去。为了克服在信道传输过程中产生的信号的非线性失真，提高功放的线性度，发射通道的定向耦合器Couple将部分调制后的信号耦合到反馈通道中去，并在反馈通道将耦合的部分调制后的信号通过低通滤波器LPF3、乘法器MIX3以及低通滤波器LPF4、乘法器MIX4实现正交解调，得到解调后的基带信号I2和Q2。
如果在毫无失真的情况下，在信号进行正交调制，再进行正交调解后，最终得到的解调信号与原始的基带信号是没有误差的，但是实际传输中，不可避免的会存在误差。比较器U1和U2将初始的基带信号（Iin，Qin）以及解调后的基带信号（I2，Q2）做比较，通过相减的方式，得到初始的基带信号在传输过程中产生的误差信号。并根据上述误差信号对信号的传输通道进行补偿，即补偿发射通道功放的失真。
在具体的实施过程中，为了保证笛卡尔发射机的笛卡尔环的稳定，使之不发生震荡，基带信号（Iin，Qin）与解调后的基带信号（I2，Q2）之间的误差信号必须控制在一定范围内，即向量（I1，Q1）和向量（I2，Q2）之间的相位差必须控制在一个有限范围内。
假设基带信号（Iin，Qin）从调制器到解调器之间的信号通道产生的相移值为D，用移相器PS4表示，为了克服上述移项值，补偿后的两个本振之间的相差为A，用移相器PS2表示，如果要使解调后的基带信号（I2,Q2）的相位与调制前的基带信号（I1，Q1）的相位相同，即实现基带信号的相干解调，那么移项值D和移项值A在数值上应该相等，方向相反。即在数值上A=D。即补偿的相位能够完全抵消在传输过程中产生的相位偏移，保证信号无误差的发送。因此，现有技术中一般都是通过补偿措施将移相器PS2的移项参数的数值补偿到和PS4的数值相同，然后将移项值A保存在发射机的固定的ROM中，使用中也不需要做调整。
现有技术中在图1中所述的仿真原理图的基础上，提供了另一种相位补偿的方法。具体方法为，断开图1中的两个开关Switch1和Switch2，并对初始的基带信号I_in和Q_in进行赋值，由于原理相同，赋值的多少都不会影响整体设计的思路，因此，为了方便计算，将初始的基带信号I_in赋值为1，将Q_in赋值为0，经过一系列的调制以及解调过程后，得到解调后的基带信号I2和Q2，其中，I2=G*COS(A-D)，Q2=G*SIN(A-D)，其中，G为幅度增益，G=r2/r1，r2、r1分别为解调后的基带信号组成的向量（I2,Q2）的幅度以及调制前的基带信号组成的向量（I1，Q1）的幅度。然后以I2=G*COS(A-D)为依据，调整移相器PS2的移项值A的大小，具体地，将A从0度一直调整到360度，同时并检测I2的值。由余弦的性质可知，I2=G*COS(A-D)，当A=D时，I2的值最大，得得到最大的补偿值。再次将得到的补偿值进行存储。然后闭合开关Switch1和Switch2，笛卡尔环发射机继续工作。
上述改进后的方法虽然算法较简单，但是上述方案只能对相位进行开环补偿，没有自适应机制，校准得到A的值，固定不再更改。一旦使用中出现老化等原因造成的相位偏差超过一定范围，则会使反馈环路发生震荡。如图2A~图2C所示，当预设的相位偏差为0度时，即D-A=0时，笛卡尔环能够正常工作，其中输入信号如图3A~3B所示。但是对由于环境、温度或者元器件老化等因素造成的数值较大的相位偏差并不能实现补偿，如图4A~图4C所示，当预设的相位偏差为60度时，即补偿前D-A=60，笛卡尔环产生了强烈的震荡，发射信号产生了严重的失真。并且上述方法中，需要在环路断开的条件下才能实施，并且采用了对初始的基带信号进行赋值的方式，而这种方式需要发射机中断正常通信，给用户带来诸多不便，并且针对不同的频点，都需要进行相位预校准，过程繁琐。
通过上述方法，只能保证笛卡尔环的初始稳定，使之不发生震荡，但是在长期的使用过程中，由于环境温度在不断的变化，发射机的各个元器件也可能存在老化等问题，导致信号发射通道中的移项值发生了变化，以至于原本存储固定在ROM中的移项值A已经不能再适用于保证基带信号（Iin，Qin）以及解调后的基带信号（I2，Q2）之间的误差信号控制在一定范围内。
【发明内容】
本发明主要解决的技术问题是提供一种发射机相位自适应调整的方法以及发射机，能够有效的实现发射机的相位自适应调整，提高发射机对环境变化和元器件老化的适应性，保证发射通道中信号的稳定。
为解决上述技术问题，本发明第一方面提供一种发射机相位自适应调整的方法，包括：
采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信号对应，所述第二解调信号与所述第二基带信号对应；
由所述第一基带信号与所述第二基带信号组成第一向量，所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；
根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第一方面，在第一方面的第一种可能实施方式中，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤包括：
实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第一方面，在第一方面的第二种可能实施方式中，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤包括：
在预定周期内采集并存储所述正弦值与所述余弦值；
在所述在预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第一方面或第一方面的第一至第二种任一可能实施方式，在第一方面的第三实施方式中，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤之后还包括：
将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送。
结合第一方面，在第一方面的第四种可能实施方式中，所述第一解调信号与所述第二解调信号为与所述第一基带信号以及所述第二基带信号正交解调后的信号。
为解决上述技术问题，本发明第二方面提供一种发射机，所述发射机具有相位自适应调整功能，包括：采集单元、运算单元以及补偿单元，
所述采集单元用于采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应；
所述运算单元用于由所述第一基带信号与所述第二基带信号组成第一向量，所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；
所述补偿单元用于根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第二方面，在第二方面的第一种可能实施方式中，所述补偿单元具体用于实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第二方面，在第二方面的第二种可能实施方式中，所述发射机还包括存储单元，
所述存储单元用于在预定周期内采集并存储所述正弦值与所述余弦值；
所述补偿单元具体用于在所述预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第二方面、第二方面的第一至第二任意一种可能实施方式，第二方面的第三种实施方式中，所述发射机还包括发射单元，所述发射单元用于将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送。
结合第二方面，在第二方面的第四种可能实施方式中，所述运算单元与所述补偿单元位于所述发射机的前向通道、反馈通道、前向射频通道的本振通道以及反馈通道的本振通道的任一处。
为解决上述技术问题，本发明第三方面提供一种发射机，所述发射机具有相位自适应调整功能，包括：处理器以及存储器，
所述处理器用于采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应；
所述处理器还用于由所述第一基带信号与所述第二基带信号组成第一向量，由所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿；
所述存储器用于，存储所述处理器中运行的程序、以及所述程序运行过程中产生的数据。
结合第三方面，在第三方面的第一种可能实施方式中，所述处理器具体用于实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第三方面，在第三方面的第二种可能实施方式中，所述处理器具体用于在预定周期内采集并存储所述正弦值与所述余弦值；并在所述预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
结合第三方面，在第三方面的第三种可能实施方式中，所述处理器位于所述发射机的前向通道、反馈通道、前向射频通道的本振通道以及反馈通道的本振通道的任一处。
本发明的有益效果是：区别于现有技术的情况，本实施方式的发射机通过采集发射机正向通道的正交的第一基带信号和第二基带信号，组成第一向量，采集反馈通道中的第一解调信号和第二解调信号，组成第第二向量，根据第一向量和第二向量的相位差确定发射机在信号传输中产生的相位偏差的正弦值与余弦值，并根据所述正弦值与余弦值对第一基带信号以及第二基带信号进行补偿后发射出去。通过上述方式，即使在元器件出现老化，也能得到与老化后元器件对应的补偿后的第一基带信号和第二基带信号，在不中断发射机通信的条件下，保证基带信号与解调后的基带信号之间的误差控制在有效范围内，克服老化等不利因素对发射机的影响，进而能够保证发射机信号发射的基本稳定性，也增强发射机的实用性。
【附图说明】
图1是现有技术笛卡尔环发射机工作方式的仿真原理示意图；
图2A是现有技术笛卡尔环发射机相位偏差为0度时调制前后第一对比示意图；
图2B是现有技术笛卡尔环发射机相位偏差为0度时调制前后第二对比示意图；
图2C是现有技术笛卡尔环发射机相位偏差为0度时发射信号的波形示意图；
图3A是现有技术笛卡尔环发射机相位调制前的第一基带信号Iin波形示意图；
图3B是现有技术笛卡尔环发射机相位调制前的第二基带信号Qin波形示意图；
图4A是现有技术笛卡尔环发射机相位偏差为60度时调制前后信号第一对比示意图；
图4B是现有技术笛卡尔环发射机相位偏差为60度时调制前后信号第二对比示意图；
图4C是现有技术笛卡尔环发射机相位偏差为60度时发射信号的波形示意图；
图5是本发明自适应调整发射机第一实施方式的仿真原理示意图；
图6是本发明发射机自适应调整方法一实施方式的流程示意图；
图7是本发明积分比较电路的仿真原理示意图；
图8是本发明确定相位偏移的数学原理示意图；
图9是本发明确定相位差正弦值与余弦值的仿真原理示意图；
图10是本发明顺时针补偿第一基带信号和第二基带信号的仿真原理示意图；
图11是本发明自适应调整发射机第二实施方式的仿真原理示意图；
图12是本发明自适应调整发射机第三实施方式的仿真原理示意图；
图13是本发明自适应调整发射机第四实施方式的仿真原理示意图；
图14A是本发明笛卡尔环发射机相位偏差为60度时调制前后信号第一对比示意图；
图14B是本发明笛卡尔环发射机相位偏差为60度时调制前后信号第二对比示意图；
图14C是本发明笛卡尔环发射机相位偏差为60度时发射信号的波形示意图；
图15是本发明发射机自适应调整方法另一实施方式的流程示意图；
图16是本发明自适应调整发射机第五实施方式的仿真原理示意图；
图17是本发明发射机一实施方式的结构示意图；
图18是本发明发射机另一实施方式的结构示意图；
图19是本发明发射机再一实施方式的结构示意图。
【具体实施方式】
参阅图5，图5是本发明自适应调整发射机一实施方式的仿真原理示意图，通过仿真图模拟发射机的工作过程。其中，本发明的发射机为笛卡尔环发射机。
如图5所示，本实施方式的笛卡尔环发射机包括对正交的基带信号进行正交解调的前向通道，前向通道包括低通滤波器LPF1、乘法器MIX1，低通滤波器LPF2、乘法器MIX2，将调制后的射频信号发射出去的天线端口RF_out，将部分调制后的信号进行解调得到解调信号的反馈通道，反馈通道包括定向耦合器Couple，低通滤波器LPF3、乘法器MIX3，低通滤波器LPF4、乘法器MIX4，笛卡尔环发射机还包括将上述基带信号和解调信号进行比较的信号采集电路U102和对基带信号进行相位补偿的补偿电路U101。
正交的第一基带信号Iin和第二基带信号Qin，经过低通滤波器LPF1、乘法器MIX1，以及低通滤波器LPF2、乘法器MIX2实现正交调制，得到调制信号。为了保证信号的稳定性，反馈通道的定向耦合器Couple将部分调制后的信号耦合到反馈通道中，部分调制后的信号通过低通滤波器LPF3、乘法器MIX3以及低通滤波器LPF4、乘法器MIX4实现正交解调，得到解调后的第一解调信号I2和第二解调信号Q2，信号采集电路U102采集发射机第一基带信号Iin、第二基带信号Qin、反馈通道中分别与第一基带信号Iin和第二基带信号Qin对应的第一解调信号I2和第二解调信号Q2，并根据第一基带信号Iin和第二基带信号Qin、第一解调信号I2和第二解调信号Q2确定由第一基带信号Iin和第二基带信号Qin组成的向量与第一解调信号I2和第二解调信号Q2组成的向量的相位差的正弦值和余弦值，补偿电路U101根据所述正弦值与所述余弦值分别对所述第一基带信号Iin和第二基带信号Qin进行补偿，并将补偿后的第一基带信号与第二基带信号经过低通滤波器LPF1、乘法器MIX1，以及低通滤波器LPF2、乘法器MIX2正交调制，放大器AMP1放大后，通过天线RF_out进行发送出去。
在具体硬件设备中，比较电路U102与补偿电路U101可直接集成在笛卡尔环发射机的控制器中，也可以通过添加额外的硬件来实现，在此不做限定。
具体，结合参阅图6，图6是本发明发射机相位自适应调整的方法一实施方式的流程示意图。本实施方式的发射机相位自适应调整的方法包括如下步骤:
601:采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信号对应，所述第二解调信号与所述第二基带信号对应。
具体地，进一步结合图5，正交的第一基带信号Iin和第二基带信号Qin，经过积分比较电路U1和U2以及低通滤波器LPF1、乘法器MIX1，以及低通滤波器LPF2、乘法器MIX2实现正交调制，得到调制信号。其中，U1与U2的工作方式如图7所示。为了与第一解调信号以及第二解调信号区别开来，本实施方式中的基带信号将第一基带信号Iin记为I1，第二基带信号记为Q1。调制信号经过放大器AMP1放大后得到射频信号，理论上，发射机将射频信号从天线端口RF_out发射出去即可。但是为了克服笛卡尔环发射机信号在传输过程中不可避免的相位偏移的问题，保证信号的稳定性，反馈通道的定向耦合器Couple将部分调制后的信号耦合到反馈通道中去，并在反馈通道将耦合的部分调制后的信号通过低通滤波器LPF3、乘法器MIX3以及低通滤波器LPF4、乘法器MIX4实现正交解调，得到解调后的第一解调信号I2和第二解调信号Q2。
为了实现对第一基带信号和第二基带信号的补偿，发射机分别采集第一基带信号I1、第二基带信号Q1、与第一基带信号I1对应的第一解调信号I2和与第二基带信号对应的第二解调信号Q2。在仿真示意图图5中完成本步骤的元件为信号采集电路U102。在实际的发射机中可直接由控制芯片来实现。
602：由所述第一基带信号与所述第二基带信号组成第一向量，所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值。
由于本实施方式中，对反馈通道中采集到的第一解调信号I2以及第二解调信号Q2是通过正交调解得到的，如果在信号传输中不存在相位偏移，经过解调后的第一解调信号I2以及第二解调信号Q2的相位与调制前的第一基带信号I1、第二基带信号Q1的相同的，因此，要实现相位的补偿，首先对相位偏移进行确定。
本实施方式确定相位偏移的方式是将第一基带信号I1、第二基带信号Q1组成第一向量1（I1，Q1），将第一解调信号I2和第二解调信号Q2组成第二向量2（I2，Q2），然后计算第一向量1（I1，Q1）和第二向量2（I2，Q2）的相位差的正弦值和余弦值。
如图8所示，图8是本发明确定相位偏移的数学原理示意图。r1为第一向量1（I1，Q1）的幅度，r2为第二向量2（I2，Q2）的幅度，x表示第一向量1（I1，Q1）与第二向量2（I2，Q2）之间的相位角，对应到发射机中，即为第一基带信号I1、第二基带信号Q1，分别第一基带信号I1,第二基带信号Q1相对应与第一解调信号I2和第二解调信号Q2的相位偏差x。
本实施方式中以第一解调信号I2和第二解调信号Q2相对于第一基带信号I1、第二基带信号Q1出现了逆时针的相位偏移x来举例说明，那么对应地，需要将第一基带信号I1、第二基带信号Q1进行顺时针补偿x，
设第一向量1 (I1,Q1)=I1+j*Q1 =r*exp(j*θ2)*exp(-j*x) =r*exp(j*(θ2-x))，
即I1+j*Q1=r1*(cos(θ2-x)+j*sin(θ2-x))=r1*cos(θ2-x)+j*r*sin(θ2-x)，其中，r1为第一向量1（I1，Q1）与第二向量2（I2，Q2）的幅度，假设第一向量1（I1，Q1）与第二向量2（I2，Q2）均为单位向量；
用第二向量2（I2，Q2）表示第一向量1（I1，Q1）如下所示：
I1= r*cos(θ2-x) = r*cos(θ2)*cos(x)+r*sin(θ2)*sin(x) = I2* cos(x)+Q2* sin(x)；
Q1= r*sin(θ2-x) = r*sin(θ2)*cos(x)-r*cos(θ2)*sin(x) = Q2* cos(x)-I2*sin(x)
也可对应地用第一向量1（I1，Q1）将第二向量2（I2，Q2）表示：
I2 = I1*cos(x) - Q1*sin(x)，
Q2 = I1*sin(x) + Q1*cos(x)。
进一步地根据上述对应关系，相位偏差的正弦值sin(x)和余弦值cos(x)可以通过第一向量1（I1，Q1）和第二向量2（I2，Q2）来表示：
cos(x) = I1*I2 + Q1*Q2，
sin(x) =I1*Q2 - I2*Q1。
对应到图5中的仿真示意图可以看出，本步骤可以由信号采集电路U102来实现，对应到实际硬件电路中，本步骤可以直接集成到发射机的控制器中，也可以通过调节额外的加法器和乘法器来实现，对应的加法器和乘法器的工作原理仿真图如图9所示。
603：根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
确定相位偏差的正弦值和余弦值以后，笛卡尔环发射机实时地根据相位偏差的正弦值和余弦值对第一基带信号I1、第二基带信号Q1进行补偿。
具体地，如上一个步骤所示，当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了逆时针的相位偏差时，则根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行顺时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1== I2* cos(x)+Q2* sin(x)；
Q1= = Q2* cos(x)-I2*sin(x)。
对应到图5中的仿真示意图可以看出，本步骤可以由补偿电路U101来实现，对应到实际硬件电路中，本步骤可以直接集成到发射机的控制器中，也可以通过调节额外的加法器和乘法器来实现，对应的加法器和乘法器的工作原理仿真图如图10所示。
当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了顺时针的相位偏差时，则根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行逆时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1 = I2*cos(x) – Q2*sin(x)，
Q1 = I2*sin(x) + Q2*cos(x)。
需要说明的是，本实施方式中两组计算公式，只是在本发明思想下通过数学的方法，引进向量的方法来举例说明，而非限制，在其他实施方式中，也可以根据本实施方式的补偿思想通过其他计算方法来实现对第一基带信号I1、第二基带信号Q1进行补偿。任何通过本发明中补偿思想对相位偏差进行补偿的方式均属于本发明保护的范围。
并且，本发明中也并非仅仅限制于在前向通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他实施方式中，也可以在反馈通道上实现对第一基带信号I1、第二基带信号Q1进行补偿，其工作方式的仿真原理图如图11所示，其中，补偿的思路和计算方法与本实施方式相同，在此不做赘述。
另外，笛卡尔环发射机除了可以在前向通道或反馈通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他的实施方式中，还可以在前向通道的本振通道或反馈通道的本振通道进行相位补偿，在前向通道的本振通道或反馈通道的本振通道上进行相位补偿与在前向通道或反馈通道直接对第一基带信号I1、第二基带信号Q1进行补偿的思想一致，但是由于第一基带信号I1、第二基带信号I1为低频信号，在前向通道的本振通道或反馈通道的本振通道进行相位补偿时，需要工作在高频信号区，具体工作原理的仿真示意图如图12和图13所示。其中，图12为前向通道的本振通道进行相位补偿的仿真原理示意图。如13为反馈通道的本振通道进行相位补偿的仿真原理示意图。
得到补偿后的第一基带信号以及第二基带信号以后，本实施方式还包括将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送的步骤。
例如，对应到图5中，将补偿后的第一基带信号经过低通滤波器LPF1、乘法器MIX1进行调制得到补偿后的第一调制信号，补偿后的第二基带信号经过低通滤波器LPF2、乘法器MIX2进行调制得到补偿后的第二调制信号，且第一调制信号与第二调制信号为正交调制，再将调制后的第一调制信号以及第二调制信号经过放大器AMP1放大后，通过天线RF_out进行发送出去。
通过上述方式，能够在不中断正常通信的情况下实时自动调整相位，增强产品对环境因素，老化因素等不利影响造成的相位偏差的适应能力，即使相位偏差较大时，也能得到较稳定的发射信号，如图14A~14C所示，其中，为了对比本发明与现有技术效果的区别，输入的第一基带信号与第二基带信号与现有技术相同，如图3A~3B所示。
区别于现有技术，本实施方式的发射机通过采集发射机正向通道的正交的第一基带信号和第二基带信号，组成第一向量，采集反馈通道中的第一解调信号和第二解调信号，组成第第二向量，根据第一向量和第二向量的相位差确定发射机在信号传输中产生的相位偏差的正弦值与余弦值，并根据所述正弦值与余弦值对第一基带信号以及第二基带信号进行补偿后发射出去。通过上述方式，即使在元器件出现老化，也能得到与老化后元器件对应的补偿后的第一基带信号和第二基带信号，在不中断发射机通信的条件下，保证基带信号与解调后的基带信号之间的误差控制在有效范围内，克服老化等不利因素对发射机的影响，进而能够保证发射机信号发射的基本稳定性，也增强发射机的实用性。
在经过大量的实验发现，相位偏差在短时间内一般不会有较大的变化，并不需要实时地第一基带信号和第二基带信号进行采集，以节省发射机控制器资源。
在另一个实施方式中，参阅图15，图15是本发明发射机相位自适应调整的方法的另一实施方式的流程示意图。本实施与上一个实施方式的区别在于，在发射机由所述第一基带信号与所述第二基带信号组成第一向量，由所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值的步骤以后，还包括：
步骤1503：在预定周期内采集并存储正弦值与余弦值。
正如上述所分析的，由于在短时间内相位偏差的变化并不太明显，对应的正弦值与余弦值的变化也在有限范围内，因此，本实施方式设定一个预定周期，在预定周期内采集相位差的正弦值与余弦值，并将采集到正弦值与余弦值进行存储，在本次周期内，均通过存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，待下一个周期到来时，再重新进行采集和存储，通过新采集的相位的正弦值与余弦值对本次周期的第一基带信号和第二基带信号进行补偿。
为了形象的说明上述情况，通过仿真图模拟上述工作过程。如图16所示，图16是本发明自适应调整发射机第五实施方式的仿真原理示意图。本实施方式的仿真原理图与上几个实施方式的仿真原理图的区别在于，在采集电路U102与补偿电路U101之间还包括采样保存电路U103，采样保持电路U103，通过另外添加的一个使能信号对其进行触发，使能信号每触发一次，采样保持电路U103就采集一次信号，并将本次信号保存起来，供本次周期内对第一基带信号和第二基带信号进行补偿。
在实际硬件操作中，本步骤也可以直接集成在发射机的控制器中，也可以通过额外的添加采集存储器来实现，添加的采集存储器不仅可以置于采集电路与补偿电路的中间，还可以置于采集电路和补偿电路的两端，也可以直接将三个电路集成在一个电路中，作为一个整体，只要能够完成采集，存储以及补偿的功能即可，在此不做限制。
另外，当发射机采用的是在反馈通道对第一基带信号、第二基带信号进行补偿，或前向通道的本振通道上对相位进行补偿，或者在反馈通道的本振通道上对相位进行补偿均可添加上述步骤，在此不做限定。
区别于现有技术，本实施方式的发射机通过采集发射机正向通道的正交的第一基带信号和第二基带信号，组成第一向量，采集反馈通道中的第一解调信号和第二解调信号，组成第第二向量，根据第一向量和第二向量的相位差确定发射机在信号传输中产生的相位偏差的正弦值与余弦值，并根据所述正弦值与余弦值对第一基带信号以及第二基带信号进行补偿后发射出去。通过上述方式，即使在元器件出现老化，也能得到与老化后元器件对应的补偿后的第一基带信号和第二基带信号，在不中断发射机通信的条件下，保证基带信号与解调后的基带信号之间的误差控制在有效范围内，克服老化等不利因素对发射机的影响，进而能够保证发射机信号发射的基本稳定性，也增强发射机的实用性。
区别于上一个实施方式，本实施方式的笛卡尔环发射机在获取到相位的正弦值与余弦值后，在预定周期内采集并存储相位差的正弦值与余弦值，并在本次周期内根据存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，能够在保证发射信号稳定性的同时，进一步节约发射机资源，提高发射机工作效率，增强发射机的实用性。
参阅图17，图17是本发明发射机一实施方式的结构示意图。其中，本实施方式的发射机为笛卡尔环发射机。
本实施方式的发射机包括采集单元1701、运算单元1702、补偿单元1703。
采集单元1701用于采集采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应。
为了实现对第一基带信号和第二基带信号的补偿，采集单元1701分别采集第一基带信号I1、第二基带信号Q1、与第一基带信号I1对应的第一解调信号I2和与第二基带信号对应的第二解调信号Q2。
运算单元1702用于由所述第一基带信号与所述第二基带信号组成第一向量，所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值。
由于本实施方式中，对反馈通道中采集到的第一解调信号I2以及第二解调信号Q2是通过正交调解得到的，如果在信号传输中不存在相位偏移，经过解调后的第一解调信号I2以及第二解调信号Q2的相位与调制前的第一基带信号I1、第二基带信号Q1的相同的，因此，要实现相位的补偿，首先对相位偏移进行确定。
运算单元1702确定相位偏移的方式是将第一基带信号I1、第二基带信号Q1组成第一向量1（I1，Q1），将第一解调信号I2和第二解调信号Q2组成第二向量2（I2，Q2），然后计算第一向量1（I1，Q1）和第二向量2（I2，Q2）的相位差的正弦值和余弦值。
进一步地参阅图8，r1为1（I1，Q1）的幅度，r2为第二向量2（I2，Q2）的幅度，x表示第一向量1（I1，Q1）与第二向量2（I2，Q2）之间的相位角，对应到发射机中，即为第一基带信号I1、第二基带信号Q1，与第一解调信号I2和第二解调信号Q2的相位偏差x。
运算单元1702以第一解调信号I2和第二解调信号Q2相对于第一基带信号I1、第二基带信号Q1出现了逆时针的相位偏移x来举例说明，那么对应地，补偿单元1703需要将第一基带信号I1、第二基带信号Q1进行顺时针补偿x，
运算单元1702的计算过程如下所示，
设第一向量1 (I1,Q1)=I1+j*Q1 =r*exp(j*θ2)*exp(-j*x) =r*exp(j*(θ2-x))，
即I1+j*Q1=r1*(cos(θ2-x)+j*sin(θ2-x))=r1*cos(θ2-x)+j*r*sin(θ2-x)，其中，r1为第一向量1（I1，Q1）与第二向量2（I2，Q2）的幅度，假设第一向量1（I1，Q1）与第二向量2（I2，Q2）均为单位向量；
用第二向量2（I2，Q2）表示第一向量1（I1，Q1）如下所示：
I1= r*cos(θ2-x) = r*cos(θ2)*cos(x)+r*sin(θ2)*sin(x) = I2* cos(x)+Q2* sin(x)；
Q1= r*sin(θ2-x) = r*sin(θ2)*cos(x)-r*cos(θ2)*sin(x) = Q2* cos(x)-I2*sin(x)
也可对应地用第一向量1（I1，Q1）将第二向量2（I2，Q2）表示：
I2 = I1*cos(x) - Q1*sin(x)，
Q2 = I1*sin(x) + Q1*cos(x)。
运算单元1702进一步地根据上述对应关系，相位偏差的正弦值sin(x)和余弦值cos(x)可以通过第一向量1（I1，Q1）和第二向量2（I2，Q2）来表示：
cos(x) = I1*I2 + Q1*Q2，
sin(x) =I1*Q2 - I2*Q1。
补偿单元1703用于根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
运算单元1702确定相位偏差的正弦值和余弦值以后，补偿单元1703实时地根据相位偏差的正弦值和余弦值对第一基带信号I1、第二基带信号Q1进行补偿。
具体地，当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了逆时针的相位偏差时，补偿单元1703根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行顺时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1== I2* cos(x)+Q2* sin(x)；
Q1= = Q2* cos(x)-I2*sin(x)。
当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了顺时针的相位偏差时，则根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行逆时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1 = I2*cos(x) – Q2*sin(x)，
Q1 = I2*sin(x) + Q2*cos(x)。
需要说明的是，本实施方式中补偿电路1703使用的两组计算公式，只是在本发明思想下通过数学的方法，引进向量的方法来举例说明的，而非限制，在其他实施方式中，也可以根据本实施方式的补偿思想通过其他计算方法来实现对第一基带信号I1、第二基带信号Q1进行补偿。任何通过本发明中补偿思想对相位偏差进行补偿的方式均属于本发明保护的范围。
并且，本发明中补偿单元1703也并非仅仅限制于在前向通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他实施方式中，补偿单元1703也可以在反馈通道上实现对第一基带信号I1、第二基带信号Q1进行补偿，其中，补偿的思路和计算方法与本实施方式相同，在此不做赘述。
另外，补偿单元1703除了可以在前向通道或反馈通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他的实施方式中，还可以在前向通道的本振通道或反馈通道的本振通道进行相位补偿，在前向通道的本振通道或反馈通道的本振通道上进行相位补偿与在前向通道或反馈通道直接对第一基带信号I1、第二基带信号Q1进行补偿的思想一致，但是由于第一基带信号I1、第二基带信号I1为低频信号，在前向通道的本振通道或反馈通道的本振通道进行相位补偿时，需要工作在高频信号区，在此不做限定。
进一步的参阅图17，为了将补偿后的第一基带信号、第二基带信号发射出去，本实施方式的发射机还包括发射单元1704，发射单元1704用于将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送。
具体地，发射单元1704将补偿后的第一基带信号以及第二基带信号分别与各自对应的低通滤波器以及乘法器进行调制后得到的第一调制信号以及第二调制信号经过放大器放大后，通过天线发送出去。
通过上述方式，能够在不中断正常通信的情况下实时自动调整相位，增强产品对环境因素，老化因素等不利影响造成的相位偏差的适应能力，即使相位偏差较大时，也能得到较稳定的发射信号。
区别于现有技术，本实施方式的发射机通过采集单元采集发射机正向通道的正交的第一基带信号和第二基带信号，组成第一向量，采集反馈通道中的第一解调信号和第二解调信号，组成第第二向量，运算单元根据第一向量和第二向量的相位差确定发射机在信号传输中产生的相位偏差的正弦值与余弦值，补偿单元根据所述正弦值与余弦值对第一基带信号以及第二基带信号进行补偿后发射出去。通过上述方式，即使在元器件出现老化，也能得到与老化后元器件对应的补偿后的第一基带信号和第二基带信号，在不中断发射机通信的条件下，保证基带信号与解调后的基带信号之间的误差控制在有效范围内，克服老化等不利因素对发射机的影响，进而能够保证发射机信号发射的基本稳定性，也增强发射机的实用性。
在经过大量的实验发现，相位偏差在短时间内一般不会有较大的变化，并不需要实时地第一基带信号和第二基带信号进行采集，以节省发射机控制器资源。
为了实现上述功能，在另一个实施方式中，如图18所示，本实施方式的发射机除了包括采集单元1801、运算单元1802、补偿单元1803、发射单元1804，还包括存储单元1805，所述存储单元用于在预定周期内采集并存储正弦值与余弦值。
正如上述所分析的，由于在短时间内相位偏差的变化并不太明显，对应的正弦值与余弦值的变化也在有限范围内，因此，本实施方式设定一个预定周期，存储单元1805在预定周期内采集相位差的正弦值与余弦值，并将采集到正弦值与余弦值进行存储，在本次周期内，补偿单元1803均通过存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，待下一个周期到来时，存储单元1804再重新进行采集和存储，补偿单元1803通过新采集的相位的正弦值与余弦值对本次周期的第一基带信号和第二基带信号进行补偿。
具体地，发射机通过另外添加的一个使能信号对存储单元1805进行触发，使能信号每触发一次，存储单元1805就采集一次信号，并将本次信号保存起来，供补偿单元1803本次周期内对第一基带信号和第二基带信号进行补偿。
另外，当补偿单元1803在反馈通道对第一基带信号、第二基带信号进行补偿，或前向通道的本振通道上对相位进行补偿，或者在反馈通道的本振通道上对相位进行补偿时均可添加补偿单元1805，通过存储单元1805在预定周期内采集并存储正弦值与余弦值，供补偿单元1803本次周期内对第一基带信号和第二基带信号进行补偿。在此不在赘述。
区别于上一个实施方式，本实施方式的笛卡尔环发射机在采集单元获取到相位的正弦值与余弦值后，存储单元在预定周期内采集并存储相位差的正弦值与余弦值，补偿单元在本次周期内根据存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，能够在保证发射信号稳定性的同时，进一步节约发射机资源，提高发射机工作效率，增强发射机的实用性。
参阅图19，图19是本发明发射机再一实施方式的结构示意图。其中，本实施方式的发射机为笛卡尔环发射机。
本实施方式的1900发射机包括处理器1901以及存储器1902。发射机1900的处理器1901以及存储器1902通过总线1903耦合在一起，其中总线1903除包括数据总线之外，还可以包括电源总线、控制总线和状态信号总线等。但是为了清楚说明起见，在图中将各种总线都标为总线1903。
处理器1901用于采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应；
所述处理器190还用于由所述第一基带信号与所述第二基带信号组成第一向量，由所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。并将补偿后的第一基带信号与第二基带信号通过调制放大后通过天线进行发送。
发射机的正交的第一基带信号Iin和第二基带信号Qin分别经过积分比较电路以及低通滤波器、乘法器进行正交调制后，得到调制信号。为了与第一解调信号以及第二解调信号区别开来，本实施方式中的基带信号将第一基带信号Iin记为I1，第二基带信号记为Q1。调制信号经过放大器放大后得到射频信号，理论上，发射机将射频信号从天线端口发射出去即可。但是为了克服笛卡尔环发射机信号在传输过程中不可避免的相位偏移的问题，保证信号的稳定性，发射机反馈通道通过定向耦合器将部分调制后的信号耦合到反馈通道中去，并在反馈通道将耦合的部分调制后的与第一基带信号以及第二基带信号对应的调制信号分别通过低通滤波器以及乘法器进行正交解调，得到解调后的与第一基带信号I1对应的第一解调信号I2和与第二基带信号Q1对应的第二解调信号Q2。
为了实现对第一基带信号和第二基带信号的补偿，处理器1901分别采集第一基带信号I1、第二基带信号Q1、与第一基带信号I1对应的第一解调信号I2和与第二基带信号对应的第二解调信号Q2。
由于本实施方式中，对反馈通道中采集到的第一解调信号I2以及第二解调信号Q2是通过正交调解得到的，如果在信号传输中不存在相位偏移，经过解调后的第一解调信号I2以及第二解调信号Q2的相位与调制前的第一基带信号I1、第二基带信号Q1的相同的，因此，要实现相位的补偿，首先对相位偏移进行确定。
处理器1901确定相位偏移的方式是将第一基带信号I1、第二基带信号Q1组成第一向量1（I1，Q1），将第一解调信号I2和第二解调信号Q2组成第二向量2（I2，Q2），然后计算第一向量1（I1，Q1）和第二向量2（I2，Q2）的相位差的正弦值和余弦值。
假设r1为1（I1，Q1）的幅度，r2为第二向量2（I2，Q2）的幅度，x表示第一向量1（I1，Q1）与第二向量2（I2，Q2）之间的相位角，对应到发射机中，即为第一基带信号I1、第二基带信号Q1，与第一解调信号I2和第二解调信号Q2的相位偏差x。
以第一解调信号I2和第二解调信号Q2相对于第一基带信号I1、第二基带信号Q1组成的向量出现了逆时针的相位偏移x角度来举例说明。对应地，处理器1901要将第一基带信号I1、第二基带信号Q1组成的向量进行顺时针补偿x角度，
具体地，设第一向量1 (I1,Q1)=I1+j*Q1 =r*exp(j*θ2)*exp(-j*x) =r*exp(j*(θ2-x))，
即I1+j*Q1=r1*(cos(θ2-x)+j*sin(θ2-x))=r1*cos(θ2-x)+j*r*sin(θ2-x)，其中，r1为第一向量1（I1，Q1）与第二向量2（I2，Q2）的幅度，假设第一向量1（I1，Q1）与第二向量2（I2，Q2）均为单位向量；
用第二向量2（I2，Q2）表示第一向量1（I1，Q1）如下所示：
I1= r*cos(θ2-x) = r*cos(θ2)*cos(x)+r*sin(θ2)*sin(x) = I2* cos(x)+Q2* sin(x)；
Q1= r*sin(θ2-x) = r*sin(θ2)*cos(x)-r*cos(θ2)*sin(x) = Q2* cos(x)-I2*sin(x)
也可对应地用第一向量1（I1，Q1）将第二向量2（I2，Q2）表示：
I2 = I1*cos(x) - Q1*sin(x)，
Q2 = I1*sin(x) + Q1*cos(x)。
处理器1901进一步地根据上述对应关系，相位偏差的正弦值sin(x)和余弦值cos(x)可以通过第一向量1（I1，Q1）和第二向量2（I2，Q2）来表示：
cos(x) = I1*I2 + Q1*Q2，
sin(x) =I1*Q2 - I2*Q1。
处理器1901确定相位偏差的正弦值和余弦值以后，补偿单元1703实时地根据相位偏差的正弦值和余弦值对第一基带信号I1、第二基带信号Q1进行补偿。
具体地，当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了逆时针的相位偏差时，处理器1901根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行顺时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1== I2* cos(x)+Q2* sin(x)；
Q1= = Q2* cos(x)-I2*sin(x)。
当第一解调信号I2和第二解调信号Q2组成的第二向量2（I2，Q2）相对于第一基带信号I1、第二基带信号Q1组成的第一向量1（I1，Q1）出现了顺时针的相位偏差时，处理器1901根据第一解调信号I2和第二解调信号Q2以及相位偏差的正弦值和余弦值，对第一基带信号I1、第二基带信号Q1进行逆时针补偿，得到补偿后的第一基带信号I1、第二基带信号Q1如下所示:
I1 = I2*cos(x) – Q2*sin(x)，
Q1 = I2*sin(x) + Q2*cos(x)。
需要说明的是，本实施方式中处理器1901在实现相位补偿使使用的两组计算公式，只是在本发明思想下通过数学的方法，引进向量的方法来举例说明的，而非限制，在其他实施方式中，也可以根据本实施方式的补偿思想通过其他计算方法来实现对第一基带信号I1、第二基带信号Q1进行补偿。任何通过本发明中补偿思想对相位偏差进行补偿的方式均属于本发明保护的范围。
并且，本发明中处理器1901也并非仅仅限制于在前向通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他实施方式中，处理器1901也可以在反馈通道上实现对第一基带信号I1、第二基带信号Q1进行补偿，其中，补偿的思路和计算方法与本实施方式相同，在此不做赘述。
另外，处理器除了可以在前向通道或反馈通道对第一基带信号I1、第二基带信号Q1进行补偿，在其他的实施方式中，还可以在前向通道的本振通道或反馈通道的本振通道进行相位补偿，在前向通道的本振通道或反馈通道的本振通道上进行相位补偿与在前向通道或反馈通道直接对第一基带信号I1、第二基带信号Q1进行补偿的思想一致，但是由于第一基带信号I1、第二基带信号Q1为低频信号，在前向通道的本振通道或反馈通道的本振通道进行相位补偿时，需要工作在高频信号区，在此不做限定。
处理器1901完成对第一基带信号I1、第二基带信号Q1的补偿后，将补偿后的第一基带信号以及第二基带信号分别与各自对应的低通滤波器以及乘法器进行调制后得到的第一调制信号以及第二调制信号经过放大器放大后，通过天线发送出去。
通过上述方式，能够在不中断正常通信的情况下实时自动调整相位，增强产品对环境因素，老化因素等不利影响造成的相位偏差的适应能力，即使相位偏差较大时，也能得到较稳定的发射信号。
存储器1902用于存储所述处理器中运行的程序、以及所述程序运行过程中产生的数据。可以包括只读存储器和随机存取存储器，并向处理器1901提供指令和数据。存储器1902的一部分还可以包括非易失性随机存取存储器（NVRAM）。
存储器1902存储了如下的元素，可执行单元或者数据结构，或者它们的子集，或者它们的扩展集:
操作指令：包括各种操作指令，用于实现各种操作。
操作系统：包括各种系统程序，用于实现各种基础业务以及处理基于硬件的任务。
在本发明实施例中，处理器1901通过调用存储器1902存储的操作指令（该操作指令可存储在操作系统中），来执行上述操作。
处理器1901还可以称为CPU（Central Processing Unit，中央处理单元）。存储器1902可以包括只读存储器和随机存取存储器，并向处理器901提供指令和数据。存储器1902的一部分还可以包括非易失性随机存取存储器（NVRAM）。
上述本发明实施例揭示的方法可以应用于处理器1901中，或者由处理器1901实现。处理器1901可能是一种集成电路芯片，具有信号的处理能力。处理器1901也可以和产生第一基带信号和第二基带信号的芯片集成在一起，并且可以集成比较器和对第一基带，第二基带的移相功能。
在实现过程中，上述方法的各步骤可以通过处理器1901中的硬件的集成逻辑电路或者软件形式的指令完成。上述的处理器1901可以是通用处理器、数字信号处理器（DSP）、专用集成电路（ASIC）、现成可编程门阵列（FPGA）或者其他可编程逻辑器件、分立门或者晶体管逻辑器件、分立硬件组件。可以实现或者执行本发明实施例中的公开的各方法、步骤及逻辑框图。通用处理器可以是微处理器或者该处理器也可以是任何常规的处理器等。结合本发明实施例所公开的方法的步骤可以直接体现为硬件译码处理器执行完成，或者用译码处理器中的硬件及软件单元组合执行完成。软件单元可以位于随机存储器，闪存、只读存储器，可编程只读存储器或者电可擦写可编程存储器、寄存器等本领域成熟的存储介质中。该存储介质位于存储器1902，处理器1901读取存储器1902中的信息，结合其硬件完成上述方法的步骤。
区别于现有技术，本实施方式的处理器通过采集发射机正向通道的正交的第一基带信号和第二基带信号，组成第一向量，采集反馈通道中的第一解调信号和第二解调信号，组成第第二向量，根据第一向量和第二向量的相位差确定发射机在信号传输中产生的相位偏差的正弦值与余弦值，并根据所述正弦值与余弦值对第一基带信号以及第二基带信号进行补偿后发射出去。通过上述方式，即使在元器件出现老化，也能得到与老化后元器件对应的补偿后的第一基带信号和第二基带信号，在不中断发射机通信的条件下，保证基带信号与解调后的基带信号之间的误差控制在有效范围内，克服老化等不利因素对发射机的影响，进而能够保证发射机信号发射的基本稳定性，也增强发射机的实用性。
另外，在经过大量的实验发现，相位偏差在短时间内一般不会有较大的变化，并不需要实时地第一基带信号和第二基带信号进行采集，以节省发射机控制器资源。
在另一个实施方式中，再次参阅图19，处理器1901在预定周期内采集相位差的正弦值与余弦值，并将采集到正弦值与余弦值进行存储，在本次周期内，均通过存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，待下一个周期到来时，再重新进行采集和存储，并通过新采集的相位的正弦值与余弦值对本次周期的第一基带信号和第二基带信号进行补偿。
具体地，发射机通过另外添加的一个使能信号对处理器1901的存储功能进行触发，使能信号每触发一次，处理器1901就重新采集一次信号，并将本次信号保存起来，供处理器本次周期内对第一基带信号和第二基带信号进行补偿。
另外，当处理器1901在反馈通道对第一基带信号、第二基带信号进行补偿，或前向通道的本振通道上对相位进行补偿，或者在反馈通道的本振通道上对相位进行补偿时均可实现上述功能，通过在预定周期内采集并存储正弦值与余弦值，供本次周期内对第一基带信号和第二基带信号进行补偿。在此不在赘述。
区别于上一个实施方式，本实施方式的笛卡尔环发射机处理器在获取到相位的正弦值与余弦值后，进一步在预定周期内采集并存储相位差的正弦值与余弦值，并在本次周期内根据存储的正弦值与余弦值对第一基带信号和第二基带信号进行补偿，能够在保证发射信号稳定性的同时，进一步节约发射机资源，提高发射机工作效率，增强发射机的实用性。
以上所述仅为本发明的实施方式，并非因此限制本发明的专利范围，凡是利用本发明说明书及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本发明的专利保护范围内。

Claims (14)

  1. 一种发射机相位自适应调整的方法，其特征在于，包括：
    采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信号对应，所述第二解调信号与所述第二基带信号对应；
    由所述第一基带信号与所述第二基带信号组成第一向量，由所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；
    根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  2. 根据权利要求1所述的方法，其特征在于，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤包括：
    实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  3. 根据权利要求1所述的方法，其特征在于，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤包括：
    在预定周期内采集并存储所述正弦值与所述余弦值；
    在所述在预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  4. 根据权利要求1-3任一项所述的方法，其特征在于，所述根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿的步骤之后还包括：
    将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送。
  5. 根据权利要求1所述的方法，其特征在于，所述第一解调信号与所述第二解调信号为与所述第一基带信号以及所述第二基带信号正交解调后的信号。
  6. 一种发射机，其特征在于，所述发射机具有相位自适应调整功能，包括：采集单元、运算单元以及补偿单元，
    所述采集单元用于采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应；
    所述运算单元用于由所述第一基带信号与所述第二基带信号组成第一向量，所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；
    所述补偿单元用于根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  7. 根据权利要求6所述的发射机，其特征在于，所述补偿模块单元具体用于实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  8. 根据权利要求6所述的发射机，其特征在于，所述发射机还包括存储单元，
    所述存储单元用于在预定周期内采集并存储所述正弦值与所述余弦值；
    所述补偿单元具体用于在所述预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  9. 根据权利要求6~8任一项所述的发射机，其特征在于，所述发射机还包括发射模块单元，所述发射模块单元用于将补偿后的第一基带信号与第二基带信号经过调制放大后通过天线进行发送。
  10. 根据权利要6所述的发射机，其特征在于，所述运算模块单元与所述补偿模块单元位于所述发射机的前向通道、反馈通道、前向射频通道的本振通道以及反馈通道的本振通道的任一处。
  11. 一种发射机，其特征在于，所述发射机具有相位自适应调整功能，包括：处理器以及存储器，
    所述处理器用于采集所述发射机正向通道的第一基带信号、第二基带信号，以及反馈通道中的第一解调信号以及第二解调信号，其中，所述第一基带信号与所述第二基带信号为正交信号；所述第一解调信号与所述第一基带信息对应，所述第二解调信号与所述第二基带信号对应；
    所述处理器还用于由所述第一基带信号与所述第二基带信号组成第一向量，由所述第一解调信号与所述第二解调信号组成第二向量，确定所述第一向量与所述第二向量的相位差的正弦值和余弦值；根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿；
    所述存储器用于，存储所述处理器中运行的程序、以及所述程序运行过程中产生的数据。
  12. 根据权利要求11所述的发射机，其特征在于，所述处理器具体用于实时地根据所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  13. 根据权利要求11所述的发射机，其特征在于，所述处理器具体用于在预定周期内采集并存储所述正弦值与所述余弦值；并在所述预定周期内根据存储的所述正弦值与所述余弦值分别对所述第一基带信号和所述第二基带信号进行补偿。
  14. 根据权利要求11所述的发射机，其特征在于，所述处理器位于所述发射机的前向通道、反馈通道、前向射频通道的本振通道以及反馈通道的本振通道的任一处。
PCT/CN2015/090748 2015-09-25 2015-09-25 发射机相位自适应调整的方法以及发射机 Ceased WO2017049596A1 (zh)

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20030119473A1 (en) * 1998-11-09 2003-06-26 Smith Stephen H. Adjustable balanced modulator
CN1750531A (zh) * 2004-09-17 2006-03-22 株式会社日立国际电气 失真补偿正交调制器和无线发送器
CN101616125A (zh) * 2008-06-26 2009-12-30 大唐移动通信设备有限公司 一种零中频发射机和校准零中频发射信号的方法

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20030119473A1 (en) * 1998-11-09 2003-06-26 Smith Stephen H. Adjustable balanced modulator
CN1750531A (zh) * 2004-09-17 2006-03-22 株式会社日立国际电气 失真补偿正交调制器和无线发送器
CN101616125A (zh) * 2008-06-26 2009-12-30 大唐移动通信设备有限公司 一种零中频发射机和校准零中频发射信号的方法

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