WO2015109869A1 - High resolution doa estimation method and system - Google Patents

High resolution doa estimation method and system Download PDF

Info

Publication number
WO2015109869A1
WO2015109869A1 PCT/CN2014/088099 CN2014088099W WO2015109869A1 WO 2015109869 A1 WO2015109869 A1 WO 2015109869A1 CN 2014088099 W CN2014088099 W CN 2014088099W WO 2015109869 A1 WO2015109869 A1 WO 2015109869A1
Authority
WO
WIPO (PCT)
Prior art keywords
signal
received signal
points
maximum
receiving antenna
Prior art date
Application number
PCT/CN2014/088099
Other languages
French (fr)
Chinese (zh)
Inventor
谢宁
郭伟斌
王晖
林晓辉
曾捷
Original Assignee
深圳大学
谢宁
郭伟斌
王晖
林晓辉
曾捷
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 深圳大学, 谢宁, 郭伟斌, 王晖, 林晓辉, 曾捷 filed Critical 深圳大学
Publication of WO2015109869A1 publication Critical patent/WO2015109869A1/en

Links

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/42—Simultaneous measurement of distance and other co-ordinates
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S3/00—Direction-finders for determining the direction from which infrasonic, sonic, ultrasonic, or electromagnetic waves, or particle emission, not having a directional significance, are being received
    • G01S3/02—Direction-finders for determining the direction from which infrasonic, sonic, ultrasonic, or electromagnetic waves, or particle emission, not having a directional significance, are being received using radio waves
    • G01S3/74—Multi-channel systems specially adapted for direction-finding, i.e. having a single antenna system capable of giving simultaneous indications of the directions of different signals

Definitions

  • the invention belongs to the field of wireless communication technologies, and in particular relates to a high-resolution DOA estimation method and system suitable for a MIMO radar system.
  • MIMO The radar uses multiple antenna techniques to simultaneously transmit independent signal beams to detect targets and receive corresponding target transmit signals.
  • the transmitted signal carries information about the target of the launch, such as angle, distance, Doppler shift, etc., which can be extracted at the receiving end by means of a matched filter.
  • MIMO The radar can flexibly adopt the high-bandwidth, two-way digital beamforming and waveform diversity techniques of the new-generation radar system, and requires each antenna to transmit mutually orthogonal signals.
  • the array elements of the antenna array are spatially separated by a certain interval and space. Targets form spatial diversity, which can improve the ability to detect air targets.
  • the characteristics of the transmitted signal in MIMO radar and the design of spatial diversity improve the resolution of the DOA estimation method.
  • the existing DOA estimation algorithms used in MIMO radar mainly include: multi-signal classification (MUSIC) method, Capon method, amplitude and phase estimation (APES) method, and maximum likelihood ratio test (GLRT) method. These algorithms can all be applied to DOA estimation in MIMO radar. To some extent (such as the number of transmitting antennas and receiving antennas is large, the number of sampling points is large) can provide relatively high DOA resolution, but these The shortcomings of the method are as follows: (1) The number of target sources that can be estimated is limited, especially in the case where the number of transmitting antennas and receiving antennas is small, the number of target sources that can be estimated depends on the transmitting array. And the number of antennas that can be shared by the receiving array.
  • the DOA estimation algorithm of the existing method can estimate the maximum number of target sources. , where M t represents the number of transmitting antennas, N r represents the number of receiving antennas; (2) When the number of transmitting antennas and receiving antennas is small, the estimation performance is unstable, the accuracy is not high enough, and the resolution capability is not strong.
  • the first technical problem to be solved by the present invention is to provide a high resolution DOA estimation method.
  • the aim is to increase the degree of freedom of the antenna without increasing the existing receiving and transmitting antennas, thereby increasing the resolution of the DOA estimation and the number of target sources that can be estimated.
  • the present invention is achieved by a high resolution DOA estimation method, the method comprising the steps of:
  • Step A Each receiving antenna receives a transmission signal reflected by the target source
  • Step B scanning the received signal of each receiving antenna by using each transmitting signal
  • Step C step B
  • the scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each receiving antenna;
  • Step D constructing a virtual extended signal according to the phase obtained in step C and the transmitted signal;
  • Step E calculating a covariance of the new received signal by using the virtual extended signal and the original received signal to form a new received signal
  • the Capon beamforming coefficient which in turn completes the DOA estimate.
  • a second technical problem to be solved by the present invention is to provide a high resolution DOA estimation system, including:
  • a scanning module configured to scan a received signal of each receiving antenna by using each of the transmitting signals; the transmitting signal is reflected by the target source;
  • phase calculation module configured to multiply the scanned signals by the transmitted signals respectively, to obtain a phase corresponding to each peak point in the received signal of each receiving antenna
  • a virtual extended signal construction module configured to construct a virtual extended signal according to the phase obtained by the phase calculation module and the transmit signal
  • An estimation module configured to form the virtual extended signal and the received signal into a new received signal, and calculate a covariance sum of the new received signal The Capon beamforming coefficient, which in turn completes the DOA estimate.
  • the present invention makes full use of the mutual orthogonal characteristics of the transmit waveforms in the MIMO radar and the design of the spatial diversity, and performs matched filtering and recovery signals on the received signals, and then performs virtual extension of the signals. Therefore, the degree of freedom of the antenna is increased without increasing the antenna (mainly equivalent to increasing the actual number of receiving antennas), thereby improving the estimation accuracy and the number of target sources that can be estimated.
  • the number of target sources that can be estimated is greater than the limit of the original method (where M t is the number of transmit antennas and N r is the number of receive antennas).
  • FIG. 1 is a flowchart showing an implementation of a high resolution DOA estimation method provided by the present invention
  • Figure 2 is an illustration of the existing capon provided by the present invention. An implementation flow chart for selecting between the estimation method and the estimation method provided by the present invention;
  • the capon method, the actual increase antenna capon method, and the estimated angle root mean square error RMSE of the estimation method provided by the present invention are compared with the SNR;
  • the capon method, the actual increase of the antenna capon method, and the estimation method provided by the present invention are compared with the RMSE as a function of the number of target sources.
  • the transmitted signal can be expressed as:
  • T represents the period of the transmitted signal
  • I a time delay
  • Figure 1 shows the implementation flow of the high resolution DOA estimation method provided by the present invention, which is described in detail below.
  • Step A Each receiving antenna receives a transmission signal reflected by the target source.
  • the receiving antenna receives the signal, and the signal received by each receiving antenna is a row vector signal with a sampling point of L.
  • Step B scanning the received signal of each receiving antenna by using a transmitting signal.
  • the invention utilizes the characteristics of the correlation between the transmitted waveforms, and scans the received signals of each receiving antenna with the transmitted signals;
  • the received signal arriving at the receiving antenna after the target reflection can be expressed as:
  • c,f and Re represents the speed of light, the carrier frequency, and the reflection coefficient of the kth target source.
  • d k (0) represents the distance from the initial time of the kth target source to the origin
  • d mk t/r (t) represents the distance between the mth transmit/receive antenna and the kth target source.
  • n 1 (t) and n 2 (t) represent the received noise signals of the two receiving antennas, and the mean and the variance are equal.
  • the estimated error is: .
  • step B count the number N of maximum points scanned by each receiving antenna in step B, and the number of maximum points of each receiving antenna.
  • step C is performed, and when the number N of the maximum value points of the respective receiving antennas is equal and not greater than the preset maximum number of thresholds, then Using the original Capon
  • the estimation method performs an estimation of the DOA.
  • the preset threshold value of the maximum number of points is 2 .
  • Step C step B
  • the scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each of the receiving antennas.
  • Step D Construct a virtual received signal according to the phase obtained in step C and the transmitted signal as the obtained virtual extended signal.
  • step B build the first virtual extension signal as:
  • Step E The new received signal is composed of the virtual extended signal and the original received signal, the covariance and beamforming coefficients of the new received signal are calculated, the corresponding estimated spectrum is calculated by using the obtained beamforming coefficient, and the obtained estimated spectrum is subjected to an extreme value.
  • Point search select the maximum point as the estimation result, complete Estimate of the DOA.
  • N r is the number of receiving antennas
  • T is the transposition of the matrix
  • y1m , y2m , yN r m is the first, second, and N r after being reflected by the target source at the mth pulse.
  • the estimated spectrum of the target reflection coefficient can be obtained as: (19)
  • Figure 11 shows the high resolution DOA provided by the present invention. Estimate the structural principle of the system, in which each module can be realized by software, hardware or a combination of software and hardware.
  • the high resolution DOA estimation system includes a scanning module 111 and a phase calculation module 112. , a virtual extended signal construction module 113, and an estimation module 114.
  • the scanning module 111 For scanning the received signal of each receiving antenna with each transmitted signal, the transmitted signal is reflected by the target source; then the phase calculation module 112 The scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each of the receiving antennas.
  • Virtual extended signal construction module 113 based on phase calculation module 112 The obtained phase and the transmitted signal construct a virtual extended signal; finally, the virtual extended signal and the received signal are combined by the estimation module 114 to form a new received signal, and the covariance and Capon of the new received signal are calculated.
  • the beamforming coefficients which in turn complete the estimation of the DOA.
  • the estimation module 114 obtains a new received signal by the following formula:
  • N r is the number of receiving antennas
  • T is the transposition of the matrix
  • y1m , y2m , yN r m is the first, second, and N r after being reflected by the target source at the mth pulse.
  • the system further includes a determining module for the statistical scanning module 111 For each number N of the thresholds of the maximum number of points that are scanned by each receiving antenna, when the number of maximum points of the respective receiving antennas is equal to N and greater than the preset threshold of the maximum number of points Trigger phase calculation module 112 The calculation is performed, and when the number N of the maximum value points of the respective receiving antennas is equal and not greater than the preset threshold value of the maximum number of points, the trigger estimation module 114 uses the original Capon estimation method for DOA. Estimate. It has been verified by experiments that the preset threshold value of the maximum number of points is 2, which is more effective.
  • the invention improves the degree of freedom of the antenna without increasing the existing receiving antenna and the transmitting antenna, and is especially suitable when the number of sampling points is small and the SNR is small. High-resolution DOA estimation in MIMO radars with low or high number of sampling points.

Abstract

The present invention applies to the technical field of MIMO radars. A high resolution DOA estimation method and system. The method comprises the following steps: all receive antennas receiving transmitted signals reflected by target sources (A); scanning a received signal of each receive antenna by using each transmitted signal (B); separately multiplying the scanned signal by the transmitted signal to obtain a phase corresponding to each peak signal in the received signal of each receive antenna (C); constructing a virtual received signal according to the obtained phase and the transmitted signal to serve as an obtained virtual extended signal (D); and forming a new received signal by the virtual extended signal and the original received signal, and calculating a covariance and a Capon beamforming coefficient of the new received signal, so as to complete DOA estimation (E). By means of the method, the estimation accuracy is improved and the number of target sources that can be estimated is increased without adding antennas.

Description

高分辨率 DOA 估计方法及系统  High resolution DOA estimation method and system Technical FieldTechnical Field
本发明属于无线通信技术领域，尤其涉及一种适用于 MIMO 雷达系统的高分辨率 DOA 估计方法及系统。  The invention belongs to the field of wireless communication technologies, and in particular relates to a high-resolution DOA estimation method and system suitable for a MIMO radar system.
Background ArtBackground Art
MIMO 雷达利用多天线技术同时发射独立的信号波束来探测目标，并接收相应的目标发射信号。发射信号中承载着有关发射目标的信息，如角度、距离、多普勒平移等等，这些信息都可以利用匹配滤波器的方法在接收端提取出来。 MIMO 雷达可以灵活采用新一代雷达系统的高带宽、双程数字波束合成和波形分集技术，同时要求各天线发射相互正交的信号，其天线阵列的各个阵元在空间分置一定的间隔，对空间目标形成空间分集，可以提高对空中目标的检测能力。 MIMO 雷达中的发射信号的特点以及空间分集的设计提高了 DOA 估计方法的分辨率。 MIMO The radar uses multiple antenna techniques to simultaneously transmit independent signal beams to detect targets and receive corresponding target transmit signals. The transmitted signal carries information about the target of the launch, such as angle, distance, Doppler shift, etc., which can be extracted at the receiving end by means of a matched filter. MIMO The radar can flexibly adopt the high-bandwidth, two-way digital beamforming and waveform diversity techniques of the new-generation radar system, and requires each antenna to transmit mutually orthogonal signals. The array elements of the antenna array are spatially separated by a certain interval and space. Targets form spatial diversity, which can improve the ability to detect air targets. The characteristics of the transmitted signal in MIMO radar and the design of spatial diversity improve the resolution of the DOA estimation method.
已有的应用于 MIMO 雷达中的 DOA 估计算法主要有：多信号分类 (MUSIC) 方法、 Capon 方法、幅度和相位估计 (APES) 方法、最大似然比测试 (GLRT) 方法。这些算法本身可以都可以应用到 MIMO 雷达中的 DOA 估计，在一定程度上 ( 如发射天线和接收天线根数较多，采样点个数大的情形 ) 可以提供比较高的 DOA 分辨率，但是这些方法的缺点主要有： (1) 可以估计的目标源个数都受到一定的限制，尤其是在发射天线和接收天线根数较少的情况下，其可以估计的目标源个数依赖与发射阵列和接收阵列的可以共享的天线根数，已有方法的 DOA 估计算法可以估计的目标源个数最大值为
Figure 1402-appb-I000001
，其中 Mt 表示的发射天线根数， Nr 表示接收天线根数； (2) 算法在发射天线和接收天线根数较少时，估计性能不稳定，精度不够高，分辨率能力不强。The existing DOA estimation algorithms used in MIMO radar mainly include: multi-signal classification (MUSIC) method, Capon method, amplitude and phase estimation (APES) method, and maximum likelihood ratio test (GLRT) method. These algorithms can all be applied to DOA estimation in MIMO radar. To some extent (such as the number of transmitting antennas and receiving antennas is large, the number of sampling points is large) can provide relatively high DOA resolution, but these The shortcomings of the method are as follows: (1) The number of target sources that can be estimated is limited, especially in the case where the number of transmitting antennas and receiving antennas is small, the number of target sources that can be estimated depends on the transmitting array. And the number of antennas that can be shared by the receiving array. The DOA estimation algorithm of the existing method can estimate the maximum number of target sources.
Figure 1402-appb-I000001
, where M t represents the number of transmitting antennas, N r represents the number of receiving antennas; (2) When the number of transmitting antennas and receiving antennas is small, the estimation performance is unstable, the accuracy is not high enough, and the resolution capability is not strong.
Technical ProblemTechnical Problem
本发明所要解决的第一个技术问题在于提供一种 高分辨率 DOA 估计方法 ，旨在不增加现有接收天线和发射天线的情况下提高天线的自由度，从而提高 DOA 估计的分辨率以及可以估计的目标源个数。  The first technical problem to be solved by the present invention is to provide a high resolution DOA estimation method. The aim is to increase the degree of freedom of the antenna without increasing the existing receiving and transmitting antennas, thereby increasing the resolution of the DOA estimation and the number of target sources that can be estimated.
Technical SolutionTechnical Solution
本发明是这样实现的，一种 高分辨率 DOA 估计方法，所述方法包括下述步骤： The present invention is achieved by a high resolution DOA estimation method, the method comprising the steps of:
步骤 A ，各接收天线接收由目标源反射的发射信号； Step A: Each receiving antenna receives a transmission signal reflected by the target source;
步骤 B ，利用每个发射信号对每根接收天线的接收信号进行扫描； Step B: scanning the received signal of each receiving antenna by using each transmitting signal;
步骤 C ，将步骤 B 所扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位； Step C, step B The scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each receiving antenna;
步骤 D ，根据步骤 C 得到的相位以及发射信号构建虚拟扩展信号； Step D, constructing a virtual extended signal according to the phase obtained in step C and the transmitted signal;
步骤 E ，利用由所述虚拟扩展信号和原始的接收信号组成新的接收信号，计算所述新的接收信号的协方差和 Capon 波束形成系数，进而完成 DOA 的估计。 Step E: calculating a covariance of the new received signal by using the virtual extended signal and the original received signal to form a new received signal The Capon beamforming coefficient, which in turn completes the DOA estimate.
本发明所要解决的第二个技术问题在于提供一种高分辨率 DOA 估计系统，包括： A second technical problem to be solved by the present invention is to provide a high resolution DOA estimation system, including:
扫描模块，用于利用每个发射信号对每根接收天线的接收信号进行扫描；所述发射信号由目标源反射； a scanning module, configured to scan a received signal of each receiving antenna by using each of the transmitting signals; the transmitting signal is reflected by the target source;
相位计算模块，用于将扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位； a phase calculation module, configured to multiply the scanned signals by the transmitted signals respectively, to obtain a phase corresponding to each peak point in the received signal of each receiving antenna;
虚拟扩展信号构建模块，用于根据所述相位计算模块得到的相位以及发射信号构建虚拟扩展信号； a virtual extended signal construction module, configured to construct a virtual extended signal according to the phase obtained by the phase calculation module and the transmit signal;
估计模块，用于将所述虚拟扩展信号和接收信号组成新的接收信号，计算所述新的接收信号的协方差和 Capon 波束形成系数，进而完成 DOA 的估计。 An estimation module, configured to form the virtual extended signal and the received signal into a new received signal, and calculate a covariance sum of the new received signal The Capon beamforming coefficient, which in turn completes the DOA estimate.
Advantageous EffectsAdvantageous Effects
本发明与现有技术相比，充分利用了 MIMO 雷达中发射波形的相互正交的特点以及空间分集的设计，对接收信号进行匹配滤波恢复信号，然后进行信号的虚拟扩展。从而在不增加天线的情况下，提高了天线的自由度 ( 主要是相当于增加了实际的接收天线根数 ) ，因此提高了估计精度和可以估计的目标源个数。可以估计的目标源个数大于原始方法的极限值
Figure 1402-appb-I000002
（其中， Mt 为发射天线根数、 Nr 为接收天线根数）。 Compared with the prior art, the present invention makes full use of the mutual orthogonal characteristics of the transmit waveforms in the MIMO radar and the design of the spatial diversity, and performs matched filtering and recovery signals on the received signals, and then performs virtual extension of the signals. Therefore, the degree of freedom of the antenna is increased without increasing the antenna (mainly equivalent to increasing the actual number of receiving antennas), thereby improving the estimation accuracy and the number of target sources that can be estimated. The number of target sources that can be estimated is greater than the limit of the original method
Figure 1402-appb-I000002
(where M t is the number of transmit antennas and N r is the number of receive antennas).
Description of DrawingsDescription of Drawings
图 1 是本发明 提供的 高分辨率 DOA 估计方法的实现流程图； 1 is a flowchart showing an implementation of a high resolution DOA estimation method provided by the present invention;
图 2 是本发明 提供的在现有的 capon 估计方法和本发明天提供的估计方法之间选择的实现流程图； Figure 2 is an illustration of the existing capon provided by the present invention. An implementation flow chart for selecting between the estimation method and the estimation method provided by the present invention;
图 3A 、 3B 、 3C 是在采样点个数 L=2^7 、信噪比 SNR=0dB 的情况下，分别采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法得到的 DOA 估计图； Figure 3A, 3B, and 3C are the number of sampling points L=2^7, signal-to-noise ratio SNR=0dB In the case of the original capon method, the actual increase of the antenna capon method, and the estimation method obtained by the estimation method provided by the present invention;
图 4A 、 4B 、 4C 是在采样点个数 L=2^7 、信噪比 SNR=20dB 的情况下，分别采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法得到的 DOA 估计图； Figure 4A, 4B, 4C are the number of sampling points L=2^7, signal-to-noise ratio SNR=20dB In the case of the original capon method, the actual increase of the antenna capon method, and the estimation method obtained by the estimation method provided by the present invention;
图 5A 、 5B 、 5C 是在采样点个数 L=2^10 、信噪比 SNR=0dB 的情况下，分别采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法得到的 DOA 估计图； Figure 5A, 5B, and 5C are the number of sampling points L=2^10, SNR SNR=0dB In the case of the original capon method, the actual increase of the antenna capon method, and the estimation method obtained by the estimation method provided by the present invention;
图 6A 、 6B 、 6C 是在采样点个数 L=2^10 、信噪比 SNR=20dB 的情况下，分别采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法得到的 DOA 估计图； Figure 6A, 6B, and 6C are the number of sampling points L=2^10, and the signal-to-noise ratio SNR=20dB In the case of the original capon method, the actual increase of the antenna capon method, and the estimation method obtained by the estimation method provided by the present invention;
图 7A 、 7B 分别是在采样点个数 L=2^7 和采样点个数 L=2^10 的情况下，采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法的估计角度均方根误差 RMSE 随 SNR 的变化比较示意图； Figures 7A and 7B show the original in the case of the number of sampling points L=2^7 and the number of sampling points L=2^10. The capon method, the actual increase antenna capon method, and the estimated angle root mean square error RMSE of the estimation method provided by the present invention are compared with the SNR;
图 8A 、 8B 分别是在 SNR=0dB 和 SNR=20dB 的情况下，采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法时 RMSE 随采样点个数的变化比较示意图； Figures 8A and 8B show the original capon with SNR=0dB and SNR=20dB, respectively. The method, the actual increase of the antenna capon method, and the estimation method provided by the present invention, the RMSE is compared with the change of the number of sampling points;
图 9A 、 9B 分别是在采样点个数 L=2^7 和 SNR=0dB 的情况下，采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法时 RMSE 随目标源个数的变化比较示意图； Figures 9A and 9B show the original capon with the number of sampling points L=2^7 and SNR=0dB, respectively. The method, the actual increase of the antenna capon method, and the estimation method provided by the present invention, the RMSE is compared with the change of the number of target sources;
图 10A 、 10B 分别是在采样点个数 L=2^10 和 SNR=0dB 的情况下，采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法时 RMSE 随目标源个数的变化比较示意图。 Figures 10A and 10B are the originals in the case of the number of sampling points L=2^10 and SNR=0dB, respectively. The capon method, the actual increase of the antenna capon method, and the estimation method provided by the present invention are compared with the RMSE as a function of the number of target sources.
Mode for InventionMode for Invention
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。 The present invention will be further described in detail below with reference to the accompanying drawings and embodiments. It is understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
在 MIMO 雷达中，发射信号可以表示为：
Figure 1402-appb-C000001
 In MIMO radar, the transmitted signal can be expressed as:
Figure 1402-appb-C000001
(1)(1)
其中 i={1,...,Mt} 表示发射天线数，wi 表示哈达玛矩阵的第i 列，si 表示由等概率分布 -1 和 1 组成的实数随机矩阵的第i 列， t 表示时间。 MIMO 雷达中发射波形之间相互正交且独立，因此存在：
Figure 1402-appb-C000002
 (2)Where i={1,...,M t } represents the number of transmitting antennas, w i represents the ith column of the Hadamard matrix, and s i represents the ith column of the real random matrix consisting of equal probability distributions -1 and 1. t represents time. The transmit waveforms in MIMO radar are orthogonal and independent of each other, so there are:
Figure 1402-appb-C000002
 (2)
其中 T 表示发射信号的周期，
Figure 1402-appb-C000003
表示时间延迟，
Figure 1402-appb-C000004
 是一个很小的数值，当采样点个数 L=512 时，
Figure 1402-appb-C000005
 接近 0.1 ，且随着采样点个数越大
Figure 1402-appb-C000006
 越小，本发明就充分利用这一点对信号进行匹配恢复。为了说明具体步骤，下文以发射天线根数Mt=1 ，接收天线根数Nr=2 ，目标源个数 K=2为实例进行说明。Where T represents the period of the transmitted signal,
Figure 1402-appb-C000003
 Indicates a time delay,
Figure 1402-appb-C000004
 Is a small value, when the number of sampling points is L=512,
Figure 1402-appb-C000005
 Close to 0.1, and the larger the number of sampling points
Figure 1402-appb-C000006
 The smaller the present invention, the more fully utilized this to match and recover the signal. In order to explain the specific steps, the following description will be given by taking the number of transmitting antennas M t =1 , the number of receiving antennas N r = 2, and the number of target sources K=2.
图 1 示出了本发明 提供的 高分辨率 DOA 估计方法的实现流程，详述如下。 Figure 1 shows the implementation flow of the high resolution DOA estimation method provided by the present invention, which is described in detail below.
步骤 A ，各接收天线接收由目标源反射的发射信号。 Step A: Each receiving antenna receives a transmission signal reflected by the target source.
接收天线接收信号，且每根接收天线接收的信号为一个采样点为L 的行向量信号。 The receiving antenna receives the signal, and the signal received by each receiving antenna is a row vector signal with a sampling point of L.
步骤 B ，利用发射信号对每根接收天线的接收信号进行扫描。 Step B: scanning the received signal of each receiving antenna by using a transmitting signal.
本发明利用发射波形之间的相关性的特点，用发射信号对每根接收天线的接收信号进行扫描； The invention utilizes the characteristics of the correlation between the transmitted waveforms, and scans the received signals of each receiving antenna with the transmitted signals;
在第 m 个脉冲，经过目标反射后到达接收天线的接收信号可以表示为： At the mth pulse, the received signal arriving at the receiving antenna after the target reflection can be expressed as:
Figure 1402-appb-C000007
(3)
Figure 1402-appb-C000007
 (3)
Figure 1402-appb-C000008
(4)
Figure 1402-appb-C000008
 (4)
其中c，f 和
Figure 1402-appb-C000009
 分别表示光速，载波频率和第 k 个目标源的反射系数。dk(0) 表示第k 个目标源初始时刻到原点的距离，dmk t/r(t) 表示第m 个发射 / 接收天线到第k 个目标源之间的距离。n1(t) 和 n2(t) 表示 2 根接收天线的接收的噪声信号，且均值和方差相等。假设发射波形为窄带信号，目标相对移动缓慢，则接收信号中接收到的由于目标导致的延迟都相同为2dk(0)/c ，因此接收信号可以简化为： Where c,f and
Figure 1402-appb-C000009
 Represents the speed of light, the carrier frequency, and the reflection coefficient of the kth target source. d k (0) represents the distance from the initial time of the kth target source to the origin, and d mk t/r (t) represents the distance between the mth transmit/receive antenna and the kth target source. n 1 (t) and n 2 (t) represent the received noise signals of the two receiving antennas, and the mean and the variance are equal. Assuming that the transmitted waveform is a narrowband signal and the target moves relatively slowly, the delay due to the target received in the received signal is the same as 2d k (0)/c, so the received signal can be simplified as:
Figure 1402-appb-C000010
(5)
Figure 1402-appb-C000010
 (5)
Figure 1402-appb-C000011
(6)
Figure 1402-appb-C000011
 (6)
为了简化公式 (5) 和 (6) ，做如下假设：  To simplify equations (5) and (6), make the following assumptions:
Figure 1402-appb-C000012
(7)
Figure 1402-appb-C000012
 (7)
Figure 1402-appb-C000013
(8)
Figure 1402-appb-C000013
 (8)
所有目标源的反射系数相等，即
Figure 1402-appb-C000014
 。则公式 (5) 和 (6) 可以简化为： The reflection coefficients of all target sources are equal, ie
Figure 1402-appb-C000014
 . Then equations (5) and (6) can be simplified to:
Figure 1402-appb-C000015
(9)
Figure 1402-appb-C000015
 (9)
Figure 1402-appb-C000016
(10)
Figure 1402-appb-C000016
 (10)
利用信号的相关性的特点，因为
Figure 1402-appb-C000017
是一个很小的值，当采样点个数很大时这个值小于 0.1 。为了说明的方便，定义一个
Figure 1402-appb-C000018
表示发射波形和噪声之间的互相关系数，在 SNR=0dB 时，这个值接近 0.1 。充分利用上述特点，可以对
Figure 1402-appb-C000019
进行恢复： Take advantage of the correlation of the signal because
Figure 1402-appb-C000017
 It is a small value, which is less than 0.1 when the number of sampling points is large. For the convenience of explanation, define a
Figure 1402-appb-C000018
 Indicates the number of correlations between the transmitted waveform and the noise. At SNR = 0 dB, this value is close to 0.1. Make full use of the above characteristics, you can
Figure 1402-appb-C000019
 To recover:
Figure 1402-appb-C000020
(11)
Figure 1402-appb-C000020
 (11)
Figure 1402-appb-C000021
(12)
Figure 1402-appb-C000021
 (12)
Figure 1402-appb-C000022
(13)
Figure 1402-appb-C000022
 (13)
Figure 1402-appb-C000023
(14)
Figure 1402-appb-C000023
 (14)
其中估计误差为 :
Figure 1402-appb-C000024
 。The estimated error is:
Figure 1402-appb-C000024
 .
进一步地，如图 2 所示，还包括在现有的 capon 估计方法与本发明提供的估计方法直接选择的步骤。首先统计步骤 B 中每根接收天线扫描到的极大值点的个数 N ，当各个接收天线的极大值点的个数 N 相等且大于预设的极大值点个数阈值时，执行步骤 C ，而当各个接收天线的极大值点的个数 N 相等且不大于预设的极大值点个数阈值时，则采用原始的 Capon 估计方法进行 DOA 的估计。本发明中，上述预设的极大值点个数阈值为 2 。 Further, as shown in Figure 2, it is also included in the existing capon The step of estimating the method directly with the estimation method provided by the present invention. First, count the number N of maximum points scanned by each receiving antenna in step B, and the number of maximum points of each receiving antenna. When the threshold is greater than the preset maximum number of thresholds, step C is performed, and when the number N of the maximum value points of the respective receiving antennas is equal and not greater than the preset maximum number of thresholds, then Using the original Capon The estimation method performs an estimation of the DOA. In the present invention, the preset threshold value of the maximum number of points is 2 .
步骤 C ，将步骤 B 所扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位。 Step C, step B The scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each of the receiving antennas.
步骤 D ，根据步骤 C 得到的相位以及发射信号构建虚拟接收信号，作为得到的虚拟扩展信号。 Step D: Construct a virtual received signal according to the phase obtained in step C and the transmitted signal as the obtained virtual extended signal.
利用步骤 B 中恢复出来的
Figure 1402-appb-C000025
, 构建第一个虚拟扩展信号为：Recovered in step B
Figure 1402-appb-C000025
 , build the first virtual extension signal as:
Figure 1402-appb-C000026
(15)
Figure 1402-appb-C000026
 (15)
利用同样的方法可以得到第二个虚拟扩展信号为：  Using the same method, you can get the second virtual extension signal as:
Figure 1402-appb-C000027
(16)
Figure 1402-appb-C000027
 (16)
步骤 E ，利用由虚拟扩展信号和原始的接收信号组成新的接收信号，计算新的接收信号的协方差和波束形成系数，利用得到的波束形成系数计算对应的估计谱，对得到的估计谱进行极值点的搜索，选取其中的极大值点作为估计结果，完成 DOA 的估计。 Step E The new received signal is composed of the virtual extended signal and the original received signal, the covariance and beamforming coefficients of the new received signal are calculated, the corresponding estimated spectrum is calculated by using the obtained beamforming coefficient, and the obtained estimated spectrum is subjected to an extreme value. Point search, select the maximum point as the estimation result, complete Estimate of the DOA.
因此，新的接收信号 r1 表示为：Therefore, the new received signal r 1 is expressed as:
Figure 1402-appb-C000028
(17)
Figure 1402-appb-C000028
 (17)
其中， Nr 表示接收天线的根数， T 表示矩阵的转置， y1m 、 y2m ， yNrm 为在第 m 个脉冲时，由目标源反射后到达第 1 根、第 2 根、第 Nr 根接收天线的接收信号，
Figure 1402-appb-C000029
 为构建的虚拟扩展信号。Where N r is the number of receiving antennas, T is the transposition of the matrix, y1m , y2m , yN r m is the first, second, and N r after being reflected by the target source at the mth pulse. The receiving signal of the root receiving antenna,
Figure 1402-appb-C000029
 A virtual extension signal for the build.
利用得到的新的接收信号，计算其协方差矩阵为：R=E{r1r1 H} ，则其波束形成系数为：Using the obtained new received signal, calculate its covariance matrix as: R = E{r 1 r 1 H } , then its beamforming coefficient is:
Figure 1402-appb-C000030
(18)
Figure 1402-appb-C000030
 (18)
由波束形成系数，可以得到目标反射系数的估计谱为：
Figure 1402-appb-C000031
(19)From the beamforming coefficient, the estimated spectrum of the target reflection coefficient can be obtained as:
Figure 1402-appb-C000031
 (19)
其中Rx=XTX* 。然后按照原始的 Capon 估计方法完成 DOA 的估计，不再赘述。Where R x = X T X * . Then the DOA estimation is completed according to the original Capon estimation method, and will not be described again.
图 3 至图 10 从各个方面对 采用原始 capon 方法、实际增加天线 capon 方法、本发明提供的估计方法实现的 DOA 估计效果进行了对比，可以看出本发明提供的估计方法在信噪比 SNR 比较低和采样点个数比较大时，其估计性能比原始的 Capon 方法更好。 Figure 3 to Figure 10 from various aspects of the original capon method, the actual increase of the antenna capon The method and the DOA estimation effect achieved by the estimation method provided by the present invention are compared. It can be seen that the estimation method provided by the present invention has lower estimation performance than the original one when the signal to noise ratio SNR is relatively low and the number of sampling points is relatively large. The Capon method is better.
图 11 示出了本发明提供的 高分辨率 DOA 估计系统的结构原理，其中各个模块可以通过软件、硬件或软硬件结合的方式实现。 Figure 11 shows the high resolution DOA provided by the present invention. Estimate the structural principle of the system, in which each module can be realized by software, hardware or a combination of software and hardware.
参照图 11 ，本高分辨率 DOA 估计系统包括扫描模块 111 、相位计算模块 112 、虚拟扩展信号构建模块 113 、估计模块 114 。其中，扫描模块 111 用于利用每个发射信号对每根接收天线的接收信号进行扫描，发射信号由目标源反射；然后相位计算模块 112 将扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位。虚拟扩展信号构建模块 113 根据相位计算模块 112 得到的相位以及发射信号构建虚拟扩展信号；最后，由估计模块 114 将虚拟扩展信号和接收信号组成新的接收信号，计算新的接收信号的协方差和 Capon 波束形成系数，进而完成 DOA 的估计。 Referring to FIG. 11, the high resolution DOA estimation system includes a scanning module 111 and a phase calculation module 112. , a virtual extended signal construction module 113, and an estimation module 114. Wherein, the scanning module 111 For scanning the received signal of each receiving antenna with each transmitted signal, the transmitted signal is reflected by the target source; then the phase calculation module 112 The scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each of the receiving antennas. Virtual extended signal construction module 113 based on phase calculation module 112 The obtained phase and the transmitted signal construct a virtual extended signal; finally, the virtual extended signal and the received signal are combined by the estimation module 114 to form a new received signal, and the covariance and Capon of the new received signal are calculated. The beamforming coefficients, which in turn complete the estimation of the DOA.
其中，估计模块 114 通过如下公式得到新的接收信号：
Figure 1402-appb-C000032
 The estimation module 114 obtains a new received signal by the following formula:
Figure 1402-appb-C000032
其中，Nr 表示接收天线的根数， T 表示矩阵的转置， y1m 、 y2m ， yNrm 为在第 m 个脉冲时，由目标源反射后到达第 1 根、第 2 根、第 Nr 根接收天线的接收信号，
Figure 1402-appb-C000033
 为构建的虚拟扩展信号。Where N r is the number of receiving antennas, T is the transposition of the matrix, y1m , y2m , yN r m is the first, second, and N r after being reflected by the target source at the mth pulse. The receiving signal of the root receiving antenna,
Figure 1402-appb-C000033
 A virtual extension signal for the build.
进一步地，该系统还包括一判断模块，用于 统计扫描模块 111 对每根接收天线扫描到的大于预设的极大值点个数阈值的个数 N ，当各个接收天线的极大值点的个数 N 相等且大于预设的极大值点个数阈值时，触发相位计算模块 112 执行计算，而当各个接收天线的极大值点的个数 N 相等且不大于预设的极大值点个数阈值时，触发 估计模块 114 采用原始的 Capon 估计方法进行 DOA 的估计。经试验验证，上述预设的极大值点个数阈值为 2 时效果较为理想。 Further, the system further includes a determining module for the statistical scanning module 111 For each number N of the thresholds of the maximum number of points that are scanned by each receiving antenna, when the number of maximum points of the respective receiving antennas is equal to N and greater than the preset threshold of the maximum number of points Trigger phase calculation module 112 The calculation is performed, and when the number N of the maximum value points of the respective receiving antennas is equal and not greater than the preset threshold value of the maximum number of points, the trigger estimation module 114 uses the original Capon estimation method for DOA. Estimate. It has been verified by experiments that the preset threshold value of the maximum number of points is 2, which is more effective.
上述各模块的运算原理如上文，此处不再一一赘述。 The arithmetic principles of the above modules are as described above, and will not be repeated here.
本发明在不增加现有接收天线和发射天线的情况下提高天线的自由度，尤其适用于当采样点个数比较少且 SNR 比较低或者采样点个数比较多的情况下的 MIMO 雷达中高分辨率的 DOA 估计。 The invention improves the degree of freedom of the antenna without increasing the existing receiving antenna and the transmitting antenna, and is especially suitable when the number of sampling points is small and the SNR is small. High-resolution DOA estimation in MIMO radars with low or high number of sampling points.
以上所述仅为本发明的较佳实施例而已，并不用以限制本发明，凡在本发明的精神和原则之内所作的任何修改、等同替换和改进等，均应包含在本发明的保护范围之内。 The above is only the preferred embodiment of the present invention, and is not intended to limit the present invention. Any modifications, equivalent substitutions and improvements made within the spirit and principles of the present invention should be included in the protection of the present invention. Within the scope.

Claims (10)

  1. 一种 高分辨率 DOA 估计方法，其特征在于，所述方法包括下述步骤：A high resolution DOA estimation method, characterized in that the method comprises the following steps:
    步骤 A ，各接收天线接收由目标源反射的发射信号；Step A: Each receiving antenna receives a transmission signal reflected by the target source;
    步骤 B ，利用每个发射信号对每根接收天线的接收信号进行扫描；Step B: scanning the received signal of each receiving antenna by using each transmitting signal;
    步骤 C ，将步骤 B 所扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位；Step C, step B The scanned signals are respectively multiplied by the transmitted signals to obtain phases corresponding to respective peak points in the received signals of each receiving antenna;
    步骤 D ，根据步骤 C 得到的相位以及发射信号构建虚拟扩展信号；Step D, constructing a virtual extended signal according to the phase obtained in step C and the transmitted signal;
    步骤 E ，利用所述虚拟扩展信号和接收信号组成新的接收信号，计算所述新的接收信号的协方差和 Capon 波束形成系数，进而完成 DOA 的估计。Step E, using the virtual extended signal and the received signal to form a new received signal, calculating a covariance and a Capon of the new received signal The beamforming coefficients, which in turn complete the estimation of the DOA.
  2. 权利要求1所述的高分辨率DOA估计方法，其特征在于，在步骤B与步骤C之间，还包括下述步骤：The high-resolution DOA estimation method according to claim 1, wherein between step B and step C, the method further comprises the steps of:
    步骤B1，统计步骤B中每根接收天线扫描到的极大值点的个数N；Step B1, the number N of maximum points scanned by each receiving antenna in step B is counted;
    步骤B2，当各个接收天线的极大值点的个数N相等且大于预设的极大值点个数阈值时，执行步骤C。In step B2, when the number N of the maximum value points of the respective receiving antennas is equal and greater than the preset threshold value of the maximum number of points, step C is performed.
  3. 如权利要求1所述的高分辨率DOA估计方法，其特征在于，步骤E中新的接收信号r1通过如下公式得到:
    Figure 1402-appb-C000034
         The high resolution DOA estimation method according to claim 1, wherein the new received signal r1 in step E is obtained by the following formula:
    Figure 1402-appb-C000034
    其中，Nr表示接收天线的根数，T表示矩阵的转置，y1m、y2m，yNrm为在第m个脉冲时，由目标源反射后到达第1根、第2根、第Nr根接收天线的接收信号，
    Figure 1402-appb-C000035
    为构建的虚拟扩展信号。    Where N r represents the number of receiving antennas, T represents the transposition of the matrix, y1m, y2m, yNrm is the first, second, and Nth receiving antennas reflected by the target source at the mth pulse. Receiving signal,
    Figure 1402-appb-C000035
     A virtual extension signal for the build.
  4. 如权利要求2所述的高分辨率DOA估计方法，其特征在于，在步骤B与步骤C之间，还包括下述步骤：The high-resolution DOA estimation method according to claim 2, further comprising the steps of step B and step C:
    步骤B3，当各个接收天线的极大值点的个数N相等且不大于预设的极大值点个数阈值时，则采用原始的Capon估计方法进行DOA的估计。In step B3, when the number N of the maximum value points of the respective receiving antennas is equal and not greater than the threshold value of the preset maximum value points, the original Capon estimation method is used to perform DOA estimation.
  5. 如权利要求2或4所述的高分辨率DOA估计方法，其特征在于，所述预设的极大值点个数阈值为2。The high-resolution DOA estimation method according to claim 2 or 4, wherein the preset threshold value of the maximum number of points is 2.
  6. 一种高分辨率DOA估计系统，其特征在于，包括：A high resolution DOA estimation system, comprising:
    扫描模块，用于利用每个发射信号对每根接收天线的接收信号进行扫描；所述发射信号由目标源反射；a scanning module, configured to scan a received signal of each receiving antenna by using each of the transmitting signals; the transmitting signal is reflected by the target source;
    相位计算模块，用于将扫描到的信号分别与发射信号相乘，得到每根接收天线的接收信号中各个峰值点对应的相位；a phase calculation module, configured to multiply the scanned signals by the transmitted signals respectively, to obtain a phase corresponding to each peak point in the received signal of each receiving antenna;
    虚拟扩展信号构建模块，用于根据所述相位计算模块得到的相位以及发射信号构建虚拟扩展信号；a virtual extended signal construction module, configured to construct a virtual extended signal according to the phase obtained by the phase calculation module and the transmit signal;
    估计模块，用于将所述虚拟扩展信号和接收信号组成新的接收信号，计算所述新的接收信号的协方差和Capon波束形成系数，进而完成DOA的估计。And an estimating module, configured to form the virtual extended signal and the received signal into a new received signal, calculate a covariance and a Capon beamforming coefficient of the new received signal, thereby completing estimation of the DOA.
  7. 如权利要求6所述的系统，其特征在于，所述系统还包括：The system of claim 6 wherein said system further comprises:
    判断模块，用于统计所述扫描模块对每根接收天线扫描到的极大值点的个数N，当各个接收天线的极大值点的个数N相等且大于预设的极大值点个数阈值时，触发所述相位计算模块执行计算。a judging module, configured to count the number N of maximum points scanned by the scanning module for each receiving antenna, when the number N of maximum points of each receiving antenna is equal and greater than a preset maximum point When the number threshold is reached, the phase calculation module is triggered to perform calculation.
  8. 如权利要求6所述的系统，其特征在于，所述估计模块通过如下公式得到新的接收信号：
    Figure 1402-appb-C000034
         The system of claim 6 wherein said estimating module obtains a new received signal by the following formula:
    Figure 1402-appb-C000034
    其中，Nr表示接收天线的根数，T表示矩阵的转置，y1m、y2m，yNrm为在第m个脉冲时，由目标源反射后到达第1根、第2根、第Nr根接收天线的接收信号，
    Figure 1402-appb-C000035
    为构建的虚拟扩展信号。    Where N r represents the number of receiving antennas, T represents the transposition of the matrix, y1m, y2m, yNrm is the first, second, and Nth receiving antennas reflected by the target source at the mth pulse. Receiving signal,
    Figure 1402-appb-C000035
     A virtual extension signal for the build.
  9. 如权利要求7所述的系统，其特征在于，所述估计模块还用于在各个接收天线的极大值点的个数N相等且不大于预设的极大值点个数阈值时，采用原始的Capon估计方法进行DOA的估计。The system according to claim 7, wherein the estimating module is further configured to: when the number N of maximum points of each receiving antenna is equal and not greater than a preset threshold of a maximum number of points, The original Capon estimation method performs DOA estimation.
  10. 如权利要求7或9所述的系统，其特征在于，所述预设的极大值点个数阈值为2。The system according to claim 7 or 9, wherein the preset threshold value of the maximum number of points is 2.
PCT/CN2014/088099 2014-01-24 2014-10-03 High resolution doa estimation method and system WO2015109869A1 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201410033733.5 2014-01-24
CN201410033733.5A CN103760519B (en) 2014-01-24 2014-01-24 High resolution DOA estimation method and system

Publications (1)

Publication Number Publication Date
WO2015109869A1 true WO2015109869A1 (en) 2015-07-30

Family

ID=50527787

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2014/088099 WO2015109869A1 (en) 2014-01-24 2014-10-03 High resolution doa estimation method and system

Country Status (2)

Country Link
CN (1) CN103760519B (en)
WO (1) WO2015109869A1 (en)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109188346A (en) * 2018-08-31 2019-01-11 西安电子科技大学 Macroscale homogenous cylindrical array list snap DOA estimation method
CN110308418A (en) * 2019-08-06 2019-10-08 中国石油大学(华东) A kind of DOA estimation framework method
WO2023207659A1 (en) * 2022-04-25 2023-11-02 中兴通讯股份有限公司 Doa determining method and device, storage medium and electronic device

Families Citing this family (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103760519B (en) * 2014-01-24 2016-02-03 深圳大学 High resolution DOA estimation method and system
CN104023397B (en) * 2014-06-20 2017-06-13 深圳大学 Multiple target DOA estimating systems and method of estimation based on gossip algorithms in distributed network
CN104239731A (en) * 2014-09-24 2014-12-24 哈尔滨工业大学 Direction estimation method of MIMO-UKF-MUSIC (Multiple Input Multiple Output-Unscented Kalman Filter-Multiple Signal Classification) target
CN104833947B (en) * 2015-04-03 2017-10-31 西北大学 A kind of any battle array receives symmetrical virtual conversion 2D DOA separation algorithms
CN104820210B (en) * 2015-04-16 2018-06-05 深圳大学 Adaptive range estimation method and system under frequency interferences
CN104808196B (en) * 2015-04-16 2018-02-06 深圳大学 Distance by radar evaluation method and system based on frequency virtual extended
KR102422396B1 (en) * 2015-09-01 2022-07-20 주식회사 에이치엘클레무브 Method of spatial interpolation for linear phased array antenna and appratus thereof
EP3151028B1 (en) * 2015-09-29 2018-11-14 Rohde & Schwarz GmbH & Co. KG Direction finder and method for direction finding wherein a quality criterion for the incoming signals is determined
EP3465255A1 (en) * 2016-06-01 2019-04-10 Sony Mobile Communications Inc. Radar probing employing pilot signals
CN107621623B (en) * 2016-07-13 2020-04-10 智易科技股份有限公司 Signal direction detection method and beam former using same
CN107045117B (en) * 2016-09-23 2019-10-25 南京工程学院 Based on Capon Wave beam forming localization method and device
CN107290732B (en) * 2017-07-11 2020-05-22 哈尔滨工程大学 Single-base MIMO radar direction finding method for large-quantum explosion
CN110515066B (en) * 2019-08-20 2023-03-24 立晟智能科技(成都)有限公司 Vehicle-mounted millimeter wave radar and target height measuring method thereof
CN111800738B (en) * 2020-07-13 2021-10-12 深圳大学 Method and system for sharing millimeter wave mobile base station online frequency spectrum based on clustering algorithm

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1384368A (en) * 2001-04-27 2002-12-11 三菱电机株式会社 Arrival bearing estimating method
US20080122681A1 (en) * 2004-12-24 2008-05-29 Kazuo Shirakawa Direction-of-arrival estimating device and program
US20090243933A1 (en) * 2008-03-28 2009-10-01 Fujitsu Limited Direction-of-arrival estimation apparatus
CN101729092A (en) * 2002-05-07 2010-06-09 松下电器产业株式会社 Radio communication device and arrival direction estimation method
CN102803984A (en) * 2009-04-23 2012-11-28 法国电信教育集团 Orientation and localization system
CN103760519A (en) * 2014-01-24 2014-04-30 深圳大学 High resolution DOA estimation method and system

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR100617843B1 (en) * 2003-07-26 2006-08-28 삼성전자주식회사 System and method for transmitting/receiving signal in mobile communication system using adaptive antenna array scheme
WO2009080057A1 (en) * 2007-12-19 2009-07-02 Telecom Italia S.P.A. Method and system for switched beam antenna communications
JP4481336B2 (en) * 2008-02-27 2010-06-16 京セラ株式会社 Channel information prediction system and channel information prediction method
US8428897B2 (en) * 2008-04-08 2013-04-23 Massachusetts Institute Of Technology Method and apparatus for spectral cross coherence

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1384368A (en) * 2001-04-27 2002-12-11 三菱电机株式会社 Arrival bearing estimating method
CN101729092A (en) * 2002-05-07 2010-06-09 松下电器产业株式会社 Radio communication device and arrival direction estimation method
US20080122681A1 (en) * 2004-12-24 2008-05-29 Kazuo Shirakawa Direction-of-arrival estimating device and program
US20090243933A1 (en) * 2008-03-28 2009-10-01 Fujitsu Limited Direction-of-arrival estimation apparatus
CN102803984A (en) * 2009-04-23 2012-11-28 法国电信教育集团 Orientation and localization system
CN103760519A (en) * 2014-01-24 2014-04-30 深圳大学 High resolution DOA estimation method and system

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109188346A (en) * 2018-08-31 2019-01-11 西安电子科技大学 Macroscale homogenous cylindrical array list snap DOA estimation method
CN109188346B (en) * 2018-08-31 2023-03-10 西安电子科技大学 Single snapshot DOA estimation method for large-scale uniform cylindrical array
CN110308418A (en) * 2019-08-06 2019-10-08 中国石油大学(华东) A kind of DOA estimation framework method
WO2023207659A1 (en) * 2022-04-25 2023-11-02 中兴通讯股份有限公司 Doa determining method and device, storage medium and electronic device

Also Published As

Publication number Publication date
CN103760519A (en) 2014-04-30
CN103760519B (en) 2016-02-03

Similar Documents

Publication Publication Date Title
WO2015109869A1 (en) High resolution doa estimation method and system
JP4842127B2 (en) Method for estimating arrival time of signal received in TH-UWB system by two-step estimation method
KR100315197B1 (en) Spread-spectrum receiver
US20080194207A1 (en) System and method for estimating the multi-path delays in a signal using a spatially blind antenna array
CN106227701B (en) A kind of automatic correcting method of the amplitude phase error of the receiving channel of array signal
EP1361679A3 (en) Radio communication device and arrival direction estimation method
CN107255796A (en) Arrowband near-field signals source localization method under a kind of non-uniform noise
Wang et al. An improved MUSIC TOA estimator for RFID positioning
Li et al. Estimation and equalization of rapidly varying sparse acoustic communication channels
Jeong et al. A high resolution time delay estimation technique in frequency domain for positioning system
WO2011102610A2 (en) Timing synchronization method and apparatus in a wireless communication system
Krasny et al. Enhanced time of arrival estimation with successive cancellation
JP3775604B2 (en) Synchronization detection device and wireless device
Jaafar et al. Joint angle and delay estimation of point sources
Wang et al. Node localization based on time reversal in wireless sensor network
US20100150219A1 (en) Sampling device and method in wireless communication system
Model Joint Multipath Delay and Direction Tracking for CDMA Array Systems
KR101040172B1 (en) Method of simultaneously estimating arriving angle and delay time of received signal in a multipath channel
Zhang et al. Blind synchronization algorithm for the DS-CDMA signals
JP2023113550A (en) Communication device, information processing method, and program
Zhou et al. Multi-target UWB passive ranging with local template uncertainty
CN116545474A (en) Communication device, information processing method, and computer-readable storage medium
Manikas et al. Joint multipath delay and direction tracking for CDMA array systems
KR101210606B1 (en) sampling device and method in wireless communication system
US7643539B2 (en) Multi-path equalizer configuration technique

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 14879818

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 14879818

Country of ref document: EP

Kind code of ref document: A1