WO2015065680A1 - Transmitter (tx) residual sideband (rsb) and local oscillator (lo) leakage calibration using a reconfigurable tone generator (tg) and lo paths - Google Patents
Transmitter (tx) residual sideband (rsb) and local oscillator (lo) leakage calibration using a reconfigurable tone generator (tg) and lo paths Download PDFInfo
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- WO2015065680A1 WO2015065680A1 PCT/US2014/060006 US2014060006W WO2015065680A1 WO 2015065680 A1 WO2015065680 A1 WO 2015065680A1 US 2014060006 W US2014060006 W US 2014060006W WO 2015065680 A1 WO2015065680 A1 WO 2015065680A1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B17/00—Monitoring; Testing
- H04B17/10—Monitoring; Testing of transmitters
- H04B17/11—Monitoring; Testing of transmitters for calibration
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B17/00—Monitoring; Testing
- H04B17/10—Monitoring; Testing of transmitters
- H04B17/11—Monitoring; Testing of transmitters for calibration
- H04B17/14—Monitoring; Testing of transmitters for calibration of the whole transmission and reception path, e.g. self-test loop-back
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B17/00—Monitoring; Testing
- H04B17/20—Monitoring; Testing of receivers
- H04B17/21—Monitoring; Testing of receivers for calibration; for correcting measurements
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
- H04L2027/0016—Stabilisation of local oscillators
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
- H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
- H04L27/36—Modulator circuits; Transmitter circuits
- H04L27/362—Modulation using more than one carrier, e.g. with quadrature carriers, separately amplitude modulated
- H04L27/364—Arrangements for overcoming imperfections in the modulator, e.g. quadrature error or unbalanced I and Q levels
Definitions
- Certain aspects of the present disclosure generally relate to radio frequency (RP) circuits and, more particularly, to calibrating a residual sideband (RSB) of a transmitter path in a transceiver and to calibrating a local oscillator (LO) leakage of the transmitter path.
- RP radio frequency
- Wireless communication networks are widely deployed to provide various communication services such as telephony, video, data, messaging, broadcasts, and so on.
- Such networks which are usually multiple access networks, support communications for multiple users by sharing the available network resources.
- one network may be a 3G (the third generation of mobile phone standards and technology) system, which may provide network service via any one of various 3G radio access technologies (RATs) including EVDO (Evolution-Data Optimized), lxRTT (1 times Radio Transmission Technology, or simply lx), W-CDMA (Wideband Code Division Multiple Access), UMTS-TDD (Universal Mobile Telecommunications System - Time Division Duplexing), HSPA (High Speed Packet Access), GPRS (General Packet Radio Service), or EDGE (Enhanced Data rates for Global Evolution).
- RATs 3G radio access technologies
- the 3G network is a wide area cellular telephone network that evolved to incorporate high-speed internet access and video telephony, in addition to voice calls. Furthermore, a 3G network may be more established and provide larger coverage areas than other network systems.
- Such multiple access networks may also include code division multiple access (CDMA) systems, time division multiple access (TDMA) systems, frequency division multiple access (FDMA) systems, orthogonal frequency division multiple access (OFDMA) systems, single-carrier FDMA (SC-FDMA) networks, 3 r Generation Partnership Project (3 GPP) Long Term Evolution (LTE) networks, Long Term Evolution Advanced (LTE -A) networks, and other 4G networks.
- CDMA code division multiple access
- TDMA time division multiple access
- FDMA frequency division multiple access
- OFDMA orthogonal frequency division multiple access
- SC-FDMA single-carrier FDMA
- 3 GPP 3 r Generation Partnership Project
- LTE Long Term Evolution
- LTE -A Long Term Evolution Advanced
- a wireless communication network may include a number of base stations that can support communication for a number of mobile stations.
- a mobile station may communicate with a base station (BS) via a downlink and an uplink.
- the downlink (or forward link) refers to the communication link from the base station to the mobile station
- the uplink (or reverse link) refers to the communication link from the mobile station to the base station.
- a base station may transmit data and control information on the downlink to a mobile station and/or may receive data and control information on the uplink from the mobile station.
- Certain aspects of the present disclosure generally relate to transmitter modules. More specifically, certain aspects of the present disclosure generally relate to reconfiguring a tone generator (TG) and the transmitter (TX) synthesizer/LO (local oscillator) paths to calibrate the TX residual sideband (RSB)/image suppression and/or the TX LO leakage/carrier suppression.
- TG tone generator
- TX transmitter
- LO local oscillator
- Certain aspects of the present disclosure provide a method for calibrating a transceiver for wireless communications.
- the method generally includes configuring a first oscillating signal as an input signal to at least a portion of a receiver (RX) path, calibrating a residual sideband (RSB) of the receiver path using a second oscillating signal as a local oscillating signal for the receiver path, and calibrating an RSB of the transmitter path by routing an output of the transmitter path to the receiver path, after calibrating the RSB of the receiver path.
- the receiver path may be a feedback receiver (FBRX) path internal to the transceiver.
- FBRX feedback receiver
- the apparatus generally includes a transmitter path, a receiver path, and a processing system.
- the processing system is typically configured to configure a first oscillating signal as an input signal to at least a portion of the receiver path, to calibrate an RSB of the receiver path using a second oscillating signal as a local oscillating signal for the receiver path, and to calibrate an RSB of the transmitter path by routing an output of the transmitter path to the receiver path, after calibrating the RSB of the receiver path.
- the apparatus generally includes means for configuring a first oscillating signal as an input signal to at least a portion of a receiver path, means for calibrating an RSB of the receiver path using a second oscillating signal as a local oscillating signal for the receiver path, and means for calibrating an RSB of the transmitter path by routing an output of the transmitter path to the receiver path, after calibrating the RSB of the receiver path.
- Certain aspects of the present disclosure provide a method for calibrating a transceiver for wireless communications.
- the method generally includes routing an output of a transmitter path to a receiver path; using a first local oscillating signal for the transmitter path; using a second local oscillating signal for the receiver path, wherein the first local oscillating signal has a first frequency different from a second frequency of the second local oscillating signal; and measuring an output of the receiver path as a local oscillator (LO) leakage for the transmitter path.
- LO local oscillator
- the apparatus generally includes a transmitter path; a receiver path; and a processing system.
- the processing system is typically configured to route an output of the transmitter path to the receiver path; to use a first local oscillating signal for the transmitter path; to use a second local oscillating signal for the receiver path, wherein the first local oscillating signal has a first frequency different from a second frequency of the second local oscillating signal; and to measure an output of the receiver path as a LO leakage for the transmitter path.
- the apparatus generally includes means for routing an output of a transmitter path to a receiver path; means for using a first local oscillating signal for the transmitter path; means for using a second local oscillating signal for the receiver path, wherein the first local oscillating signal has a first frequency different from a second frequency of the second local oscillating signal; and means for measuring an output of the receiver path as a LO leakage for the transmitter path.
- FIG. 1 is a diagram of an example wireless communications network in accordance with certain aspects of the present disclosure.
- FIG. 2 is a block diagram of an example access point (AP) and example user terminals in accordance with certain aspects of the present disclosure.
- FIG. 3A is an example block diagram of a transceiver circuit configured to calibrate a residual sideband (RSB) of a feedback receiver (FBRX) as a first step to calibrating the RSB of the transmitter (TX) path, in accordance with certain aspects of the present disclosure.
- RSB residual sideband
- FBRX feedback receiver
- FIG. 3B is an example block diagram of the transceiver circuit of FIG. 3A configured to calibrate the TX RSB after calibrating the FBRX RSB, in accordance with certain aspects of the present disclosure.
- FIG. 3C is an example block diagram of the transceiver circuit of FIG. 3A configured to calibrate the RSB of the FBRX as an alternative to the configuration in FIG. 3A, in accordance with certain aspects of the present disclosure.
- FIG. 3D is an example block diagram of the transceiver circuit of FIG. 3A configured to calibrate the TX RSB after calibrating the FBRX RSB according to the configuration in FIG. 3C, in accordance with certain aspects of the present disclosure.
- FIG. 4 is an example block diagram of the transceiver circuit of FIG. 3A configured to calibrate the TX local oscillator (LO) leakage, in accordance with certain aspects of the present disclosure.
- LO local oscillator
- FIG. 5A is an example block diagram of a tone generator (TG) used in FIGs. 3A and 4, in accordance with certain aspects of the present disclosure.
- TG tone generator
- FIG. 5B is an example block diagram of a multi-stage voltage-controlled oscillator (VCO) for the TG of FIG. 5A, in accordance with certain aspects of the present disclosure.
- VCO voltage-controlled oscillator
- FIG. 6 is a flow diagram of example operations for calibrating the RSB of a transmitter path, in accordance with certain aspects of the present disclosure.
- FIG. 7 is a flow diagram of example operations for calibrating the LO leakage of a transmitter path, in accordance with certain aspects of the present disclosure.
- CDMA Code Division Multiple Access
- OFDM Orthogonal Frequency Division Multiplexing
- TDMA Time Division Multiple Access
- SDMA Spatial Division Multiple Access
- SC-FDMA Single Carrier Frequency Division Multiple Access
- TD- SCDMA Time Division Synchronous Code Division Multiple Access
- Multiple user terminals can concurrently transmit/receive data via different (1) orthogonal code channels for CDMA, (2) time slots for TDMA, or (3) sub- bands for OFDM.
- a CDMA system may implement IS-2000, IS-95, IS-856, Wideband-CDMA (W-CDMA), or some other standards.
- An OFDM system may implement Institute of Electrical and Electronics Engineers (IEEE) 802.11, IEEE 802.16, Long Term Evolution (LTE) (e.g., in TDD and/or FDD modes), or some other standards.
- IEEE Institute of Electrical and Electronics Engineers
- LTE Long Term Evolution
- a TDMA system may implement Global System for Mobile Communications (GSM) or some other standards. These various standards are known in the art.
- FIG. 1 illustrates a wireless communications system 100 with access points and user terminals.
- An access point is generally a fixed station that communicates with the user terminals and may also be referred to as a base station (BS), an evolved Node B (eNB), or some other terminology.
- a user terminal may be fixed or mobile and may also be referred to as a mobile station (MS), an access terminal, user equipment (UE), a station (STA), a client, a wireless device, or some other terminology.
- a user terminal may be a wireless device, such as a cellular phone, a personal digital assistant (PDA), a handheld device, a wireless modem, a laptop computer, a tablet, a personal computer, etc.
- PDA personal digital assistant
- Access point 110 may communicate with one or more user terminals 120 at any given moment on the downlink and uplink.
- the downlink i.e., forward link
- the uplink i.e., reverse link
- a user terminal may also communicate peer-to-peer with another user terminal.
- a system controller 130 couples to and provides coordination and control for the access points.
- System 100 employs multiple transmit and multiple receive antennas for data transmission on the downlink and uplink.
- Access point 110 may be equipped with a number N ap of antennas to achieve transmit diversity for downlink transmissions and/or receive diversity for uplink transmissions.
- a set N u of selected user terminals 120 may receive downlink transmissions and transmit uplink transmissions.
- Each selected user terminal transmits user-specific data to and/or receives user-specific data from the access point.
- each selected user terminal may be equipped with one or multiple antennas (i.e., N ut ⁇ 1).
- the N u selected user terminals can have the same or different number of antennas.
- Wireless system 100 may be a time division duplex (TDD) system or a frequency division duplex (FDD) system.
- TDD time division duplex
- FDD frequency division duplex
- the downlink and uplink share the same frequency band.
- the downlink and uplink use different frequency bands.
- System 100 may also utilize a single carrier or multiple carriers for transmission.
- Each user terminal may be equipped with a single antenna (e.g., in order to keep costs down) or multiple antennas (e.g., where the additional cost can be supported).
- FIG. 2 shows a block diagram of access point 110 and two user terminals 120m and 120x in wireless system 100.
- Access point 110 is equipped with N ap antennas 224a through 224ap.
- User terminal 120m is equipped with N ut m antennas
- Access point 110 is a transmitting entity for the downlink and a receiving entity for the uplink.
- Each user terminal 120 is a transmitting entity for the uplink and a receiving entity for the downlink.
- a "transmitting entity” is an independently operated apparatus or device capable of transmitting data via a frequency channel
- a “receiving entity” is an independently operated apparatus or device capable of receiving data via a frequency channel.
- the subscript “dn” denotes the downlink
- the subscript “up” denotes the uplink
- N up user terminals are selected for simultaneous transmission on the uplink
- Ndn user terminals are selected for simultaneous transmission on the downlink
- N up may or may not be equal to Ndn
- N up and Ndn may be static values or can change for each scheduling interval. Beam-steering or some other spatial processing technique may be used at the access point and user terminal.
- a TX data processor 288 receives traffic data from a data source 286 and control data from a controller 280.
- TX data processor 288 processes (e.g., encodes, interleaves, and modulates) the traffic data ⁇ d up ⁇ for the user terminal based on the coding and modulation schemes associated with the rate selected for the user terminal and provides a data symbol stream ⁇ s up ⁇ for one of the N ut antennas.
- a transceiver front end (TX/RX) 254 receives and processes (e.g., converts to analog, amplifies, filters, and frequency upconverts) a respective symbol stream to generate an uplink signal.
- the transceiver front end 254 may also route the uplink signal to one of the N ut,m antennas for transmit diversity via an RF switch, for example.
- the controller 280 may control the routing within the transceiver front end 254.
- Memory 282 may store data and program codes for the user terminal 120 and may interface with the controller 280.
- a number N up of user terminals may be scheduled for simultaneous transmission on the uplink.
- Each of these user terminals transmits its set of processed symbol streams on the uplink to the access point.
- N ap antennas 224a through 224ap receive the uplink signals from all N up user terminals transmitting on the uplink.
- a transceiver front end 222 may select signals received from one of the antennas 224 for processing.
- a combination of the signals received from multiple antennas 224 may be combined for enhanced receive diversity.
- the access point's transceiver front end 222 also performs processing complementary to that performed by the user terminal's transceiver front end 254 and provides a recovered uplink data symbol stream.
- the recovered uplink data symbol stream is an estimate of a data symbol stream ⁇ s up ⁇ transmitted by a user terminal.
- An RX data processor 242 processes (e.g., demodulates, deinterleaves, and decodes) the recovered uplink data symbol stream in accordance with the rate used for that stream to obtain decoded data.
- the decoded data for each user terminal may be provided to a data sink 244 for storage and/or a controller 230 for further processing.
- a TX data processor 210 receives traffic data from a data source 208 for Ndn user terminals scheduled for downlink transmission, control data from a controller 230 and possibly other data from a scheduler 234. The various types of data may be sent on different transport channels. TX data processor 210 processes (e.g., encodes, interleaves, and modulates) the traffic data for each user terminal based on the rate selected for that user terminal. TX data processor 210 may provide a downlink data symbol streams for one of more of the Ndn user terminals to be transmitted from one of the N ap antennas.
- the transceiver front end 222 receives and processes (e.g., converts to analog, amplifies, filters, and frequency upconverts) the symbol stream to generate a downlink signal.
- the controller 230 may control the routing within the transceiver front end 222.
- Memory 232 may store data and program codes for the access point 110 and may interface with the controller 230
- N ut m antennas 252 receive the downlink signals from access point 110.
- the transceiver front end 254 may select signals received from one of the antennas 252 for processing.
- a combination of the signals received from multiple antennas 252 may be combined for enhanced receive diversity.
- the user terminal's transceiver front end 254 also performs processing complementary to that performed by the access point's transceiver front end 222 and provides a recovered downlink data symbol stream.
- An RX data processor 270 processes (e.g., demodulates, deinterleaves, and decodes) the recovered downlink data symbol stream to obtain decoded data for the user terminal.
- a local oscillator is typically included in radio frequency front-ends (RFFEs), such as transceiver front end 222 or 254, to generate a signal utilized to convert a signal of interest to a different frequency using a mixer.
- RFFEs radio frequency front-ends
- this frequency conversion process produces the sum and difference frequencies of the LO frequency and the frequency of the signal of interest.
- the sum and difference frequencies are referred to as the beat frequencies.
- tuning to different frequencies indicates using a variable-frequency oscillator, which involves compromises between stability and tunability.
- Contemporary systems employ frequency synthesizers with a voltage-controlled oscillator (VCO) to generate a stable, tunable LO with a particular tuning range.
- VCO voltage-controlled oscillator
- ET envelope tracking
- EPT envelope power tracking
- TX transmitter
- RSB residual sideband
- LO local oscillator
- the TX RSB and/or LO leakage may most likely be calibrated.
- calibration of these radio frequency (RF) parameters at high frequency is technically challenging.
- phase and gain mismatches for RSB compensation
- DC offsets for LO leakage compensation
- DAC digital-to-analog converter
- ICs transceiver integrated circuits
- TX LO leakage calibration is to use the same TX LO for both the TX signal path and the feedback receiver (FBRX) path.
- the RF tone at the power amplifier (PA) output in the TX path may then be coupled to the FBRX and down-converted as a DC tone at the FBRX output.
- the DC tone may be used to adjust the DC offsets before the TX DAC inputs to decrease the TX LO leakage.
- the improvement in the TX LO leakage after the calibration is limited.
- both the TX RSB and LO leakage are calibrated on a part-to-part basis, as part of the "internal device calibration" on the user terminal 120. This is possible since the calibration can be autonomous and no external signal is needed from the callbox or other external equipment (i.e., self-calibration).
- RSB calibration, correction, or adjustment may also be referred to as quadrature mismatch calibration, sideband suppression, or image suppression.
- quadrature mismatch calibration sideband suppression
- image suppression image suppression
- the RSB of a receiver path may be compensated first, and then the TX RSB may be compensated using the calibrated receiver path.
- the RSB of a receiver path e.g., the FBRX RSB
- the TX RSB may be compensated using the calibrated receiver path.
- any receiver path may be used, for ease of explanation the description that follows uses the FBRX since outputs from the transmitter path are intended to be routed to the FBRX for internal measurements.
- FIG. 3A is an example block diagram of a transceiver circuit in a first configuration 300 for calibrating the FBRX RSB, in accordance with certain aspects of the present disclosure.
- the bolded circuit components illustrate the portions of the transceiver circuit being used for each step in the TX RSB calibration. Since it is difficult to produce a pure tone having only a single frequency without any harmonics, a "tone" as used herein generally refers to a signal characterized by a single specific fundamental frequency, where harmonics are at least 20 dB down from the amplitude of the fundamental frequency.
- the output of a tone generator (TG) 302 used to produce a continuous wave (CW) signal is configured as the RF input to the FBRX path 304 via a switch 305 (shown in the closed position).
- a tone generator (TG) 302 used to produce a continuous wave (CW) signal e.g., a single tone generator (STG) outputting a single frequency
- STG single tone generator
- the output of the TG 302 may be amplified, buffered, or attenuated by a variable gain amplifier (VGA) 303 before being input to the FBRX path 304.
- VGA variable gain amplifier
- the tone (labeled "RF TG”) may be amplified, buffered, or attenuated by a low noise amplifier (LNA) 306, the output of the LNA 306 is mixed with the LO for the TX path (labeled "LO TX") at a mixer 308 to generate frequency-converted signals in the baseband, and the frequency-converted signals are filtered by a baseband filter (BBF) 310 (e.g., a low-pass filter).
- BBF baseband filter
- the FBRX path 304 may also include an analog-to-digital converter (ADC) 312, although the ADC may not be internal to the transceiver integrated circuit (IC).
- ADC analog-to-digital converter
- the output of the TG 302 (and the VGA 303) may be input to the mixer 308 directly, rather than input to the LNA 306.
- tones at the signal frequency (RF TG - LO TX, where LO TX is the LO for the TX path) and at the image frequency (LO TX - RF TG) are available at the I and Q outputs of the FBRX ADC 312.
- the power difference (labeled "RSB FBRX") between the two tones represents the FBRX RSB or, equivalently, the FBRX phase and gain imbalance.
- the results of the FBRX RSB calibration may be stored in nonvolatile memory (e.g., memory 282) and recalled or otherwise used during the remainder of the TX RSB calibration, during other calibrations using the FBRX path, and during normal operation of the user terminal 120.
- the FBRX RSB calibration may be performed at different operating parameters (e.g., at different temperatures and/or at different frequencies). In this case, the results of the FBRX RSB calibration may be stored with respect to these different operating parameters and may be recalled or otherwise used accordingly.
- FIG. 3B is an example block diagram of the transceiver circuit of FIG. 3 A in a second configuration 350 for calibrating the TX RSB after calibrating the FBRX RSB, in accordance with certain aspects of the present disclosure.
- the output of the TX frequency synthesizing circuit 352 (labeled "TX Synth") is configured as the LO for both the TX path 354 and the FBRX path 304.
- the output of the TX frequency synthesizing circuit 352 may be amplified by an amplifier 355 and/or frequency divided by a frequency dividing circuit 356 before being sent via switches 358, 360 (shown in the closed position) to the mixers 308, 362.
- the TX path 354 may comprise a BBF 366, the mixer 362 for mixing the filtered signals from the BBF 336 with LO for the TX path (labeled "LO TX") to generate a frequency- converted RF signal, and a driver amplifier (DA) 368 for amplifying the RF signal.
- the TX path 354 may also include a power amplifier (PA) 370 for amplifying the amplified RF signal from the DA 368, although the PA 370 may not be internal to the transceiver IC.
- PA power amplifier
- the DAC 364 may also be considered as part of the TX path 354, the DAC may be external to the transceiver IC.
- the output of the TX path 354 (labeled "RF TX") is coupled to the input of the FBRX path 304 (e.g., via a duplexer 372 or a switch, an RF coupler 374, a programmable attenuator 376, and a switch 378 (shown in the closed position)).
- the power difference (labeled "RSB TX") between the two tones represents the TX RSB or, equivalently, the TX phase and gain imbalance.
- the results of the TX RSB calibration may be stored in nonvolatile memory (e.g., memory 282) and recalled or otherwise used during normal operation of the user terminal 120.
- the TX RSB calibration may be performed at different operating parameters (e.g., at different temperatures, at different frequencies, and/or at different TX output power levels).
- the results of the TX RSB calibration may be stored with respect to these different operating parameters and may be recalled or otherwise used accordingly.
- FIG. 3C is an example block diagram of the transceiver circuit of FIG. 3 A in a third configuration 380 for calibrating the FBRX RSB, in accordance with certain aspects of the present disclosure.
- the output of the TX path 354 (which may be a tone labeled "RF TX") is coupled to the input of the FBRX path 304 (e.g., via the duplexer 372 or a switch, the RF coupler 374, the programmable attenuator 376, and the switch 378), rather than the output of the TG 302.
- the output of the TX path 354 (or the attenuated output of the programmable attenuator 376, if used) may be amplified by the LNA 306, the amplified output of the LNA 306 may be mixed with the output of the TG 302 (labeled "LO TG") provided via a switch 384 (shown in the closed position) at the mixer 308 to generate frequency-converted signals in the baseband, and the frequency-converted signals may be filtered by the BBF 310.
- the output of the TG 302 may be amplified by an amplifier 382 before being input to the mixer 308.
- the output of the TX path 354 (or the attenuated output of the programmable attenuator 376) may be input to the mixer 308 directly, rather than input to the LNA 306.
- tones at the signal frequency (RF TX - LO TG) and at the image frequency (LO TG - RF TX) are available at the I and Q outputs of the FBRX ADC 312.
- the power difference (labeled "RSB FBRX") between the two tones represents the FBRX RSB or, equivalently, the FBRX phase and gain imbalance.
- FIG. 3D is an example block diagram of the transceiver circuit of FIG. 3A configured to in a fourth configuration 390 for calibrating the TX RSB after calibrating the FBRX RSB according to the third configuration 380 in FIG. 3C, in accordance with certain aspects of the present disclosure.
- the fourth configuration 390 is similar to the second configuration 350 of FIG. 3B, except that the TG 302 (labeled "LO TG") functions as the LO for the FBRX path 304, rather than the output of the TX frequency synthesizing circuit 352.
- the switch 360 is open, and the switch 384 is closed.
- the output of the TG 302 may be amplified by an amplifier 382 before being input to the mixer 308.
- the output of the TX path 354 (or the attenuated output of the programmable attenuator 376) may be input to the mixer 308 directly, rather than input to the LNA 306.
- the power difference (labeled "RSB TX") between the two tones represents the TX RSB or, equivalently, the TX phase and gain imbalance.
- LO leakage calibration, correction, or adjustment may also be referred to as carrier suppression.
- carrier suppression For ease of description and to avoid confusion, the present disclosure hereinafter uses LO leakage calibration.
- a third configuration 400 of FIG. 3A's transceiver circuit is used, as illustrated in FIG. 4.
- the TG 302 is configured as the LO to the FBRX at a frequency different from the TX LO, and the output of the TG 302 may be amplified by the amplifier 382 and input to the mixer 308 via the switch 384 (shown in the closed position). Switches 305 and 360 are open in the third configuration 400.
- the TX frequency synthesizing circuit 352 is configured as the LO for the TX path 354.
- the output of the TX path 354 is coupled to the input of the FBRX path 304 (e.g., via the duplexer 372 or a switch, the RF coupler 374, the programmable attenuator 376, and the switch 378), as described above.
- a tone at LO TX - LO TG is available at the FBRX ADC outputs.
- the power of this tone represents the amount of LO leaked at the output of the TX path 354.
- the magnitude of the captured data is measured by using the sum of the square of the in-phase and the square of the quadrature signals (i.e., I 2 +Q 2 ). This is equivalent to calculating the power of the FBRX ADC outputs at LO TX - LO TG by using a fast Fourier transform (FFT). Any of various suitable search algorithms (e.g., a binary search) may be performed to find the minimum magnitude (e.g., I 2 +Q 2 ) by adjusting the DC offsets of the TX DAC inputs.
- FFT fast Fourier transform
- the results of the LO leakage calibration may be stored in nonvolatile memory (e.g., memory 282) and recalled during normal operation of the user terminal 120.
- the LO leakage calibration may be performed at different operating parameters (e.g., at different temperatures, at different frequencies, and/or with different TX output power levels).
- the results of the LO leakage calibration may be stored with respect to these different operating parameters and may be recalled or otherwise used accordingly.
- the output of either the DA 368 or the PA 370 may be coupled back to the FBRX input.
- the TX output may be coupled back to the FBRX input via a single coupler (e.g., RF coupler 374) in front of the antenna to simplify the coupling path.
- the switches 305, 358, 360, 384 in the TG (LO and RF outputs) and LO paths, as shown in FIGs. 3A, 3B, and 4 may be substituted by tri-state buffers.
- the TG 302 may be implemented as a phase- locked loop (PLL) 502 with a VCO 504, as illustrated in FIG. 5A.
- PLL phase- locked loop
- the VCO 504 for the TG may be a multi-stage VCO.
- FIG. 5B is an example block diagram of a four- stage VCO 520 for the TG 302 of FIG. 5A, in accordance with certain aspects of the present disclosure. This four-stage oscillator may provide quadrature LOs to the TX and/or FBRX paths via various buffers and/or amplifiers 522, as shown in FIG. 5A.
- the TG 302 may be configured to either provide LO signals or an adjustable RF signal to the FBRX path 304, for example.
- the VCO 504 in the TG may be implemented as an oscillator followed by a quadrature phase-splitter or other functionally equivalent circuitry.
- Certain aspects of the present disclosure provide calibration techniques such that the TX RSB and LO leakage constraints may be complied with over process corners, including the more restrictive specifications of an ET/EPT system. This helps enable the use of a low-cost PA in a transmitter with competitive ACLR while maintaining good power efficiency.
- These calibration techniques involve part-to-part calibration (e.g., individual user terminal calibration), which typically results in better performance when compared to statistically derived compensation for all user terminals 120.
- the compensation accounts for the non-idealities in the full TX chain. This improves the performance after the calibration, especially in cases where the TX DAC 364 and the remainder of the TX path 354 are partitioned into two separate ICs.
- FIG. 6 is a flow diagram of example operations 600 for calibrating the RSB of a transmitter path, in accordance with certain aspects of the present disclosure.
- the operations 600 may begin, at 602, by configuring a first oscillating signal as an input signal to at least a portion of a receiver (RX) path.
- the receiver path may be a feedback receiver (FBRX) path, for example, which may be internal to the transceiver.
- the FBRX path may be external to the transceiver (e.g., on another IC different from the transceiver IC).
- the at least the portion of the receiver path includes a low noise amplifier (LNA), a mixer, and a (baseband) filter.
- LNA low noise amplifier
- mixer mixer
- baseband baseband
- the at least the portion of the receiver path includes a mixer and a (baseband) filter, without the LNA being included in the at least the portion (even if present in the receiver path).
- the receiver path may also include an analog-to- digital converter (ADC), although the ADC may not be internal to the transceiver integrated circuit (IC).
- ADC analog-to- digital converter
- a residual sideband (RSB) of the receiver path may be calibrated using a second oscillating signal as a local oscillating signal for the receiver path.
- calibrating the RSB of the receiver path at 604 involves amplifying the first oscillating signal with a low noise amplifier (LNA) and mixing the amplified signal with the local oscillating signal for the receiver path to produce a baseband frequency at a difference between frequencies of the amplified signal and the local oscillating signal (e.g., RF TG - LO TX).
- calibrating the RSB of the receiver path involves mixing the first oscillating signal with the local oscillating signal for the receiver path to produce a baseband frequency at a difference between frequencies of the first oscillating signal and the local oscillating signal.
- an RSB of the transmitter path may be calibrated by routing an output of the transmitter path to the receiver path, after calibrating the RSB of the receiver path.
- the second oscillating signal may be used as the local oscillating signal for the receiver path during the TX RSB calibration at 606.
- the routing at 606 entails routing the output of the transmitter path to the receiver path via at least one of a power amplifier (PA), a duplexer, a radio frequency (RF) switch, or a coupler.
- PA power amplifier
- RF radio frequency
- the routing at 606 involves routing the output of the transmitter path to the receiver path via a coupler in front of an antenna (i.e., between the antenna and the transmitter path) and at least one of multiple power amplifiers, multiple duplexers, or multiple RF switches.
- the transmitter path may include a (baseband) filter, a mixer, and a driver amplifier (DA).
- the transmitter path may also include a digital-to-analog converter (DAC), although the DAC may not be internal to the transceiver IC.
- DAC digital-to-analog converter
- calibrating the RSB of the transmitter path at 606 involves receiving an input to the transmitter path from a DAC, filtering the input to the transmitter path to produce a filtered signal, and mixing the filtered signal with a third oscillating signal as a local oscillating signal for the transmitter path to produce the output of the transmitter path at a radio frequency (e.g., the sum of the local oscillating signal's frequency and the filtered signal's frequency).
- the third oscillating signal may be the same as the second oscillating signal.
- the second and third oscillating signals may be different.
- calibrating the RSB of the transmitter path at 606 entails attenuating the output of the transmitter path to produce an attenuated signal, amplifying the attenuated signal with an LNA, and mixing the amplified signal with the local oscillating signal for the receiver path to produce a baseband frequency at a difference between frequencies of the amplified signal and the local oscillating signal.
- calibrating the RSB of the transmitter path at 606 involves amplifying the output of the transmitter path (e.g., without attenuation) with an LNA and mixing the amplified output with the local oscillating signal for the receiver path to produce a baseband frequency at a difference between frequencies of the amplified output and the local oscillating signal.
- calibrating the RSB of the transmitter path involves calculating phase and gain mismatches for compensating inputs to a DAC associated with the transmitter path.
- the operations 600 may further include disconnecting the first oscillating signal from the at least the portion of the receiver path before calibrating the RSB of the transmitter path.
- the third oscillating signal may be the second oscillating signal (i.e., the second and third oscillating signals are the same signal).
- calibrating the RSB of the receiver path at 604 and calibrating the RSB of the transmitter path at 606 are both performed in the time domain (as opposed to the frequency domain).
- the operations 600 may further include adjusting a gain of a variable gain amplifier (VGA) for amplifying, buffering, or attenuating the first oscillating signal, such that the amplified, buffered, or attenuated signal is used as the input signal to the least the portion of the receiver path.
- VGA variable gain amplifier
- the second oscillating signal is produced by a VCO associated with the transmitter path during normal transceiver operations.
- the first oscillating signal is produced by a tone generating circuit, which may be associated with calibration operations of the transceiver.
- the tone generating circuit may be internal to the transceiver.
- the tone generating circuit may be external to the transceiver (e.g., on a different IC than the transceiver).
- the tone generating circuit includes a multi-stage voltage-controlled oscillator (VCO).
- VCO voltage-controlled oscillator
- the second oscillating signal may be produced by a VCO associated with the transmitter path during normal transceiver operations.
- the tone generating circuit may be a single tone generating circuit.
- the first oscillating signal is produced by the transmitter path and routed to the at least the portion of the receiver path.
- the second oscillating signal may be produced by a tone generating circuit, which may be associated with calibration operations of the transceiver.
- the tone generating circuit may be internal or external to the transceiver.
- FIG. 7 is a flow diagram of example operations 700 for calibrating the LO leakage of a transmitter path, in accordance with certain aspects of the present disclosure.
- the operations 700 may begin, at 702, by routing an output of a transmitter path to a receiver (RX) path.
- the receiver path may be a feedback receiver (FBRX) path, for example, which may be internal to the transceiver.
- the routing involves routing the output of the transmitter path to the receiver path via at least one of a power amplifier (PA), a duplexer, an RF switch, or a coupler.
- PA power amplifier
- duplexer a duplexer
- RF switch RF switch
- the routing at 702 entails routing the output of the transmitter path to the receiver path via a coupler in front of an antenna (i.e., between the antenna and the transmitter path) and at least one of multiple power amplifiers, multiple duplexers, or multiple RF switches.
- a first local oscillating signal may be used for the transmitter path, and at 706, a second local oscillating signal may be used for the receiver path.
- the first local oscillating signal has a first frequency different from a second frequency of the second local oscillating signal.
- the first local oscillating signal is produced by a voltage-controlled oscillator (VCO) associated with the transmitter path during normal transceiver operations.
- the second local oscillating signal is produced by a tone generating circuit associated with calibration operations of the transceiver.
- the tone generating circuit may be internal (or external) to the transceiver.
- the tone generating circuit may be a single tone generating circuit.
- an output of the receiver path is measured as a local oscillator (LO) leakage for the transmitter path.
- measuring the LO leakage occurs in the time domain (as opposed to the frequency domain).
- the operations 700 may further include calibrating the LO leakage of the transmitter path by using the LO leakage measured at the output of the receiver path to compensate inputs to a DAC associated with the transmitter path.
- the operations 700 further include adjusting a direct current (DC) offset of an input to the transmitter path to yield different LO leakages at the output of the receiver path; measuring magnitudes of the different LO leakages; and selecting the adjusted DC offset yielding a minimum LO leakage magnitude for the transceiver.
- the input to the transmitter path includes an input to a DAC associated with the transmitter path.
- the adjusting may involve performing a binary search (or any other suitable search algorithm) based on measuring the magnitudes of the different LO leakages.
- measuring the magnitudes of the different LO leakages entails measuring a magnitude of an in-phase (I) signal output from the receiver path; measuring a magnitude of a quadrature (Q) signal output from the receiver path; and calculating a sum of a square of the magnitude of the I signal and a square of the magnitude of the Q signal.
- measuring the magnitudes of the different LO leakages involves measuring a magnitude of the output of the receiver path at a difference between the first and second frequencies. The difference between the first and second frequencies may be a non-DC baseband tone.
- the operations 700 further include operating the transceiver using the selected DC offset.
- the operations 700 may further include inputting a DC signal to a DAC associated with the transmitter path, at least before measuring the output of the receiver path.
- the operations 700 may further include receiving an input to the transmitter path from a DAC, filtering the input to the transmitter path to produce a filtered signal, and mixing the filtered signal with the first local oscillating signal to produce the output of the transmitter path at a baseband frequency.
- means for transmitting may comprise a transmitter (e.g., the transceiver front end 254 of the user terminal 120 depicted in FIG. 2 or the transceiver front end 222 of the access point 110 shown in FIG.
- a transmitter e.g., the transceiver front end 254 of the user terminal 120 depicted in FIG. 2 or the transceiver front end 222 of the access point 110 shown in FIG.
- Means for receiving may comprise a receiver (e.g., the transceiver front end 254 of the user terminal 120 depicted in FIG. 2 or the transceiver front end 222 of the access point 110 shown in FIG. 2) and/or an antenna (e.g., the antennas 252ma through 252mu of the user terminal 120m portrayed in FIG. 2 or the antennas 224a through 224ap of the access point 110 illustrated in FIG. 2).
- Means for processing or means for determining may comprise a processing system, which may include one or more processors, such as the RX data processor 270, the TX data processor 288, and/or the controller 280 of the user terminal 120 illustrated in FIG. 2.
- determining encompasses a wide variety of actions. For example, “determining” may include calculating, computing, processing, deriving, investigating, looking up (e.g., looking up in a table, a database or another data structure), ascertaining and the like. Also, “determining” may include receiving (e.g., receiving information), accessing (e.g., accessing data in a memory) and the like. Also, “determining” may include resolving, selecting, choosing, establishing and the like.
- a phrase referring to "at least one of a list of items refers to any combination of those items, including single members.
- "at least one of: a, b, or c” is intended to cover: a, b, c, a-b, a-c, b-c, and a-b-c.
- DSP digital signal processor
- ASIC application specific integrated circuit
- FPGA field programmable gate array
- PLD programmable logic device
- a general- purpose processor may be a microprocessor, but in the alternative, the processor may be any commercially available processor, controller, microcontroller, or state machine.
- a processor may also be implemented as a combination of computing devices, e.g., a combination of a DSP and a microprocessor, a plurality of microprocessors, one or more microprocessors in conjunction with a DSP core, or any other such configuration.
- the methods disclosed herein comprise one or more steps or actions for achieving the described method.
- the method steps and/or actions may be interchanged with one another without departing from the scope of the claims.
- the order and/or use of specific steps and/or actions may be modified without departing from the scope of the claims.
- an example hardware configuration may comprise a processing system in a wireless node.
- the processing system may be implemented with a bus architecture.
- the bus may include any number of interconnecting buses and bridges depending on the specific application of the processing system and the overall design constraints.
- the bus may link together various circuits including a processor, machine-readable media, and a bus interface.
- the bus interface may be used to connect a network adapter, among other things, to the processing system via the bus.
- the network adapter may be used to implement the signal processing functions of the PHY layer.
- a user terminal 120 see FIG.
- a user interface e.g., keypad, display, mouse, joystick, etc.
- the bus may also link various other circuits such as timing sources, peripherals, voltage regulators, power management circuits, and the like, which are well known in the art, and therefore, will not be described any further.
- the processing system may be configured as a general-purpose processing system with one or more microprocessors providing the processor functionality and external memory providing at least a portion of the machine-readable media, all linked together with other supporting circuitry through an external bus architecture.
- the processing system may be implemented with an ASIC (Application Specific Integrated Circuit) with the processor, the bus interface, the user interface in the case of an access terminal), supporting circuitry, and at least a portion of the machine-readable media integrated into a single chip, or with one or more FPGAs (Field Programmable Gate Arrays), PLDs (Programmable Logic Devices), controllers, state machines, gated logic, discrete hardware components, or any other suitable circuitry, or any combination of circuits that can perform the various functionality described throughout this disclosure.
- FPGAs Field Programmable Gate Arrays
- PLDs Programmable Logic Devices
- controllers state machines, gated logic, discrete hardware components, or any other suitable circuitry, or any combination of circuits that can perform the various functionality described throughout this disclosure.
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Abstract
Description
Claims
Priority Applications (4)
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CN201480058956.5A CN105850063A (en) | 2013-10-29 | 2014-10-10 | Transmitter (tx) residual sideband (rsb) and local oscillator (lo) leakage calibration using a reconfigurable tone generator (tg) and lo paths |
KR1020167014010A KR20160078425A (en) | 2013-10-29 | 2014-10-10 | Transmitter (tx) residual sideband (rsb) and local oscillator (lo) leakage calibration using a reconfigurable tone generator (tg) and lo paths |
EP14795701.3A EP3063888A1 (en) | 2013-10-29 | 2014-10-10 | Transmitter (tx) residual sideband (rsb) and local oscillator (lo) leakage calibration using a reconfigurable tone generator (tg) and lo paths |
JP2016524448A JP2016541152A (en) | 2013-10-29 | 2014-10-10 | Transmitter (TX) residual sideband (RSB) and LO leakage calibration using reconfigurable tone generator (TG) and local oscillator (LO) paths |
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US20150118980A1 (en) | 2015-04-30 |
KR20160078425A (en) | 2016-07-04 |
CN105850063A (en) | 2016-08-10 |
EP3063888A1 (en) | 2016-09-07 |
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