WO2015006676A1 - Alignement d'antennes à faisceaux jumelés à large bande - Google Patents

Alignement d'antennes à faisceaux jumelés à large bande Download PDF

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Publication number
WO2015006676A1
WO2015006676A1 PCT/US2014/046325 US2014046325W WO2015006676A1 WO 2015006676 A1 WO2015006676 A1 WO 2015006676A1 US 2014046325 W US2014046325 W US 2014046325W WO 2015006676 A1 WO2015006676 A1 WO 2015006676A1
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WIPO (PCT)
Prior art keywords
array
output
radiating elements
wideband
hybrid
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PCT/US2014/046325
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English (en)
Inventor
Igor E. Timofeev
Gang Yi PENG
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Andrew Llc
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Publication of WO2015006676A1 publication Critical patent/WO2015006676A1/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/246—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for base stations
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/22—Antenna units of the array energised non-uniformly in amplitude or phase, e.g. tapered array or binomial array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/22—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the orientation in accordance with variation of frequency of radiated wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/50—Feeding or matching arrangements for broad-band or multi-band operation

Definitions

  • the present invention generally relates to radio communication. More particularly, the invention relates to wideband multi-beam antennas for cellular communication systems.
  • each antenna For common cellular applications where a given site has three sectors, each serviced by one antenna, each antenna usually has 65 degree azimuth Half Power Beam width (HPBW). Six sector cells may be employed at such sites to increase system capacity. Antennas with 33 degree and 45 degree HPBW are the most common for 6 sector applications. However, replacing three antennas with six antennas (each of which is 2 times wider than a common 65 degree antenna) is not a compact and low cost solution.
  • HPBW Half Power Beam width
  • Dual-beam may be used to reduce number of antennas on the tower.
  • One key aspect of a multi-beam antenna is the beam forming network (BFN).
  • BFN beam forming network
  • An example of a known dual-beam antenna from prior art may be found in Encyclopedia for RF and Microwave engineering, 2005 John Wiley and Sons, pp.335 - 339.
  • a two beam by two column (2X2) BFN is used in the known dual beam antenna.
  • the main drawback of this prior art antenna is high levels of side and backlobes (about -lOdB), which is not acceptable for modern systems due high interference.
  • Another drawback is poor coverage: more than 50% of radiated power is wasted out of the desired two 60 degree sectors.
  • a Frequency Dependent Divider is included in the beam forming network for wideband beam forming and creation of frequency reconfigurable antennas.
  • the FDD integrated in the beam forming network, provides for changes in amplitude distribution on array elements with respect to frequency.
  • the FDD may be configured to change the power ratio on its outputs with respect to frequency. For example, for lowest frequency, all power goes to port 1, for highest frequency all power goes to port 2, and for central frequency power is about equal for both ports of FDD.
  • a new compact frequency-dependent divider is proposed, comprising 3dB divider, 90 degree hybrid and delay line between them. But other schemes of FDD (for example, filters) may be used.
  • a wideband antenna includes a plurality of radiating elements arranged in an array and a feed network.
  • the feed network has at least one input and a plurality of outputs coupled to the plurality of radiating elements.
  • the feed network further includes at least one frequency dependent power divider for varying the amplitude of a signal provided to at least two of the plurality of radiating elements as a function of a frequency of a signal.
  • the feed network increasingly tapers a power distribution to radiating elements at each end of the wideband array as a function of increasing frequency.
  • the feed network further comprises a plurality of inputs and the antenna produces a plurality of beams.
  • the feed network may further include a 90° hybrid having two inputs and the antenna produces two beams.
  • the frequency dependent divider may comprise a power divider having a first output and a second output, a 90° hybrid, having a first input coupled to the first output of the power divider, and a second input, and a delay line, coupled between the second output of the power divider and the second input of the 90° hybrid.
  • the delay line may be a regular transmission line, a regular transmission line combined with a Shiffman phase shifter, a transmission line incorporating a series inductances and parallel capacitors, or other suitable structure.
  • a dual beam wideband array includes at least first, second and third radiating elements, the first, second and third radiating elements.
  • a 90° hybrid having a first beam input and a second beam input is included.
  • the 90° hybrid has a first output and a second output, the second output being coupled to the first radiating element.
  • the array further includes a first frequency dependent power divider having an input coupled to the first output of the first 90° hybrid and a first output coupled to the second radiating element and a second output coupled to the third radiating element.
  • the second output of the frequency dependent power divider is coupled to the third radiating element.
  • the dual beam wideband array consists of three radiating elements, and the second and third radiating elements are at opposite ends of the array.
  • the dual beam wideband array consists of four radiating elements, and the second and third radiating elements are at one end of the array.
  • the dual beam wideband array further includes a second frequency-dependent divider and a power divider coupling the first output of the 90° hybrid to the respective inputs of the first and second frequency dependent dividers, and the array further comprises a fourth radiating element and a fifth radiating element.
  • the second frequency dependent divider is coupled to fourth and fifth radiating elements.
  • Fig. 1 A is schematic diagram of a wideband beam forming network and array according to one aspect of the present invention.
  • Fig. IB illustrates a simulated radiation pattern of one beam produced by the beam forming network and array of Fig. 1A.
  • Fig. 2A is schematic diagram of another example of a beam forming network and array according to another aspect of the present invention.
  • Fig. 2B illustrates a simulated radiation pattern one beam produced by the network illustrated in Fig. 2A.
  • Fig. 3 A is schematic diagram of another example of a beam forming network and array according to another aspect of the present invention.
  • Fig. 3B illustrates a simulated radiation pattern of one beam produced by the beam forming network and array illustrated in Fig. 3A.
  • Fig. 3C illustrates simulated radiation patterns for two beams produced by the beam forming network and array illustrated in Fig. 3 A.
  • Fig. 4A illustrates a first example of a delay line according to one aspect of the present invention.
  • Fig. 4B illustrates a second example of a delay line according to one aspect of the present invention.
  • Fig. 4C illustrates a third example of a delay line according to one aspect of the present invention.
  • Fig.5 A illustrates a first example of how beam forming networks according to the present invention and having different numbers of radiating elements may be combined in an antenna array.
  • Fig.5B illustrates a second example of how beam forming networks according to the present invention and having different numbers of radiating elements may be combined in an antenna array.
  • Fig.5C illustrates a third example of how beam forming networks according to the present invention and having different numbers of radiating elements may be combined in an antenna array.
  • Fig.5D illustrates a fourth example of how beam forming networks according to the present invention and having different numbers of radiating elements may be combined in an antenna array.
  • Fig. 1 A shows schematic diagram of beam forming network 10 and an array 50 of three radiating elements 51, 52 and 53.
  • This example accepts two inputs, Beam 1 and Beam 2, and produces two beams.
  • the beam forming network 10 comprises a 90° hybrid 12, a frequency dependent divider 20, and a 180° phase shifter 14. Inputs Beam 1 and Beam 2 are input to 90° hybrid 12.
  • a first output of hybrid 12 is coupled to the frequency dependent divider 20.
  • a second output of hybrid 12 is coupled to a middle radiating element 52 of the array 50.
  • Hybrid 12 may comprise a commercially available wideband 90° hybrids, for example Anaren X3C17-03WS-CT, which as a bandwith of 690 - 2700MHz, with almost constant 90° shift over all frequency band.
  • the 3dB power dividers, 16, 22 may be a multi-section Wilkinson dividers.
  • the frequency dependent divider 20 comprises a power divider 22, a delay line 24, and a 90° hybrid 26.
  • the power divider 22 splits the signal from the first output of hybrid 12 into two signals. In this example, the power division of power divider 22 is equal.
  • a first output of the power divider 22 is coupled to a first input of hybrid 26.
  • a second output of the power divider 22 is coupled to the delay line 24.
  • the output of delay line 24 is coupled to a second input of hybrid 26.
  • a first output of the frequency dependent divider 20 is coupled to radiating element 51.
  • radiating element 51 is the first element in the array 50.
  • the second output of the frequency dependent divider 20 is coupled to the third element of the array 50, radiating element 53, via 180° phase shifter 14. While 180° phase shifter 14 may be implemented as a discrete component, 180° phase shifter 14 may also be implemented by using a dipole radiator for the radiating element, and alternating the feedpoint relative to the other dipole elements.
  • the delay line 24 imposes a phase delay to a signal which coupled to the second input of hybrid 26.
  • the delay line is a fixed length, the phase delay experienced by a signal varies with frequency. That is, for a given fixed time delay, higher-frequency signals experience more phase delay than low frequency signals.
  • Hybrid 26, therefore, receives equal amplitude signals, where the signals to one input experience increasing phase delay with increasing frequency.
  • Hybrid 26 outputs equal phase, variable amplitude signals, where the amount of amplitude difference increases with increasing frequency.
  • amplitude ratio between outputs of the frequency dependent divider 20 (and the first and third radiating elements, 51, 52, of array 50) may be written as:
  • Al/A3 [(1 - sintp) /(l+sincp)] 1 ⁇ 2
  • P1/P3 lOlog [(1 - sincp) /(l+sincp)] [dB], where ⁇ is electrical length of delay line.
  • ⁇ 0° or 180°, both elements have the same amplitude.
  • ⁇ 90° or 270°, one element has 0 amplitude, and another one amplitude 1.
  • the frequency dependent divider 20 is placed between radiating elements 51 and 53.
  • the delay line is selected to be a regular transmission line with an electrical length of 180° for 1.7GHz.
  • beam forming network 10 provides a power distribution at radiating elements 51, 52 and 53, respectively, of 0.7, 1, and 0.7 at 1.7 GHz, 0.36, 1 and 0.88 at 2.2 GHz, and 0.14, 1 and 0.98 at 2.7 GHz.
  • Beam forming network 10 also provides 90° phase differences between radiating elements to create two beams.
  • Fig. IB results of a simulation of radiating patterns for one beam at three frequencies are shown. Spacing between elements for this example is selected at 80mm and 60mm. As one can see from Fig. IB, HPBW is stabilized to 41+/-3 0 in this example.
  • FIG. 2A illustrates a schematic diagram of another example of the present invention.
  • Beam forming network 30 produces two beams via array 60 comprising radiating elements 61-64.
  • Beam Forming Network 30 comprises a 90° hybrid 12a, or power divider 16, a frequency dependent divider 20, and 180° phase shifter 14.
  • Hybrid 12a may comprise a non-equal 90° hybrid 1 (-3.8dB, -2.4dB) for improved sidelobe suppression.
  • Beam 1 and Beam 2 signals are input to hybrid 12a.
  • a first output of hybrid 12a is coupled to power divider 16.
  • a second output of hybrid 12a is coupled to radiating element 63 (the third radiating element of array 60).
  • a first output of power divider 16 is coupled to frequency dependent divider 20.
  • the first and second outputs of frequency dependent divider 20 are coupled to radiating elements 6 land 62 of array 60, respectively (the first and second elements of array 60).
  • a second output of power divider 16 is coupled to 180° phase shifter 14, which is in turn coupled to radiating element 64.
  • the power tapering is frequency dependent for radiating elements 61 and 62, and not frequency dependent for radiating elements 63 and 64.
  • Amplitude and phase distribution is shown in Fig. 2A (above the radiating elements).
  • the amplitude distribution at 1.7 GHz is 0.6, 0, 1, and 0.6 at radiating elements 61, 62, 63 and 64, respectively.
  • the amplitude distribution at 2.2 GHz is 0.45, 0.42, 1 and 0.6
  • the amplitude distribution at 2.7 GHz is 0, 0.6, 1 and 0.6.
  • elements 1, 3, 4 are radiating, at 2.2GHz all four elements are radiating, and at 2.7GHz, elements 2, 3, 4 are radiating. That is, beam forming network 30, by reducing amplitude effectively to zero for some radiating elements at certain frequencies, effectively reconfigures Array 60 on a frequency- dependent basis. This feature of frequency re-configurability allows to stabilize beam width and beam position for both beams.
  • Calculated radiation patterns are shown in Fig. 2B for 1.7, 2.2, 2.7 GHz (for one beam). As one can see from Fig. 2B, not only is HPBW is stabilized (36+/-4 0 ), but also beam position is stabilized (21.5+/-1.5).
  • all radiating elements of the Array 60 may be continue to be driven, but at different amplitudes at different frequencies.
  • central and periphery elements have almost the same amplitude (for example, 0.75; 1; 1; 0.75).
  • periphery elements have much lower amplitude (for example, 0.2; 1; 1; 0.2).
  • Fig. 3 A illustrates a schematic diagram of another example of the present invention.
  • Beam forming network 40 produces two beams via array 70 comprising radiating elements 71- 75.
  • Beam forming network 40 comprises a 90° hybrid 12a, a power divider 16, two frequency dependent dividers 20, and two 180° phase shifters 14.
  • Beam 1 and Beam 2 signals are input to hybrid 12a.
  • a first output of hybrid 12a is coupled to power divider 16.
  • a second output of hybrid 12a is coupled to radiating element 73 (the third radiating element of array 70).
  • a first output of power divider 16 is coupled to a first frequency dependent divider 20.
  • a second output of power divider 16 is coupled to a second frequency dependent divider 20.
  • the first and second outputs of the first frequency dependent divider 20 are coupled to radiating elements 71 and 72 of array 70, respectively (the first and second elements of array 60).
  • the first and second outputs of the second frequency dependent divider 20 are coupled to radiating elements 74 and 75 of array 70, respectively (the fourth and fifth elements of array 70).
  • Hybrid 12a may comprise a non-equal 90° hybrid 12a (-3.8dB, -2.4dB) for improved sidelobe suppression ( ⁇ -16dB in this example).
  • Amplitude and phase distribution is shown in Fig. 3A (above the radiating elements), and calculated patterns are shown in Fig. 3B for 1.7, 2.2 and 2.7GHz (for one beam) and in Fig.3C (for both beams).
  • the amplitude distribution is 0.55, 0.25, 1, 0.25, and 0.55 for radiating elements 71, 72, 73, 74, 75, respectively.
  • the amplitude distribution at 2.2 GHz is 0.36, 0.45, 1, 0.45 and 0.36
  • the amplitude distribution at 2.7 GHz is 0, 0.6, 1, 0.6 and 0.
  • radiating elements 71, 73, and 75 are handling the most radio frequency energy.
  • radiating elements 72, 73, 74 are handling the most radio frequency energy.
  • radiating elements 72, 73 and 75 are handling all of the radio frequency energy, and radiating elements 71 and 75 are not radiating. Accordingly, this is another example of a frequency reconfigurable antenna. By selectively using different radiating elements at different frequencies, the effective aperature of array 70 is changing proportional to wavelength for both beams, providing almost constant HPBW and beam position angle.
  • Fig. 3 A is more complicated relative to the examples of Fig.1 A and Fig.2A, but constant HPBW over wide (50%) bandwidth, constant beam position and low sidelobe level constitutes an improvement over the prior art.
  • HPBW and beam position are very stable: 34+/-2 0 and 21+/- ⁇ , respectively.
  • beam forming networks were shown for 1.7 - 2.7 GHz, but the invention is not limited to this frequency band and may be implemented using any other frequencies.
  • Fig. 4A, 4B and 4C illustrate three different variations of delay lines.
  • Fig.4A illustrates a regular transmission line, where phase delay is directly proportional to frequency.
  • Fig. 4B illustrates a delay line comprising a regular transmission line combined with a Shiftman phase shifter. Because a Shiffman phase shifter provides constant phase over frequency band, phase for this delay line will change more slowly with frequency compared to a regular transmission line as illustrated in Fig. 4A.
  • Fig. 4C shows a loaded line, where narrow sections (series inductances) are combined with wide sections (parallel capacitances), providing 15 - 30% "faster” phase change compare to regular line.
  • Wideband 180° phase shifter 14 may be easy realized with dipole radiator, by alternating feedpoint (for 0°, central conductor of feed line is connected to 1 st dipole arm, for 180°, it is connected to 2 nd dipole arm).
  • This solution provides constant 180° phase shift over whole frequency band without having to add a discrete phase shifter component.
  • a combination of 3, 4 and 5 element linear arrays as described in Fig. 1 A, 2A, 3 A may be implemented. Such combinations may be advantageously used to reduce azimuth sidelobe level.
  • Figures 5A and 5B illustrate alternating five element arrays 70 and four element arrays 60.
  • Figures 5C and 5D illustrate alternating pairs of five element arrays 70 and four element arrays 60.
  • horizontal spacing between elements can also be different. Examples shown in Fig. 5 are related to antennas with +/-45 degree dual polarization (most common in base station antenna technology), but of course the same solutions can be applied to antennas with any single or dual polarization.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

L'invention concerne une antenne à large bande comprenant une pluralité d'éléments rayonnants (51-53) disposés dans un alignement (50) et un réseau (10) d'alimentation. Le réseau d'alimentation comprend au moins un répartiteur (20) de puissance dépendant de la fréquence servant à faire varier l'amplitude d'un signal transmis à au moins deux éléments de la pluralité d'éléments rayonnants en fonction de la fréquence d'un signal. Le réseau d'alimentation peut comporter en outre une pluralité d'entrées et l'antenne peut produire une pluralité de faisceaux. Le répartiteur dépendant de la fréquence peut comporter un répartiteur de puissance doté d'une première sortie et d'une deuxième sortie, un hybride à 90°, doté d'une première entrée couplée à la première sortie du répartiteur de puissance et d'une deuxième entrée, et une ligne à retard, couplée entre la deuxième sortie du répartiteur de puissance et la deuxième entrée de l'hybride à 90°.
PCT/US2014/046325 2013-07-12 2014-07-11 Alignement d'antennes à faisceaux jumelés à large bande WO2015006676A1 (fr)

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CN109119765A (zh) * 2017-06-22 2019-01-01 康普技术有限责任公司 含带增强半功率波束宽度控制的天线阵列的蜂窝通信系统
CN109449590A (zh) * 2018-12-20 2019-03-08 东莞市云通通讯科技有限公司 双波束基站天线
WO2019217906A1 (fr) 2018-05-11 2019-11-14 Quintel Cayman Limited Système d'antenne cellulaire multibande
KR20200084035A (ko) * 2017-11-16 2020-07-09 위틀레이 코퍼레이션 프로프라이어테리 리미티트 생물막의 제거 방법
WO2020258029A1 (fr) * 2019-06-25 2020-12-30 Commscope Technologies Llc Antennes de station de base multifaisceaux ayant des éléments rayonnants à large bande
CN112640215A (zh) * 2018-08-24 2021-04-09 康普技术有限责任公司 用于方位波束宽度稳定的具有交错竖直阵列的带透镜基站天线
WO2022166018A1 (fr) * 2021-02-02 2022-08-11 罗森伯格技术有限公司 Antenne de formation de deux faisceaux, et antenne hybride comprenant celle-ci

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Cited By (15)

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Publication number Priority date Publication date Assignee Title
CN109119765A (zh) * 2017-06-22 2019-01-01 康普技术有限责任公司 含带增强半功率波束宽度控制的天线阵列的蜂窝通信系统
KR102392343B1 (ko) 2017-11-16 2022-04-29 위틀레이 코퍼레이션 프로프라이어테리 리미티트 생물막의 제거 방법
KR20200084035A (ko) * 2017-11-16 2020-07-09 위틀레이 코퍼레이션 프로프라이어테리 리미티트 생물막의 제거 방법
EP3791442A4 (fr) * 2018-05-11 2022-02-09 Quintel Cayman Limited Système d'antenne cellulaire multibande
WO2019217906A1 (fr) 2018-05-11 2019-11-14 Quintel Cayman Limited Système d'antenne cellulaire multibande
CN112640215B (zh) * 2018-08-24 2022-09-23 康普技术有限责任公司 用于方位波束宽度稳定的具有交错竖直阵列的带透镜基站天线
CN112640215A (zh) * 2018-08-24 2021-04-09 康普技术有限责任公司 用于方位波束宽度稳定的具有交错竖直阵列的带透镜基站天线
CN109449590A (zh) * 2018-12-20 2019-03-08 东莞市云通通讯科技有限公司 双波束基站天线
US11019506B2 (en) 2019-06-25 2021-05-25 Commscope Technologies Llc Multi-beam base station antennas having wideband radiating elements
CN112437998A (zh) * 2019-06-25 2021-03-02 康普技术有限责任公司 具有宽带辐射元件的多波束基站天线
WO2020258029A1 (fr) * 2019-06-25 2020-12-30 Commscope Technologies Llc Antennes de station de base multifaisceaux ayant des éléments rayonnants à large bande
US11595827B2 (en) 2019-06-25 2023-02-28 Commscope Technologies Llc Multi-beam base station antennas having wideband radiating elements
CN112437998B (zh) * 2019-06-25 2023-07-18 康普技术有限责任公司 具有宽带辐射元件的多波束基站天线
US11917427B2 (en) 2019-06-25 2024-02-27 Commscope Technologies Llc Multi-beam base station antennas having wideband radiating elements
WO2022166018A1 (fr) * 2021-02-02 2022-08-11 罗森伯格技术有限公司 Antenne de formation de deux faisceaux, et antenne hybride comprenant celle-ci

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