WO2013160462A1 - Convertisseur de commande servant à faire fonctionner au moins une led - Google Patents

Convertisseur de commande servant à faire fonctionner au moins une led Download PDF

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Publication number
WO2013160462A1
WO2013160462A1 PCT/EP2013/058776 EP2013058776W WO2013160462A1 WO 2013160462 A1 WO2013160462 A1 WO 2013160462A1 EP 2013058776 W EP2013058776 W EP 2013058776W WO 2013160462 A1 WO2013160462 A1 WO 2013160462A1
Authority
WO
WIPO (PCT)
Prior art keywords
input
switching converter
output
voltage
converter
Prior art date
Application number
PCT/EP2013/058776
Other languages
German (de)
English (en)
Inventor
Richard Dilger
Markus Heckmann
Arnulf Rupp
Markus NORDHAUSEN
Original Assignee
Osram Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Osram Gmbh filed Critical Osram Gmbh
Publication of WO2013160462A1 publication Critical patent/WO2013160462A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/38—Switched mode power supply [SMPS] using boost topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/355—Power factor correction [PFC]; Reactive power compensation
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/375—Switched mode power supply [SMPS] using buck topology
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a switching converter according to the preamble of patent claim 1.
  • a sinusoidal alternating clamping ⁇ voltage having an effective value of 230 V
  • current and voltage transformations necessary to provide a current having a constant current intensity as possible comprising two voltage transformers, wherein the first voltage converter, in particular an up ⁇ converter , and the second voltage converter are coupled together via a DC circuit capacitor.
  • a rectifier is connected in front of the first voltage converter.
  • the first voltage converter is usually designed as a power factor correction circuit which synchronizes the input current and the input voltage, since in particular for powers of 25 W predetermined directives with regard to the mains current harmonics are to be fulfilled.
  • the power coupled into the second voltage converter via the intermediate circuit capacitor is almost constant over its course over time.
  • an electrolytic capacitor is preferably used with the largest possible capacity to the best possible Smoothing the voltage and the power to allow.
  • the second voltage converter converts the voltage such that the oppel ⁇ th to the output of the voltage converter LEDs may be supplied with a current as constant as possible current intensity.
  • the second voltage ⁇ converter is generally constructed as a buck converter, as for driving a LED usually only a small voltage is required.
  • the object of the present invention is to provide a switching converter for operating at least one LED, which has a longer service life. This object is achieved by a switching converter having the features of patent claim 1.
  • the switching converter according to the invention for operating at least one LED comprises an input having a first and a second input terminal for coupling to an AC voltage source, an output having a first and a second output terminal for coupling to the at least one LED, wherein an output variable can be provided at the output, and a rectifier having an input coupled to the input of the switching converter and an output.
  • the switching converter comprising a ⁇ matterssreaktanznetztechnik having an input coupled to the output of the rectifier and an output, wherein the mattersreaktanznetztechnik comprises at least a first controllable electronic switch.
  • the switching converter has a capacitive energy store, which is coupled to the output of the input reactance network, and at least one first electronic control circuit, by means of which the switching converter can be regulated at its input to a desired value of the input current.
  • the at least ei ⁇ ne first control circuit is designed such that the switching converter is controllable at its input to a desired value of the input current, wherein the desired value in its time course spectral components at a fundamental frequency of a fundamental with a fundamental amplitude and at least one frequency at least one Harmonic with a predetermined amplitude, the at least one frequency is an integer multiple of the fundamental frequency.
  • Such a design of at least one ers ⁇ th control circuit it is possible to input current harmoniously distorting.
  • the amplitudes of the harmonics can be specified.
  • the amplitudes are preferably predetermined in such a way that a power which is fed from the input reactance network into the capacitive energy store is maximally uniform over its time course. Due to the harmonic distortion of the power less energy must be stored by the capacitive energy storage over half a period based on the period of the fundamental frequency. This makes it possible to design the capacitive energy storage with a smaller capacity than with an undistorted power input.
  • harmonics with the 3 frequency of the fundamental frequency can be a power that is fed from the input reactance network in the capacitive energy storage, which is so harmonic distorted that their time course is maximally uniform, ie that the deviation power versus time average power and time average power versus power factor corrected power proportional to the square of a sine wave, as is common in the art.
  • the amplitudes of the harmonics with frequencies up to 49 times the fundamental frequency can be specified.
  • the input voltage is a sinusoidal AC voltage having a frequency
  • the first control circuit is adapted to regulate the switching converter at its input to a desired value of the input current, wherein the desired value in its time course has a fundamental with the same frequency as that of the input voltage
  • the first control circuit is adapted to control the switching ⁇ converter at its input to a desired value of the input current, wherein the desired value in its time ⁇ course has a fundamental oscillation, which has no phase shift relative to the input voltage.
  • the harmonics of the input current may have any phase shift from the fundamental.
  • the control circuit can also be designed to open the switching converter To control an input current having harmonics with a predetermined phase shift from the fundamental.
  • the phase shifts can be defined as the process that the network delivered by flexibilttanz- power is more evenly in its course over time, especially so that the capaci ⁇ ty of the capacitive energy storage can be further reduced.
  • the predeterminable amplitude of the at least one harmonic is less than or equal to the amplitude predetermined by a distortion standard for a power take-off. Since more stringent specifications with respect to the harmonic distortion, in particular with respect to the amplitudes of harmonics of the input current, are generally available from a power extraction from the power supply starting from about 25 W., it is provided to select the predefinable amplitudes still in the range of the permissible amplitudes, and preferably as close as possible at the maximum permissible amplitudes.
  • the switching converter may have a Popereaktanznetzwerk having an input coupled to the capacitive energy storage device, and an output for coupling to the at least one LED, wherein the off ⁇ gangsreaktanznetztechnik comprises at least one second êtba- ren electronic switch.
  • the switching converter preferably comprises at least one second control circuit , by means of which the switching converter can be regulated to an output variable.
  • the switching converter can advantageously by means of the second control circuit to a desired output chip tion or a desired output current.
  • the output is an output current, since the operation of LEDs as smooth as possible direct current is advantageous.
  • the at least one second control circuit is designed to regulate the switching converter to an output variable as a function of an instantaneous value of a tapped off across the capacitive energy storage voltage. Since by the use of a capacitive energy store and a smaller capacity can be tapped at the capacitive energy storage voltage having a greater undulation, it is advantageous to form the second control circuit such that output variable in the regulation to an off ⁇ , in particular an output current of the zeitli ⁇ che history is taken into account at the capacitive energy storage voltage and not just their time average. Such a configuration of the second control circuit makes it possible to control, in spite of large ripples, the voltage applied to the output reactance network to an output current which is almost constant over time.
  • the input reactance network can be designed as an up-converter.
  • the out ⁇ gangsreaktanznetztechnik can be configured as buck converter.
  • the capacitive energy storage is a ceramic capacitor or a foil capacitor.
  • Ceramic capacitors and lien capacitors have a relatively high Le ⁇ service life and are further formed for a large wavy ⁇ ness of the applied voltage, while Elect ⁇ rolytkondensatoren are not designed for such a large ripple.
  • the capacitance of the ceramic capacitor or of the film capacitor is dimensioned such that a tapped off on the ceramic capacitor or film capacitor voltage has aponswel- lotti, which is greater than 30% of the maximum value of the voltage applied to the input of the switching converter input ⁇ voltage.
  • the same energy can be stored by increasing the intermediate circuit voltage, in particular by the greater ripple of the voltage across the capacitor, and with a ceramic or film capacitor smaller capacity, as with an electrolytic capacitor large capacity and small DC link voltage.
  • the ripple of the voltage provided by the capacitor to the Jardinreaktanznetztechnik be greater than 100 volts, in particular greater than 200 volts.
  • the ripple of the voltage in the prior art is about 60 V, since a Elektrolytkondensa ⁇ tor tolerated no greater ripple voltage where ⁇ is required by a larger capacity.
  • the capacity of the Ke ⁇ ramikkondensators or film capacitor sized is that the instantaneous value of the tapped off at the ceramic capacitor or film capacitor voltage is greater than the instantaneous value of the anlie ⁇ ing voltage at the input of the switching converter.
  • Fig. 1 is a schematic representation of a switching wall lers according to an embodiment of the inven ⁇ tion;
  • Fig. 2 is a schematic diagram of a Messdia gram of the tapable capacitor capacitor voltage and the output current provided at the output of the switching converter according to an embodiment of the invention
  • Fig. 3 is a graphical representation of one of
  • Input reactance network to a capacitor delivered power without harmonic distortion a graphical representation of a harmonic distortion input current according to an embodiment of the invention; a graphical representation of the input ⁇ reactance network according to the current strength of Figure 4a harmonically distorted, output power according to an embodiment of the invention; a graphical representation of another harmonic distortion input current according to an embodiment of the invention; and a graphical representation of the input ⁇ reactance network according to the current from FIG. 5a harmonically distorted, output power according to an embodiment of the invention.
  • Fig. 1 shows a schematic representation of a switching converter 10 according to an embodiment of OF INVENTION ⁇ dung.
  • This comprises an input reactance network 12, which is coupled to a Popereaktanznetzwerk 13 via a capacitive energy storage Cl.
  • a sinusoidal alternating voltage can be present at the input E1, E2 of the switching converter 10, in particular with 230 V rms voltage, which is rectified by a rectifier 11.
  • the output reactance network 13 can be used as a downward converter, in particular as a buck converter, be designed so that a suitable for the operation of at least one LED output voltage U A at the output AI, A2 of the switching converter is provided.
  • the The The inventorsreaktanz- network 12 may be formed as a boost converter, in particular as a boost converter, whereby the voltage can be set high, so that the tapped on the capacitive energy storage Cl voltage U K is greater than the voltage applied to the input E1, E2 input voltage U E. Further toward the capacitive energy storage Cl such that the periodically varying in time, from the input ⁇ reactance 12 extracted power P (t) by energy in the capacitive energy storage gie appointedung Cl as constant as possible over time in the output power Po reactance 13 is coupled in , Furthermore, the switching converter 10 may comprise an electronic control circuit, by means of which the switching converter 10 can be regulated to a desired value of the input current I E (t).
  • the input current I E (t) is adjustable so that it has a fundamental of the same frequency as the input voltage U E and harmonics with integer multiples, in particular odd multiples, this frequency and vorgebba - has amplitude. Due to this harmonic Verzer ⁇ tion of the input current I E (t) and thus also the inputs 12 gansreaktanznetzwerk the removable power P (t), the deviation of the power P (t) from the temporal average power Po in the amount in the time average reduc- are compared with a power P (t), which is proportional to the square of a sine wave.
  • this embodiment of the invention can werk Congressigt that less energy E during half a period T / 2 with respect to the period T of Grundschwindung must be stored by the capacitive energy storage Cl and the capacitive Energyspei- rather Cl can be configured with a much smaller capacity.
  • a ceramic capacitor or film capacitor with a smaller capacitance C than is customary in the prior art can be used as the capacitive energy store C1, which show a large number of advantages over the electrolytic capacitors commonly used.
  • ceramic and film capacitors for a much larger chip ripple is AU are designed, which provides the ability to ⁇ , by increasing the intermediate circuit voltage, the Ka capacity to reduce the ceramic capacitor or film capacitor on.
  • a ceramic capacitor or film capacitor has a much longer life than an electrolytic capacitor, which increases the life and reliability of the entire switching converter 10, since the capacitive Energy storage Cl is the life-determining element.
  • the capacitive voltage U K provided by the capacitive energy storage Cl to the Ricoreaktanznetztechnik 13 has a correspondingly greater voltage ripple AU. Accordingly ⁇ speaking the Ricoreaktanznetztechnik 13 is to be ⁇ forms, such voltage ripple AU Sieren to compensate.
  • a second control circuit may be provided which provides a nearly constant output current I A at the output AI, A2 of the circuit arrangement 10, for example, the output reactance network may comprise an active switch, in particular a controllable electronic switch.
  • the first and second control scarf ⁇ tion may also be formed as a single control circuit, in particular, it may be formed such that two different and independent control tasks can be solved by this one control circuit.
  • the input and Cosmeticreaktanznetztechnik 12 is form 13 together as a Cuk converter, in particular, the control can to an input current ⁇ E (t) and an output current I A of the switching converter 10 by driving only one controllable electronic switch take place by means of the drive circuit 14.
  • a further very advantageous possibility is the control of the switching ⁇ converter 10 to an input current ⁇ E (t) and to realize ter an off ⁇ output current I A by two controllable electronic scarf, wherein preferably the input and Volunteerreaktanznetztechnik 12, 13 one active each Include switch. These two switches can also be controlled by the drive circuit 14.
  • the triggering of the second switch can be effected as a function of the voltage U K which can be tapped on the capacitive energy store C1, not only as a function of the time average of this voltage U K , as is usual in the prior art, but also taking into account the time profile of the voltage U K , that is to say as a function of an instantaneous value of the voltage U K which can be tapped off at the capacitive energy store C1.
  • the triggering of the second switch can be effected as a function of the voltage U K which can be tapped on the capacitive energy store C1, not only as a function of the time average of this voltage U K , as is usual in the prior art, but also taking into account the time profile of the voltage U K , that is to say as a function of an instantaneous value of the voltage U K which can be tapped off at the capacitive energy store C1.
  • the boost converter can be provided as a further embodiment variant to design the boost converter as a power factor correction circuit, in particular in such a way that a distortion standard with respect to the system current drain is maintained.
  • the efficiency of such a switching converter 10 at min ⁇ least 80% -86% is, in particular, what corresponds to ei ⁇ ner usual in the art efficiency. This is remarkable insofar as, in spite of the larger voltage ripple AU, no significant losses occur due to additional loading of the circuit components, in particular of semiconductor elements.
  • FIG. 2 shows a measurement diagram of the time profile of the capacitor voltage U K provided by the capacitive energy store C 1 and of the output current I A provided by the output reactance network 13 Switching converter 10 shown according to an embodiment of the invention. Furthermore, in FIG.
  • the rectified AC voltage U G present at the input of the input reactance network 12, which is designed as a boost converter, in particular as a power factor correction circuit, is shown in its time profile.
  • the input voltage U E present at the input E1, E2 of the switching converter 10 has a frequency of 50 Hz.
  • the capacitor voltage U K of the capacitive energy store C1 has a very large voltage ripple AU of approximately 300 V, which is is more than 90% of the maximum value of the input voltage U E applied to the input E1, E2. This is made possible only by the use of a ceramic capacitor or film capacitor as a DC link capacitor, since the electrolytic capacitors commonly used are not designed for such a large voltage ripple.
  • the output current I A of the switching converter 10 is shown in its time course.
  • the large voltage ripple AU compensate relatively well, so that the output current I A has only a small current ripple ⁇ of about 40 mA, which corresponds approximately to 10% of the maximum value of the output current I A.
  • the formed Re ⁇ gelscados to the output current I A in consideration of the time instantaneous value of the tapped at the capacitor capacitor voltage U K to control, thereby making it possible to provide a relatively constant th output current I A, for example, for Operate LEDs to provide.
  • FIG 3 shows a graphical representation of a power P (t) delivered without harmonic distortion by an input reactance network 12.
  • the average power to be coupled into the output reactance network 13 is P o
  • an energy E must be stored by the capacitive energy store C 1 over a half oscillation period T / 2, which energy can be stored in the hatched areas in FIG 3 corresponds.
  • Fig. 4a shows a graphic representation of har ⁇ cally distorted input current I E (t).
  • the associated harmonic distorted power P (t) is shown in Fig. 4b Darge ⁇ represents.
  • the average power to be coupled into the output reactance network 13 is Po 25 W for a sinusoidal alternating voltage with an effective value of 230V as the input voltage U E.
  • the energy E to be stored by the capacitive energy store C1 is in turn represented by the hatched areas. Due to the harmonic distortion, these surfaces, ie the energy E to be stored by the capacitive energy store Cl, are much smaller than in the undistorted power P (t) shown in FIG.
  • the input current I ß it was distorted by appropriate Ausbil ⁇ tion of the first control circuit so that the provisions of class C of the mains current distortion standard with respect to the amplitude components of the higher harmonics are still met.
  • the vorgeb ⁇ cash amplitudes of the harmonics were selected so that they correspond to the maximum permissible amplitudes of these mains current distortion norm and continue only the amplitudes up to the 11th harmonic were preset.
  • the harmonics in this example have no phase shift from the fundamental of the input current Isit).
  • the switching converter 10 of the invention is particularly advantageously additionally provides the ability to control the input current I ß it) of the switching converter 10 such that the harmonics of a phase shift with respect to each have other and also with respect to the fundamental.
  • this also predeterminable phase shifts can be used to particularly skillful manner, the input current ⁇ E (t) and thus also the dance network of Peoplesreak- 12 output power P (t) in such a way to modi ⁇ fy that the capacitive energy storage Cl even further in its size can be reduced.
  • FIG. 5a is a graphical representation of another harmonically distorted current ⁇ E (t) and Fig. 5b is a graph of ⁇ fromcertainsreaktanznetzwerk 12 corresponding to the input current I (t) of FIG. 5a har ⁇ monic distorted output power P (t ).
  • the average power Po to be coupled into the output reactance network 13 is again 25 W in the case of a sinusoidal alternating voltage with an effective value of 230 V as the input voltage U E.
  • the input current IU was (t) distorted by appropriately specified differently surrounded by the first amplitude control circuit, that the provisions of the class D, the mains current distortion standard are yet fulfilled with respect to the amplitude components of the higher harmonics.
  • the shaded areas correspond in turn to be saved from the capacitive energy storage Cl energy E.
  • the energy to be stored e can be further reduced by a greater harmonic distortion ⁇ to.
  • a reduction of the required capacitance of the capacitive energy store C1 by approximately 41% in the case of a distortion according to FIG. 4 a and FIG. 4 b, and by approximately 60% in the case of an distortion according to FIG. 5 a and FIG. 5b are achieved with respect to an undistorted signal.
  • a switching converter for operating at least one LED it is provided that makes it possible to reduce the Ka ⁇ capacity of the capacitive energy storage device by a first control circuit is adapted to distort ei ⁇ NEN input current harmonic, so that the to be stored by the capacitive energy store energy reduced.
  • a first control circuit is adapted to distort ei ⁇ NEN input current harmonic, so that the to be stored by the capacitive energy store energy reduced.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un convertisseur de commande servant à faire fonctionner au moins une LED et présentant une durée de vie plus longue. Le convertisseur de commande (10) selon l'invention comprend une entrée (E1, E2) destinée à être reliée à une source de tension alternative, une sortie (A1, A2) destinée à être reliée à la ou aux LED, un réseau de réactance d'entrée (12) possédant une entrée reliée à une sortie d'un redresseur (11), le réseau de réactance d'entrée (12) comprenant au moins un premier commutateur électronique commandable, un accumulateur d'énergie capacitif (C1) relié à la sortie du réseau de réactance d'entrée (12) et au moins un premier circuit de réglage électronique au moyen duquel le convertisseur de commande (10) peut être réglé par une excitation correspondante du commutateur électronique au niveau de son entrée (E1, E2) à une valeur de consigne du courant d'entrée (IE(t)). Le ou les premiers circuits de réglage sont conçus de telle façon que le convertisseur de commande (10) peut être réglé au niveau de son entrée (E1, E2) à une valeur de consigne du courant d'entrée (IE(t)). La courbe temporelle de ladite valeur de consigne présente des composantes spectrales à une fréquence de base d'une oscillation fondamentale ayant une amplitude de base et à une fréquence d'au moins une harmonique ayant une amplitude prédéfinissable, la ou lesdites fréquences étant un multiple entier de la fréquence de base.
PCT/EP2013/058776 2012-04-26 2013-04-26 Convertisseur de commande servant à faire fonctionner au moins une led WO2013160462A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102012206976.3A DE102012206976B4 (de) 2012-04-26 2012-04-26 Schaltwandler zum Betreiben mindestens einer LED
DE102012206976.3 2012-04-26

Publications (1)

Publication Number Publication Date
WO2013160462A1 true WO2013160462A1 (fr) 2013-10-31

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WO (1) WO2013160462A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2015144394A1 (fr) * 2014-03-24 2015-10-01 Osram Gmbh Circuiterie et procédé pour faire fonctionner des sources lumineuses à semi-conducteurs

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102014205469A1 (de) * 2014-03-24 2015-09-24 Osram Gmbh Schaltungsanordnung und Verfahren zum Betreiben von Halbleiterlichtquellen

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19713814A1 (de) 1997-04-03 1998-10-15 Siemens Ag Schaltnetzteil
US20100188007A1 (en) * 2007-06-27 2010-07-29 Koninklijke Philips Electronics N.V. Supplying a signal to a light source
EP2315497A1 (fr) 2009-10-09 2011-04-27 Nxp B.V. Circuit de commande avec contrôle de la tension de réserve et correction du facteur de puissance
DE102010039154A1 (de) 2010-08-10 2012-02-16 Tridonic Gmbh & Co. Kg Modulation eines PFC bei DC-Betrieb

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19713814A1 (de) 1997-04-03 1998-10-15 Siemens Ag Schaltnetzteil
US20100188007A1 (en) * 2007-06-27 2010-07-29 Koninklijke Philips Electronics N.V. Supplying a signal to a light source
EP2315497A1 (fr) 2009-10-09 2011-04-27 Nxp B.V. Circuit de commande avec contrôle de la tension de réserve et correction du facteur de puissance
DE102010039154A1 (de) 2010-08-10 2012-02-16 Tridonic Gmbh & Co. Kg Modulation eines PFC bei DC-Betrieb

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2015144394A1 (fr) * 2014-03-24 2015-10-01 Osram Gmbh Circuiterie et procédé pour faire fonctionner des sources lumineuses à semi-conducteurs
CN106165540A (zh) * 2014-03-24 2016-11-23 欧司朗股份有限公司 用于运行半导体光源的电路装置和方法
US10159123B2 (en) 2014-03-24 2018-12-18 Osram Gmbh Circuit arrangement and method for operating semiconductor light sources

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DE102012206976A1 (de) 2013-10-31

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