WO2011147216A1 - 广播信号发射方法和装置 - Google Patents

广播信号发射方法和装置 Download PDF

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Publication number
WO2011147216A1
WO2011147216A1 PCT/CN2011/071362 CN2011071362W WO2011147216A1 WO 2011147216 A1 WO2011147216 A1 WO 2011147216A1 CN 2011071362 W CN2011071362 W CN 2011071362W WO 2011147216 A1 WO2011147216 A1 WO 2011147216A1
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Prior art keywords
sub
array
arrays
signal
weight vector
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PCT/CN2011/071362
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English (en)
French (fr)
Inventor
蒋伟
杨学志
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华为技术有限公司
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Priority to EP11785988.4A priority Critical patent/EP2579677A4/en
Publication of WO2011147216A1 publication Critical patent/WO2011147216A1/zh
Priority to US13/685,426 priority patent/US20130076566A1/en

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/40—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with phasing matrix
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/246—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for base stations
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0667—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal
    • H04B7/0671—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal using different delays between antennas

Definitions

  • the embodiments of the present invention relate to the field of communications technologies, and in particular, to a broadcast signal transmitting method and apparatus. Background technique
  • the cell system (ie, cellular) is the basic implementation of today's mobile communication networks.
  • the base station is the core of the cell and the key to realizing mobile communication.
  • the signal transmission of the base station can be divided into two categories: a dedicated channel and a common channel, wherein the dedicated channel carries information required by a single mobile terminal, and belongs to point-to-point communication between the base station and the terminal; the common channel carries the common needs of all mobile terminals in the cell.
  • BCH Broadcast Channel
  • PCH Paging Channel
  • MCH Multimedia Broadcasting And Multicasting Service
  • MBMS Multimedia Broadcasting And Multicasting Service
  • the wireless transmission channel of the multi-antenna system can be classified into an associated fading channel and an independent fading channel depending on the antenna spacing and the reflection environment. If the antenna spacing is small, the surrounding reflectors are small, or the angle spread is small, the channel fading correlation between the antennas is large. If the antenna spacing is large and the reflection is sufficient and the angle expansion is large, the channel fading between the antennas is independent.
  • the macro cell i.e., the macro cell
  • many multi-antenna systems of existing base stations have associated fading channels, for example, smart antenna systems or mobile terminals in multiple reflections in weakly reflective environments (such as plains, water or grasslands, etc.)
  • MIMO Multiple Input Multiple Output
  • one antenna of the multi-antenna system can be selected, and the selected antenna is configured with a high power amplifier to implement a broadcast signal cell or Full coverage of the sector.
  • the power amplifier has high cost and large power consumption, so that comprehensive coverage of a cell or a sector cannot be effectively realized.
  • the embodiment of the invention provides a broadcast signal transmitting method and device, which realizes comprehensive coverage of a broadcast signal in a cell or a sector in a multi-antenna system, and effectively reduces economic costs.
  • An embodiment of the present invention provides a broadcast signal transmitting method, including:
  • the basic weight vector is such that a beam peak-to-average power ratio of each sub-array is lower than a preset threshold, and the beam patterns of different sub-arrays are complementary in a direction dimension ;
  • An embodiment of the present invention provides a broadcast signal transmitting apparatus, including:
  • a dividing processing module configured to divide an antenna array in the multi-antenna system to obtain a plurality of sub-arrays
  • a basic weight vector obtaining module configured to acquire basic weights of each of the plurality of sub-arrays: the beam patterns of the different sub-arrays are complementary in the direction dimension;
  • a first weighting processing transmitting module configured to perform weighting processing on the transmitting signals on the array elements in the sub-arrays corresponding to each of the basic weight vectors to obtain a first signal according to the weight coefficients in each of the basic weight vectors And applying the array element to transmit the first signal.
  • the broadcast signal transmitting method and apparatus of the embodiment of the present invention obtains a plurality of sub-arrays by dividing the antenna array in the multi-antenna system, and acquires a basic weight vector of each sub-array of the plurality of sub-arrays, the basic weight vector
  • the beam peak-to-average power ratio of each sub-array is made lower than a preset threshold, and the beam patterns of different sub-arrays are complemented in the direction dimension, and corresponding to each basic weight vector according to the weight coefficient in each basic weight vector
  • the transmitted signals on the array elements in the sub-array are weighted Processing the first signal, and applying the array element to transmit the first signal, so that the beam pattern of each sub-array is complementary in the direction dimension, thereby averaging the average pattern of the plurality of sub-arrays in each direction
  • the power gains are basically equal, which ensures that all mobile terminals in the cell or sector can receive the same quality signal at the same time, realizing the comprehensive coverage of the broadcast signal in the
  • FIG. 1 is a flow chart of an embodiment of a broadcast signal transmitting method according to the present invention.
  • FIG. 2 is a flowchart of another embodiment of a broadcast signal transmitting method according to the present invention.
  • FIG. 3 is a schematic diagram of signal transmission in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 2;
  • FIG. 4 is a schematic structural view of a uniform linear array of eight antennas;
  • FIG. 5 is a schematic structural diagram of two four-antenna uniform linear array division
  • FIG. 6 is a schematic structural diagram of an eight-element dual-polarized antenna division
  • FIG. 7 is a schematic diagram of signal transmission in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 2;
  • FIG. 8 is a flowchart of still another embodiment of a broadcast signal transmitting method according to the present invention;
  • 9 is a schematic diagram of signal transmission based on Alamouti coding and phase rotation in the implementation of the broadcast signal transmitting method of the present invention;
  • FIG. 10 is a schematic diagram of signal transmission based on Alamouti coding and cyclic delay method in the implementation of the broadcast signal transmitting method of the present invention
  • FIG. 11 is a schematic diagram showing a space-time mapping relationship in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8;
  • FIG. 12 is a schematic diagram showing a relationship of a space frequency mapping in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8;
  • FIG. 13 is a diagram showing two complementary beam patterns and average beam patterns in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8;
  • FIG. 14 is an updated two complementary beam pattern and an average beam pattern in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8;
  • 16 is a schematic diagram of signal transmission according to time or frequency switching transmit diversity in an embodiment of a broadcast signal transmitting method according to the present invention
  • 17 is a complementary beam pattern and average beam pattern in the embodiment of the broadcast signal transmitting method of the present invention.
  • FIG. 18 is a schematic structural diagram of an embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • FIG. 19 is a schematic structural diagram of another embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • FIG. 20 is a schematic structural diagram of still another embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • FIG. 21 is still another embodiment of a broadcast signal transmitting apparatus according to the present invention; Schematic diagram of the structure. detailed description
  • FIG. 1 is a flowchart of an embodiment of a method for transmitting a broadcast signal according to the present invention. As shown in FIG. 1, the method in this embodiment may include:
  • Step 101 Perform division processing on the antenna array in the multi-antenna system to obtain multiple sub-arrays.
  • the multi-antenna system may be a single antenna array, a plurality of antenna arrays, or a polarized antenna array or the like.
  • the implementation of dividing the antenna array in the multi-antenna system to obtain multiple sub-arrays may be implemented by, but not limited to, the following implementation manners:
  • a single antenna array For a single antenna array, a single antenna array is divided to obtain a plurality of closely spaced sub-arrays. Each sub-array may include at least one array element.
  • the division processing manner specifically adopted by the antenna array in the multi-antenna system is not limited, and those skilled in the art may adopt an arbitrary division processing manner as needed.
  • the antenna array can be a linear array, a circular array, a square matrix, and any other array of antenna arrays ij; the spacing of the antenna elements is generally half a wavelength, and can also be other array elements that can maintain channel correlation. Interval, such as two wavelengths, even ten wavelengths, and so on.
  • Step 102 Acquire a basic weight vector of each sub-array in the plurality of sub-arrays, and the basic weight vector enables The beam peak-to-average power ratio of each sub-array is lower than a preset threshold, and the beam patterns of different sub-arrays are complementary in the directional dimension.
  • Step 103 Perform weighting processing on the transmit signals on the array elements of the sub-arrays corresponding to each basic weight vector according to the weight coefficients in each basic weight vector to obtain a first signal, and apply the array elements to transmit the first signal.
  • each basic weight vector may include a plurality of weight coefficients
  • each sub-array may include a plurality of array elements
  • the number of weight coefficients of the basic weight vector corresponding to each sub-array is equal to the number of array elements of the sub-array.
  • the transmission signals on the array elements of the sub-array are weighted to obtain a first signal, that is, weighting the transmitted signals on the array elements of each sub-array to obtain a first a signal, and applying the array element to transmit the first signal, so that the beam pattern coverage angle of each sub-array is wide and the peak-to-average power ratio is low, and the beam patterns of different sub-arrays are complementary in the direction dimension. .
  • the transmit signal on the array elements of the sub-array is weighted, and the array element pair weighting processing of the sub-array is applied.
  • the beam pattern of the sub-array may have a low gain in some specific directions, even when the gain is zero, and according to the weight coefficient of the basic weight vector corresponding to another sub-array of the plurality of sub-arrays, Weighting the transmitted signal on the array elements of the other sub-array, and applying the array elements of the sub-array to transmit the weighted processed signal, so that the beam pattern of the sub-array has a higher position in the specific direction.
  • the gain is such that the average beam pattern of the beam patterns of the plurality of sub-arrays has less gain fluctuations in that particular direction.
  • the signal transmitted by the sub-array received by the mobile terminal in the specific direction at the moment may be weak.
  • the signals transmitted by the other sub-arrays received by the mobile terminal in the specific direction at the moment are stronger, and may be channel coded or diversity.
  • the technology compensates for the performance loss caused by the weaker transmission signal of one of the plurality of sub-arrays, thereby ensuring that the mobile terminal in the specific direction can normally receive the broadcast signal.
  • the power ratio is lower than the preset threshold, and the beam patterns of the different sub-arrays are complementary in the direction dimension, and the transmit signals on the array elements of each sub-array are weighted according to the weight coefficients of each basic weight vector to obtain the first a signal, and applying the array element to transmit the first signal, because the beam pattern coverage angle of each sub-array is wide, the peak-to-average power ratio is low, and the average beam pattern of the beam pattern of all sub-arrays is in the whole cell or fan
  • the difference in gain in each direction in the region is equal to zero or less than a predetermined value, so that the transmission power of the entire multi-antenna system in all directions is substantially equal, thereby realizing the broadcast signal in the multi-antenna system in various directions in the cell or sector.
  • FIG. 2 is a flowchart of another embodiment of a broadcast signal transmitting method according to the present invention
  • FIG. 3 is a schematic diagram of signal transmission in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 2, as shown in FIG. 2 and FIG.
  • the method of the example may include:
  • Step 201 Perform channel coding processing, constellation modulation processing, and space-time-frequency coding processing on the broadcast signal to obtain a multi-channel code stream signal.
  • channel coding processing and constellation modulation processing may be performed on the broadcast signal to acquire a multiplex symbol stream. Therefore, the transmitted signal on the array elements of each sub-array can be a code stream signal or a symbol stream.
  • the broadcast signal is specifically a Multimedia Broadcasting and Multicasting Service (MBMS) and a bit stream of a cell common channel signal.
  • MBMS Multimedia Broadcasting and Multicasting Service
  • a specific implementation manner of acquiring a multi-channel code stream signal by performing space-time frequency coding processing on a broadcast signal is: performing channel coding processing on a bit stream of a multimedia broadcast multicast service and a cell common channel signal, respectively. , interleaving processing and constellation mapping processing, acquiring (complex) symbol streams. Then, the acquired (complex) symbol stream is subjected to space-time-frequency coding processing to obtain a multi-channel code stream signal, and the number of code streams is equal to the number of sub-arrays, and correspondingly.
  • the bit stream of the multimedia broadcast multicast service and the cell common control signal may perform channel coding processing, interleaving processing, and constellation mapping processing, respectively, to acquire a single (multiplex) symbol stream, and send the symbol stream to the plurality of sub-arrays
  • Each sub-array, that is, the transmit signal of each sub-array is the same.
  • the space-time-frequency coding method may be, but not limited to, Alamouti coding, Space-Time Block Coding (STBC), Space-Frequency Block Coding (SFBC), and time-switched transmit diversity ( Time Switched Transmit Diversity; short for: TSTD) and Frequency Switched Transmit Diversity (FSTD).
  • STBC Space-Time Block Coding
  • SFBC Space-Frequency Block Coding
  • FSTD Frequency Switched Transmit Diversity
  • This embodiment does not limit the specific space-time-frequency coding method.
  • Those skilled in the art may use any of the above space-time-frequency coding methods or combinations thereof or other possible space-time-frequency coding methods as needed.
  • Step 202 Perform logical division processing on a single antenna array to obtain multiple sub-arrays.
  • the multi-antenna system is taken as a single antenna array, and the technical solution of the embodiment is described in detail.
  • the single antenna array is logically divided to obtain multiple sub-arrays, and each sub-array includes at least one array element.
  • Each array element can only be selected once by all subarrays, in other words, any two Different subarrays do not contain the same array elements.
  • each element of the single antenna array before the division process is selected once, that is, the sum of the array elements of all the sub-arrays is equal to all the elements in the single antenna array before the division process.
  • FIG. 4 is a schematic structural diagram of eight-antenna uniform linear array division.
  • a single antenna array is logically divided, and two sub-arrays are obtained, which are sub-array 1 and sub-array ⁇ 'j 2, respectively.
  • Each subarray contains four array elements. This embodiment does not limit the arrangement of the array elements, the number of array elements, and the spacing of the array elements. Those skilled in the art can set them as needed.
  • Step 202 in this embodiment may also adopt other implementation manners depending on the type of the antenna array:
  • step 202 may be: dividing a plurality of antenna arrays according to a separation distance to obtain a plurality of sub-arrays.
  • the multi-antenna system includes a plurality of antenna arrays that are far apart.
  • FIG. 5 is a schematic structural diagram of two four-antenna uniform linear array divisions. As shown in FIG. 4, the obtained two sub-arrays are respectively an antenna array 1 and The antenna array 2, each sub-array comprises four array elements, the distance between each array element is expressed as, generally half wavelength, the distance between the sub-arrays is greater than, and the two four-antenna uniform linear arrays may be the same.
  • the two antenna arrays with physical locations on the base station may also be antenna arrays installed on two different base stations. This embodiment does not limit the arrangement of the array elements, the number of array elements, the spacing of the array elements, and the distance between different sub-arrays. Those skilled in the art can set them as needed.
  • step 202 may be: dividing the polarized antenna array according to the polarization direction to obtain multiple sub-arrays.
  • the multi-antenna system is a polarized antenna array
  • FIG. 6 is a schematic structural diagram of an eight-element dual-polarized antenna.
  • two sub-arrays are acquired, each sub-array comprising four array elements, one The four elements in the sub-array are horizontally polarized; the four elements in the other sub-array are vertically polarized.
  • the arrangement of the array elements, the number of array elements, and the spacing of the array elements are not limited, and those skilled in the art can set them as needed. It is worth noting that all array elements in each sub-array are polarized in the same way to have associated channel fading.
  • the antenna array to which the present invention is applicable may be a linear array, a circular array, a square matrix, and any other array of antenna arrays; the spacing of the antenna elements is generally half a wavelength, and may also be other array elements capable of maintaining channel correlation. Interval, such as two wavelengths, even ten wavelengths, and so on.
  • Step 203 Acquire a basic weight vector of each sub-array of the plurality of sub-arrays, the basic weight vector is such that a beam peak-to-average power ratio of each sub-array is lower than a preset threshold, and the beam patterns of different sub-arrays are complementary in a direction dimension. .
  • the method of computer traversal selection may be adopted, and the weight coefficients in the basic weight vector acquired in this embodiment have the same modulus value, The weight coefficient of the same modulus value can cause all the array elements of the antenna array to transmit power, thereby improving the efficiency of the power amplifier.
  • the method for obtaining the basic weight vector in this embodiment is flexible and simple.
  • the general implementation method of obtaining the basic weight vector is as follows: Suppose that N complex numbers with a modulus value of 1 are selected as the available weight coefficients on the unit circle of the complex coordinates.
  • the number of array elements of the antenna array is ⁇ 1
  • a complex number on 16 or 32 unit circles may be selected as the available weight coefficient, or the number of antenna array elements may be increased, for example, an array of 12 or 16 array elements, and a weight vector of each traversal. Both beam pattern calculation, peak-to-average power ratio calculation, etc. need to be performed separately, and the calculation is relatively complicated.
  • the step 202 is used to perform the partitioning process on the antenna array to obtain multiple sub-arrays, so that the number of array elements in each sub-array is small.
  • the antenna array is The eight-antenna array is divided into four array elements.
  • Step 204 Perform weighting processing on the code stream signals on the array elements in each sub-array according to the weight coefficients in each basic weight vector to obtain a first signal, and apply the array elements to transmit the first signal.
  • each basic weight vector includes a plurality of weight coefficients, and each weight vector includes a number of weight coefficients that are the same as the number of array elements included in the sub-array corresponding to each basic weight vector.
  • FIG. 7 is a schematic diagram of signal transmission in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 2. As shown in FIG. 7, the number of array elements of the sub-array is taken as an example.
  • the basic weight vector corresponding to the array, the basic weight vector can cause the sub-array to perform weighting processing on the received one-way code stream signal according to the corresponding basic weight vector.
  • the basic power vector has a low peak-to-average power ratio.
  • the beam patterns of different sub-arrays are complementary in the direction dimension, the average beam pattern of all sub-arrays is approached to the omnidirectional beam generated by the single antenna.
  • Step 205 Perform update processing on each of the basic weight vectors in a time dimension or a frequency dimension, and respectively obtain updated weight vectors.
  • the phase rotation method Randomly obtain a phase value ⁇ from [0 2; ⁇ , each subarray
  • the basic weight vector is applied to the sub-array for weighting processing, and has two characteristics: in the complex set of modulo equals, arbitrary Two complex numbers are selected as the weight coefficients. (1) Regardless of the weight coefficient, the peak-to-average power ratio (or peak value) of the beam pattern remains unchanged; (2) When one of the weight coefficients is unchanged, the other weight When the coefficient is negative, the corresponding beam pattern and the beam pattern of the two weight coefficients are not negative.
  • the basic weight vector can be acquired and updated in a random manner.
  • the basic weight vector is selected by randomly selecting two weight coefficients to form a first basic weight vector corresponding to a sub-array, wherein the two weight coefficient modules are equal to 1, and
  • i ; performing a negative value processing on a weight coefficient in the first basic weight vector, for example: taking a negative value processing on the second weight coefficient of the first basic weight vector, and acquiring a second basic corresponding to the other sub-array Weight vector.
  • the two weight coefficients are randomly selected, and the updated two weight vectors can be obtained according to the above method, and the figures are complementary.
  • the weighting process is performed on each of the array elements of each sub-array to obtain a second signal, and the second signal is transmitted by the array element.
  • each sub-array is fixed to one basic beam pattern, and multiple beam patterns of different sub-arrays are complementary, but since the number of beam patterns is small, the transmission power of the multi-antenna system is in all directions. There may be differences. Therefore, the basic weight vector corresponding to each sub-array can be updated in the time dimension or the frequency dimension, so that the average beam pattern of all sub-arrays has better isotropic, thereby realizing the comprehensiveness of the cell or the sector. Coverage, and effectively reduce economic costs.
  • Delay method On each array element, the first signal is obtained by weighting the transmitted signal according to the weight coefficient, and the second signal is obtained by delay processing the first signal, wherein the delay on each array element The amount is different, and the maximum delay amount is less than the preset value. For example, linear incremental delay is used, no delay is performed on the first array element, ⁇ is delayed on the second array element, and 2 ⁇ is delayed on the third array element, and sequentially increments until the last array element, the second array element Delay (N-l) Ar. And applying each array element to transmit the second signal.
  • the broadband wireless communication system can adopt Orthogonal Frequency Division Multiplexing (OFDM) modulation, according to the discrete Fourier transform (DFT) Nature, the cyclic delay of the time domain, corresponding to the phase rotation of the frequency domain symbols.
  • OFDM Orthogonal Frequency Division Multiplexing
  • DFT discrete Fourier transform
  • the transmit signal on each sub-array is first OFDM-modulated to form an OFDM symbol, and the sub-array corresponds to the basic weight vector.
  • the first weight coefficient weights the OFDM symbol and is transmitted by the first array element of the sub-array; the second weight coefficient weights the OFDM symbol for cyclic delay, and is transmitted by the second array element of the sub-array; Similarly, until the last weight coefficient of the basic weight vector weights the OFDM symbol, it is cyclically delayed and transmitted by the last array element of the sub-array; it should be noted that the cyclic delay size of different array elements on the same sub-array Not the same.
  • a plurality of sub-arrays are obtained by dividing the antenna array, and a basic weight vector is selected for each sub-array, and the code stream signal on the array elements of each sub-array is obtained according to the basic weight vector of each sub-array.
  • the weighting process is performed such that the beam pattern coverage angle of each sub-array is wider than the preset threshold, and the beam patterns formed by different sub-arrays are complementary in the direction dimension, and all beams formed by all sub-arrays
  • the difference of the average beam pattern of the pattern in each direction is equal to zero or less than the preset value.
  • the time diversity or the frequency diversity gain is obtained, and the cell is further enhanced. Or the sector fully covers performance and effectively reduces economic costs.
  • FIG. 8 is a flowchart of still another embodiment of a broadcast signal transmitting method according to the present invention
  • FIG. 9 is a schematic diagram of signal transmission based on Alamouti encoding and phase rotation method in the implementation of the broadcast signal transmitting method of the present invention
  • FIG. The signal transmission principle diagram based on the Alamouti coding and the cyclic delay method in the implementation of the method for transmitting a broadcast signal is as shown in FIG. 8, FIG. 9 and FIG. 10, and the method in this embodiment may include:
  • Step 301 Perform channel coding processing, constellation modulation processing, and Alamouti encoding processing on the broadcast signal to obtain two air-time-frequency code streams.
  • the broadcast signal is specifically a bit stream of a multimedia broadcast multicast service and a cell common control signal.
  • the (complex) symbol stream is obtained, and each of the two symbols in the (complex) symbol stream is respectively grouped, and each two symbols are grouped.
  • the symbol stream performs space time-frequency coding to generate two channels of space-time code.
  • the Alamouti coding has two equivalent forms, and the coding matrix is as shown in the formula (2) and the formula (3), wherein the coding matrix row corresponds to an antenna of the spatial domain or a sub-array of the present invention, and the coding matrix The column corresponds to the OFDM symbol period of the time domain, or the OFDM subcarrier of the frequency domain.
  • the space-time-frequency code stream is a code stream signal.
  • Step 302 Perform broadband signal modulation on the acquired two channels of space time-frequency code streams.
  • symbols in a space-time code stream can be directly transmitted in order, and the processing of this step can be omitted.
  • code division multiple access Code Division Multiple Access
  • OFDM Orthogonal Frequency Division Multiplexing
  • subcarrier mapping is performed on the space-time-frequency code stream, so that appropriate time-frequency resource blocks are allocated to the symbols in each space-time-frequency code stream, and then the symbols in the allocated space-time-frequency code stream are OFDM-modulated, that is, Perform an inverse fast Fourier transform (IFFT) and insert a cyclic prefix (CP).
  • the subcarrier mapping may have two methods: space time mapping and space frequency mapping.
  • FIG. 11 is a schematic diagram showing a space-time mapping relationship in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8
  • FIG. 12 is a schematic diagram showing the relationship of the space-frequency mapping in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. As shown in FIG.
  • the subcarrier mapping is a space-time mapping
  • the first space-time code stream of the Alamouti coding matrix is placed on the same subcarrier of two consecutive OFDM symbols on the first sub-array
  • the Alamouti coding matrix is The second space-time code stream is placed on the same subcarrier of two consecutive OFDM symbols on the second sub-array and is identical to the sub-carrier position on the first sub-array.
  • the first space frequency code stream of the Alamouti coding matrix is placed on two consecutive subcarriers of the first subarray, and the second space frequency code of the Alamouti coding matrix is used.
  • the stream is placed on two consecutive subcarriers on the second subarray and is identical in position to the subcarriers on the first subarray.
  • Step 303 Perform a partitioning process on the multi-antenna system to obtain two sub-arrays, and each sub-array is used to transmit an empty time-frequency code stream.
  • the multi-antenna system is divided to obtain two sub-arrays.
  • the two sub-arrays of the eight antennas in FIG. 6 have different polarization modes, and the channel fading can be considered to be independent of each other.
  • the polarization modes of the array elements in the same sub-array are the same, and the intervals are relatively close, and channel correlation can be obtained.
  • the basic weight vectors are respectively selected, and the two spatial time-frequency code streams are separately weighted and transmitted.
  • ULA Uniform Linear Array
  • ULA Uniform Linear Array
  • This embodiment does not limit the antenna array to be specifically used.
  • Those skilled in the art can use any antenna array, any number of antennas, and antenna arrays with other array spacing as needed.
  • the antenna array is divided into four sub-arrays by using four adjacent array elements to obtain two sub-arrays each having four adjacent array elements. Since the transmitted space-time-frequency code streams are different, the signals transmitted by the two sub-arrays do not interfere.
  • the direction vector of the antenna array can be decomposed into two four-dimensional independent direction vectors, with the first array element as the reference point.
  • the direction vector of ULA is:
  • Step 304 Acquire a basic weight vector of each sub-array of the two sub-arrays, where the beam direction of the basic weight is complementary in the direction dimension.
  • the broadcast signal transmitting apparatus may acquire a basic weight vector corresponding to each of the two sub-arrays, and the two basic weight vectors may make the coverage angle of the beam pattern of the corresponding sub-array wide, the peak-to-average power ratio is low, and two The beam patterns are complementary.
  • the two basic weights corresponding to the beam pattern coverage angle, the peak-to-average power ratio, and the complementarity are obtained:
  • w 1 [l 0.7071 - 0.7071J j -0.7071 - 0.7071 ⁇ ] ⁇ ( 5 )
  • w 2 [l -0.7071 + 0.707 j 0.7071 + 0.7071 ⁇ /] ⁇ ( 6 )
  • Wl and ⁇ represent the basic weight vector
  • (.f represents the conjugate transpose of the vector.
  • Step 305 Perform weighting processing on the space-time-frequency code stream on the array element in each sub-array corresponding to each basic weight vector according to the weight coefficient in each basic weight vector to obtain the first signal, and The first signal is transmitted with the array element.
  • the two spatial time-frequency code streams on the two sub-arrays are respectively weighted by the weight coefficients in the two basic weight vectors to obtain the first signal, and the array element is used to transmit the first signal, and the beam pattern of the sub-array can be formulated. (7) Get:
  • g(0) w H a(0) ( 7 ) where represents the beam pattern
  • FIG. 13 is a diagram showing two complementary beam patterns and average beam patterns in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8.
  • the beam patterns of the two sub-arrays are represented by scribe lines and dotted lines, respectively.
  • the two beams have good complementarity: the high gain region of beam 1, such as the angle 3 0", 9 0 1 5 (7, 27 0', just compensates for the low gain region of beam 2; , the low gain region of beam 1, as shown in the figure 0 5 , 1 8 0 ', 2 10 33 0 ', beam 2 happens to have a high gain.
  • the average beam pattern of the two beam patterns is exactly circular (As shown by the solid line in Fig. 13), omnidirectional coverage can be achieved.
  • Step 306 Perform a update process on the basic weight vector in a time dimension or a frequency dimension by using a phase rotation method to obtain an updated weight vector.
  • Step 307 Perform weighting processing on the transmit signals on the array elements of each sub-array to obtain a second signal according to the weight coefficients of each updated weight vector at different times or frequencies, and apply the array element to the second signal.
  • the average beam pattern of the two basic weight vectors can complete the omnidirectional coverage of the cell.
  • the number of array elements in the antenna array is large, it is difficult to obtain two fundamental weight vectors that are completely complementary due to the high computational complexity; or the antenna channel due to the physical position error of the antenna, the phase error of the feeder, and the like.
  • the existence of phase error for example, in actual engineering,
  • the beam pattern obtained by weighting the transmitted signal of the sub-array using the basic weight vector may have a large deviation from the beam pattern obtained by theoretical calculation.
  • v 3 and v 4 represent the updated weight vector.
  • FIG. 14 is an updated two complementary beam pattern and average beam direction diagram in the embodiment of the broadcast signal transmitting method of the present invention shown in FIG. 8.
  • two updated weight vector pairs are applied to the sub-array.
  • the space-time code stream is weighted, and the updated beam pattern corresponding to each of the two sub-arrays respectively has the same peak-to-average power as the space-time code pattern on the sub-array.
  • the ratio and peak value, meanwhile, the updated two beam patterns still maintain good complementarity.
  • the broadcasted broadcast signal is encoded by using Alamouti coding to obtain two air-time-frequency code streams, so that the antenna array is divided and processed to obtain two sub-arrays, and basic parameters are selected for each sub-array.
  • the weight vector weights the code stream signal on the array elements of the sub-array according to the two basic weight vectors, and the acquired beam pattern has complementarity in the direction dimension, and the transmission power is isotropic.
  • the phase rotation method to continuously update the basic weight vector in the time dimension or the frequency dimension, the omnidirectional coverage performance of the cell is further improved, and the intra-cell coverage is ensured.
  • a mobile terminal can receive signals of the same quality at the same time and effectively reduce the economic cost.
  • the method may further obtain a second signal by using a delay method.
  • the space-time code stream on the sub-array may be subjected to CDMA modulation processing before performing weighting processing, and the acquired CDMA spread spectrum signal is respectively subjected to a basic weight vector on each array element of the sub-array.
  • the corresponding weight coefficient is weighted and transmitted after delay. For example, linear incremental delay is used, no delay is performed on the first array element, one chip is delayed on the second array element, and two chips are delayed on the third array element, and sequentially incremented until the last one.
  • the array element that is, the Nth chip is delayed by N-1 chips.
  • the method can also obtain a second signal by using a cyclic delay method.
  • the antenna array is a uniform linear array of eight antennas, and the antenna array is divided into four sub-arrays by four adjacent array elements to obtain two sub-arrays each having four adjacent array elements, wherein The first sub-array transmits one of the space-time-frequency code streams, and before the weighting process, OFDM-modulates the code stream to obtain an OFDM symbol.
  • the first weight coefficient OFDM symbol in the basic weight vector corresponding to the first sub-array obtains the second signal, and the second signal is transmitted by the first array element without delay; the second weight coefficient weights the OFDM symbol, and performs a loop
  • the delay processing obtains the second signal, and the second array element transmits the second signal; the third weight coefficient weights the OFDM symbol, and performs cyclic delay processing to obtain the second signal, and the third array element transmits the second signal.
  • the fourth weight coefficient weights the OFDM symbol, and performs cyclic delay processing to obtain a second signal, and the fourth array element transmits the second signal.
  • the second sub-array transmits the other of the two spatial time-frequency code streams, and the cyclic delay method is the same as the first sub-array.
  • DFT discrete Fourier transform
  • the space-time code stream sequence on the sub-array be s ⁇ , after OFDM modulation, the OFDM symbols are obtained, and the four array elements on the sub-array are respectively cyclically delayed, ⁇ 1 , 2 , 3 , and the corresponding OFDM modulation pre-frequency domain sequence is 1 ⁇ [ ⁇ ⁇ ', which is equivalent to the pair.
  • the signal on the carrier is weighted, and the weighting factor is ⁇ .
  • the sub-array performs weighting processing, and the total weight vector is the product of the basic weight vector and the phase weighting factor formed by the cyclic delay:
  • the total weight vector is a variable with respect to the subcarrier number, so the weight vector on each subcarrier is different from the weighting map.
  • the beam pattern is related to the subcarrier position and is expressed as:
  • ⁇ denotes the DFT length in OFDM, which is generally larger, such as 512, 1024, etc., so that a sufficient number of different beam patterns can be generated, and the average beam pattern is isotropic.
  • FIG. 15 is a flowchart of still another embodiment of a broadcast signal transmitting method according to the present invention.
  • FIG. 16 is a schematic diagram of signal transmission based on time-switched transmit diversity (TSTD) or frequency-switched transmit diversity (FSTD) in an embodiment of a broadcast signal transmitting method according to the present invention. As shown in Figures 15 and 16, the method of this embodiment may include:
  • Step 401 Perform Space-Time Block Coding (hereinafter referred to as STBC) for the broadcast signal and combine Time Switched Transmit Diversity (Time Switched Transmit Diversity; Hereinafter referred to as: TSTD), or using Space-Frequency Block Coding (hereinafter referred to as SFBC) and combined with Frequency Switched Transmit Diversity (hereinafter referred to as FSTD) for encoding processing to obtain four-way space time Frequency code stream.
  • STBC Space-Time Block Coding
  • SFBC Space-Frequency Block Coding
  • FSTD Frequency Switched Transmit Diversity
  • the broadcast signal is specifically a bit stream of a multimedia broadcast multicast service and a cell common control signal.
  • a (complex) symbol stream is obtained, and each of the four symbols in the (complex) symbol stream is spatially time-frequency coded to generate four time-frequency codes.
  • the code stream, the coding matrix is as follows:
  • Each row of the acquired coding matrix corresponds to one sub-array, and each column of the coding matrix corresponds to a symbol transmission period of the time domain, or a sub-carrier of the frequency domain.
  • Step 402 Perform broadband signal modulation on the acquired four-channel space-time-frequency code stream.
  • symbols in a space-time-frequency code stream may be directly transmitted in order, and may not be processed in this step; for a wideband communication system, code division multiple access (CDMA) modulation or positive is required.
  • CDMA code division multiple access
  • OFDM Inter-frequency division multiplexing
  • the subcarrier mapping is performed on the space-time-frequency code stream, and the symbols in the space-time-frequency code stream can adopt different sub-carrier mapping modes: (1) Space-frequency mapping: Four modulation symbol placements on each air-time-frequency code stream On the four consecutive subcarriers on the corresponding sub-array; (2) space-time mapping: four modulation symbols on each spatial time-frequency code stream are placed on the same sub-carrier of four consecutive OFDM symbols on the corresponding sub-array; (3) Space-time-frequency mapping: Four modulation symbols on each air-time-frequency code stream are placed on two consecutive sub-carriers on two consecutive OFDM symbols.
  • the above three subcarrier mapping methods are equivalent. Perform OFDM modulation on the mapped space-time-frequency code stream, that is, perform inverse fast Fourier transform (IFFT) on the block data, and then insert a cyclic prefix (CP).
  • IFFT inverse fast Fourier transform
  • CP cyclic prefix
  • Step 403 Perform a division process on the multi-antenna system to obtain four sub-arrays.
  • a four-way space-time code stream is acquired. Therefore, the multi-antenna system is divided to obtain four sub-arrays, and each sub-array selects a basic weight vector such that the beam pattern coverage angle is wide, the peak-to-average ratio is low, and the average of the four beam patterns generated by the four sub-arrays
  • the beam patterns have equal or different gains in all directions that are less than a preset value.
  • the eight-element ULA uniformly distributed at half-wavelength intervals is taken as an example to describe the technical solution of the embodiment in detail. This embodiment does not limit the antenna array to be specifically used.
  • the antenna array has two adjacent arrays.
  • the element is divided into a sub-array to obtain four sub-arrays each having two adjacent array elements, and the direction vector of the antenna array can be decomposed into four two-dimensional direction vectors, with the first array element of ULA as a reference point. , the four direction vectors are shown in equation ( 14 ):
  • Step 404 Acquire a basic weight vector of each sub-array in the plurality of sub-arrays, the basic right direction
  • four basic weight vectors are obtained, so that the beam pattern of the four sub-arrays.
  • the cover angle is wide and the peak-to-average ratio is low, and the average beam pattern of the beam patterns of the four sub-arrays has a difference in gain in each direction of the cell/sector equal to zero or less than a preset threshold.
  • the following four basic weight vectors :
  • FIG. 17 is a beam direction diagram and an average beam direction diagram of a basic weight vector in the embodiment of the broadcast signal transmitting method of the present invention. As shown in FIG. 17, the average beam pattern has the same gain in all directions.
  • Step 405 Perform weighting processing on the code stream signal corresponding to each array element of each sub-array according to each weight coefficient of the basic weight vector to obtain a first signal, and apply the array element to transmit the first signal.
  • Step 406 Perform a update process on the basic weight vector by using a phase rotation method to obtain an updated weight vector.
  • Step 407 Perform weighting processing on the transmit signals on the array elements of each sub-array to obtain a second signal according to the weight coefficients of each updated weight vector at different times or frequencies, and apply the array element to the second signal.
  • the phase rotation method can be used to update the basic weight vector in the time dimension or the frequency dimension to obtain time or frequency diversity such that the transmission power is equal in all directions.
  • the phase rotation method employed in this step 406 performs the basic weight vector in the time dimension or the frequency dimension.
  • the implementation of the update process is similar to the implementation of the update process of the base weight vector in the time dimension or frequency dimension with the phase rotation method employed by step 306 in FIG.
  • step 406 may further update the basic weight vector in a time dimension or a frequency dimension by using a random variable method, and weight the transmitted signal by using the updated weight vector on different time or frequency resources to obtain time. Or frequency diversity.
  • weight coefficients are randomly selected on the unit circle of the complex coordinates, and the selected weight coefficients are assumed to be ⁇ 1 and ⁇ , respectively, and the following four updated weight vectors are constructed:
  • Wl [i, - if, w 2
  • the beam pattern is shown in the figure, and the beams are complementary.
  • four weight coefficients are randomly selected from the unit circle of the complex coordinates, and four new weight vectors are constructed according to the foregoing method.
  • the broadcast signal is encoded by using TSTD or FSTD to obtain a four-channel space-time code stream, so that the antenna array is divided, four sub-arrays are acquired, and four beam patterns are selected.
  • the complementary basic weight vector, the array element of each sub-array selects the corresponding weight coefficient in the basic weight vector, and weights and transmits the space time-frequency code stream. Thereby more comprehensive coverage of the cell or sector is achieved.
  • each sub-array selects a basic weight vector, and the weighting process makes the beam pattern of the sub-array complementary.
  • the first space-time time-frequency code stream in the four-channel space-time code stream is OFDM-modulated to obtain an OFDM symbol, and the first weight coefficient corresponding to the basic weight vector is weighted to obtain the second signal, and no delay processing is performed, and the sub-array is used.
  • the first array element transmits the second signal; the second weight coefficient weights the OFDM symbol, and performs cyclic delay processing, and the second array element transmits the second signal.
  • the second sub-array transmits a second air-time-frequency code stream in the four-way space-time code stream,
  • the loop delay method is the same as the first subarray.
  • the method of transmitting the third sub-array and the fourth sub-array is the same as the method of the first array, and details are not described herein again.
  • the implementation of the cyclic delay method employed in this embodiment is similar to the implementation of the cyclic delay method shown in FIG.
  • FIG. 18 is a schematic structural diagram of an embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • the broadcast signal transmitting apparatus of this embodiment includes: a dividing processing module 11, a basic weight vector obtaining block 12, and a first The transmitting module 13 is weighted.
  • the partitioning processing module 11 is configured to perform a partitioning process on the antenna array in the multi-antenna system to obtain a plurality of sub-arrays.
  • the basic weight vector acquiring module 12 is configured to acquire a basic weight vector of each sub-array in the plurality of sub-arrays, and the basic weight vector is such that The beam peak-to-average power ratio of each sub-array is lower than a preset threshold, and the beam patterns of different sub-arrays are complementary in the direction dimension;
  • the first weighting processing transmitting module 13 is configured to use the weight coefficients in each of the basic weight vectors, The first transmission signal is obtained by weighting the transmission signal on the array element in the sub-array corresponding to each basic weight vector, and the first signal is transmitted by using the array element.
  • the broadcast signal transmitting apparatus of this embodiment may be used to implement the technical solution of the method embodiment shown in FIG. 1, and the implementation principle thereof is similar, and details are not described herein again.
  • the beam pattern coverage angle of each sub-array is wide, the peak-to-average power ratio is low, and the average beam pattern of the beam pattern of all sub-arrays is in the whole cell or fan
  • the difference in gain in each direction in the zone is equal to zero or less than a predetermined value, such that the transmit power of the entire multi-antenna system in all directions is equal, Furthermore, the comprehensive coverage of the broadcast signal in various directions in the cell or sector in the multi-antenna system is realized, and the economic cost is effectively reduced.
  • FIG. 19 is a schematic structural diagram of another embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • the broadcast signal transmitting apparatus of this embodiment includes: a first encoding processing module 21, a dividing processing module 22, and a basic weight vector acquisition. Module 23, first weighting processing transmit mode 24, update module 25, and second weighting process transmit module 26.
  • the first encoding processing module 21 is configured to perform channel coding processing, constellation modulation processing, and space-time-frequency encoding processing on the broadcast signal to acquire the multi-channel code stream signal.
  • the basic weight vector obtaining module 23 is configured to acquire basic weight vectors of each of the plurality of sub-arrays, the basic beam patterns are complementary in the direction dimension; the first weighting processing transmitting module 24 is configured to be used according to each of the basic weight vectors The weight coefficient respectively weights the transmitted signals on the array elements in the sub-arrays corresponding to each basic weight vector to obtain a first signal, and applies the array elements to transmit the first signal.
  • the update module 25 is configured to perform an update process on each of the base weight vectors in the time dimension or the frequency dimension to obtain the updated weight vector; the second weighting process transmitting module 26 is configured to use the updated rights at different times or frequencies.
  • the vector is respectively weighted by the transmit signal on the array elements of each sub-array to obtain a second signal, and the array element is used to transmit the second signal.
  • the partitioning processing module 22 includes a first processing unit or a second processing unit or a second processing unit, configured to divide the plurality of antenna arrays according to the separation distance; and the third processing unit is updated in this embodiment.
  • the module 25 can include a phase acquisition unit 251 and an update unit 252.
  • the phase obtaining unit 251 is configured to acquire the phase value updating unit 252 for applying the formula.
  • w New diag ⁇ e jA ⁇ e j2A ⁇ -e nM - ⁇ ] - w
  • update processing for each basic weight vector W [ Wi , W 2 , ⁇ Wm ] t , respectively, to obtain the updated weight vector.
  • ⁇ und denotes the updated weight vector
  • j is an imaginary unit
  • diag[x x ...x ditch ] denotes a diagonal matrix composed of 3 ⁇ 4 to xcountry.
  • the broadcast signal transmitting apparatus of this embodiment may be used to perform the technical solution of the method embodiment of any one of FIG. 2 to FIG. 17.
  • the implementation principle is similar, and details are not described herein again.
  • the dividing processing module divides the antenna array of the multi-antenna system by using different dividing methods, and acquires a basic weight vector of each sub-array in the plurality of sub-arrays, wherein the basic beam pattern is in the direction dimension. Complementing, and then weighting the transmitted signals on the array elements of each sub-array according to the weight coefficients of each basic weight vector, and applying the array elements to transmit the weighted processed signals.
  • the basic weight vector is updated by the phase rotation method, the updated weight vector is obtained, and the transmitted space-time code stream on the array elements in each sub-array is weighted according to the weight coefficient of the updated weight vector.
  • FIG. 20 is a schematic structural diagram of still another embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • the broadcast signal transmitting apparatus of this embodiment includes: a second encoding processing module 31, a dividing processing module 32, and a basic weight vector acquisition.
  • the second encoding processing module 31 is configured to perform channel coding processing and constellation modulation processing on the broadcast signal to acquire a multi-channel symbol stream.
  • the first weighting processing transmitting module 34 is configured to respectively respectively correspond to the sub-arrays corresponding to each basic weight vector according to the weight coefficients in each basic weight vector
  • the transmit signal on the array elements in the column is weighted to obtain a first signal, and the array element is used to transmit the first signal.
  • the updating module 35 is configured to perform an update process on each basic weight vector in a time dimension or a frequency dimension to obtain an updated weight vector; the second weighting processing transmitting module 36 is configured to use the updated weight at different times or frequencies.
  • the vector is respectively weighted by the transmit signal on the array elements of each sub-array to obtain a second signal, and the array element is used to transmit the second signal.
  • the basic weight vector obtaining module 33 may include a first basic weight vector acquiring unit 331 and a second basic weight vector acquiring unit 332.
  • the first basic weight vector obtaining unit 331 is configured to select two first weight coefficients that are equal to each other to form a basic weight vector corresponding to one of the two sub-arrays; and the second basic weight vector acquiring unit 332 is configured to One of the first weight coefficients having the same modulus takes a negative value, and constitutes a basic weight vector corresponding to another sub-array of the two sub-arrays.
  • the update module 35 can include a first update unit 351 and a second update unit 352.
  • the first updating unit 351 is configured to respectively select two second equal weight coefficients corresponding to two complementary sub-arrays of the two complementary sub-arrays, and form an updated one corresponding to one sub-array of the two sub-arrays. Weight vector.
  • the second updating unit 352 is configured to take a negative value of one of the first weight coefficients that are equal to each other, and respectively form a basic weight corresponding to another one of the two complementary sub-arrays of the two complementary sub-arrays vector.
  • the broadcast signal transmitting apparatus of this embodiment may be used to implement the technical solution of any of the method embodiments of FIG. 2 to FIG. 17.
  • the implementation principle is similar, and details are not described herein again.
  • FIG. 21 is a schematic structural diagram of still another embodiment of a broadcast signal transmitting apparatus according to the present invention.
  • the broadcast signal transmitting apparatus of this embodiment includes: a first encoding processing module 41, a dividing processing module 42, and a basic weight vector acquisition.
  • the block 41 is configured to perform channel coding processing, constellation modulation processing, and space-time-frequency coding processing on the broadcast signal to acquire a multi-channel code stream signal.
  • the basic weight vector obtaining module 43 is configured to acquire a basic weight vector of each sub-array of the plurality of sub-arrays, the basic weight vector is such that a beam peak-to-average power ratio of each sub-array is lower than a preset threshold, and a beam pattern of different sub-arrays is caused
  • the first weighting processing transmitting module 44 is configured to perform weighting processing on the transmitting signals on the array elements in the sub-arrays corresponding to each basic weight vector according to the weight coefficients in each basic weight vector, and Applying the array element to transmit the first signal after the weighting process;
  • the OFDM processing module 45 is configured to perform orthogonal frequency division multiplexing modulation processing on the transmitted signals on the array elements in each sub-array to obtain the array elements in each sub-array.
  • the first update transmitting module 46 is configured to perform weighting processing on the orthogonal frequency division multiplexing signal according to the first weight coefficient in each basic weight vector to obtain a second signal, and apply the sub The first element of the array transmits the second signal.
  • the second update transmitting module 47 is configured to perform weighting processing and delay processing on the orthogonal frequency division multiplexing signal according to the second weight coefficient to the last weight coefficient in each basic weight vector to obtain a second signal, and respectively apply the sub-array The second array to the last array element transmits the second signal.
  • the broadcast signal transmitting apparatus may further include a delay processing module, configured to perform delay processing on the weighted processed signal on the array elements in each sub-array to obtain a second signal, and apply the array element to the second signal. emission.
  • a delay processing module configured to perform delay processing on the weighted processed signal on the array elements in each sub-array to obtain a second signal, and apply the array element to the second signal. emission.
  • the broadcast signal transmitting apparatus of this embodiment may be used to implement the technical solution of the method embodiment shown in FIG. 2 to FIG. 17.
  • the implementation principle is similar, and details are not described herein again.
  • the antenna array is divided into different manners to obtain multiple sub-arrays, and basic weight vectors of each sub-array of the plurality of sub-arrays are obtained, and the basic weight vector is used to make the peak-to-average power of each sub-array.
  • the ratio is lower than the preset threshold, and the beam patterns of different sub-arrays are complementary in the direction dimension, and then the array elements in each sub-array are based on the weight coefficients of each basic weight vector.
  • the upper transmit time-frequency code stream is weighted, and the first signal transmitted by the weighting process is applied by the array element.
  • each sub-array has a wide beam coverage angle, a low peak-to-average power ratio, and a directional dimension complementarity
  • the root weight vector is continuously updated by using a cyclic delay method to obtain an updated weight vector, and according to the update Weighting coefficient of the weight vector, weighting the transmitted space-time-frequency code stream on the array elements in each sub-array to obtain a second signal, and applying the array element to transmit the second signal, thereby making the beam pattern of the sub-array
  • the average transmit power on the uplink has better isotropic, thereby further ensuring that all mobile terminals in the cell can receive the same quality signal, thereby more effectively realizing the comprehensive coverage of the broadcast signal in the cell or sector in the multi-antenna system.
  • the foregoing program may be stored in a computer readable storage medium, and the program is executed when executed.
  • the foregoing steps include the steps of the foregoing method embodiments; and the foregoing storage medium includes: a medium that can store program codes, such as a ROM, a RAM, a magnetic disk, or an optical disk.

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Description

广^ 号发射方法和装置 本申请要求于 2010 年 5 月 24 日提交中国专利局， 申请号为 201010182028.3 , 发明名称为"广播信号发射方法和装置"的中国专利申请 的优先权， 其全部内容通过引用结合在本申请中。 技术领域
本发明实施例涉及通信技术领域， 尤其涉及一种广播信号发射方法和装 置。 背景技术
无线传输技术的频率和功率资源有限， 而且受到信道衰落和干扰的影 响， 因此随着移动宽带和智能手机的普及， 传统以语音业务为主的蜂窝移 动通信网络已经很难承载移动互联网带来的爆发式数据流量。 从而使得能 够有效地提高频谱效率的多天线技术成为了下一代移动通信的主流技术。
小区制 （即蜂窝制） 是现今移动通信网络的基本实现方式。 基站是小 区的核心和实现移动通信的关键。 基站的信号发射可以分为两类： 专用信 道和公共信道， 其中， 专用信道承载单个移动终端所需信息， 属于基站和 终端之间的点对点通信； 公共信道承载小区中所有移动终端都需要的公共 信息， 例如： 长期演进 （Long Term Evolution; 简称： LTE)系统的广播信 道（ Broadcast Channel; 简称： BCH ) 、 寻呼信道（ Paging Channel; 简称： PCH )、用于多媒体广播组播业务（ Multimedia Broadcasting and Multicasting Service; 简称： MBMS ) 的组播信道（ Multicast Channel; 简称： MCH ) ， 这些公共信息需要同时传送到单个或多个蜂窝小区中的所有用户， 更适合 于以广播信号形式进行发射， 因此需要一种多天线系统中的广播信号发射 方法。
多天线系统的无线传输信道根据天线间距和反射环境不同， 可以分为 相关衰落信道和独立衰落信道。 若天线间距较小、 周围反射物比较少或者 角度扩展小时， 天线之间信道衰落相关性较大； 若天线间距较大， 且反射 比较充分、 角度扩展大时， 天线之间信道衰落相互独立。 在宏小区（即宏蜂 窝）中， 由于基站的多天线系统一般架设在较高的楼顶或者山顶上， 周围不 存在反射物， 只有天线间距大于十个波长以上时， 才能形成独立衰落。 现 有基站的多天线系统很多具有相关衰落信道， 例如， 智能天线系统或者移 动终端处于弱反射环境（如平原地带、 水面或者草原等等）的多进多出
( Multiple Input Multiple Output； 简称： MIMO ) 系统。
由于单天线发射信号具有天然的全向覆盖特性， 因此在现有的多天线 系统中， 可以选取多天线系统中的一个天线， 并对选取的天线配置高功率 放大器， 以实现广播信号的小区或扇区全面覆盖。
在实现本发明过程中， 发明人发现现有技术中至少存在如下问题： 功 率放大器成本较高、 功耗较大， 从而无法有效的实现小区或者扇区的全面 覆盖。 发明内容
本发明实施例提供一种广播信号发射方法和装置，实现了多天线系统中广 播信号在小区或者扇区的全面覆盖， 并有效的降低了经济成本。 本发明实施例提供一种广播信号发射方法， 包括：
对多天线系统中的天线阵列进行划分处理， 获取多个子阵列；
获取所述多个子阵列中每个子阵列的基本权向量，所述基本权向量使得每 个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方向图 在方向维度上互补；
根据所述每个基本权向量中的权系数，分别对所述每个基本权向量对应的 子阵列中的阵元上的发射信号进行加权处理得到第一信号，并应用所述阵元对 所述第一信号进行发射。
本发明实施例提供一种广播信号发射装置， 包括：
划分处理模块， 用于对多天线系统中的天线阵列进行划分处理， 获取多个 子阵列；
基本权向量获取模块，用于获取所述多个子阵列中每个子阵列的基本权向 得不同子阵列的波束方向图在方向维度上互补；
第一加权处理发射模块， 用于根据所述每个基本权向量中的权系数， 分别 对所述每个基本权向量对应的子阵列中的阵元上的发射信号进行加权处理得 到第一信号， 并应用所述阵元对所述第一信号进行发射。
本发明实施例的广播信号发射方法和装置，通过对多天线系统中的天线阵 列进行划分处理， 获取多个子阵列，再获取所述多个子阵列中每个子阵列的基 本权向量， 该基本权向量使得每个子阵列的波束峰均功率比低于预设门限， 并 且使得不同子阵列的波束方向图在方向维度上互补，根据每个基本权向量中的 权系数，分别对每个基本权向量对应的子阵列中的阵元上的发射信号进行加权 处理得到第一信号， 并应用阵元对该第一信号进行发射，从而使得每个子阵列 的波束方向图在方向维度上具有互补性，进而使得多个子阵列的平均方向图在 各个方向上的平均功率增益基本相等，保证了小区或者扇区内所有移动终端能 同时接收到相同质量的信号，实现了多天线系统中广播信号在小区或者扇区各 个方向上的全面覆盖， 并有效的降低了经济成本。 附图说明
为了更清楚地说明本发明实施例中的技术方案，下面将对实施例描述中所 需要使用的附图作一简单地介绍，显而易见地， 下面描述中的附图是本发明的 一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动性的前提下， 还可以根据这些附图获得其他的附图。
为了更清楚地说明本发明实施例或现有技术中的技术方案，下面将对实施 例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地， 下面描述 中的附图是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创 造性劳动性的前提下， 还可以根据这些附图获得其他的附图。
图 1为本发明广播信号发射方法一个实施例的流程图；
图 2为本发明广播信号发射方法另一个实施例的流程图；
图 3为图 2所示本发明广播信号发射方法实施例中信号发射的原理图； 图 4为八天线均匀线性阵列划分的结构示意图；
图 5为两个四天线均匀线性阵列划分的结构示意图；
图 6为八阵元双极化天线划分的结构示意图；
图 7为图 2所示本发明广播信号发射方法实施例中信号发射的原理图； 图 8为本发明广播信号发射方法又一个实施例的流程图； 图 9为图 8本发明广播信号发射方法实施中的基于 Alamouti编码和相位旋 转法的信号发射原理图；
图 10为图 8本发明广播信号发射方法实施中的基于 Alamouti编码和循环延 时法的信号发射原理图；
图 11为图 8所示本发明广播信号发射方法实施例中采用空时映射关系示意 图；
图 12为图 8所示本发明广播信号发射方法实施例中采用空频映射关系示意 图；
图 13为图 8所示本发明广播信号发射方法实施例中两个互补的波束方向图 和平均波束方向图；
图 14为图 8所示本发明广播信号发射方法实施例中更新后的两个互补的波 束方向图和平均波束方向图；
图 15为本发明广播信号发射方法又一个实施例的流程图；
图 16为本发明广播信号发射方法实施例中基于时间或频率切换发射分集 的信号发射原理图；
图 17为图 15本发明广播信号发射方法实施例中互补的波束方向图和平均 波束方向图；
图 18为本发明广播信号发射装置的一个实施例的结构示意图；
图 19为本发明广播信号发射装置的另一个实施例的结构示意图； 图 20为本发明广播信号发射装置的又一个实施例的结构示意图； 图 21为本发明广播信号发射装置的又一个实施例的结构示意图。 具体实施方式
为使本发明实施例的目的、技术方案和优点更加清楚， 下面将结合本发明 实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然， 所描述的实施例是本发明一部分实施例， 而不是全部的实施例。基于本发明中 的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其 他实施例， 都属于本发明保护的范围。
图 1为本发明广播信号发射方法一个实施例的流程图，如图 1所示，本实 施例的方法可以包括：
步骤 101、 对多天线系统中的天线阵列进行划分处理， 获取多个子阵列。 在本实施例中， 多天线系统可以为单个天线阵列、 多个天线阵列或极化天 线阵列等。对多天线系统中的天线阵列进行划分处理，获取多个子阵列的实现 方式可以采用但不限于如下的实现方式：
对于单个天线阵列而言，对单个天线阵列进行划分处理， 可以获取多个间 隔较近的子阵列。 其中， 每个子阵列可以包括至少一个阵元。
对于多个天线阵列而言，对多个天线阵列进行划分处理， 可以获取间隔较 远的多个子阵列； 另外， 还可以获取不同极化方式的子阵列， 其中， 每个子阵 列的极化方式相同。在本实施例中， 并不对多天线系统中的天线阵列具体采用 的划分处理方式进行限定，本领域技术人员可以根据需要采用任意划分处理方 式。 同时， 天线阵列可以为线性阵、 圓阵、 方阵， 以及任意其它阵形的天线阵 歹 ij ; 天线阵元的间隔一般为半个波长， 同时也可以是其它能保持信道相关性的 阵元间隔， 如两个波长， 甚至十个波长等等。
步骤 102、 获取多个子阵列中每个子阵列的基本权向量， 该基本权向量使 得每个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方 向图在方向维度上互补。
步骤 103、 根据每个基本权向量中的权系数， 分别对每个基本权向量对应 的子阵列的阵元上的发射信号进行加权处理得到第一信号，并应用阵元对第一 信号进行发射。
在本实施例中，每个基本权向量可以包括多个权系数、每个子阵列可以包 括多个阵元，并且每个子阵列对应的基本权向量的权系数数量与该子阵列的阵 元数量相等。根据每个子阵列对应的基本权向量的权系数， 分别对该子阵列的 阵元上的发射信号进行加权处理得到第一信号，即对每个子阵列的阵元上的发 射信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射，从而使 得每个子阵列的波束方向图覆盖角度宽、 峰均功率比低， 同时， 不同的子阵列 的波束方向图在方向维度上具有互补性。
举例来说，当根据多个子阵列中的一个子阵列对应的基本权向量中的权系 数，对该子阵列的阵元上的发射信号进行加权处理， 并应用该子阵列的阵元对 加权处理后的信号进行发射，该子阵列的波束方向图可能在一些特定方向上增 益很低，甚至为零增益时， 而根据该多个子阵列中的另一个子阵列对应的基本 权向量的权系数，对另一个子阵列的阵元上的发射信号进行加权处理， 并应用 该子阵列的阵元对加权处理后的信号进行发射，使得该子阵列的波束方向图在 这些特定方向上具有较高的增益，从而使得多个子阵列的波束方向图的平均波 束方向图在该特定方向上的增益波动较小。
在本实施例中， 当一个子阵列的波束方向图在特定方向上增益艮低时， 则 在该特定方向上的移动终端在该时刻接收到的该子阵列发射的信号可能较弱。 但是当其它子阵列的波束方向图在该特定方向上具有较高的增益时，使得该特 定方向上的移动终端在该时刻接收到的其他子阵列发射的信号较强，可以通过 信道编码或分集等技术，补偿多个子阵列中的一个子阵列发射信号较弱所带来 的性能损失， 进而保证该特定方向上的移动终端能够正常接收广播信号。
在本实施例中，通过对多天线系统中的天线阵列进行划分处理， 获取多个 子阵列，再获取多个子阵列中每个子阵列的基本权向量， 该基本权向量使得每 个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方向图 在方向维度上互补， 并根据每个基本权向量的权系数，对每个子阵列的阵元上 的发射信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射， 由 于每个子阵列的波束方向图覆盖角度宽、峰均功率比低， 并且全部子阵列的波 束方向图的平均波束方向图在全小区或扇区中各个方向上的增益差异等于零 或小于预定的数值，从而使得整个多天线系统在各个方向上的发射功率基本相 等， 进而实现了多天线系统中广播信号在小区或扇区中各个方向上的全面覆 盖， 并有效的降低了经济成本。
图 2为本发明广播信号发射方法另一个实施例的流程图，图 3为图 2所示 本发明广播信号发射方法实施例中信号发射的原理图，如图 2和图 3所示， 本 实施例的方法可以包括：
步骤 201、 对广播信号进行信道编码处理、 星座调制处理以及空时频编码 处理， 获取多路码流信号。
在本实施例中， 可以对广播信号进行信道编码处理和星座调制处理， 获取 多路符号流。 因此，每个子阵列的阵元上的发射信号可以为码流信号或者符号 流。 举例来说，广播信号具体为多媒体广播组播业务（ Multimedia Broadcasting and Multicasting Service; 简称： MBMS )和小区公共信道信号的比特流。 在本 实施例中，对广播信号进行空时频编码处理， 获取多路码流信号的一种具体实 现方式为：先对多媒体广播组播业务和小区公共信道信号的比特流分别进行信 道编码处理、交织处理和星座映射处理，获取（复）符号流。然后将获取的（复） 符号流进行空时频编码处理， 获取多路码流信号，码流的数量与子阵列的数量 相等， 并——对应。
或者，多媒体广播组播业务和小区公共控制信号的比特流可以分别进行信 道编码处理、 交织处理和星座映射处理， 获取单路（复）符号流， 将该符号流 发送到所述的多个子阵列的每个子阵列， 即每个子阵列的发射信号相同。
在本实施例中， 以对广播信号进行空时频编码处理， 获取多路码流信号为 例， 详细介绍本实施例的技术方案。 空时频编码方法可以采用但不限于 Alamouti编码、 空时分组码 （ Space-Time Block Coding; 简称： STBC ) 、 空 频分组码 （ Space-Frequency Block Coding; 简称： SFBC ) 、 时间切换发射分 集（Time Switched Transmit Diversity; 简称： TSTD ) 和频率切换发射分集 ( Frequency Switched Transmit Diversity; 简称： FSTD ) 。 本实施例并不对具 体采用的空时频编码方法进行限定，本领域技术人员可以根据需要采用以上任 意空时频编码方法或其组合或其它可能的空时频编码方法。
步骤 202、 对单个天线阵列进行逻辑划分处理， 获取多个子阵列。
在本实施例中， 以多天线系统为单个天线阵列为例，详细介绍本实施例的 技术方案， 对单个天线阵列进行逻辑划分处理， 获取多个子阵列， 每个子阵列 中包含至少一个阵元。 每个阵元只能被所有子阵列选取一次， 换言之， 任意两 个不同的子阵列不包含相同的阵元。 同时， 划分处理之前的单个天线阵列的每 个阵元都被选取一次，即所有子阵列的阵元之和等于划分处理之前的单个天线 阵列中所有阵元。
举例来说， 图 4为八天线均匀线性阵列划分的结构示意图， 如图 4所示， 对单个天线阵列进行逻辑划分处理，获取的两个子阵列， 分别为子阵列 1和子 阵歹 'j 2， 每个子阵列包含四个阵元。 本实施例并不对阵元空间排列方式、 阵元 数量、 阵元间距进行限定， 本领域技术人员可以根据需要进行设置。
本实施例中的步骤 202根据天线阵列的类型不同，还可以采用其它实现方 式：
一、 当多天线系统为多个天线阵列时， 步骤 202的一种实现方式可以为： 对多个天线阵列按照间隔距离进行划分处理， 获取多个子阵列。
举例来说， 多天线系统包含多个间隔较远的天线阵列， 图 5为两个四天线 均匀线性阵列划分的结构示意图， 如图 4所示， 获取的两个子阵列， 分别为天 线阵列 1和天线阵列 2， 每个子阵列包含四个阵元， 每个阵元之间的距离表示 为 ， 一般为半个波长， 子阵列之间的距离 ^大于 ， 两个四天线均匀线性阵 列可以为同一个基站上物理位置较远的两个天线阵列，也可以是安装在两个不 同基站上的天线阵列。 本实施例并不对阵元空间排列方式、 阵元数量、 阵元间 距和不同子阵列间的距离进行限定， 本领域技术人员可以根据需要进行设置。
二、 当多天线系统为极化天线阵列时， 步骤 202的一种实现方式可以为： 对极化天线阵列按照极化方向进行划分处理， 获取多个子阵列。
举例来说， 多天线系统为极化天线阵列， 图 6为八阵元双极化天线划分的 结构示意图， 如图 6所示， 获取两个子阵列， 每个子阵列包含四个阵元， 一个 子阵列中的四个阵元为水平极化方式；另一个子阵列中的四个阵元为垂直极化 方式。 本实施例并不对阵元空间排列方式、 阵元数量、 阵元间距进行限定， 本 领域技术人员可以根据需要进行设置。值得注意的是，每个子阵列中的所有阵 元极化方式相同， 以具有相关的信道衰落。
本发明适用的天线阵列可以为线性阵、 圓阵、 方阵， 以及任意其它阵形的 天线阵列； 天线阵元的间隔一般为半个波长， 同时也可以是其它能保持信道相 关性的阵元间隔， 如两个波长， 甚至十个波长等等。
步骤 203、 获取多个子阵列中每个子阵列的基本权向量， 该基本权向量使 得每个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方 向图在方向维度上互补。
本实施例中， 广播信号发射装置获取与子阵列对应的基本权向量时， 可以 采用计算机遍历选取的方式， 而且，本实施例中获取的基本权向量中的权系数 具有相同的模值， 因此，相同模值的权系数可以使得天线阵列的所有阵元等功 率发射， 从而可以提高功率放大器的效率。
本实施例中获取基本权向量的方法灵活简单，举例来说， 一般获取基本权 向量的实现方式为： 假设在复数坐标的单位圓上选取了 N个模值为 1的复数 作为可用权系数， 天线阵列的阵元数量为 ^1， 则可能获取的 M维权向量的组 合有 NM种。 假设， N=8 , M=8 , 则需要遍历的权向量数量共有 88 = 16777216。 具体的， 为了进一步提供选取精度，还可以选取 16个或 32个单位圓上的复数 作为可用权系数， 或者天线阵元的数量增加， 例如 12或 16阵元的阵列， 每个 遍历的权向量都需要单独进行波束方向图计算、峰均功率比计算等，其计算相 对复杂。 相比之下， 在本实施例中， 由于采用步骤 202来实现对天线阵列进行划分 处理， 来获取多个子阵列， 使得每个子阵列中的阵元数量较少， 举例来说， 例 如天线阵列为八天线阵列，对该阵列按照四阵元进行划分处理，每个子阵列中 的阵元数量为 4个， 那么需要遍历的权向量的数量共有 84 = 4096种； 对该八天 线阵列按照两阵元进行划分处理，每个子阵列中的阵元数量为 2个， 那么需要 遍历的权向量的数量共有 82 = 64， 因此， 本实施例中的获取基本权向量的方法 更为简单和灵活。
步骤 204、 根据每个基本权向量中的权系数， 分别对每个子阵列中的阵元 上的码流信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射。
在本实施例中， 每个子阵列中包含的阵元数可以相同， 也可以不相同。 需 要说明的是，每个基本权向量包含多个权系数，每个权向量包括的权系数的数 量与每个基本权向量对应的子阵列所包含的阵元的数量相同。图 7为图 2所示 本发明广播信号发射方法实施例中信号发射的原理图，如图 7所示， 以子阵列 的阵元数为 M为例来说，广播信号发射装置可以获取与子阵列对应的基本权 向量， 该基本权向量可以使子阵列根据对应的基本权向量，对接收的一路码流 信号进行加权处理， 需要说明的是， 该基本权向量对应的波束峰均功率比低于 预设门限， 并且不同子阵列的波束方向图在方向维度上具有互补性， 进而使得 全部子阵列的平均波束方向图趋近于单天线产生的全向波束。
步骤 205、 在时间维度或频率维度上对所述每个基本权向量进行更新处 理， 分别获取更新后的权向量。 一、 相位旋转方法。 从 [0 2; ^上随机地获取一个相位值 Δ ， 每个子阵 列对应的基本权向量表示为 W = [H¾ w2 … wMf , wm (w = l,' " ,M)表示权系 数， 为大于 1的正整数。
应用公式：
wNew = diag[\
「 ，r ( 1 )
= w w2e^ w,eJ2^ … wMeJ{M-l)^ 对每个子阵列对应的基本权向量进行更新处理，得到每个子阵列对应的更 新后的权向量。 其中： ν^表示更新后的权向量， j 为虚数单位（ / = -1 ) ， diag[ ]表示由； ^至 x„构成的对角阵。
二、 随机变量方法。
具体的， 当多天线系统的天线阵列进行划分处理， 获取的子阵列包括 两个阵元时， 应用基本权向量对子阵列进行加权处理， 具有两个特征： 在 模相等的复数集合中， 任意选取两个复数作为权系数， （ 1 )无论权系数如 何选取， 其波束方向图的峰均功率比 （或峰值）保持不变； （2 ) 当其中的 一个权系数不变， 对另一个权系数取负值时， 对应的波束方向图与两个权 系数均不取负值时的波束方向图互补。
基于上述两个特征， 可以用随机的方法获取和更新基本权向量。 举例 来说， 对于基本权向量的选取方式为， 随机选取两个权系数， 构成一个子 阵列对应的第一基本权向量， 其中， 两个权系数模均等于 1， 有 |Wl| = |w2| = i ; 对第一基本权向量中的一个权系数进行取负值处理， 例如： 对第一基本权 向量的第二权系数取负值处理，获取另一个子阵列对应的第二基本权向量。 具体为： Wl = [Wl W2f和 w2 = [Wl - W2 f。 需要获取更新后的权向量时， 重新 随机选取两个权系数， 按照上述方法便可以获取更新后的两个权向量， 并 图互补。 数， 分别对每个子阵列的阵元上的发射信号进行加权处理得到第二信号， 并应 用阵元对该第二信号进行发射。
在本实施例中，每个子阵列固定于一个基本波束方向图， 并且不同子阵列 的多个波束方向图互补，但是由于波束方向图的数量很少， 因此多天线系统的 发射功率在各个方向上可能会有差异。 因此， 可以在时间维度或频率维度上对 每个子阵列对应的基本权向量进行更新处理，以使全部子阵列的平均波束方向 图具有更好的等向性， 进而实现了小区或扇区的全面覆盖， 并有效的降低了经 济成本。
在本实施例中， 为了有效的实现小区或扇区的全面覆盖，还可以包括但不 限于以下几种实现方式：
一、 延时方法： 在每个阵元上， 根据权系数对发射信号进行加权处理 得到第一信号， 并对第一信号进行延时处理得到第二信号， 其中， 各阵元 上的延时量不相同， 最大延时量小于预设值。 例如， 采用线性增量延时， 第一阵元上不作延时， 第二阵元上延时 Δτ， 第三阵元上延时 2Δτ， 依次递 增， 直到最后一个阵元， 第 Ν阵元上延时（N- l)Ar。 并应用各个阵元对第二 信号进行发射。
二、 循环延时方法： 具体的， 由于宽带无线通信系统可采用正交频 分复用 ( Orthogonal Frequency Division Multiplexing ; 简称： OFDM )调 制， 根据离散傅里叶变换（ Digital Fourier Transform; 简称： DFT )性质， 时域的循环延时， 对应频域符号的相位旋转。 具体的， 每个子阵列上的发 射信号先经过 OFDM调制， 形成 OFDM符号， 该子阵列对应基本权向量中 的第一权系数加权该 OFDM符号， 并由该子阵列的第一阵元发射； 第二权 系数加权该 OFDM符号， 作循环延时， 并由该子阵列的第二阵元发射； 依 此类推， 直到基本权向量的最后一个权系数加权该 OFDM符号， 作循环延 时， 并由该子阵列的最后一个阵元发射； 需要说明的是， 同一个子阵列上 不同阵元的循环延时大小不相同。
在本实施例中， 通过对天线阵列进行划分处理， 获取多个子阵列， 为每 个子阵列选取一个基本权向量， 根据每个子阵列的基本权向量， 对每个子 阵列的阵元上的码流信号进行加权处理， 使得每个子阵列的波束方向图覆 盖角度宽、 峰均功率比低于预设门限， 并且不同子阵列形成的波束方向图 在方向维度上具有互补性， 全部子阵列形成的所有波束方向图的平均波束 方向图在各个方向上的差异等于零或小于预设值， 同时， 通过在时间维度 或频率维度上对基本权向量进行更新处理，获取时间分集或频率分集增益， 进一步增强了小区或者扇区全面覆盖性能， 并有效的降低了经济成本。
下面采用几个具体的实施例对本发明广播信号发射方法的技术方案进 行详细说明。
图 8为本发明广播信号发射方法又一个实施例的流程图，图 9为图 8本发 明广播信号发射方法实施中的基于 Alamouti编码和相位旋转法的信号发射原 理图； 图 10为图 8本发明广播信号发射方法实施中的基于 Alamouti编码和循 环延时法的信号发射原理图， 如图 8、 图 9和图 10所示， 本实施例的方法可 以包括：
步骤 301、 对广播信号采用信道编码处理、 星座调制处理以及 Alamouti 编码处理， 获取两路空时频码流。 举例来说，广播信号具体为多媒体广播组播业务和小区公共控制信号的比 特流。 在本实施例中， 广播信号经过信道编码和星座映射后， 获取（复）符号 流， 分别以（复）符号流中的每两个符号为一组， 并对每两个符号为一组的符 号流进行空时频编码， 产生两路空时频码流。 具体的， Alamouti编码有两种等 价形式， 编码矩阵如公式（2 )和公式（3 )所示， 其中， 编码矩阵行对应空间 域的一根天线或本发明中的一个子阵列， 编码矩阵列对应时间域的 OFDM符 号周期， 或频域的 OFDM子载波。 需要说明的是， 该空时频码流即为码流信 号。
Figure imgf000018_0001
步骤 302、 对获取的两路空时频码流进行宽带信号调制；
举例来说， 对于窄带通信系统， 空时频码流中的符号可按照顺序直接发 射， 可以不进行本步骤的处理； 而对于宽带通信系统中， 需要进行码分多址 ( Code Division Multiple Access,简称： CDMA )调制或正交频分复用（ OFDM ) 调制， 本实施例仅以 OFDM调制为例进行说明， 本发明中的其它实施例中的 OFDM调制均可由 CDMA调制进行替代。首先对空时频码流进行子载波映射， 从而为每个空时频码流中的符号分配合适的时频资源块， 再对分配后的空时 频码流中的符号进行 OFDM调制， 即进行逆快速傅立叶变换（ IFFT )并插入 循环前缀（CP )。 其中， 子载波映射可以有空时映射和空频映射两种方法。 图 11为图 8所示本发明广播信号发射方法实施例中采用空时映射关系示意图， 图 12为图 8所示本发明广播信号发射方法实施例中采用空频映射关系示意图。 如图 11所示， 当子载波映射为空时映射时， Alamouti编码矩阵的第一路 空时码流， 放置到第一子阵列上两个连续 OFDM 符号的相同子载波上， Alamouti编码矩阵的第二路空时码流， 放置到第二子阵列上两个连续 OFDM 符号的相同子载波上， 并且与第一子阵列上的子载波位置相同。
如图 12所示， 当子载波映射为空频映射时， Alamouti编码矩阵的第一空 频码流， 放置到第一子阵列两个连续的子载波上， Alamouti编码矩阵的第二 空频码流， 放置到第二子阵列上两个连续的子载波上， 并且与第一子阵列上 的子载波位置相同。 在本实施例中， 以空时映射为例， 对本实施例的技术方案 进行详细介绍。
步骤 303、 对多天线系统进行划分处理， 获取两个子阵列， 每个子阵 列用于发射一路空时频码流。
在本实施例中， 由于采用 Alamouti编码后， 获取两路空时频码流， 因此 把多天线系统进行划分处理， 获取两个子阵列。 举例来说， 以图 6中八天线的 两个子阵列具有不同的极化方式， 可以认为信道衰落相互独立，相同子阵列内 的阵元极化方式相同， 且间隔较近， 可以获取信道相关性。 根据两个子阵列的 方向向量， 分别选取基本权向量， 并对两路空时频码流分别进行加权处理后发 射。
为了更具体地说明本发明，再以图 4中所示的八天线半波长间隔的均匀线 性阵列 （Uniform Linear Array; 简称： ULA )为例， 详细介绍本实施例的技术 方案。本实施例并不对具体采用的天线阵列进行限定， 本领域技术人员可以根 据需要采用任何天线阵形，任何天线数量以及其它阵元间隔的天线阵列。具体 的， 该天线阵列以四个相邻阵元为一子阵列进行划分处理， 获取各有四个相邻 阵元的两个子阵列。 由于发射的空时频码流不同， 因此两个子阵列发射的信号 不会发生干涉效应，该天线阵列的方向向量可以分解成两个四维的独立方向向 量， 以第一阵元为参考点， 则 ULA的方向向量为：
" _ [1 两个子阵列均以 ULA的第一阵元为参考点，则两个子阵列的方向向量分别为：
Figure imgf000020_0001
其中， 表示方向角度， （.f表示向量的转置。
步骤 304、 获取两个子阵列中每个子阵列的基本权向量， 该基本权向 的波束方向图在方向维度上互补。
在本实施例中， 广播信号发射装置可以获取与两个子阵列分别对应的 基本权向量， 两个基本权向量可以使得对应子阵列的波束方向图的覆盖角 度宽、 峰均功率比低， 并且两个波束方向图互补。 举例来说， 获取使得波 束方向图覆盖角度宽、 峰均功率比低和具有互补性时对应的两个基本权向 量：
w1 =[l 0.7071 - 0.7071J j -0.7071 - 0.7071^]^ ( 5 ) w2 = [l -0.7071 + 0.707 j 0.7071 + 0.7071^/]^ ( 6 ) 其中， Wl和 ^表示基本权向量， （.f表示向量的共轭转置。
步骤 305、 根据每个基本权向量中的权系数， 分别对每个基本权向量 对应的子阵列中的阵元上的空时频码流进行加权处理得到第一信号， 并应 用阵元对第一信号进行发射。
两个子阵列上的两路空时频码流分别由两个基本权向量中的权系数进 行加权处理得到第一信号， 并应用阵元对第一信号进行发射， 子阵列的波 束方向图可以公式 （7 )获取：
g(0) = wHa(0) ( 7 ) 其中， 表示波束方向图；
图 13为图 8所示本发明广播信号发射方法实施例中两个互补的波束方向 图和平均波束方向图， 如图 13所示， 两个子阵列的波束方向图分别由划线 和点线表示， 通过图 13可知， 两个波束具有良好的互补性： 波束 1的高增 益区， 如角度30"、90 15(7、270'处， 正好补偿波束 2的低增益区； 反之， 波束 1的低增益区， 如图中05、180'、210 330'处， 波束 2恰好具有高增益。 同时， 由于两个波束方向图的平均波束方向图恰好为圓形（如图 13中实线所示）， 因此能完成全向覆盖。
步骤 306、 使用相位旋转方法在时间维度或频率维度上对基本权向量 进行更新处理， 获取更新后的权向量。
步骤 307、 在不同的时间或频率上根据每个更新后的权向量的权系数， 分别对每个子阵列的阵元上的发射信号进行加权处理得到第二信号， 并应 用阵元对第二信号进行发射。
如图 13所示， 两个基本权向量的平均波束方向图能够完成小区的全向 覆盖。 但是当天线阵列中阵元数量较多时， 由于计算复杂度过高， 很难获 取完全互补的两个基本权向量； 或由于天线的物理位置误差、 馈线的相位 误差等等因素造成的天线通道的相位误差的存在， 例如， 在实际工程中， 应用基本权向量对子阵列的发射信号进行加权处理获取的波束方向图与理 论计算获取的波束方向图可能存在较大偏差。 为了达到更好的覆盖性能并 提高鲁棒性， 可以使用相位旋转法， 在时间维度或频率维度上对基本权向 量进行更新处理， 从而使得子阵列的平均波束方向图具有良好的等向性。 举例来说， 按照图 2中使用相位旋转法， 随机获取相位值 Δ ， 假设获取的 △ = 45 ， 根据公式 （ 1 ) ， 获得两个更新后的权向量：
= [i 1 -1 1]" 8 )
Figure imgf000022_0001
其中， v3和 v4表示更新后的权向量。
图 14为图 8所示本发明广播信号发射方法实施例中更新后的两个互补的 波束方向图和平均波束方向图， 如图 14所示， 应用两个更新后的权向量对 子阵列上的空时频码流进行加权处理， 获取与两个子阵列中的每个子阵列 分别对应的更新后的波束方向图与应用基本权向量对子阵列上的空时频码 图有相同的峰均功率比和峰值， 同时， 更新后的两个波束方向图仍保持良 好的互补性。
在本实施例中， 通过采用 Alamouti编码对发射的广播信号进行编码处理， 以获取两路空时频码流，从而相应的对天线阵列进行划分处理，获取两子阵列， 为每个子阵列选取基本权向量，根据两个基本权向量，对子阵列的阵元上的码 流信号进行加权处理， 获取的波束方向图具有方向维度上的互补性，其发射功 率具有等向性。 同时，通过采用相位旋转方法在时间维度或频率维度上对基本 权向量不断进行更新处理， 进一步提高小区的全向覆盖性能，保证了小区内所 有移动终端能同时接收到同等质量的信号， 并有效的降低了经济成本。
进一步的， 该方法还可以采用延时方法得到第二信号。 举例来说， 在宽带 无线通信中， 子阵列上的空时频码流在进行加权处理前， 可采用 CDMA调制 处理， 获取的 CDMA扩频信号在子阵列的各阵元上分别由基本权向量的对应 权系数进行加权， 并作延时后发射。 例如， 采用线性增量延时， 第一阵元上不 作延时， 第二阵元上延时一个码片 （Chip ), 第三阵元上延时两个码片， 依次 递增， 直到最后一个阵元， 即第 N阵元上延时 N-1个码片。
在采用 OFDM调制的宽带通信系统中， 除了上述的延时法外， 该方法还 可以采用循环延时方法得到第二信号。在本实施例， 天线阵列为八天线的均匀 线性阵列， 并且该天线阵列以四个相邻阵元为一子阵列进行划分处理， 获取各 有四个相邻阵元的两个子阵列， 其中， 第一子阵列发射其中一路空时频码流， 在加权处理前， 对该码流进行 OFDM调制， 获取 OFDM符号。 该第一子阵列 对应的基本权向量中第一权系数加权 OFDM符号得到第二信号， 不作延时， 由第一阵元对第二信号进行发射； 第二权系数加权 OFDM符号， 并作循环延 时处理得到第二信号， 由第二阵元对第二信号进行发射； 第三权系数加权 OFDM符号， 并作循环延时处理得到第二信号， 由第三阵元对第二信号进行 发射； 第四权系数加权 OFDM符号， 并作循环延时处理得到第二信号， 由第 四阵元对第二信号进行发射。 第二子阵列发射两路空时频码流中的另一路，循 环延时方法与第一子阵列相同。 举例来说， 根据离散傅立叶变换（DFT )的性 质，在时域做循环延时， 等价于在离散傅立叶变换对应的频域符号上乘上相位 因子， 如公式（ 10 )所示：
Figure imgf000024_0001
其中， 傅立叶变换因子为 = e w， 序列 S(")、 ("_ 、 SW , 分别表 示时域序列，循环延时 后的时域序列，以及离散傅立叶变换对应的频域序列。 由上式可知， 对时域序列做循环延时 ， 等价于在频域序列上乘上相位因子 '， 可见该相位因子与频域序号 有关。 设子阵列上的空时频码流序列为 s^， 经过 OFDM调制后， 获取 OFDM符号 ， 子阵列上四个阵元分别循 环延时 ， ^1，2，3， 则对应的 OFDM调制前频域序列为1 ^[^^Μ'， 等价于对子 载波上的信号进行加权， 加权因子为 ^ 。 子阵列进行加权处理， 总的权向量 则是基本权向量和循环延时形成的相位加权因子的乘积：
Figure imgf000024_0002
总权向量是关于子载波序号 的变量， 因此每个子载波上的权向量和加权 处理图不同。 波束方向图与子载波位置相关， 表示为：
gk(0) ^ w^a(0), k = 0, 1, 2, N_l ( 12 )
Ν表示 OFDM中 DFT长度， 其取值一般较大， 如 512、 1024等， 因此可 以产生足够多的不同的波束方向图， 其平均波束方向图具有等向性。
图 15为本发明广播信号发射方法又一个实施例的流程图，图 16为本发明 广播信号发射方法实施例中基于时间切换发射分集（TSTD )或频率切换发射 分集（FSTD ) 的信号发射示意图， 如图 15和 16所示， 本实施例的方法可以 包括：
步骤 401、 对广播信号采用空时分组编码（Space-Time Block Coding; 以 下简称： STBC )并结合时间切换发射分集（ Time Switched Transmit Diversity; 以下简称： TSTD ) ， 或者采用空频分组编码（ Space-Frequency Block Coding; 以下简称： SFBC ) 并结合频率切换发射分集 （Frequency Switched Transmit Diversity; 以下简称： FSTD )进行编码处理， 获取四路空时频码流。
举例来说，广播信号具体为多媒体广播组播业务和小区公共控制信号的比 特流。 在本实施例中， 广播信号经过信道编码和星座映射后， 获取（复）符号 流， 分别以（复）符号流中的每四个符号为一组进行空时频编码， 产生四路 时频码流， 编码矩阵如下式所示：
Figure imgf000025_0001
获取的编码矩阵的每行对应一个子阵列，编码矩阵的每列对应时域的符号 发射周期， 或频域的子载波。
步骤 402、 对获取的四路空时频码流进行宽带信号调制；
举例来说，对于窄带通信系统，空时频码流中的符号可按照顺序直接发射， 可以不进行本步骤的处理； 而对于宽带通信系统中， 需要进行码分多址 ( CDMA )调制或正交频分复用 （OFDM )调制， 本实施例仅以 OFDM调制 为例进行说明。 首先对空时频码流进行子载波映射， 空时频码流中的符号可以 采用不同的子载波映射方式： （1 )空频映射： 每路空时频码流上的四个调制符 号放置在对应子阵列上的四个连续子载波上； （2 )空时映射： 每路空时频码流 上的四个调制符号放置在对应子阵列上四个连续 OFDM 符号的相同子载波 上；（3 )空时频映射：每路空时频码流上的四个调制符号放置在对应子阵列上、 连续两个 OFDM符号上的连续两个子载波上。才艮据 OFDM符号时间频率资源 的相关性， 以上三种子载波映射方式等价。 对经过映射后的空时频码流进行 OFDM调制处理， 即对分块数据进行逆快速傅立叶变换（IFFT )， 然后插入循 环前缀（ CP )。
步骤 403、 对多天线系统进行划分处理， 获取四个子阵列。
在本实施例中， 由于采用 TSTD或 FSTD进行编码处理后， 获取四路空时 频码流。 因此把多天线系统进行划分处理， 获取四个子阵列， 每个子阵列选取 一个基本权向量， 以使得波束方向图覆盖角度宽、 峰均比低， 并且四个子阵列 产生的四个波束方向图的平均波束方向图在各个方向上的增益相等或差异小 于预设值。 以半波长为间隔均匀分布的八阵元 ULA为例， 详细介绍本实施例 的技术方案。本实施例并不对具体采用的天线阵列进行限定， 本领域技术人员 可以根据需要采用任何天线阵形， 任何天线数量以及其它阵元间隔的天线阵 歹 具体的， 该天线阵列以两个相邻阵元为一子阵列进行划分处理， 获取各有 两个相邻阵元的四个子阵列，该天线阵列的方向向量可以分解成四个二维的方 向向量， 以 ULA的第一阵元为参考点， 四个方向向量如公式（ 14 )所示：
"^) = [1 e
Figure imgf000026_0001
aA (0) = [e 步骤 404、 获取多个子阵列中每个子阵列的基本权向量， 该基本权向
， 并且使得不同子阵列 的波束方向图在方向维度上互补,
在本实施例中， 获取四个的基本权向量，使得四个子阵列的波束方向图. 盖角度宽、峰均比低， 并且四个子阵列的波束方向图的平均波束方向图在小区 /扇区各个方向上的增益差异等于零或小于预设门限。 举例来说， 如下四个基 本权向量：
Figure imgf000027_0001
图 17为图 15本发明广播信号发射方法实施例中基本权向量的波束方 向图和平均波束方向图， 如图 17所示， 平均波束方向图在各个方向上的增 益相等。
步骤 405、 根据基本权向量的各权系数， 对每个子阵列对应阵元上的 码流信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射。
步骤 406、 使用相位旋转方法对基本权向量进行更新处理， 获取更新 后的权向量。
步骤 407、 在不同的时间或频率上根据每个更新后的权向量的权系数， 分别对每个子阵列的阵元上的发射信号进行加权处理得到第二信号， 并应 用阵元对第二信号进行发射。
每个子阵列天线阵元数量较多时， 选取完全互补的波束方向图对应的 基本权向量的计算量过大； 或由于天线物理位置、 不同阵元的馈线的相位 误差等等工程因素， 造成实际的波束方向图与理论计算结果有较大偏差， 多天线系统的发射功率在不同的方向上存在一定的差异。 为了提高覆盖性 能和鲁棒性， 可以使用相位旋转法， 在时间维度或频率维度上对基本权向 量进行更新处理， 获取时间或频率分集， 使得发射功率在各方向相等。 本 步骤 406采用的相位旋转方法在时间维度或频率维度上对基本权向量进行 更新处理的实现方式与图 7中的步骤 306采用的相位旋转方法在时间维度 或频率维度上对基本权向量进行更新处理的实现方式类似。
进一步的，步骤 406还可以为使用随机变量方法在时间维度或频率维度上 对基本权向量进行更新处理，在不同的时间或频率资源上使用更新后的权向量 对发射信号进行加权处理， 获取时间或频率分集。
具体的， 随机地在复数坐标的单位圓上选取四个权系数， 假设所选的 权系数分别为 ±1和 ±， 构造出如下四个更新后的权向量：
Wl =[i， - if， w2
Figure imgf000028_0001
其波束图如图所示， 波束 两两互补。 需要更新权向量时， 再随机地从复数坐标的单位圓上选取四个 权系数， 按照前述方法构成四个新的权向量。
在本实施例中， 通过采用 TSTD或 FSTD对广播信号进行编码处理， 以获 取四路空时频码流， 从而相应的对天线阵列进行划分处理， 获取四个子阵列， 并选取四个波束方向图互补的基本权向量，每个子阵列的阵元选取基本权向量 中对应权系数， 对空时频码流进行加权并发射。 从而更加有效的实现小区或扇区的全面覆盖。
举例来说， 每个子阵列选取一个基本权向量， 加权处理后使得子阵列 的波束方向图互补。 四路空时频码流中的第一路空时频码流经过 OFDM调 制， 获取 OFDM符号，对应基本权向量的第一权系数加权该 OFDM符号得 到第二信号， 不作延时处理， 由子阵列的第一阵元对第二信号进行发射； 第二权系数加权该 OFDM符号， 并作循环延时处理， 由第二阵元对第二信 号进行发射。 第二子阵列发射四路空时频码流中的第二路空时频码流， 循 环延时方法与第一子阵列相同。 第三子阵列和第四子阵列的发射方法与第 一阵列的方法相同， 在此不再赘述。 本实施例采用的循环延时方法的实现 方式与图 8所示的循环延时方法的实现方式类似。
图 18 为本发明广播信号发射装置的一个实施例的结构示意图， 如图 18 所示， 本实施例的广播信号发射装置包括： 划分处理模块 11、 基本权向量获 耳4莫块 12和第一加权处理发射模块 13。 其中， 划分处理模块 11用于对多天 线系统中的天线阵列进行划分处理， 获取多个子阵列； 基本权向量获取模块 12 用于获取多个子阵列中每个子阵列的基本权向量， 基本权向量使得每个子 阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方向图在方 向维度上互补； 第一加权处理发射模块 13用于根据每个基本权向量中的权系 数，分别对每个基本权向量对应的子阵列中的阵元上的发射信号进行加权处理 得到第一信号， 并应用阵元对第一信号进行发射。
本实施例的广播信号发射装置可以用于执行图 1 所示方法实施例的技术 方案， 其实现原理类似， 此处不再赘述。
在本实施例中，通过对多天线系统中的天线阵列进行划分处理， 获取多个 子阵列， 并获取多个子阵列中每个子阵列的基本权向量， 该基本权向量使得每 个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方向图 在方向维度上互补，再根据每个基本权向量的权系数，对每个子阵列的阵元上 的发射信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射， 由 于每个子阵列的波束方向图覆盖角度宽、峰均功率比低， 并且全部子阵列的波 束方向图的平均波束方向图在全小区或扇区中各个方向上的增益差异等于零 或小于预定的数值， 从而使得整个多天线系统在各个方向上的发射功率相等， 进而实现了多天线系统中广播信号在小区或扇区中各个方向上的全面覆盖，并 有效的降低了经济成本。
图 19为本发明广播信号发射装置的另一个实施例的结构示意图， 如图 19 所示， 本实施例的广播信号发射装置包括： 第一编码处理模块 21、 划分处理 模块 22、 基本权向量获取模块 23、 第一加权处理发射模 24、 更新模块 25和 第二加权处理发射模块 26。 其中， 第一编码处理模块 21用于对广播信号进行 信道编码处理、 星座调制处理以及空时频编码处理， 获取多路码流信号。 基本 权向量获取模块 23用于获取多个子阵列中每个子阵列的基本权向量， 该基本 的波束方向图在方向维度上互补； 第一加权处理发射模块 24用于根据每个基 本权向量中的权系数，分别对每个基本权向量对应的子阵列中的阵元上的发射 信号进行加权处理得到第一信号， 并应用阵元对第一信号进行发射。 更新模块 25 用于在时间维度或频率维度上对每个基本权向量进行更新处理， 获取更新 后的权向量； 第二加权处理发射模块 26用于在不同的时间或频率上根据更新 后的权向量，分别对每个子阵列的阵元上的发射信号进行加权处理得到第二信 号， 并应用阵元对第二信号进行发射。
在本实施例中， 划分处理模块 22包括第一处理单元或者第二处理单元或 第二处理单元用于对多个天线阵列按照间隔距离进行划分处理；第三处理单元 在本实施例中， 更新模块 25可以包括相位获取单元 251和更新单元 252。 其中， 相位获取单元 251 用于获取相位值 更新单元 252 用于应用公式 wNew = diag \ ejA≠ ej2A≠-enM-^] - w , 对每个基本权向量 W = [Wi，W2，〜Wm]t进行更 新处理， 分别获取更新后的权向量。 其中， ^„表示更新后的权向量， j 为虚 数单位， diag[xx ...x„ ]表示由； ¾至 x„构成的对角阵。
本实施例的广播信号发射装置可以用于执行图 2至图 17任一方法实施例 的技术方案， 其实现原理类似， 此处不再赘述。
在本实施例中，划分处理模块通过采用不同的划分方法对多天线系统的天 线阵列进行划分处理， 并获取多个子阵列中每个子阵列的基本权向量， 该基本 的波束方向图在方向维度上互补，再根据每个基本权向量的权系数，对每个子 阵列的阵元上的发射信号进行加权处理，并应用阵元对加权处理后的信号进行 发射。 同时， 采用相位旋转法对基本权向量进行更新， 获取更新后的权向量， 并根据更新后的权向量的权系数，对每个子阵列中的阵元上的发射空时频码流 进行加权处理得到第二信号， 并应用阵元对第二信号进行发射，从而使得多天 线系统的发射功率具有更好的等向性，从而进一步保证了所有移动终端能接收 到同质量的信号，进而更加有效的实现了多天线系统中广播信号在小区或者扇 区的全面覆盖。
图 20为本发明广播信号发射装置的又一个实施例的结构示意图， 如图 20 所示， 本实施例的广播信号发射装置包括： 第二编码处理模块 31、 划分处理 模块 32、 基本权向量获取模块 33、 第一加权处理发射模块 34、 更新模块 35 和第二加权处理发射模块 36。 其中， 第二编码处理模块 31用于对广播信号进 行信道编码处理和星座调制处理， 获取多路符号流。 第一加权处理发射模块 34用于根据每个基本权向量中的权系数， 分别对每个基本权向量对应的子阵 列中的阵元上的发射信号进行加权处理得到第一信号，并应用阵元对第一信号 进行发射。 更新模块 35用于在时间维度或频率维度上对每个基本权向量进行 更新处理， 获取更新后的权向量； 第二加权处理发射模块 36用于在不同的时 间或频率上根据更新后的权向量，分别对每个子阵列的阵元上的发射信号进行 加权处理得到第二信号， 并应用阵元对第二信号进行发射。
在本实施例中， 基本权向量获取模块 33可以包括第一基本权向量获取单 元 331和第二基本权向量获取单元 332。 其中， 第一基本权向量获取单元 331 用于选取两个模相等的第一权系数，构成两个子阵列中的一个子阵列对应的基 本权向量；第二基本权向量获取单元 332用于对两个模相等的第一权系数的其 中一个取负值， 构成两个子阵列中的另一子阵列对应的基本权向量。
更新模块 35可以包括第一更新单元 351和第二更新单元 352。 其中， 第 一更新单元 351 用于分别对两两互补的多个子阵列中的两个互补子阵列选取 两个模相等的第二权系数，构成两个子阵列中的一个子阵列对应的更新后的权 向量。 第二更新单元 352用于对两个模相等的第一权系数的其中一个取负值， 分别构成两两互补的多个子阵列中的两个互补子阵列中的另一个子阵列对应 的基本权向量。
本实施例的广播信号发射装置可以用于执行图 2至图 17任意方法实施例 的技术方案， 其实现原理类似， 此处不再赘述。
图 21为本发明广播信号发射装置的又一个实施例的结构示意图， 如图 21 所示， 本实施例的广播信号发射装置包括： 第一编码处理模块 41、 划分处理 模块 42、 基本权向量获取模块 43、 第一加权处理发射模块 44、 OFDM处理模 块 45、 第一更新发射模块 46和第二更新发射模块 47。 其中， 第一编码处理模 块 41用于对广播信号进行信道编码处理、星座调制处理以及空时频编码处理， 获取多路码流信号。 基本权向量获取模块 43用于获取多个子阵列中每个子阵 列的基本权向量，该基本权向量使得每个子阵列的波束峰均功率比低于预设门 限， 并且使得不同子阵列的波束方向图在方向维度上互补； 第一加权处理发射 模块 44用于根据每个基本权向量中的权系数， 分别对每个基本权向量对应的 子阵列中的阵元上的发射信号进行加权处理，并应用阵元对加权处理后的第一 信号进行发射； OFDM处理模块 45用于对每个子阵列中的阵元上的发射信号 进行正交频分复用调制处理，获取每个子阵列中的阵元对应的正交频分复用信 号； 第一更新发射模块 46用于根据每个基本权向量中的第一个权系数对正交 频分复用信号进行加权处理得到第二信号，并应用子阵列的第一阵元对第二信 号进行发射。 第二更新发射模块 47用于根据每个基本权向量中的第二权系数 至最后一个权系数对正交频分复用信号进行加权处理和延迟处理得到第二信 号， 并分别应用子阵列的第二阵元至最后一个阵元对第二信号进行发射。
进一步的， 该广播信号发射装置还可以包括延迟处理模块， 用于依次对每 个子阵列中的阵元上加权处理后的信号进行延时处理得到第二信号，并应用阵 元对第二信号进行发射。
本实施例的广播信号发射装置可以用于执行图 2至图 17所示方法实施例 的技术方案， 其实现原理类似， 此处不再赘述。
在本实施例中，通过采用不同的方式对天线阵列进行划分处理， 获取多个 子阵列， 并获取多个子阵列中每个子阵列的基本权向量， 该基本权向量使得每 个子阵列的波束峰均功率比低于预设门限，并且使得不同子阵列的波束方向图 在方向维度上互补，再根据每个基本权向量的权系数，对每个子阵列中的阵元 上的发射空时频码流进行加权处理，并应用阵元对加权处理后的第一信号进行 发射。从而使得每个子阵列的波束覆盖角度宽、峰均功率比低和具有方向维度 互补性， 并且通过采用循环延时方法对基本权向量不断进行更新处理， 获取更 新后的权向量， 并根据更新后的权向量的权系数，对每个子阵列中的阵元上的 发射空时频码流进行加权处理得到第二信号， 并应用阵元对第二信号进行发 射，从而使得子阵列的波束方向图上的平均发射功率具有更好的等向性，从而 进一步保证了小区内所有移动终端能接收到同质量的信号，进而更加有效的实 现了多天线系统中广播信号在小区或者扇区的全面覆盖。
本领域普通技术人员可以理解：实现上述方法实施例的全部或部分步骤可 以通过程序指令相关的硬件来完成，前述的程序可以存储于一计算机可读取存 储介质中， 该程序在执行时， 执行包括上述方法实施例的步骤； 而前述的存储 介质包括： ROM、 RAM, 磁碟或者光盘等各种可以存储程序代码的介质。
最后应说明的是： 以上实施例仅用以说明本发明的技术方案， 而非对 其限制； 尽管参照前述实施例对本发明进行了详细的说明， 本领域的普通 技术人员应当理解： 其依然可以对前述各实施例所记载的技术方案进行修 改， 或者对其中部分技术特征进行等同替换； 而这些修改或者替换， 并不 使相应技术方案的本质脱离本发明各实施例技术方案的精神和范围。

Claims

权 利 要 求
1、 一种广播信号发射方法， 其特征在于， 包括：
对多天线系统中的天线阵列进行划分处理， 获取多个子阵列； 获取所述多个子阵列中每个子阵列的基本权向量， 所述基本权向量使得 每个子阵列的波束峰均功率比低于预设门限， 并且使得不同子阵列的波束方 向图在方向维度上互补；
根据所述每个基本权向量中的权系数， 分别对所述每个基本权向量对应 的子阵列中的阵元上的发射信号进行加权处理得到第一信号， 并应用所述阵 元对所述第一信号进行发射。
2、 根据权利要求 1所述的广播信号发射方法， 其特征在于， 所述对多天 线系统中的天线阵列进行划分处理， 包括：
对单个天线阵列进行逻辑划分处理； 或者
对多个天线阵列按照间隔距离进行划分处理； 或者
对极化天线阵列按照极化方向进行划分处理。
3、根据权利要求 1或 2任一权利要求所述的广播信号发射方法， 其特征 在于， 还包括：
在时间维度或频率维度上对所述每个基本权向量进行更新处理， 分别获 取更新后的权向量； 对所述每个子阵列的阵元上的发射信号进行加权处理得到第二信号， 并应用 所述阵元对所述第二信号进行发射。
4、根据权利要求 3所述的广播信号发射方法， 其特征在于， 所述在时间 维度或频率维度上对所述每个基本权向量进行更新处理，分别获取更新后 的权向量， 包括：
获取相位值
应用公式
Figure imgf000036_0001
, 对所述每个基本权向量 w = [w^ w,, :- ^†进行更新处理， 分别获取更新后的权向量；
其中， wNew表示更新后的权向量， j为虚数单位， ag^ ]表示由 至 „ 构成的对角阵。
5、根据权利要求 1或 2任一权利要求所述的广播信号发射方法， 其特征 在于， 还包括：
依次对所述每个子阵列中的阵元上加权处理得到的所述第一信号进行延 时处理得到第二信号， 并应用阵元对所述第二信号进行发射。
6、根据权利要求 1或 2任一权利要求所述的广播信号发射方法， 其特征 在于， 还包括：
对所述每个子阵列中的发射信号进行正交频分复用调制处理， 获取每个 子阵列对应的正交频分复用信号；
根据所述每个基本权向量中的第一个权系数对所述正交频分复用信号进 行加权处理得到第二信号， 并应用所述子阵列的第一阵元对所述第二信号进 行发射；
根据所述每个基本权向量中的第二权系数至最后一个权系数对所述正交 频分复用信号进行加权处理和循环延时处理后得到所述第二信号， 并分别应 用所述子阵列的第二阵元至最后一个阵元对所述第二信号进行发射。
7、 根据权利要求 3所述的广播信号发射方法， 其特征在于， 若对多天线 系统中的天线阵列进行划分处理， 获取两两互补的多个子阵列， 并且所述每 个子阵列包括两个阵元， 所述获取所述多个子阵列中每个子阵列的基本权向 使得不同子阵列的波束方向图在方向维度上互补， 包括：
分别对所述两两互补的多个子阵列中的两个互补子阵列， 选取两个模相 等的第一权系数， 构成所述两个互补子阵列中的一个子阵列对应的基本权向 量；
对所述两个模相等的第一权系数的其中一个取负值， 分别构成所述两两 互补的多个子阵列中的两个互补子阵列中的另一个子阵列对应的基本权向 量。
8、 根据权利要求 7所述的广播信号发射方法， 其特征在于， 若所述子阵 列包括两个阵元， 所述在时间维度或频率维度上对所述每个基本权向量进行 更新处理， 分别获取更新后的权向量， 包括：
选取两个模相等的第二权系数， 构成所述两个子阵列中的一个子阵列对 应的更新后的权向量；
对所述两个模相等的第二权系数的其中一个取负值， 构成所述两个子阵 列中的另一个阵列对应的更新后的权向量。
9、 根据权利要求 3所述的广播信号发射方法， 其特征在于， 所述对多天 线系统中的天线阵列进行划分处理， 获取多个子阵列之前， 还包括：
对广播信号进行信道编码处理、 星座调制处理以及空时频编码处理， 获 取多路码流信号； 或者 对广播信号进行信道编码处理和星座调制处理， 获取多路符号流。
10、 根据权利要求 9所述的广播信号发射方法， 其特征在于， 所述空时 频编码具体包括 Alamouti编码、 空时分组码、 空频分组码、 时间切换发射分 集或频率切换发射分集。
11、 一种广播信号发射装置， 其特征在于， 包括：
划分处理模块， 用于对多天线系统中的天线阵列进行划分处理， 获取多 个子阵列；
基本权向量获取模块， 用于获取所述多个子阵列中每个子阵列的基本权 且使得不同子阵列的波束方向图在方向维度上互补；
第一加权处理发射模块， 用于根据所述每个基本权向量中的权系数， 分 别对所述每个基本权向量对应的子阵列中的阵元上的发射信号进行加权处理 得到第一信号， 并应用所述阵元对所述第一信号进行发射。
12、 根据权利要求 11所述的广播信号发射装置， 其特征在于， 所述划分 处理模块包括：
第一处理单元， 用于对单个天线阵列进行逻辑划分处理； 或者
第二处理单元， 用于对多个天线阵列按照间隔距离进行划分处理； 或者
13、 根据权利要求 11或 12任一权利要求的广播信号发射装置， 其特征 在于， 还包括：
更新模块， 用于在时间维度或频率维度上对所述每个基本权向量进行更 新处理， 获取更新后的权向量； 第二加权处理发射模块， 用于在不同的时间或频率上根据更新后的权向 量，分别对所述每个子阵列的阵元上的发射信号进行加权处理得到第二信号， 并应用所述阵元对所述第二信号进行发射。
14、 根据权利要求 13所述的广播信号发射装置， 其特征在于， 所述更新 模块包括：
相位获取单元， 用于获取相位值 φ；
更新单元， 用于应用公式
Figure imgf000039_0001
ε]Αφ 2L (M- " ： ，对所述每个 基本权向量 W = [Wl，w2， WMf进行更新处理， 分别获取更新后的权向量；
其中， wNew表示更新后的权向量， j为虚数单位， d ag[x ..x„ ]表示由; ^至;^ 构成的对角阵。
15、 根据权利要求 11或 12任一权利要求所述的广播信号发射装置， 其 特征在于， 还包括：
延迟处理模块， 用于依次对所述每个子阵列中的阵元上加权处理得到的 所述第一信号进行延时处理得到第二信号， 并应用阵元对所述第二信号进行 发射。
16、 根据权利要求 11或 12任一权利要求所述的广播信号发射装置， 其 特征在于， 还包括：
正交频分复用调制处理模块， 用于对所述每个子阵列中的发射信号进行 正交频分复用调制处理， 获取每个子阵列对应的正交频分复用信号；
第一更新发射模块， 用于根据所述每个基本权向量中的第一个权系数对 所述正交频分复用信号进行加权处理得到第二信号， 并应用所述子阵列的第 一阵元对所述第二信号进行发射； 第二更新发射模块， 用于根据所述每个基本权向量中的第二权系数至最 后一个权系数对所述正交频分复用信号进行加权处理和循环延迟处理得到所 述第二信号， 并分别应用所述子阵列的第二阵元至最后一个阵元对所述第二 信号进行发射。
17、 根据权利要求 13所述的广播信号发射装置， 其特征在于， 若对多天 线系统中的天线阵列进行划分处理， 获取两两互补的多个子阵列， 并且所述 每个子阵列包括两个阵元， 所述基本权向量获取模块包括：
第一基本权向量获取单元， 用于分别对所述两两互补的多个子阵列中的 两个互补子阵列选取两个模相等的第一权系数， 构成所述两个子阵列中的一 个子阵列对应的基本权向量；
第二基本权向量获取单元， 用于对所述两个模相等的第一权系数的其中 一个取负值， 分别构成所述两两互补的多个子阵列中的两个互补子阵列中的 另一个子阵列对应的基本权向量。
18、 根据权利要求 17所述的广播信号发射装置， 其特征在于， 所述更新 模块包括：
第一更新单元， 用于选取两个模相等的第二权系数， 构成所述两个子阵 列中的一个子阵列对应的更新后的权向量；
第二更新单元， 用于对所述的两个模相等的第二权系数的其中一个取负 值， 构成所述两个子阵列中的另一个阵列对应的更新后的权向量。
19、 根据权利要求 13所述的广播信号发射装置， 其特征在于， 还包括： 第一编码处理模块， 用于对广播信号进行信道编码处理、 星座调制处理 以及空时频编码处理， 获取多路码流信号； 或者 第二编码处理模块， 用于对广播信号进行信道编码处理和星座调制处 获取多路符号流。
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