WO2008028321A1 - Procède et système de communications - Google Patents

Procède et système de communications Download PDF

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Publication number
WO2008028321A1
WO2008028321A1 PCT/CN2006/002197 CN2006002197W WO2008028321A1 WO 2008028321 A1 WO2008028321 A1 WO 2008028321A1 CN 2006002197 W CN2006002197 W CN 2006002197W WO 2008028321 A1 WO2008028321 A1 WO 2008028321A1
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WO
WIPO (PCT)
Prior art keywords
channel
sinr
radio
signal
estimation
Prior art date
Application number
PCT/CN2006/002197
Other languages
English (en)
Inventor
Hai Wang
Qingyu Miao
Original Assignee
Telefonaktiebolaget L M Ericsson (Publ)
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Telefonaktiebolaget L M Ericsson (Publ) filed Critical Telefonaktiebolaget L M Ericsson (Publ)
Priority to EP06775514.0A priority Critical patent/EP2055017A4/fr
Priority to PCT/CN2006/002197 priority patent/WO2008028321A1/fr
Priority to US12/438,673 priority patent/US20100067563A1/en
Publication of WO2008028321A1 publication Critical patent/WO2008028321A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/04—TPC
    • H04W52/18—TPC being performed according to specific parameters
    • H04W52/24—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters
    • H04W52/248—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters where transmission power control commands are generated based on a path parameter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/309—Measuring or estimating channel quality parameters
    • H04B17/336—Signal-to-interference ratio [SIR] or carrier-to-interference ratio [CIR]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/04—TPC
    • H04W52/18—TPC being performed according to specific parameters
    • H04W52/24—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters
    • H04W52/241—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters taking into account channel quality metrics, e.g. SIR, SNR, CIR, Eb/lo
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/04—TPC
    • H04W52/18—TPC being performed according to specific parameters
    • H04W52/24—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters
    • H04W52/242—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters taking into account path loss
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W52/00—Power management, e.g. TPC [Transmission Power Control], power saving or power classes
    • H04W52/04—TPC
    • H04W52/18—TPC being performed according to specific parameters
    • H04W52/24—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters
    • H04W52/246—TPC being performed according to specific parameters using SIR [Signal to Interference Ratio] or other wireless path parameters where the output power of a terminal is based on a path parameter calculated in said terminal

Definitions

  • the present invention relates to radio communications systems, and more especially it relates to communications es- timation of signal to interference ratio, signal to noise ratio and signal to interference and noise ratio. Particularly, it relates to such estimation in CDMA type of systems .
  • SINR signal to interference ratio
  • SIR signal to noise ratio
  • SNR signal to interference and noise ratio
  • SINR signal to interference and noise ratio
  • FIG 1 schematically illustrates a radio base station «RBS», in UMTS functionally referred to as Node B, and user equipment «UB» .
  • the radio base station «RBS» emits radio signals destined for the user equipment «UE» in downlink direction «DL» and the mobile station emits radio signals destined for the radio base station «RBS» in uplink direc- tion «UL».
  • Each of the user equipment «UE» and radio base station «RBS» may use one or more antennas common for transmissions in both uplink and downlink directions, or different antennas for uplink and downlink directions.
  • Prior art transmission power control may be arranged in an inner loop and an outer loop.
  • the inner loop requires fast estimation to compensate for rapid changes typically due to fading of desired signal or new unwanted signals reaching the receiver.
  • Indirect user-quality measures such as SINR, for estimation of varying channel characteristics are well suited for such inner loop estimation.
  • SINR Indirect user-quality measures
  • In outer loop estimation requirements on speed may be relaxed and estimates on direct user quality parameters may be used, e.g. bit error rate, BER, or frame error rate, FER.
  • R v is covariance of total received signal and noise
  • h is channel coefficient vector
  • h is estimated channel coefficient vector
  • pto t is the power of the total transmitted signal
  • p p ii o t is the power of the transmitted pilot sig- nal
  • SFp ⁇ ot is spreading factor of the pilot signal
  • Section 3.3 describes a multipath searcher, and section 3.4 RAKE receiver architecture.
  • the carrier to interference ratio, C/1 required for d.e- modulation is discussed and in section 4.2, the cell capacity is expressed in terms of information bit energy-to- interference-plus-noise ratio.
  • Kimmo Kettunen 'Enhanced Maximal Ratio Combining for RaJce Receivers in Mobile CDMA Terminals, ' 5th Nordic Signal Processing Symposium NORSIG-2002, October 4-7, 2002 Hurti- gruten, Norway, proposes a maximal ratio combining scheme for rake receivers in mobile CDMA terminals not requiring estimation of rake finger noise powers.
  • the rake receiver structure of the system model correlates received signals at delays ⁇ x , ⁇ 2 , ... ⁇ L with a signature sequence of the user and a scrambling sequence for the cell under consideration.
  • the various multipath components 1, 2, ... I- are then cora- bined.
  • a conventional and a suggested combining scheme are analyzed.
  • Figure 2 illustrates schematically symbol-level combining
  • Figure 3 illustrates a basic block diagram for chip-level combining.
  • a path searcher «Path Search» searches for a time-window of strongest signal path components.
  • a number, L, of delay elements « ⁇ x » , «t 2 » ... «x h » distinguishes «D s s>, «Dh» L different signal paths of different propagation path delay over the communications channel and should span the channel delay spread for best performance.
  • the appropriately delayed signal paths are despread «DS S » «DS C » with a spreading sequence «s(t, ⁇ s )» with appropriate phase « ⁇ s republic
  • each delayed signal path is despread «DS S
  • a combined signal is despread «DSc» .
  • the combining «MRC S » , «MRCc» is optimal ratio combining, where the various paths are weighted in relation to their signal strength, corresponding to the respective complex conjugated channel gain of the paths, «h * (t, ⁇ h ) » as estimated «Channel Estimation*.
  • Gunaratne et al. conclude that post-RAKE estimation processing outperforms pre-RAKE processing for target values of Eb/No considered.
  • the conclusion is explained by the pre- R ⁇ KE SIR estimation scheme causing unnecessary 'power down 1 commands being generated at the base station, BS, causing the User Equipment, UE, to lower its power even when the actual received Bj 3 /N 0 is low, thereby causing higher bit error rate, BER.
  • Greater estimation errors are expected with pre-RAKE estimation due to the individual paths having smaller E b /N 0 ratio than the combined signal of post-RAKE processing.
  • International Patent Application WOO060763 estimates signal to interference ratio by forming a weighted sum of individual interference estimates along each of a plurality of multi -paths, where the weighting is determined in accordance with estimated signal power along the various multi- paths. The estimate of signal to interference ratio is then formed as the ratio of the combined power estimate and the weighted sum of individual interference estimates .
  • 3GPP 3 rd Generation Partnership Project
  • 3GPP Technical Specification Group, Technical Specification Group Radio Access Network, Physical layer procedures (FDD), 3GPP TS 25.214 V6.4.0, France, December 2004, establishes the characteristics of the physicals layer procedures in the FDD mode of UTRA.
  • Section 5.1.2.5 describes setting of uplink DPCCH/DFDCH power difference.
  • the section also describes respective gain factors ⁇ c and ⁇ a of the DPCCH ('Dedicated Physical Control Channel') and DPDCH ('Dedicated Physical Data Channel ' ) codes of various transport format combinations, TFCs.
  • Each TFC is indicated by a Transport Format Combination Indicator, TPCI, to the receiving side. Thereby, the TFC can be identified and received data be decoded and demultiplexed.
  • TPCI Transport Format Combination Indicator
  • Prior-art solutions generally provide accurate pilot symbol SINR after RAKE combining, when the channel impairments are dominated by additive white gaussian noise, AWGN. However, in other channel environments, such estimates tend to be less accurate. Further, in the case of high user data rates, the interference from the user itself is the dominating disturbing component. Existing prior-art SINR egti- mation does not perform well nor in such cases.
  • Another object of embodiments of the invention is to pro- vide a method and system where the required time for SINR estimation is sufficiently short.
  • a related object of embodiments of the invention is to provide a method and system suitable for inner-loop power control in a system with inner and outer transmission power control ,
  • a further object of preferred embodiments of the invention is to provide a method and system suitable for operations in a receiver utilizing rake combining of various signal paths .
  • an object of embodiments of the invention is to provide a method and system adapted to a WCDMA system.
  • SINR esti- mation including one or more channel parameters.
  • the one or more channel parameters are estimated in the SINR estimator of a receiver entity or transferred to the receiver entity from a sender entity.
  • Figure 1 schematically illustrates a radio base station and user equipment communicating in uplink and downlink di- rections in a radio communications system according to prior art .
  • Figure 2 illustrates schematically symbol-level combining, according to prior art.
  • Figure 3 illustrates a basic block diagram for chip-level combining, according to prior art.
  • Figure 4 demonstrates an example estimation of received noise power p n according to the invention.
  • Figure 5 schematically illustrates a basic block structure of a first non-limiting example embodiment of the invention.
  • Figure 6 illustrates a SINR estimator according to a second non-limiting example embodiment of the invention.
  • Figure 7 illustrates principal blocks of a non-limiting example realization of the invention
  • Figure 8 illustrates schematically two apparatus of a simplified radio communications system operating according to the invention.
  • the invention discloses SINR estimation utilizing channel affected parameters, such as channel orthogonality factor or channel coefficients.
  • an orthogonality factor of the channel, for which SINR is estimated is determined in addition to channel noise and received power.
  • weighted channel gain factors and received signal autocorrelation function form a basis for the SINR estima- tion, the weighted channel gain factors determining the power relation including desired signal power and undesired or total signal power.
  • a non- limiting example use of the invention is soft value scaling.
  • Another non-limiting example use is SINR estima- tion for TPC command generation.
  • an orthogonality factor, ⁇ is defined as
  • the SINR can then be expressed as
  • RTWP is Received Total Wideband Power
  • a and p n is received noise power.
  • the channel estimate, h (n) includes, as well as SINR sym , the pilot transmission power information,
  • an example SINR estimate according to the first embodiment is, flIMR.y. -SP p i i o t • where P n is bounded by the interval
  • a preferred example estimate, P n , of received noise power p n is achieved as illustrated in figure 4 ,
  • a desired user signal «rU(3esired» is determined from a received signal «y(n ⁇ ».
  • the received signal is passed through a signal matched filter «r(n)», the filter being matched to the transmitted signal.
  • the filtered signal «ry(n)» output from the signal matched filter «r(n)» is despread by correlating with the complex conjugate of the spreading code SC «SC * Colour
  • the despread signal ry S c(n) is then correlated with the channelization code «CC» for the
  • the received level is Ij after channel transport of data to a receiving unit.
  • This power, J j will be perceived as interference or noise in the receiving unit unless it stems from the serving base station.
  • the power «Pr» of the received filtered signal «ry(n)» is composed of wide-band interference and noise «IN Wb » and transmitted signal power from the serving base station «Ij», scaled by the power amplification of the channel impulse response and the matched filter «
  • the variance of the resulting signal «rUdeai r ed» corresponds to the power of the effective interference plus noise «IN ⁇ b» for the despread narrowband signal. It corresponds to the interference plus noise «IN w b» of the wideband signal divided by the spreading factor «SF» .
  • a coarse estimate, p n , of the noise power is
  • Figure 5 schematically illustrates a basic block structure of the first non-limiting example embodiment «a6» of the invention.
  • the blocks «al»- «a.5» directly correspond to functional parallel or serial steps as described above.
  • the channel impulse response in equation (11) is preferably determined from information on the channel coefficients of a RAKE receiver (not illustrated in figure 5) , Also received total wideband power «a3» and an estimate of received noise power «a4» are determined from the input.
  • the noise power is preferably estimated in accordance with the method and apparatus described above in relation to figure 4. Also a coarse estimate, e.g, according to equation (13) or (15) is useful.
  • the parameters determined «a2», «a3, «a4» are input to an estimator «a5»
  • the first non-limiting example embodiment has been illustrated with individual blocks «al»- «a5».
  • the invention also covers integrating illustrated blocks or parts of blocks into merged blocks, parts of blocks being configured in relation to other illustrated blocks, or even the blocks «al»- «a5» being integrated into a single entity «a6».
  • the invention covers realizations of the blocks entirely in hardware or in hardware with adapted software.
  • no particular estimate of received noise power is required.
  • the ratio of UE pilot transmission power, Ppii ot* and total transmission power, ptoti is known to the radio access network.
  • the ratio is
  • ⁇ o and ⁇ d are weighted gain factors for DPCCH ( 'Dedi- cated Physical Control Channel 1 ) and DPDCH ('Dedicated Physical Data Channel')/ respectively.
  • the gain factors ⁇ c and ⁇ d are signaled by layers higher than the physical layer as specified in 3GPP Technical Specification TS 25.214 V6.4.Q.
  • the base station or Node B using UMTS terminology, should decode TFCI to know which transport format is used.
  • HSPA High Speed Packet Access
  • HS-DPCCH 'High Speed Dedicated Physical Control Channel'
  • E-DPCCH 1 E-DCH Dedicated Physical Control Channel 1
  • E-DPDCH 1 E-DCH Dedicated Physical Data Channel 1
  • ⁇ c and ⁇ d are gain factors as specified above
  • ⁇ hS is gain factor for HS-DPCCH, which is derived from power offsets and the power offsets being applied to HSPA users as compared to non-HSPA users.
  • ⁇ ec and ⁇ ed are gain factors for E-DPCCH and E-DPDCH. These values are similar to ⁇ c and ⁇ a signaled by layers higher than the physical layer as specified in 3GPP Technical Specification TS 25.214 V6.4.0.
  • the estimated channel impulse response is preferably achieved from a Rake receiver, H denotes Hermitian trans- form, is determined in accordance with equation (17) and is determined, preferably in a processing entity, from the auto-correlation function of the received wide- band signal before despreading and combining.
  • H denotes Hermitian trans- form
  • a netfts of autocorrelation matrix R v are
  • v*(n) denotes the complex conjugate of the total received signal, v ⁇ n) , including noise and interference.
  • Figure S illustrates a SINR estimator «b5» according to the second non- limiting example embodiment.
  • an estimate of the channel impulse response is determined «bl».
  • the estimate is achieved from channel coefficients of a Rake re- ceiver.
  • the input autocorrelation is estimated «b2» and the power ratio of total received wideband power and pilot power before despreading and combining, cf. equation (16) for non-HSPA users and equation (17) for HSPA user.
  • An estimate of the power ratio is determined from channel gains preferably communicated on a control channel and forming part of the input to the SINR estimator.
  • the SINR estimate is finally determined «b4» from the estimates of the preceding blocks «bl», «b2», «fc>3».
  • the estimator «b5» preferably comprises one or more processing entities .
  • Figure 7 illustrates principal blocks of a non-limiting example realization of the invention wherein an apparatus «A ⁇ p» of SINR estimation in a radio communications system comprises at least one receiving means «R» and at least one processing means « ⁇ » .
  • Receiving means «R» receives one or more channel specific parameters.
  • the one or more parameters are transferred to processing means « ⁇ » adapted for inclusion of the one or more channel specific parameters, such as channel orthogonality or channel gain factors as described above.
  • the channel gain is estimated in the receiver.
  • the one or more channel gain factors are provided by a transmitter (not illustrated) and transferred from the receiving means «R» to the processing means « ⁇ » .
  • FIG 8 illustrates schematically two apparatus «Tx» , «Rx» of a simplified radio communications system operating according to the invention.
  • Transmitting and receiving apparatus «Tx», «Rx» in the figure are, e.g., user equipment and base station equipment «UE», «RBS» in figure 1.
  • the transmitting apparatus «Tx» wirelessly sends information to the receiving apparatus «Rx» .
  • the receiving apparatus «Rx» includes a detector for detecting radio transmissions received from the transmitting entity «Tx» .
  • the receiver and transmitter properties of, e.g., a user equipment are general in nature.
  • the use of concepts such as mobile station, MS, or radio base station, RBS, within this patent application is not intended to limit the invention only to devices associated with these acronyms. It concerns all devices operating correspondingly, or being obvious to adapt thereto by a person skilled in the art, in relation to the invention.
  • the invention relates to mobile stations without a subscriber identity module, SIM, as well as user equipments including one or more SIMs.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Quality & Reliability (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Noise Elimination (AREA)
  • Mobile Radio Communication Systems (AREA)

Abstract

L'invention concerne une estimation de communications, dans des systèmes de communication radio, et en particulier dans des système de type CDMA, un rapport signal sur brouillage, un rapport signal sur bruit et un rapport signal sur brouillage et bruit. Cette estimation comprend un ou plusieurs paramètres spécifiques de canal et un ou plusieurs paramètres relatifs au signal reçu, au bruit et au brouillage.
PCT/CN2006/002197 2006-08-25 2006-08-25 Procède et système de communications WO2008028321A1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
EP06775514.0A EP2055017A4 (fr) 2006-08-25 2006-08-25 Procède et système de communications
PCT/CN2006/002197 WO2008028321A1 (fr) 2006-08-25 2006-08-25 Procède et système de communications
US12/438,673 US20100067563A1 (en) 2006-08-25 2006-08-25 Method and system of communications

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2006/002197 WO2008028321A1 (fr) 2006-08-25 2006-08-25 Procède et système de communications

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WO2008028321A1 true WO2008028321A1 (fr) 2008-03-13

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US (1) US20100067563A1 (fr)
EP (1) EP2055017A4 (fr)
WO (1) WO2008028321A1 (fr)

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JP5909417B2 (ja) 2012-07-13 2016-04-26 ルネサスエレクトロニクス株式会社 半導体装置及び受信装置
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US20100067563A1 (en) 2010-03-18
EP2055017A4 (fr) 2013-08-07

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