WO2007138073A2

WO2007138073A2 - Transceiver array, and method for processing signals in a transceiver array

Info

Publication number: WO2007138073A2
Application number: PCT/EP2007/055247
Authority: WO
Inventors: Roland Jenkins; Christian Roth
Original assignee: Palm, Inc.
Priority date: 2006-05-30
Filing date: 2007-05-30
Publication date: 2007-12-06
Also published as: WO2007138073A3; DE102006025169A1

Abstract

Disclosed is a transceiver array comprising a non-linear element (10) and an antenna (20) which can be connected to the non-linear element. Additionally, a duplexer (30) is provided which encompasses a first terminal (31) for feeding a transmit signal, a second terminal (32) for emitting a receive signal, and a third terminal (33). The third terminal (330 of the duplexer (30) is coupled to the non-linear element (10) by means of a phase shifter (40).

Description

description

Transceiver arrangement and method for signal processing in a transmission / reception arrangement

The invention relates to a transmission / reception arrangement, a method for signal processing in a transmission / reception arrangement as well as a use of the transmission / reception arrangement.

In today's radio transmission systems, it is often possible to transmit and receive radio signals simultaneously. This is called a full-duplex operation. Transmission frequency and reception frequency are often different and have a certain frequency spacing from each other, which is also referred to as duplex spacing.

In the presence of an interfering signal with a disturbing frequency which has the duplex spacing as frequency spacing with respect to the transmitting frequency, an intermodulation signal can be formed which has a frequency which corresponds to the receiving frequency. Intermodulation products can be formed on every slightly non-linear element, for example in the path between the antenna and a duplexer, such as an electronic switch.

By way of example, a conventional transmission / reception arrangement is shown in FIG. The arrangement comprises a duplexer 30 having an input 31 for supplying a transmission signal, a connection 32 for outputting a reception signal and a connection 33 which is coupled to an antenna 20 via a switching device 50. The duplexer 30 is included to a switching input 54 of a plurality of switching inputs 52, 53, 54, 55 of the switching device 50 is connected. A switch can be used to establish a conductive connection to a switching output 51.

During is by the duplexer 30, a transmission signal having the transmission frequency f _T χ via the switching device 50 applied to the antenna 20 is simultaneously received via the antenna 20, an interference signal having a Storfrequenz f _B. At the switching device 50, which acts as a nonlinear element, an intermodulation signal with an intermodulation _frequency f _{IM3 is} formed from the transmission signal and the interference signal, which corresponds for example just to a corresponding reception _frequency f _RX . Thus, the intermodulation signal is forwarded as a received signal from the duplexer 30 via the terminal 32 to a receive path, not shown here. This usually leads to an impairment of the reception quality.

Intermodulation products can be formed in radio transmission systems from any high-frequency signals. The respective intermodulation frequency results from the sum or the difference of arbitrary multiples of the frequencies of the high-frequency signals involved.

FIG. 8 shows an exemplary intermodulation diagram for a third-order intermodulation product. Shown is the power P of a high-frequency signal over the respective frequency f. A transmission signal with the frequency f _τx has a frequency difference Δfl with _respect to a disturbance signal with the frequency f _B. The spacing of the transmission frequency _f.tau.x to the reception frequency f.sub.Rx amounts to .DELTA.f2, wherein in the present example the frequency distances .DELTA.fl and .DELTA.f2 are the same. Through an intermodulation third order, an intermodulation _{signal is} formed with an intermodulation frequency f _IM3 , which results from twice the transmission frequency f _τx less the interference frequency f _B. With the frequency spacing Δfl of the interference frequency f _B , the intermodulation frequency f _{IM3 is} thus equal to the reception frequency

J-RX •

Because of this nonlinear behavior, the use of switches in the antenna path of full duplex radio transmission systems is problematic. However, when multiple frequency bands or radio standards such as Universal Mobile Telecommunications System, UMTS, or Global System for Mobile Communications, GSM, to be operated on a single antenna, it is difficult to dispense with the use of switches. Alternatively, two or more antennas can be used, according to the number of desired frequency bands or radio standards. Since the transmission frequency and interference frequency are usually close to each other, it is also not possible to filter out the interference signal satisfactorily.

It is therefore an object of the invention to provide a transmission / reception arrangement in which an interfering influence of intermodulation products due to interference signals is reduced. It is a further object of the invention to provide a method with which the formation of intermodulation products is reduced by interference in a transmitting / receiving device. Furthermore, it is an object of the invention to show a use for the transmission / reception arrangement. These objects are achieved with the subject matters of the independent claims. Embodiments and developments of the invention are the subject of the dependent claims.

The object is achieved, for example, by a transmitting / receiving arrangement which comprises a nonlinear element and an antenna which can be connected to the nonlinear element. Furthermore, the transceiver arrangement comprises a duplexer having a first terminal for supplying a transmission signal, a second terminal for outputting a reception signal and a third terminal. A phase shifter couples the third port of the duplexer to the nonlinear element.

In the transmission / reception arrangement according to the invention, a transmission signal can be output via the duplexer, the phase shifter, the nonlinear element and an antenna as a radio signal. At the same time, a signal can be received via the antenna, which acts as an interference signal. This can lead to the formation of intermodulation products at the nonlinear element. The height or amplitude of the intermodulation products depends on the amplitude, in particular a voltage amplitude of the interference signal at the nonlinear element. Due to the filter properties of the duplexer, this usually has a high reflection for interference signals with a noise frequency, from which intermodulation signals can be formed at a frequency corresponding to the respective reception frequency.

If the duplexer were connected directly to the non-linear element, this would lead to a high amplitude of the noise signal at the nonlinear element and thus to a high amplitude. de an intermodulation signal lead. This intermodulation signal would interfere with a receive path that is connected, for example, to the second port of the duplexer.

The phase shifter between the duplexer and the non-linear element changes the reflection behavior of the duplexer for the underlying interference signal. This reduces the amplitude of the interference signal at the non-linear element, which also leads to less pronounced intermodulation products. Thus, fewer disturbances reach the reception path.

The non-linear element may, for example, comprise a switching device having a plurality of switching inputs and a switching output. The antenna can be connected to the switching output and the phase shifter couples the third connection of the duplexer to one of the switching inputs.

If a plurality of frequency bands and / or radio standards are to be selectively radiated and received via an antenna, a switching device can be provided, via which a switching between the different frequency bands or radio standards takes place. A switching device generally has non-linear properties, so that intermodulation products can be formed on it. For example, the switching device may comprise a plurality of transistors, each of which couples one of the switching inputs to the switching output. The transistors may be formed as field effect transistors, for example. - S -

In the switching device, one of the switching inputs is usually coupled in a low-resistance manner to the switching output, while the remaining switching inputs are coupled to the switching output in a high-impedance, ie non-conductive manner. For transistors, this is done either by conducting or non-conductive switching of the controlled routes. In particular, when field effect transistors are used, the non-linear junction capacitances of the transistors in the locked, non-conducting state contribute to the formation of the intermodulation products.

A transmission / reception arrangement may comprise a further duplexer which has a first connection for supplying a further transmission signal, a second connection for outputting a further reception signal and a further third connection. In addition, a further phase shifter can be provided which couples the third connection of the further duplexer with a further one of the switching inputs.

Thus, a duplexer can be connected to each of the switching inputs via a phase shifter, which is designed for a particular frequency band with a respective transmission frequency and a corresponding reception frequency. For example, a transmission / reception path for the GSM standard can be connected to one of the switching inputs, while a transmission / reception path for a frequency band according to the UMTS standard is connected to a further switching input. Since a phase shifter can be provided for each of the connected duplexers, a reflection behavior of a respective duplexer can be suitably changed according to the respective transmission frequency and reception frequency, so that the disturbing influence of intermodulation products is reduced in each case.

The duplexer may be configured to process the transmit signal and the receive signal in full-duplex mode. For example, the duplexer includes a duplex filter having two bandpass filters. The bandpass filters are permeable in each case for the corresponding transmission frequency or reception frequency. Thus, a transmission signal from the first terminal to the third terminal and a received signal from the third terminal to the second terminal can be simultaneously passed through.

In order to change the reflection behavior of the duplexer, a reflection factor of the duplexer for a noise signal having a noise frequency may be transformed by the phase shifter such that an amplitude of the noise signal at the nonlinear element is minimized. The transformation of the reflection factor essentially corresponds to an impedance transformation. The reflection factor is usually determined from the ratio of an amplitude of an incident wave and the amplitude of a returning, reflected wave. Since the interference signal with the interference frequency is not transmitted by the duplexer, for example by the filter properties of the bandpass filter, but is almost completely reflected, the duplexer generally has a high reflection factor. By means of the phase shifter, however, the reflection factor can be transformed such that it is approximately -1 at the nonlinear element, that is, for example, the switching device. Without a phase shifter, the duplexer for the interfering signal with the disturbance frequency would act almost like a so-called idle, resulting in approximately a maximum of Set voltage amplitude of the interference signal. Due to the transformation via the phase shifter, the duplexer can now act on the nonlinear element as a so-called short circuit, in which the propagating and reflected wave of the interference signal cancel each other out, thereby resulting in a voltage minimum of the interference signal. By reducing the amplitude, in particular the voltage amplitude of the noise signal at the nonlinear element and the formation of interfering intermodulation products is reduced.

The phase shifter can be provided so that a frequency difference of a transmission frequency of the transmission signal to the interference frequency is equal to a frequency difference of a reception frequency of the reception signal to the transmission frequency. Transmitting frequency and receiving frequency have a fixed distance in the rule, which is also referred to as duplex spacing. Interference signals with an interference frequency, which also have the duplex spacing at the transmission frequency, generally have the greatest influence on the formation of intermodulation products. By adapting the phase shifter to such a critical interference frequency, the disturbing influence of intermodulation products can be effectively reduced ,

In an embodiment, the phase shifter may comprise a line having a length that depends on a desired frequency and a desired phase shift. The frequency can result from the transmission frequency and the respective duplex spacing of the corresponding reception frequency. A necessary phase shift may depend, inter alia, on the respective reflection factor of the duplexer. The necessary length between duplexer and switching device or non-linear element can thus for example the wavelength of the noise frequency can be determined. If the duplexer has a reflection factor that corresponds to a full idle, the line may be provided as a quarter-wave line. As a result, the reflection factor of the duplexer on the nonlinear element is transformed into a complete short circuit, that is to say a voltage minimum for the interference signal. The term lambda quarter stands for a line with a length that corresponds to a quarter of the wavelength of the interference frequency on the line.

The phase shifter may also include an LC network. Through the LC network, a phase shift or an impedance transformation, which transforms the reflection factor of the duplexer corresponding to the non-linear element.

The transmission / reception arrangement can be designed in particular for operation according to the UMTS standard and / or the GSM standard.

The transmission / reception arrangement can be used in one of the described embodiments in a mobile communication device. For example, it can be used in a mobile phone for the UMTS and / or the GMS standard. It is also possible to use the transmission / reception arrangement in a base station for a radio network.

The object is further achieved by a method for signal processing in a transmission / reception arrangement. In this case, a transmission signal is transmitted at a transmission frequency via a signal path comprising a duplexer and a nonlinear element includes. A received signal with a reception frequency as well as a interference signal with a sensor frequency are also received via the signal path. A reflection factor of the duplexer is transformed so as to minimize an amplitude of the disturbance signal at the nonlinear element.

By minimizing the amplitude of the interference signal, in particular a voltage amplitude at the non-linear element, the formation of intermodulation products from the transmission signal and the interference signal is reduced. Thus, the influence of interfering intermodulation signals having a frequency corresponding to the receiving frequency can be reduced.

The transformation of the reflection factor essentially corresponds to an impedance transformation. The transformation can thus be done by a phase shifter. For example, the transformation is performed by a line with a length that depends on a desired frequency and a desired phase shift. The frequency results from the frequency of the disturbance, from which interfering intermodulation signals are generated. This frequency of disturbance has a certain wavelength on the line, which influences the length of the line for transforming. Furthermore, the length depends on the desired phase shift, which results from the reflection factor of the duplexer for the disturbance frequency and the desired reflection factor at the non-linear element.

For example, the transformation takes place via a quarter-wave line which has a length which corresponds to a quarter of the wavelength of the interference signal on the line. The transformation can also be done through an LC network. The LC network effects an impedance transformation that alters the reflection factor of the non-linear element duplexer.

In one embodiment of the method, the non-linear element may comprise a switching device, via which further signal paths can be formed, each with a further duplexer. Reflection factors of the respective further duplexers are in this case transformed in such a way that an amplitude of the interference signal at the nonlinear element is minimized.

Thus, the method can be used in a transmission / reception arrangement which is designed, for example, for a plurality of frequency bands and / or radio standards. A transformation of the reflection factors of the duplexer for the respective interference signals is adjusted to a respective transmission frequency and reception frequency of the respective duplexer. The transformation of the reflection factor of the other duplexers can also be done via a phase shifter, a corresponding line or through an LC network.

The method may be adapted such that a frequency separation of the transmission frequency from the interference frequency is equal to a frequency separation of the reception frequency from the transmission frequency. Thus, in each case the reflection factor for a noise signal can be transformed over which interfering intermodulation products are formed.

Sending and receiving can be done via an antenna. Furthermore, the transceiver arrangement can be designed for operation according to the UMTS standard and / or the GSM standard. In the following, the invention will be explained in detail with reference to exemplary embodiments with reference to the drawings.

Show it:

FIG. 1 shows a first exemplary embodiment of a transmission / reception arrangement according to the invention,

FIG. 2 shows an exemplary diagram for a reflection factor,

FIG. 3 shows a second embodiment of a transmitting / receiving arrangement according to the invention,

FIG. 4 shows a third exemplary embodiment of a transmitting / receiving arrangement according to the invention,

5 shows an embodiment of a switching device according to the invention,

FIG. 6 shows an exemplary embodiment of an LC network according to the invention,

Figure 7 shows an embodiment of a conventional transmitting / receiving arrangement and

FIG. 8 shows an exemplary intermodulation diagram.

FIG. 1 shows an exemplary embodiment of a transceiver arrangement according to the invention. A duplexer 30 has a first terminal 31 for supplying a transmission signal, a second one Terminal 32 for outputting a received signal and a third terminal 33. This third terminal 33 is coupled via a phase shifter 40 to a non-linear element 10, to which an antenna 20 is connected.

A transmission signal supplied via the terminal 31 is radiated through the antenna 20 via the phase shifter 40 and the non-linear element 10. The duplexer 30 is designed for a full-duplex operation, so that signals can be received simultaneously via the antenna 20, including a received signal, which is output from the duplexer 30 at the second terminal 32 to a receive path, not shown. The duplexer 30 includes a duplex filter with two bandpasses, which are tuned to the transmission frequency or the reception frequency.

In addition, interference signals can be received via the antenna 20. The nonlinear properties of the nonlinear element 10 can lead to the formation of intermodulation products from interfering signals and the transmission signal. In particular, such interference signals can be problematic, which have an interference frequency, from which intermodulation products are formed with the reception frequency. A wave of interfering signal may pass through non-linear element 10 and phase shifter 40 to duplexer 30, from where it is reflected back to the nonlinear element. However, due to the phase shifter 40, the shaft undergoes a phase rotation so that, in the ideal case, the reflected and reflected waves on the nonlinear element cancel each other out. This creates a local minimum of the amplitude of the interference signal, in particular the voltage amplitude of the interference signal. Thereby It also reduces the amount of intermodulation products formed from the noise signal.

FIG. 2 shows an exemplary diagram for a reflection factor. A reflection factor r can be represented in the complex plane. At the point marked r = 1, a traveling wave and a reflected wave are in phase. As a result, their amplitudes can be added and there is a maximum voltage for the corresponding signal. This point is also called idle. At the point r = -l the traveling and the reflected wave have a phase difference of 180 ° to each other, which can lead to the cancellation of the corresponding signal. This point is also called a short circuit. The reflection factor depends, among other things, on the frequency of the corresponding signal.

As a rule, a duplexer has a reflection factor in the range of the point r = 1 for the relevant interference frequency, ie the frequency from which the largest intermodulation products can be formed with the reception frequency. By a transformation of the reflection factor, which substantially corresponds to an impedance transformation, the unfavorable reflection factor of the duplexer in the area of the point r = -l, that is ideally up to the point r = -l, can be changed.

FIG. 3 shows a further exemplary embodiment of a transmitting / receiving arrangement according to the invention. Functionally or functionally identical components carry the same reference numerals. The phase shifter 40 comprises a line 41, the third terminal 33 of the duplexer 30 with a Switching input 54 of a switching device 50 couples. The switching device 50 is encompassed by the non-linear element 10 and has further switching inputs 52, 53, 55 and a switching output 51, to which the antenna 20 is connected. By means of the antenna 20, for example, a Storsignal with the relevant frequency f _{b is} received. From this together with the transmission signal to the nonlinear switching device 50 intermodulation products with a frequency fi _M3 formed, which corresponds to a reception frequency f _RX , as shown for example in Figure 8.

The frequency of the fault has a wavelength λ on the line 41. The line is in its length 1 for the exemplary case that the duplexer for the disturbance frequency f _{B has} a reflection factor of 1, adjusted so that the length 1 corresponds to a quarter of the wavelength λ. As a result, from the duplexer 30 to the switching device 50, a transformation of the reflection factor from the point r = 1 to the point r = -l, as shown in FIG. A local course of a voltage amplitude of the interference signal via the line 41 is shown below the line 41. The representation is shown in standardized form as the ratio of the voltage amplitude U to a maximum voltage amplitude U _Max . It can be seen that a maximum of the local voltage amplitude is reached directly at the terminal 33 of the duplexer 30, which corresponds to a reflection factor of 1. At the other end of the line, ie at the switching input 54, it can be seen that a minimum voltage is established there, which corresponds approximately to a reflection factor of -1. In the illustrated embodiment, the formation of intermodulation products with the reception frequency f _RX is thus minimized. This leads to an improvement in the reception quality of the transmission / reception arrangement. FIG. 4 shows a further exemplary embodiment of a transmitting / receiving arrangement according to the invention. In addition to the duplexer 30 and the phase shifter 40, a further duplexer 30a and a further phase shifter 40a are provided. Also, the further duplexer 30a has a first terminal 31a, via which a further transmission signal can be supplied. The further transmission signal generally has a different transmission frequency than the transmission signal at the duplexer 30. Via a second terminal 32a of the further duplexer 30a, a further received signal can be output, which usually also differs in its frequency from the frequency at the duplexer 30. A third terminal 33a of the further duplexer 30a is coupled to the switching input 55 via the further phase shifter 40a. The phase shift of the further phase shifter 40a is adapted to the transmission frequency and reception frequency of the further duplexer 30a and a resulting interference frequency.

To the other switching input 52, 53 duplexer can be connected in the same way with or without phase shifter. This is not shown here for reasons of clarity.

With the transmission / reception arrangement shown in FIG. 4, it is possible to achieve a minimization of the intermodulation products formed in each case for different frequency bands and / or radio standards.

For example, in a mobile phone according to the UMTS standard, the transmission frequency f _τx 1950 MHz. At a duplex distance Δf2 of 190 MHz, a reception frequency of 2140 MHz results. A relevant frequency f _b lies around the Duplex distance Δf2 below the transmission frequency f _τx and thus at 1760 MHz. A dimensioning of the phase shifter can thus take place for this interference frequency f _B.

FIG. 5 shows an exemplary embodiment of a switching device

50 according to the invention. The switching inputs 52, 53, 54, 55 are connected via transistors 56, 57, 58, 59 with the switching output

51 coupled. A control of the transistors 56, 57, 58, 59, which are formed as field effect transistors, takes place via control terminals 560, 570, 580, and 590, respectively. In operation of the transmission / reception arrangement, one transistor is usually conductively controlled, while the other transistors are disabled. This ensures that only one duplexer is conductively coupled to the switching output and an antenna 20 which can be connected thereto. A formation of intermodulation products takes place in the switching device 50 in particular by the nonlinear properties of the junction capacitances of the respectively blocked transistors. By using one or more phase shifters for coupling one or more duplexers, it becomes possible to realize a transmission / reception arrangement with a plurality of frequency bands and / or radio standards, without the reception quality being impaired by intermodulation products.

FIG. 6 shows an embodiment of an LC network according to the invention. The phase shifter 40 may also comprise an LC element 42 instead of or in addition to a line 41. This has a coil L and two capacitors Cl, C2. The combination of the coil L and the capacitors Cl, C2 causes a phase shift of a signal passing through the LC-member 42. This results in an impedance transformation on, which acts as a transformation of the reflection factor of a duplexer for the disturbance frequency. The values of the inductance of the coil L and the capacitances of the capacitors C1, C2 are to be adjusted according to the original reflection factor of the duplexer for the disturbance frequency and the disturbance frequency.

The inventive principle can be used for example in a dual-mode telephone, that is, in a telephone for operation according to the UMTS and the GSM standard.

LIST OF REFERENCE NUMBERS

10: nonlinear element 20: antenna

30, 30a: Duplexer

31, 32, 33: terminals 31a, 32a, 33a: terminals 40: phase shifter

41: pipe

42: LC network

1: length

50: switching device

52, 53, 54, 55: switching input

51: Switching output

56, 57, 58, 59: Transistors

560, 570, 580, 590: control inputs

U, U _Max : amplitude

L: coil

Cl, C2: Condenser f _B : Interference frequency fRx: Reception frequency f _T χ: Transmission frequency fi _M3 Intermodulation frequency

Δfl, Δf2: frequency spacing λ: wavelength r: reflection factor

Claims

claims

A transmission / reception arrangement comprising a nonlinear element (10); an antenna (20) connectable to the non-linear element (10); a duplexer (30) having a first terminal (31) for supplying a transmission signal, a second terminal (32) for outputting a reception signal, and a third terminal (33); and a phase shifter (40) coupling the third port (33) of the duplexer (30) to the non-linear element (10).

A transceiver assembly according to claim 1, wherein the non-linear element (10) comprises switching means (50) having a plurality of switching inputs (52, 53, 54, 55) and a switching output (51); the antenna (20) is connectable to the switching output (51); and the phase shifter (40) couples the third port (33) of the duplexer (30) to one of the shift inputs (52, 53, 54, 55).

3. transmission / reception arrangement according to claim 2, comprising a further duplexer (30a) having a first terminal (31a) for supplying a further transmission signal, a second terminal (32a) for emitting a further received signal and a third terminal (33a) , and a further phase shifter (40a) which couples the third terminal (33a) of the further duplexer (30a) to a further one of the switching inputs (52, 53, 54, 55).

4. Transceiver assembly according to claim 2 or 3, wherein the switching device (50) comprises a plurality of transistors (56, 57, 58, 59) each having one of the switching inputs (52, 53, 54, 55) with the switching output ( 51).

5. Transceiver assembly according to claim 4, wherein the transistors (56, 57, 58, 59) are designed as field effect transistors.

6. Transceiver arrangement according to one of claims 1 to 5, wherein the duplexer (30) is adapted to process the transmission signal and the reception signal in full duplex operation.

The transceiver assembly of claim 6, wherein the duplexer (30) comprises a duplex filter having two bandpass filters.

8. Transceiver assembly according to one of claims 1 to 7, wherein a reflection factor of the duplexer (30) for a noise signal with a noise frequency (f _B ) by the phase shifter (40) is transformed such that an amplitude (U) of the Interference signal at the nonlinear element (10) is minimized.

9. Transceiver according to claim 8, wherein a frequency difference (Δfl) of a transmission frequency (fixed) of the transmission signal to the interference frequency (f _B ) equal to a frequency spacing (.DELTA.f2) of a reception frequency (f _RX ) of the received signal to the transmission frequency (f _T χ) is.

10. Transceiver assembly according to one of claims 1 to 9, wherein the phase shifter (40) comprises a line (41) having a length (1), which depends on a desired frequency and a desired phase shift.

11. Transceiver assembly according to claim 10, wherein the line (41) is a λ / 4 line.

12. Transceiver assembly according to one of claims 1 to 9, wherein the phase shifter (40) comprises an LC network (42).

13. Transceiver arrangement according to one of claims 1 to 12, which is designed for operation according to the Universal Mobile Telecommunications System Standard and / or the Global System for Mobile Communications Standard.

14. Use of a transmitting / receiving arrangement according to one of claims 1 to 13 in a mobile communication device.

15. A method of signal processing in a transceiver assembly comprising the steps of:

Transmitting a transmit signal having a transmit frequency (f _T χ) over a signal path comprising a duplexer (30) and a nonlinear element (10);

Receiving a received signal having a reception frequency (f _RX ) and a noise signal having a noise frequency (f _B ) via the signal path; Transforming a reflection factor of the duplexer (30) such that an amplitude (U) of the spurious signal at the nonlinear element (10) is minimized.

16. The method of claim 15, wherein the transforming by a phase shifter (40).

17. The method of claim 15 or 16, wherein the transforming by a line (41) having a length (1), which depends on a desired frequency and a desired phase shift.

18. The method of claim 17, wherein the line (41) is a λ / 4 line.

The method of claim 15 or 16, wherein said transforming is by an LC network (42).

20. The method according to any one of claims 15 to 19, wherein the transforming an amplitude of an intermodulation signal is minimized, which is formed at the non-linear element (10) from the transmission signal and the noise signal.

21. The method according to any one of claims 15 to 20, wherein the non-linear element (10) comprises a switching device (50) over which further signal paths each with a further duplexer (30a) can be formed, and reflection factors of the respective further duplexer (30a ) like this be transformed such that the amplitude (U) of the interference signal at the non-linear element (10) is minimized.

22. The method according to any one of claims 15 to 21, wherein a frequency difference (Δfl) of the transmission frequency (f _T χ) to the interference frequency (f _B ) equal to a frequency spacing (.DELTA.f2) of the reception frequency (f _RX ) to the transmission frequency (f _T χ) is.

23. The method according to any one of claims 15 to 22, wherein the transmission and reception via an antenna (20).

24. The method according to any one of claims 15 to 23, wherein the transceiver arrangement is designed for operation according to the Universal Mobile Telecommunications System Standard and / or the Global System for Mobile Communications Standard.