WO2007077442A1 - Coupleur d’énergie électromagnétique et réseau d’antennes - Google Patents

Coupleur d’énergie électromagnétique et réseau d’antennes Download PDF

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Publication number
WO2007077442A1
WO2007077442A1 PCT/GB2007/000007 GB2007000007W WO2007077442A1 WO 2007077442 A1 WO2007077442 A1 WO 2007077442A1 GB 2007000007 W GB2007000007 W GB 2007000007W WO 2007077442 A1 WO2007077442 A1 WO 2007077442A1
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WO
WIPO (PCT)
Prior art keywords
electro
magnetic energy
coupler according
transmission means
energy transmission
Prior art date
Application number
PCT/GB2007/000007
Other languages
English (en)
Inventor
Jimmy Ho
Lance Darren Bamford
Christopher Ian Wilkinson
Sijiao Sun
Original Assignee
Jaybeam Limited
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Jaybeam Limited filed Critical Jaybeam Limited
Publication of WO2007077442A1 publication Critical patent/WO2007077442A1/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/04—Coupling devices of the waveguide type with variable factor of coupling

Definitions

  • the present invention relates to an electro-magnetic energy coupler and an antenna array.
  • Mobile communications operators optimise the antennas in their network based on a number of antenna parameters, in particular the elevation and azimuth beamwidths (unless otherwise stated, reference to beamwidth refers to the beamwidth measured from the 3dB points, that is the angle (in degrees) between the half power points of the main lobe of the beam) and the direction that the beam is steered in. Mobile communications operators wish to be able to accurately control these parameters.
  • Mobile communications antenna systems should be compact. This provides two advantages. Firstly, if the antenna is compact it is generally lightweight, and hence easier to install. Secondly, a compact antenna is less visible, which is particularly important as people are becoming increasingly concerned with the • visual impact of mobile communications antennas on their environment and smaller antennas are less intrusive.
  • the azimuth beamwidth that antenna manufacturers provide to mobile telecommunication operators is a defined range of values from small to large azimuth beamwidth.
  • base stations provide defined, fixed azimuth beamwidths of 35 ° +5 ° , 45 ° ⁇ 5 ° , 65 ° ⁇ 5 ° and 85 ° +5 ° .
  • antennas that have an azimuthal beamwidth variable between 35° ⁇ 5 ° to 85° ⁇ 5° are in great demand.
  • the azimuth beamwidth of an antenna can be controlled and adjusted using various techniques. These are described below.
  • the azimuth beamwidth is controlled by restricting the aperture of the antenna using a metallic structure around the aperture. Reducing aperture width leads to increased azimuth beamwidths and vice versa. Hence, using this technique, a compact antenna cannot provide a small azimuth beamwidth.
  • a patch element can be used to give a similar effect to reducing aperture size.
  • the patch can be theoretically modelled by two magnetic dipoles in an array formation, with each magnetic dipole located at the patch edges.
  • the distance between the magnetic dipoles dictates the azimuth beamwidth via the array factor (this is the effect of the arrangement of the array on the output radiation pattern) hence it is difficult to achieve large stable azimuth beamwidths with patch elements for bandwidths greater than 15% of the average or mean operating frequency.
  • a technique often used to widen the beamwidth of a dual polarised patch is to use dielectric loading which reduces the distance between the magnetic dipoles thereby reducing the aperture dimensions and hence widening the azimuth beamwidth.
  • a typical azimuth beamwidth is around 75 ° .
  • the ground plane needs to be minimised to allow back scattering of the field.
  • Forcing a dual polarised patch antenna to produce large azimuth beamwidths has other implications on its performance particularly in isolation, which can be significantly degraded and narrow banded.
  • a patch element is typically used for a 65° azimuth beamwidth. They are also used for 35° azimuth beamwidth. In which case, patch antennas are arrayed together in the azimuth plane, which increases aperture width for a decrease in azimuth beamwidth. This system does not provide an antenna with an azimuth beamwidth that can be varied through a range of beamwidths.
  • US Patent US-B-6774854 discloses an alternative for implementing variable azimuth beamwidth control.
  • the method employs a hinge between two patch elements.
  • the azimuth beamwidth is varied by varying the relative orientation between the two patch elements.
  • This arrangement gives rise to pattern perturbation for larger beamwidths which can be restrictive to mobile communication operators.
  • Another difficulty encountered with this arrangement is that the feeds to the patch elements need to be flexible in order to allow for the hinge movement. It is difficult to make suitable feeds.
  • the azimuth beamwidth of an antenna array can be altered by selecting the relative powers transmitted to the individual elements in the antenna array.
  • Coupled-line couplers are usually used to transmit a fixed power level from a power source to an antenna element.
  • An example of a coupled-line coupler 10 is shown in Figure 1. It comprises two parallel strip lines 12 and 14 that are electro- magnetically coupled over a length of approximately a quarter of a wavelength of the mean or average operating wavelength of the coupler 10.
  • the input stripline 12 comprises a through line 16 that has a coaxial input 18 electrically connected to a first coaxial output 20 via a quarter wavelength coupled section 22.
  • the output strip line 14 comprises a through line 24 that has a coaxial coupled output 26 electrically connected to a second coaxial output 28 via a quarter wavelength coupled section 30.
  • the outer sheath 32 of the first coaxial output is electrically connected to the inner core 34 of the second coaxial output 28 via a 50ohm electrical resistor 36.
  • the transmitted power level in coupled-line couplers 10 cannot be varied satisfactorily because changing the transmitted power level changes the impedance match between the coupled section 22 and the coaxial coupled output 26.
  • the coaxial coupled output section 26 has to overlap with the through line 16 and this results in a very large impedance mismatch.
  • another coupled-line coupler 10 must be installed that is configured specifically to transmit the required power level, for the required azimuth beamwidth.
  • a typical requirement is an amplitude range of -9dB to -35dB of coupling power to the output ports with a +0.5dB amplitude variation at each amplitude value and good impedance match across the operating frequency band.
  • US Patent US-B-6809694 discloses an antenna system comprising five columns of antenna elements with each column comprising ten antenna elements. Phase control of the antenna elements in each column can be used to control the azimuth beamwidth. This patent also discloses phase control to steer the elements in the azimuth plane. This leads to distortion at the measured azimuth plane 3dB and 1OdB points as the pointing angle is increased. Furthermore, this arrangement gives a large azimuth aperture.
  • a preferred embodiment of the invention is described in more detail below and takes the form of an electro-magnetic energy coupler 100 for varying the electromagnetic energy supplied from an input 102 to an output 104.
  • the coupler 100 comprises an input 102 including a first electro-magnetic energy transmission means 110 and a second electro-magnetic energy transmission means 138 spaced from the first electro-magnetic energy transmission means 110 and electrically connected to it.
  • the coupler 100 also comprises an output 108 electro-magnetically coupled to the input 102.
  • the coupler 100 is arranged such that as the electro-magnetic coupling between the input 102 and output 108 is varied, the input 102 and output 108 remain substantially impedance matched.
  • An antenna array 400, 500, 600 is also described comprising at least one antenna 308, 402, 404, 406 wherein the electro-magnetic energy transmitted to the at least one antenna 308, 402, 404, 406 is controlled by the electro-magnetic energy coupler 100.
  • Figure 1 is a schematic diagram of a known coupled-line coupler
  • Figure 2 is a perspective view of a coupler embodying an aspect of the present invention with a slider in a first position;
  • Figure 3 is a perspective view of the coupler of Figure 2 with the slider in a second position
  • Figure 4 is a perspective view of the slider of the coupler of Figures 2 and 3;
  • Figure 5 is a plan view of an impedance matching means of the coupler of Figures 2 and 3;
  • Figure 5a is a side view of a portion of the coupler of Figure 6;
  • FIG. 6 is an exploded perspective view of another coupler embodying the present invention.
  • FIG. 7 is a schematic diagram of an antenna array embodying another aspect of the present invention.
  • Figure 8 is another schematic diagram of the antenna array of Figure 7;
  • FIG. 9 is a schematic diagram of an antenna array embodying an aspect of the present invention.
  • Figure 10 is a schematic diagram of another antenna array arrangement embodying an aspect of the present invention
  • Figure 11 is a perspective view from above of the interior of an antenna array embodying an aspect of the present invention
  • Figure 11a is a schematic view of the antenna array of Figure 11 ;
  • Figure 12 is a perspective view of a portion of the antenna array of Figure 11 ;
  • Figure 13 is a perspective view from above of a component of the exterior of the antenna array of Figure 11 ;
  • Figure 14 is a perspective view from below of a portion of the interior of the antenna array of Figure 11 ;
  • Figure 15 is a perspective view from below of a portion of Figure 14;
  • Figure 16 is a perspective view from below of another portion of Figure 14.
  • Figure 17 is a perspective view of a section through a component of the interior of the antenna array of Figure 11.
  • the coupler 100 comprises a coaxial input 102 electrically connected to a coaxial output 104 via a quarter of the mean or average operating wavelength long coupled section 106.
  • the coupled section 106 is electro-magnetically coupled to a coaxial coupled output section or electro-magnetic output portion 108 such that a fraction of the energy entering the coaxial input 102 is transmitted to the coaxial coupled output section 108 and a fraction is transmitted to the coaxial output 104.
  • the coupler 100 can vary the transmitted microwave power while substantially retaining an impedance match between the power source and an output device, such as an antenna or antenna array (the output device is not limited to being an antenna or antenna array).
  • the coupler 100 comprises an electro-magnetic energy input portion or through line 110 comprising a first electro-magnetic energy transmission means in the form of a planar microwave transmission line generally in a U shape 112 having arms 114 that are parallel to each other and that are electrically connected together by an elongate body portion 116 extending perpendicular to one end of each of the arms 114 to join the arms 114 together.
  • Leg portions 118 project outwardly perpendicular to each of the free ends 120 of the arms 114.
  • the leg portions 118 narrow at their outer edge 122 as they join the free ends 120 of the arms 114.
  • the arms 114 narrow at the ends 124 that join to the body portion 116 and the body portion 116 continues to narrow to a trunk 126 that has parallel sides 128.
  • the free end 130 of one of the leg portions 118 forms an input port 132 and the free end 130 of the other leg portion 118 forms a first output port 134.
  • the body portion 116 is electrically connected to an impedance matching portion 136, which is shown best in Figure 5.
  • the impedance matching portion 136 comprises a second electro-magnetic energy transmission means 138 in the form of a very high impedance microwave transmission line 140 (the first very high impedance microwave transmission line) or electrical connection.
  • the transmission line 140 projects outwardly perpendicular to the body portion 116 from a position half way along the body portion 116.
  • the transmission line is narrower than the body portion and it projects slightly from the body portion 116.
  • the second electro-magnetic energy transmission means 138 further comprises a second high impedance microwave transmission line 144.
  • the first very high impedance transmission line 140 has a higher impedance than the second high impedance transmission line 144.
  • the second high impedance microwave transmission line is electrically connected to the first very high impedance microwave transmission line 140 and extends parallel to the body portion 116 and along most of its length, forming a T shape electro-magnetic energy transmission means or parasitic line 146.
  • a plurality of second 138 electro-magnetic energy transmission means are provided. Preferably, between two and ten second electro-magnetic energy transmission means are provided. In the illustrated example, a total of four are provided.
  • the further second electro-magnetic energy transmission means 138, 142 extend from the centre of a neighbouring electro-magnetic transmission means to form a plurality of T shape sections 146 projecting from one another.
  • the second high impedance microwave transmission line 138 has a circular cross section. However, the line 138 may have other shape cross sections, for example, square or rectangular.
  • the first very high impedance microwave transmission lines 140 are 0.001 times the average or mean operating wavelength long. They are 0.001 times the average or mean operating wavelength wide.
  • the second high impedance microwave transmission lines 138 are one quarter of the average or mean operating wavelength long and approximately 0.001 times the average or mean operating wavelength wide.
  • the spacing 148 between the cross portion of each of the T shape sections 146 is very close. In this example, the spacing 148 is 0.001 times the average or mean operating wavelength.
  • the coupler 100 further comprises a slider 150 that forms an electro-magnetic energy coupling between the impedance matching portion 136 and an electro-magnetic energy output portion 108.
  • the slider 150 is slideable along a slide axis 152 that extends perpendicular to the axis of the elongate body portion 116.
  • the slider 150 (shown best in Figure 4) is generally a planar U shape comprising a base contact portion 154 and two side contact portions 156 projecting outwardly perpendicular to and from either end of the base contact portion 154.
  • the base contact portion 154 comprises a pair of plates 158,160 that extend outwardly from a base plate 155 along the slide axis 152 from either side of the plane of the slider 150 forming jaws 162.
  • the jaws 162 are adapted to make an electro-magnetic coupling with both sides of the impedance matching portion 136. In this example, the jaws 162 are spaced apart by approximately 2mm.
  • One plate 158 extends further along the slide axis 152 but less far perpendicular to the slide axis 152 than the other plate 160.
  • the side contact portions 156 are electrically connected to and extend from the free ends of the base plate 155.
  • Each of the side contact portions 156 has a narrow entrance portion 164 that is narrower than the base plate 155 and extends from the ends of the base plate 155 to a plate 166.
  • the side contact portions 156 project outwardly from the ends of the base plate 155 in the same plane or base plate 155.
  • Each side contact portion 156 bifurcates at a stop portion 168 into two contact plates 170 that are spaced apart from either side of the plane of the base plate 155 and extend parallel to the slide axis 152 to form an electro-magnetic energy coupling to both faces 172 of the electro-magnetic energy output portion 108.
  • the electro-magnetic energy output portion 108 or power divider is fixed relative to the electro-magnetic energy input portion 110.
  • the electro-magnetic energy output portion 108 is planar and extends along the slide axis 152.
  • the electro-magnetic energy output portion 108 comprises a U shape body 174, in which each of the two arms 178 of the U shape body 174 narrow as they extend to the base portion 180 of the U shape body 174.
  • the electro-magnetic energy output portion further comprises a T shape head 176. It is electrically connected to the centre of the base portion 180 of the U shape body 174.
  • the stem 182 of the T shape head 176 extends along the slide axis 152 from the centre of the base portion 180 of the U shape body 174.
  • the arms 175 of the T shape head 176 extend perpendicularly to the slide axis 152.
  • One free end 184 the T shape head 176 forms a second output port and the other free end 186 of the T shape head 176 forms a third output port.
  • Each of the arms 178 of the U shape body 174 of the electro-magnetic energy output portion 108 is located between two contact plates 170 of the slider 150. An electrical connection is made between both of the contact plates 170 at either side of the slider 150 and the arm 178 of the U shape body 174 that is located between the contact plates 170.
  • an insulating layer 190 is located on the outer surfaces of the impedance matching portion 136 and the outer surfaces of the U shape body 174.
  • the insulating layer 190 is typically 0.05mm thick although it may be between 0.05mm to 0.2mm thick.
  • the insulating layer 190 results in no direct electrical connection between the slider 150 and the electro-magnetic energy input portion 110, and the slider 150 and the electro-magnetic energy output portion 108.
  • the slider 150 is capacitively coupled to the electro-magnetic energy input portion 110 and output portion 108.
  • the insulating layer 190 may be made from adhesive tape, Trackslip (registered trade mark) (a low friction surface finish in the form of PTFE (poly tetrafluoroethylene) containing solder resist)) or Kapton (registered trade mark) (a polymide film).
  • Trackslip registered trade mark
  • Kapton registered trade mark
  • the insulating layer 190 reduces or prevents intermodulation products (IMP).
  • Figure 5a also shows a ground plane 192 spaced from the coupler 100.
  • the coupler 100 is spaced from the ground plane 192 by 2mm (as shown by arrow 194).
  • the gap 196 may be between 0.5mm and 5mm.
  • the component parts of the coupler 100 may be moulded from plastic material or punched from metal.
  • the slider 150 is moved or slid from the electro-magnetic energy input portion 110 towards the output portion 108 (and vice versa) along the slide axis 152.
  • the electro-magnetic coupling between the impedance matching portion 136 and the slider 150 is decreased and as the slider 150 slides towards the impedance matching portion 136 the electro-magnetic coupling between the impedance matching portion 136 and the slider 150 is increased.
  • the electro-magnetic coupling between the base contact portion 154 of the slider 150 and the impedance matching portion 136 is lowest when the stop portions 168 of the slider 150 engage with the free ends 188 of the U shape body 174 of the electro-magnetic energy output portion 108.
  • the stop portions 168 provide a means for preventing the slider 150 from sliding further.
  • the electro-magnetic coupling between the impedance matching portion 136 and the slider 150 is greatest when there is the greatest overlap between the base contact portion 154 of the slider 150 and the impedance matching portion 136. That is to say, the base contact portion 154 is closest to the impedance matching portion 136.
  • An electrical connection is maintained between the slider 150 and the U shape body 174.
  • variable power can be transmitted from the electro-magnetic energy input portion 102 to the electro-magnetic energy output portion 108 by changing the coupling between the input 102 and output portions 108 while maintaining the impedance match between the input 102 and output portions 108.
  • the output portion or power divider 108 first combines and then divides the power input into it. In doing so, the arms 175 of the T shape head 176 of the output portion 108 each receive the same magnitude and phase of electromagnetic energy.
  • the slider 150 is made from moulded plastic metallised with silver.
  • any suitable electrical conductor could be used.
  • the bifurcated contact plates 170 of the slider 150 provide strong electromagnetic coupling because both sides or lips of each plate 170 draw power from the high impedance parasitic lines of the impedance matching means 146.
  • This configuration has very little effect on the impedance match when the slider 150 is slid along the slide axis 152 to achieve different power amplitudes.
  • a second embodiment of a coupler 200 is shown in the exploded view of Figure 6 and like components to those shown in the embodiment of Figures 2 to 5 have been given like reference numerals.
  • the electro-magnetic energy input portion 104 and electromagnetic energy output portion transmission lines 108 have the same shape in plan view as those described above and take the form of a microstrip, stripline or co-planar waveguide. They are made from copper on a single planar plastics substrate 202. They can be made by selectively etching copper from a plastics sheet originally with a surface covered entirely in copper. That is, they are made as a printed circuit board.
  • the slider 150 is provided on a planar superstrate 204 that lies on the surface of the substrate 202.
  • the slider comprises a rectangular, plastics sheet superstrate 204 having a U shape metallic electro-magnetic energy transmission line 206, that is made in the same way as the substrate components described above. That is, they are made as a printed circuit board.
  • the slider 150 is located such that the base 208 of the U shape electro-magnetic energy transmission line portion 206 is aligned with and forms an electro-magnetic coupling with the impedance matching portion 136, and the arms 210 of the U shape electromagnetic energy transmission line portion 206 are aligned with and form an electro-magnetic coupling with corresponding arms of the U shape body 174 of the electro-magnetic energy output portion 108.
  • Two slots 212 are provided in the superstrate 204 beyond the outer edges 214 of the U shape transmission line 206.
  • Tapped through holes 214 are provided in the substrate 202 on either side of the stem 182 of the T shape head 176 of the electro-magnetic energy output portion 108.
  • a plastics (preferably nylon) screw 213 is located through each of the slots 212 and screwed into a tapped through hole 214 in the substrate 202.
  • This arrangement allows the superstrate 204 to be held or pressed to the substrate 202 and the superstrate 204 to be slid in its plane parallel to the surface 214 of the substrate 202 along the slide axis 152 between a first stop position 215, where the screws 213 engage with one end 216 of the slots 212, and a second stop position 218, where the screws 213 engage with the other end 220 of the slots 212.
  • the electro-magnetic coupling is highest and in the second stop position 218 where the base 208 of the U shape transmission line 206 of the superstrate 204 is furthest from the through line 104 the electro-magnetic coupling is lowest.
  • a thin electrically insulating planar layer approximately 0.05mm in thickness can be placed between the substrate 202 and the superstrate 204 to prevent metal to metal contact between the slider 150 and the electro-magnetic energy output portion 108 and electro-magnetic energy input portion 104 which can cause intermodulation distortion at mobile telecommunications base station frequencies.
  • an insulating layer for example Trackslip (registered trade mark) (a low friction surface finish in the form of a PTFE (polytetrafluoroethylene) containing solder resist), adhesive tape, Kapton (registered trade mark) (a polyimide film)), in the form of a 0.05mm thick insulating layer is located between the substrate 202 and superstrate 204 prevents or limits IMP (intermodulation products).
  • IMP intermodulation products
  • the substrate is suspended above a 2mm layer of air.
  • the substrate can be suspended above any non-conductive medium of any height.
  • the disadvantage with increasing the height of the substrate is that the impedance line width becomes too wide.
  • it is preferable to limit the gap to between 0.5mm and 5mm.
  • a coupler or couplers of the types described above can be used to control the azimuth beamwidth of an antenna.
  • Figure 7 illustrates schematically how this can be done.
  • the system 300 comprises an input 302 for electro-magnetic power.
  • the inputted power is fed into a beam shaping control circuit 304.
  • the beam shaping control circuit 304 takes the input power and redistributes it to a plurality of antenna elements 308 (in this case, three antenna elements 308) arranged along an axis 310.
  • the beam shaping control circuit 304 providing power to the two outer antenna elements 312 as well as the centre element 314, very narrow beamwidths are produced by fully illuminating the full aperture width. Broad beamwidths are produced by only providing power to the centre antenna element 314.
  • the couplers 100,200 described above can be used in a beam shaping control circuit 304 to control the azimuth beamwidth, and in particular large azimuth beamwidths ranging from 35 ° to 90 ° , of an antenna array 400 comprising an array of antenna elements 402, 404, 406.
  • Good impedance match and isolation for large azimuth beamwidths is achieved using the dipole implementation, with an array formation, to achieve the required narrow azimuth beamwidth.
  • an array of three antenna elements 402, 404, 406 is used in the azimuth plane.
  • the three dual polarised dipole antenna elements 402,404,406 are located along an axis 408.
  • the antenna elements are electrically connected to a first 410 and second coupler 412 of the type of coupler 100 or 200 described above, to form an azimuth beamwidth controlling set.
  • Each dual polarised dipole antenna element 402,404,406 comprises a first 414 and a second dipole antenna 416 arranged perpendicular to one another, in a cruciform shape.
  • Each dipole antenna 414,416 comprises a T shape planar member 418 in which each half of the planar member forms an inverted L shape half dipole member 420, 422.
  • Figure 8 illustrates how the dual polarised dipole antenna elements 402,404,406 are electrically connected to a pair of couplers 410,412 using coaxial cable 424.
  • any suitable electro-magnetic energy transmission line can be used.
  • the blocks 150 represent slider 150.
  • the couplers 410,412 are electrically connected to the dual polarised dipole antenna elements 402,404,406 as follows.
  • the first dipole members 414 are electrically connected to the first coupler 410.
  • the electrical connections are as follows.
  • the first dipole member 414 of the first outer antenna 402 is electrically connected to the second output port 403 of the first coupler 410
  • the first dipole member 414 of the middle antenna 404 is electrically connected to the first output port 405 of the first coupler 410
  • the second outer antenna 406 is electrically connected to the third output port 407 of the first coupler 410.
  • the second dipole members 416 of the dipole antennas elements 402, 404, 406 are electrically connected to the second coupler 412.
  • the second dipole member 416 of the first outer antenna 402 is electrically connected to the second output port 409 of the second coupler 412
  • the second dipole member 416 of the middle antenna 404 is electrically connected to the first output port 411 of the second coupler 412
  • the second dipole member 416 of the second outer antenna 406 is electrically connected to the third output port 413 of the second coupler 412.
  • the ability to vary the azimuth beamwidth depends on the couplers 410, 412 which adjusts power to the outer antenna elements 402, 406.
  • the beamwidth can be made narrower by increasing the coupling power to the outer antenna elements 402, 406 and broader by reducing power to the outer antenna elements 402, 406.
  • the azimuth beamwidth of an antenna can be changed continuously from 35 " ⁇ 5 O through to 90 ° ⁇ 5 ° depending on the position of the U- shape transmission line or slider 150.
  • the energy coupled to the coupled line or electro-magnetic energy output portion 108 is at its maximum. This results in a 35 ° azimuth beamwidth.
  • the azimuth beamwidth broadens as the energy to the outer antenna elements 402,406 is lowered.
  • the energy coupled to the coupled line or electromagnetic energy output portion 108 is at its minimum. This results in the largest azimuth beamwidth. In this configuration, this is 90°.
  • FIG. 9 shows a schematic of a preferred arrangement of an antenna array 500 using azimutha! beamwidth controlling sets of the type described above. Furthermore, the antenna array 500 can be scanned in the azimuth plane.
  • the array 500 of Figure 9 comprises single polarisaton antenna elements 308 in contrast to the dual polarisation elements of Figure 8.
  • the antenna array 500 comprises a plurality of antenna elements 308 (single polarisation elements) aligned in a grid configuration.
  • the antenna elements 308 arranged along and spaced apart along a first axis 501 form an azimuth beamwidth controlling set 502 (shown by dashed lines in Figure 9).
  • the antenna elements 308 arranged along and spaced apart along a second axis 505, perpendicular to the first axis 501 form an elevation plane scanning set 503.
  • the antenna array 500 comprises an electro-magnetic signal input 502 (a signal from a mobile telecommunications provider), which is electrically connected to a coupler 100, 200, which is then electrically connected to a plurality of phase shifters 504 (in this case, three phase shifters 504).
  • the coupler 100, 200 is the same as the coupler 410 of Figure 8.
  • the first output port 405 is electrically connected to middle phase shifter 504, which is electrically connected to each antenna element 308 in a middle elevation plane scanning set 503.
  • the second output port 403 and the third output port 407 are each connected to an outer plane shifter 504, which are each electrically connected to each antenna element 308 in an outer elevation plane scanning set 503.
  • Each phase shifter 504 is electrically connected to each of the antenna elements 308 in an elevation plane scanning set 503.
  • the phase of the electro-magnetic signal output from each antenna element 308 in an elevation plane scanning set 503 is different from each other.
  • the electro-magnetic waves from each antenna element 308 interfere with the electro-magnetic waves from the other antenna elements 308, which affects the directionality of the combined electro-magnetic wave of the antenna array 500.
  • the antenna array 500 allows variation in the azimuthal beamwidth by varying the power supplied to each antenna element 308 in each azimuth beamwidth controlling set 502 as described above and as illustrated in Figure 8.
  • Figure 10 shows a schematic of another embodiment of an antenna array 600.
  • the antenna array 600 of Figure 10 comprises single polarisation antenna elements 308 in contrast to the dual-polarisation elements of Figure 8.
  • the antenna array 600 comprises a plurality of antenna elements 308 (single polarisation elements) aligned in a grid configuration.
  • the antenna elements 308 arranged along and spaced apart along a first axis 601 form an azimuth beamwidth controlling set 602 (shown by dashed lines).
  • There are a plurality of azimuth beamwidth controlling sets 602 (in this case, three) spaced apart along a second axis 603 perpendicular to the first axis 601.
  • input power 604 which carries a mobile telecommunications signal from a mobile telecommunications service provider, is input into a phase shifter 606.
  • the phase shifter 606 has a plurality of output ports 608 (output ports 403, 405 and 407 of the coupler 100, 200) (in this case, three).
  • Each of the output ports 608 is electrically connected to a coupler 610, of the type described above.
  • Each coupler 610 has a plurality of output ports 612 (in this case, three).
  • Each output port 608 of each coupler 610 is electrically connected to an antenna element 308 of an azimuth beamwidth controlling set 602.
  • the phase of the electromagnetic waves transmitted to the azimuth beamwidth controlling sets 602 can be varied relative to one another. This allows the electro-magnetic radiation transmitted from the antenna array 600 to be scanned electrically in the elevation plane. Varying the power between the antenna element 308 of an azimuth beamwidth controlling set 602 varies the azimuth beamwidth of the
  • Scanning in the azimuth plane is achieved by mechanically tilting the whole antenna array 600 as illustrated in Figure 11a.
  • the preferred embodiment is to steer the beam mechanically. This allows the pattern purity of the signal output from the antenna array 600 to be preserved. The system for doing this is described in below.
  • Scanning in the azimuth plane is achieved by mechanically tilting the whole antenna array 500. An arrangement similar to that described below is also used to mechanically tilt the whole antenna array 500.
  • the antenna system 700 comprises an elongate substrate 702 on which an array of dual polarised dipole antenna elements 308 of the type described above are mounted.
  • the substrate 702 is mounted to an elongate chassis 704 by a plurality of rotatable supports 706 (in this example, four supports), which are spaced apart along the longitudinal axis 708 of the chassis 704.
  • the supports 706 are shown best in Figure 12.
  • Each support 706 comprises a base 710, which is coupled to the chassis 704 (not shown in Figure 12).
  • An electric motor (not shown) having a body and a driven axle is attached to the base 710.
  • the body of the electric motor is coupled the base 710.
  • the driven axle of the electric motor is attached to a gearing mechanism that allows the table 712 to be pivoted about a pivot axle 714 in its centre.
  • the table is attached to the substrate 702.
  • Aluminium ground planes 716 project outwardly from the surface of both ends 718 of the chassis 704 (see Figure 11) and are complementary in shape to the radome 720 (shown in Figure 13), which covers the substrate 702.
  • the radome 720 is elongate and has an arch-shape cross section.
  • the radome 720 is made from fibreglass.
  • the radome 720 is connected to the sides 722 of the chassis 704.
  • an antenna array three antenna elements 308 wide (in the azimuth plane) by fourteen antenna elements 308 long (in the elevation plane) is provided.
  • Other numbers of antenna elements 308 may be used depending on the required antenna array specification.
  • the dipole antenna elements 308 are spaced apart by 0.61 ⁇ in the azimuth plane.
  • the dipole elements are spaced apart by 0.77 ⁇ in the elevation plane (where ⁇ is the mean or average operating wavelength). These spacings are the minimum distances that provide isolation between the elements of better than 3OdB.
  • the dipole antenna elements 308 can be spaced apart by other distances. Preferably, the dipole antenna elements 308 are spaced apart in the azimuth plane by 0.35 ⁇ to 1.1 ⁇ . Preferably, the dipole antenna elements 308 are spaced apart in the elevation plane by 0.35 ⁇ to 1.1 ⁇ .
  • Figure 15 illustrates clamping springs 750. They keep a required pressure between the substrate 202 and superstrate 204. That is, they keep pressure between the U sections and the circuit board over which U sections slide.
  • a feed network links the dual polarised dipole elements 308 to the variable coupled line couplers 100 described above ( Figure 17).
  • Any transmission medium can be used, for example, coaxial lines, microstrip lines, stripline or co- planar waveguides.
  • a set of phase shifters 606 (as shown in Figure 16) is provided to scan the beam in the elevation plane (as described above), and a number of variable coupled line couplers (as described above) are provided for shaping the azimuth beamwidth. The azimuth scan and elevation scan operate independently of each other.
  • a control signal is sent to the electric motors, which causes the driven axle of the electric motors to rotate and thus the tables 712 tilt about their pivot axles 714.
  • Rotation of the rotatable supports 706 causes the substrate 702 to rotate inside the radome 720.
  • the scan angle by mechanical steering in the azimuthal plane is restricted to +30 ° although other embodiments can operate at larger scan angles.
  • the dipole antenna elements 308 are steered electrically from 0° to 16° in the elevation plane.
  • Both the azimuth and elevation scan devices can be connected to an Antenna Interface Standards Group (AISG) compliant antenna drive unit (ADU) which allow the telecommunications operator to optimise this antenna system remotely.
  • AISG Antenna Interface Standards Group
  • ADU antenna drive unit
  • Using power control as opposed to phase control to manipulate the azimuth beamwidth minimises the required azimuth aperture width and hence reduces physical size.
  • the proposed technique only requires three array elements in the azimuth plane resulting in an antenna width of less than 2 ⁇ (where ⁇ is the mean or average operating wavelength).
  • the coupler arrangement described herein does not usually require phase compensation as the power to the outer element is altered. However, if phase does become an issue, a phase compensation circuit in the form of the couplers 100, 200 described above can be placed on each of the output ports.
  • the system described above can operate in the PCS band (1850 MHz to 1990 MHz) but it could be extend to other frequency bands such as GSM900 (870 to 960MHz), GSM1800 (1710 to 1880MHz) and UMTS (1900 to 2170MHz).
  • This system is applicable to the majority of first generation to third generation antenna products supplied to mobile communication operators worldwide.
  • variable azimuth beamwidth (and hence variable gain because gain is inversely proportional to the square of the bandwidth), variable azimuth scan and variable elevation scan provide an "all in one" antenna solution for the base station industry.
  • the antenna system described above provides the range of azimuth beamwidths required by the mobile telecommunications base station industry with the required amplitude range, flatness, impedance match across the required operating frequency band, and stability across the operating frequency band.
  • the beam shaping system described herein provides a symmetrical azimuth radiation pattern over all azimuth beamwidth variants required by the base station industry and yet requires only three antenna elements to do so, hence only a narrow aperture width is required. By mechanically scanning in the azimuth plane, the radiation pattern is preserved for all pointing angles.
  • the antenna system is also highly tolerant to errors in the manufacture of the components. It provides telecommunication operators with great freedom when attempting to optimise a network because they have near total control over the transmitted power distribution.
  • the first very high impedance microwave transmission line 140 may be between 0.0005 and 0.003 times the average or mean operating wavelength long. They may be between 0.0005 and 0.003 times the average or mean operating wavelength wide.
  • the second high impedance microwave transmission line may be between 0.0005 and 0.003 times the average or mean operating wavelength wide.

Landscapes

  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

L’invention concerne un coupleur d’énergie électromagnétique (100) pour faire varier l’énergie électromagnétique délivrée d’une entrée (102) vers une sortie (104). Le coupleur (100) comprend une entrée (102) incluant un premier moyen de transmission d’énergie électromagnétique (110) et un deuxième moyen de transmission d’énergie électromagnétique (138) espacé du premier moyen de transmission d’énergie électromagnétique (110) et relié électriquement à celui-ci. Le coupleur (100) comprend également une sortie (108) couplée de manière électromagnétique à l’entrée (102). Le coupleur (100) est conçu de telle sorte que lorsque le couplage électromagnétique entre l’entrée (102) et la sortie (108) varie, l’accord d’impédance entre l’entrée (102) et la sortie (108) est quasiment maintenu. L’invention concerne également un réseau d’antennes (400, 500, 600) comprenant au moins une antenne (308, 402, 404, 406), l’énergie électromagnétique transmise à ladite ou auxdites antennes (308, 402, 404, 406) étant commandée par le coupleur d’énergie électromagnétique (100).
PCT/GB2007/000007 2006-01-05 2007-01-03 Coupleur d’énergie électromagnétique et réseau d’antennes WO2007077442A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
GB0600142A GB0600142D0 (en) 2006-01-05 2006-01-05 An electro-magnetic energy coupler and an antenna array
GB0600142.4 2006-01-05

Publications (1)

Publication Number Publication Date
WO2007077442A1 true WO2007077442A1 (fr) 2007-07-12

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Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102255118A (zh) * 2010-05-17 2011-11-23 摩比天线技术（深圳）有限公司 一种移相器、移相网络及电调天线
US8373514B2 (en) 2007-10-11 2013-02-12 Qualcomm Incorporated Wireless power transfer using magneto mechanical systems
US8378523B2 (en) 2007-03-02 2013-02-19 Qualcomm Incorporated Transmitters and receivers for wireless energy transfer
US8378522B2 (en) 2007-03-02 2013-02-19 Qualcomm, Incorporated Maximizing power yield from wireless power magnetic resonators
US8447234B2 (en) 2006-01-18 2013-05-21 Qualcomm Incorporated Method and system for powering an electronic device via a wireless link
US8482157B2 (en) 2007-03-02 2013-07-09 Qualcomm Incorporated Increasing the Q factor of a resonator
US8629576B2 (en) 2008-03-28 2014-01-14 Qualcomm Incorporated Tuning and gain control in electro-magnetic power systems
US9124120B2 (en) 2007-06-11 2015-09-01 Qualcomm Incorporated Wireless power system and proximity effects
US9130602B2 (en) 2006-01-18 2015-09-08 Qualcomm Incorporated Method and apparatus for delivering energy to an electrical or electronic device via a wireless link
US9601267B2 (en) 2013-07-03 2017-03-21 Qualcomm Incorporated Wireless power transmitter with a plurality of magnetic oscillators
US9774086B2 (en) 2007-03-02 2017-09-26 Qualcomm Incorporated Wireless power apparatus and methods
CN107799860A (zh) * 2017-10-24 2018-03-13 苏州市新诚氏通讯电子股份有限公司 氮化铝30dB带引脚耦合模块

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GB942712A (en) * 1961-08-18 1963-11-27 Sanders Associates Inc A variable transmission line coupler
US3221275A (en) * 1964-04-03 1965-11-30 Alfred Electronics Variable directional coupler utilizing specially shaped coupling aperture, used as non-dissipative microwave attenuator

Patent Citations (2)

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Publication number Priority date Publication date Assignee Title
GB942712A (en) * 1961-08-18 1963-11-27 Sanders Associates Inc A variable transmission line coupler
US3221275A (en) * 1964-04-03 1965-11-30 Alfred Electronics Variable directional coupler utilizing specially shaped coupling aperture, used as non-dissipative microwave attenuator

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8447234B2 (en) 2006-01-18 2013-05-21 Qualcomm Incorporated Method and system for powering an electronic device via a wireless link
US9130602B2 (en) 2006-01-18 2015-09-08 Qualcomm Incorporated Method and apparatus for delivering energy to an electrical or electronic device via a wireless link
US8378522B2 (en) 2007-03-02 2013-02-19 Qualcomm, Incorporated Maximizing power yield from wireless power magnetic resonators
US8378523B2 (en) 2007-03-02 2013-02-19 Qualcomm Incorporated Transmitters and receivers for wireless energy transfer
US8482157B2 (en) 2007-03-02 2013-07-09 Qualcomm Incorporated Increasing the Q factor of a resonator
US9774086B2 (en) 2007-03-02 2017-09-26 Qualcomm Incorporated Wireless power apparatus and methods
US9124120B2 (en) 2007-06-11 2015-09-01 Qualcomm Incorporated Wireless power system and proximity effects
US8373514B2 (en) 2007-10-11 2013-02-12 Qualcomm Incorporated Wireless power transfer using magneto mechanical systems
US8629576B2 (en) 2008-03-28 2014-01-14 Qualcomm Incorporated Tuning and gain control in electro-magnetic power systems
CN102255118A (zh) * 2010-05-17 2011-11-23 摩比天线技术（深圳）有限公司 一种移相器、移相网络及电调天线
CN102255118B (zh) * 2010-05-17 2014-05-07 摩比天线技术（深圳）有限公司 一种移相器、移相网络及电调天线
US9601267B2 (en) 2013-07-03 2017-03-21 Qualcomm Incorporated Wireless power transmitter with a plurality of magnetic oscillators
CN107799860A (zh) * 2017-10-24 2018-03-13 苏州市新诚氏通讯电子股份有限公司 氮化铝30dB带引脚耦合模块
CN107799860B (zh) * 2017-10-24 2023-08-15 苏州市新诚氏通讯电子股份有限公司 氮化铝30dB带引脚耦合模块

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