WO2007069191A2 - Appareil de modulation multi-mode - Google Patents

Appareil de modulation multi-mode Download PDF

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Publication number
WO2007069191A2
WO2007069191A2 PCT/IB2006/054760 IB2006054760W WO2007069191A2 WO 2007069191 A2 WO2007069191 A2 WO 2007069191A2 IB 2006054760 W IB2006054760 W IB 2006054760W WO 2007069191 A2 WO2007069191 A2 WO 2007069191A2
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WIPO (PCT)
Prior art keywords
phase
signal
modulation
modulated
signals
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PCT/IB2006/054760
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English (en)
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WO2007069191A3 (fr
Inventor
Jan Vromans
Gerben W. De Jong
Leonardus J. M. Ruitenburg
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Nxp B.V.
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Priority to EP06842441A priority Critical patent/EP1969796A2/fr
Publication of WO2007069191A2 publication Critical patent/WO2007069191A2/fr
Publication of WO2007069191A3 publication Critical patent/WO2007069191A3/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H04L27/366—Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3211—Modifications of amplifiers to reduce non-linear distortion in differential amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3282—Acting on the phase and the amplitude of the input signal
    • H03F1/3288—Acting on the phase and the amplitude of the input signal to compensate phase shift as a function of the amplitude
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/217—Class D power amplifiers; Switching amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H03F3/45076—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier
    • H03F3/4508—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier using bipolar transistors as the active amplifying circuit
    • H03F3/45085—Long tailed pairs
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/351—Pulse width modulation being used in an amplifying circuit

Definitions

  • the present invention relates to a multi-mode modulation apparatus and method of modulating a carrier signal by a baseband signal in at least two modulation modes.
  • Modulation systems are known for modulating a carrier signal based on a baseband signal, for instance for modulating a radio frequency (RF) carrier based on information which is to be transmitted in a cellular communication system.
  • RF radio frequency
  • variable envelope modulation methods Due to increasing requirements on spectral efficiency, variable envelope modulation methods have become more and more popular.
  • variable envelope modulation methods are disadvantageous in that conventional power amplifiers (PA) may cause heat and/or operation time problems in the transmitter equipment, in particular in thermally limited equipment like terminal devices.
  • PA power amplifier
  • switching mode PAs have been developed to increase power efficiency. These switching mode PAs are however extremely non-linear and may thus lead to increased distortions.
  • Linear Amplification with Non-linear Components in which any arbitrary bandpass signal, which has both amplitude and phase variations is represented by means of two signals which are of constant amplitude and have only phase variations. These two angle-modulated signals can be amplified separately using power efficient non-linear amplifiers. The outputs of these amplifiers are then combined by a summing unit in order to produce the desired variable amplitude signal.
  • a problem of this system is the combination of two non-coherent amplified signals.
  • PWM pulse- width modulation
  • the original signal is coded to a two-level signal that has pulses of varying width.
  • the mean value of the two-level signal follows the desired output signal and can be extracted by filtering.
  • Pulse density modulation (PDM) is an alternative way to accomplish the same task.
  • Another pulse modulation method which resembles the above-described PWM systems, is enabled by a sigma-delta modulation system.
  • a bandpass sigma-delta modulator can be employed for transforming a modulated sinusoidal carrier to a two-level signal.
  • AM amplitude-modulated
  • PM phase-modulated
  • a class of prior art polar-modulation solutions are those where the AM component is added via modulation of the supply voltage of the PA. In order to achieve high power efficiency, this supply voltage modulation should be done via an efficient switching Direct Current-Direct Current (DC-DC) converter. It is however difficult to achieve high modulation bandwidth and to get rid of the switching ripple.
  • a second class of prior-art polar-modulation solutions are those where the input of a switching PA is driven with a two-level PWM signal which is generated by comparing the AM and PM modulated carrier signal with a triangular (or saw-tooth) signal which fundamental frequency is at least twice the carrier frequency. This solution leads to a high PA switching frequency (over-sampling) and severe linearity requirements for the triangular (or saw-tooth) signal.
  • a third class of prior-art polar-modulation solutions are those where the input of the switching PA is driven with a two-level pulse-density signal which is generated by a bandpass sigma-delta converter.
  • this solution requires an even higher PA switching frequency and thus a significant over- sampling ratio.
  • US 2004/0246060 Al discloses a modulation system which provides a two- level signal with a desired modulation suited to be amplified by a switching mode PA.
  • This prior art proceeds from the idea that the known LINC system can be redesigned to provide a two-level constant envelope signal.
  • the information which is to be represented by a final modulation, e.g. amplitude and/or phase of an analog control signal, is coded into two control signals controlling the modulation applied by two constant envelope modulators.
  • the modulation may comprise a phase modulation in case the output constant envelope signals are sinusoidal signals, and a modulation of transition times in case the output constant envelope signals are pulsed signals.
  • the two constant envelope signals are then combined to a single two-level constant envelope signal.
  • a single constant envelope signal is provided in the form of a two-level signal which can be amplified using a single non-linear amplifier, e.g. a switching mode amplifier.
  • a single non-linear amplifier e.g. a switching mode amplifier.
  • the non-coherent power combining of the traditional LINC system can be avoided.
  • the width of the resulting pulses is not discrete, so that quantization noise can be reduced. It is an object of the present invention to provide a multi-mode modulation apparatus and method, by means of which different modulation types, such as PWM and linear modulation, can be provided without any need for over- sampling and linear triangular or saw-tooth signals.
  • phase-modulated outputs of two oscillator means controlled based on first and second control signals, which are derived from the baseband signal, are selectively combined to obtain a predetermined type or mode of modulation.
  • first and second control signals which are derived from the baseband signal
  • AM-PM RF carriers can be generated by linear addition of sine wave or sinusoidal voltage controlled oscillator (VCO) signals, and even polar modulation is possible when the RF carrier is only phase-modulated and the supply of the PA is directly fed with the envelope or amplitude component.
  • VCO voltage controlled oscillator
  • the amplitude modulation of the fundamental frequency of the phase-modulated PWM signal can be used as power control.
  • Such a power control scheme can be used in combination with any conventional way of power control by simply adapting the power supply of the PA. This combination will result in an even higher dynamic range for the power control.
  • the combining means may comprise a logic gate (e.g. OR-gate, AND-gate, NOR-gate, etc. or any combination thereof) for logically combining respective binary square- wave signals generated from the first and second phase-modulated output signals to obtain the modulated output signal in accordance with a pulse-width modulation as a first one of the at least two modulation modes. Additionally, the combining means may comprise adding means for adding the first and second phase-modulated output signals to obtain the modulated output signal in accordance with a linear modulation as a second one of the at least two modulation modes. Thereby, quite simple combination elements can be used to obtain PWM and linear modulated output signals.
  • a logic gate e.g. OR-gate, AND-gate, NOR-gate, etc. or any combination thereof
  • the at least one logical gate may comprise a NOR-gate and an AND-gate for logically combining the respective binary square- wave signals to obtain push-pull signals for a balanced power amplifier, e.g., in a switched operation mode for a two-level modulation mode (such as the PWM modulation mode).
  • the combining means may comprise inverter means for inverting said modulated output signal to obtain push-pull signals for a balanced power amplifier, e.g., in a linear operation mode for a linear modulation mode.
  • the control means may comprise switching means for switching between respective output signals of the OR-gate and the adding means. Again, flexible multi-mode modulation can be obtained in a simple manner by switching between the respective output signals of the combining means.
  • predistortion means may be provided for applying a predetermined predistortion to at least one of a phase-related component and an amplitude- related component of said baseband signal in response to said selective modulation mode, wherein the first control signal is generated by adding the phase -related and amplitude- related components in a summing means and the second control signal is generated by subtracting the phase-related and amplitude-related components in a subtracting means.
  • the selective predistortion provides the advantage that the modulated output signal is optimized based on the selected modulation mode.
  • the predistortion means may be adapted to selectively either remove a sin(x)/x distortion or generate an amplitude- modulated carrier, in response to the selected modulation mode.
  • the first and second controlled oscillator means may be phase-locked by respective phase-locked loop circuits which are connected to a reference oscillator.
  • the transmitting or RF frequency may easily be changed by simply controlling the reference frequency supplied by the reference oscillator.
  • Fig. 1 shows a schematic block diagram of a PLL multi-mode modulator according to the preferred embodiment
  • Fig. 2 shows signal waveforms of the preferred embodiment as obtained by an AM component
  • Fig. 3 shows a waveform of a symmetrical PWM signal at different timings
  • Fig. 4 shows signal waveforms of the preferred embodiment as obtained by a PM component
  • Fig. 5 shows a schematic circuit diagram of an alternative example of a signal combination portion of Fig. 1 suitable for driving a balanced PA
  • Fig. 6A shows an output spectrum in the PWM mode in case of AM only
  • Fig. 6B shows a time signal corresponding to the output spectrum of Fig. 6A
  • Fig. 7 shows an output spectrum of the preferred embodiment in the PWM mode in case of a PM only
  • Fig. 8 shows an output spectrum of the preferred embodiment in the PWM mode in case of AM and PM;
  • Fig. 9 A shows an output spectrum of the preferred embodiment in the linear mode in case of AM only.
  • Fig. 9B shows a time signal corresponding to the output spectrum of Fig. 9A.
  • phase-locked loop (PLL) multi-mode modulator which can be applied to achieve efficient modulation in transmitters for Wireless Local Area Networks (WLANs), WPANs (Wireless Personal Area Networks), Bluetooth systems, Orthogonal Frequency Division Multiplex (OFDM) systems, Global System for Mobile communication (GSM), Universal Mobile Telecommunications System (UMTS), Code Division Multiple Access (CDMA) systems, low-power mobile communication devices, etc.
  • WLANs Wireless Local Area Networks
  • WPANs Wireless Personal Area Networks
  • Bluetooth systems Orthogonal Frequency Division Multiplex
  • OFDM Orthogonal Frequency Division Multiplex
  • GSM Global System for Mobile communication
  • UMTS Universal Mobile Telecommunications System
  • CDMA Code Division Multiple Access
  • Fig. 1 shows a schematic block diagram of the PLL modulation apparatus according to the preferred embodiment.
  • An amplitude component A(t) and a phase component ⁇ p(t) of a baseband signal are supplied to a baseband processing circuit 10 which comprises a selective predistortion unit 110 controlled by a control signal which depends on the selected modulation mode, e.g., PWM or linear modulation.
  • a control signal which depends on the selected modulation mode, e.g., PWM or linear modulation.
  • an amplitude -related phase modulation component ⁇ M (0 and a phase- related phase modulation signal ⁇ p(t) are obtained which are supplied to respective summing nodes 27, 37 of two PLL circuits.
  • the PLL circuits comprise a first VCO 26 and a second VCO 36, which are phase-locked by their respective PLL circuit.
  • the phase-related phase modulation signal ⁇ p(t) is directly supplied to both summing nodes 27 and 37, while the amplitude -related phase modulation signal ⁇ M (0 is directly supplied to the first summing node 27 of the first PLL circuit and via an inverter 40 to the second summing node 37 of the second PLL circuit.
  • the first PLL circuit comprises a PLL loop in which a reference frequency with a reference phase ⁇ ref is supplied to a phase detector 22 where it is compared to an output frequency of the first VCO 26, which has been frequency-divided by a first divider circuit 24.
  • the output of the first phase detector 22 is supplied to a loop filter 28 which supplies the filtered control signal to the first VCO 26 in order to control the phase of the output signal of the first VCO 26 based on the reference phase ⁇ ref of the reference oscillator 50.
  • the modulation is achieved by a third summing node 25 where the summed phase modulation signals ⁇ p(t) and ⁇ M (0 are added to the output of the first phase detector 22 in order to control the phase of the output signal of the first VCO 26.
  • the second PLL circuit comprises a second phase detector 32, a second loop filter 38 and a second divider circuit 34. It operates in a similar manner and comprises a fourth summing node 35 to which the difference of the two phase modulation signals ⁇ p(t) and ⁇ M (t) is supplied and which adds it to the output of the second phase detector 32.
  • phase-modulated output signal ⁇ lo of the first VCO 26 and the phase - modulated output signal ⁇ 2 O of the second VCO 36 are connected to an adding circuit 70 where they are added and supplied to a first terminal of a switch 80. Additionally, the phase- modulated output signals ⁇ lo and ⁇ 2 O of the first and second VCOs 26, 36 are supplied to sign circuits 60 where the sinusoidal signals are converted to binary two-level signals corresponding to the sign of the sinus amplitude. The binary sign signals are then supplied to an OR-gate 62 where they are logically combined (i.e. OR-ed) and supplied to a second terminal of the switch 80.
  • the binary output signal of the OR-gate 62 has a first logical value " 1 " if at least one of the two input sign signals has a first logical value " 1 " . If both input sign signals have the second logical value, i.e. "0", the OR-gate 62 generates the logical output value "0".
  • the switch 80 which may be any electronic switching device, such as a passive or active semiconductor switching element, is controlled by a control signal for selecting the modulation mode, which is also supplied to the baseband processing circuit 10. Based on this control signal, one of the outputs of the OR-gate 62 and the adding circuit 70 is selected and supplied as a modulation output S RF (0 to a PA 90.
  • the power-amplified modulation output may then be supplied e.g. to a transmission antenna via a bandpass filter.
  • the baseband processing circuit 10 comprises only one predistortion unit 110 for applying a predistortion to the amplitude component A(t) in order to generate the amplitude-related phase modulation signal ⁇ M (0-
  • a suitable predistortion may as well be supplied to the phase-related phase modulation signal ⁇ P (t), if desired.
  • PWM RF output signal can be amplitude-modulated and phase-modulated to generate a suitable signal for an efficient switching PA 90.
  • the baseband envelope and phase information is modulated on two locked PLL circuits which are running at RF frequency. OR-gating of the two square- wave VCO output signals will then result in the wanted AM-PM two-level PWM signal.
  • This modulation method there is no need for over-sampling and no need for a highly linear triangular or saw-tooth signal which is normally used for generating PWM signals. Only one additional PLL circuit is required to generate the phase modulation in case of two-level RF carriers.
  • AM-PM RF carriers can be generated by selecting linear modulation and thus linear addition of the sine wave VCO signals, and even polar modulation is possible when the RF carrier is only phase- modulated and the supply of the PA 90 is directly fed with the envelope.
  • phase- modulated signals the amplitude modulation of the fundamental frequency of the phase- modulated PWM signal can be used for power control.
  • the first and second VCOs 26, 36 are phase-locked to the same reference frequency by means of two PLLs. If the PWM modulation mode is selected, the two square- wave output VCO signals are fed to the OR-gate 62, which results in an unmodulated square-wave output signal with a 50% duty cycle. In case of the linear modulation mode, two sine wave VCO signals are added at the adding circuit 70, which results in case of no modulation in a sine wave equal to the reference frequency.
  • the two PLL circuits can be provided with an extra divider to extend the range of the phase detectors 22, 32.
  • both VCOs 26, 36 will become phase-modulated by adding a modulation signal at their loop filter circuits 28, 38.
  • the loop bandwidth of the PLL circuits is sufficient to follow the desired phase modulation which is injected to the loop filter 28, 38.
  • RF-modulated carriers two-level signal
  • RF signals are generated to be used for conventional PA concepts.
  • a corresponding phase predistortion is selected at the predistortion unit 110, and in addition the output of the OR-gate 62 is selected.
  • the predistorted amplitude-related phase modulation signal ⁇ M (0 which represents the envelope or the amplitude information of the baseband signal results in an amplitude modulation of the fundamental of the PWM signal.
  • the first VCO 26 will be phase-modulated with a positive modulation signal + ⁇ M and the second VCO 36 will be phase-modulated with a negative modulation signal - ⁇ M -
  • Fig. 2 shows signal waveforms of the preferred embodiment resulting from the effects of the amplitude-related phase modulation signal ⁇ M (0-
  • the upper waveform indicates the modulation output S RF (0 if the amplitude-related phase modulation is zero.
  • the second and third waveforms indicate effects of a change of the amplitude-related phase modulation signal by ⁇ M -
  • the change ⁇ M leads to a shift of the output signal ⁇ lo(t) of the first VCO 26 to the left and of the output signal ⁇ 2 o (t) of the second VCO 36 to the right.
  • the fundamental of the PWM is amplitude-modulated by a differential predistorted amplitude -related phase modulation signal ⁇ M (0-
  • the fundamental of the PWM carrier can be amplitude- modulated by predistortion of the duty-cycle by removing the sin(x)/x distortion.
  • the fourth waveform of Fig. 2 shows a modulation output S RF (0 for the circuitry of Fig. 1 with increased pulse width and thus lower amplitude of the fundamental frequency of this rectangular signal.
  • S RF modulation output
  • the amplitude of the fundamental has the largest value and a further increase in pulse width will result in a lower amplitude of the fundamental.
  • VCO output signals ⁇ lo(t) and ⁇ 2o(t) could as well be implemented by other logic gates, such as an AND gate, a NOR gate, etc..
  • the lowest two curves of Fig. 2 show modulation outputs S RF (0 if the OR-gate 62 is replaced by an AND-gate and a NOR-gate, respectively. Still, a suitable AM modulation is obtained.
  • the needed predistortion at the predistortion unit 110 for the PWM modulation mode is described in the following.
  • phase-related phase modulation signal ⁇ p(t) which represents the phase of the baseband signal
  • ⁇ p(t) the phase of the baseband signal
  • Fig. 4 shows signal waveforms similar to Fig. 2 but for the case of a phase-related phase modulation signal ⁇ p(t) only.
  • both output signal ⁇ lo and ⁇ 2 O of the first and second VCOs 26, 36 are shifted in the same direction by the amount of phase-related phase modulation ⁇ P (t), and thus lead to a phase modulation of the modulation output
  • phase predistortion unit 110 If the linear modulation mode is selected, another phase predistortion is selected at the predistortion unit 110, and the output of the linear adding circuit 70 for the output sine waves of the first and second VCOs 26, 36 is selected.
  • the predistortion applied to the amplitude -related phase modulation signal CD M (O, which represents the envelope information of the baseband signal, must be changed to get an amplitude-modulated output carrier.
  • the desired envelope can be expressed as follows:
  • a normal amplitude-modulated signal can be expressed by:
  • the signals generated by the first and second VCOs 26, 36 are given by:
  • phase modulation is done with a common mode phase modulation, so that the total output signals of the first and second VCOs 26, 36 with amplitude and phase modulation can be expressed as follows:
  • ⁇ l o (t) cos( ⁇ 0 t + arccos(A(t)) + ⁇ p(t))
  • ⁇ 2 o (t) cos( ⁇ 0 t - arccos(A(t)) + ⁇ p(t))
  • Fig. 5 shows a schematic circuit diagram of an alternative example of the combination portion of Fig. 1 for combining the VCO output signals ⁇ lo and ⁇ 2 O in a manner suitable for driving a PA 90 which is now in a balanced configuration.
  • push- pull signals sl(t) and s2(t) with basically opposite phase (linear modulation mode) or logical state (PWM modulation mode) have to be applied to respective control terminals (e.g. base terminals) of a balanced transistor pair, while the balanced PWM output signal is then obtained between the respective output terminals (e.g. collector terminals) of the transistor pair.
  • Such a balanced PWM output signal provides the advantage that all even harmonics of the fundamental carrier with their sidebands are cancelled, so that a cleaner spectrum is achieved at the output of the balanced PA 90.
  • the opposite logical state of the push-pull signals sl(t) and s2(t) can be achieved e.g. by replacing the OR-gate 62 of Fig. 1 by a combination of a NOR gate 63 and an AND gate 64 after the sign circuits 60. The respective output terminals of the NOR-gate 63 and the AND-gate 64 are then selectively connected in parallel by the switch 80 to the respective control terminals of the balanced PA 90.
  • the opposite phase of the push-pull signals sl(t) and s2(t) can be achieved e.g. by adding an inverter circuit 72 at the output of the adding circuit 70 of Fig. 1. The respective output terminals of the adding circuit 70 and the inverter circuit 72 are then selectively connected in parallel by the switch 80 to the respective control terminals of the balanced PA 90.
  • Fig. 6A shows an output spectrum in case of a sole amplitude modulation in the PWM modulation mode.
  • the three central spectral lines show the carrier and the two sideband frequencies of a typical amplitude modulation, while harmonics caused by the rectangular shape of the carrier signal start at higher sideband frequencies.
  • Fig. 6B shows a corresponding time signal with the envelope A(t), the RF carrier (RF), the duty cycle (DC) and the predistorted phase modulation (PM).
  • Fig. 6 shows an output spectrum for the case of a sole phase modulation in the PWM modulation mode. This spectrum clearly resembles a typical phase modulation spectrum.
  • Fig. 8 shows an output spectrum in case of a combined amplitude and phase modulation in the PWM modulation mode.
  • Figs. 9A and 9B relate to the case of a linear modulation mode for amplitude modulation only.
  • the absence of any harmonics indicates an amplitude modulation with sinusoidal carrier signal as can be gathered from Fig. 9B where the envelope A(t), the RF signal (RF) and pre-distorted phase modulation (PM) of the PLL circuits are shown.
  • the present invention is not intended to be restricted to the preferred embodiment described above, but can be implemented in any modulation apparatus where at least first and second oscillator circuits are controlled by respective components of a baseband signal to obtain respective phase-modulated output signals.
  • the combination of the phase-modulated output signals is not intended to be restricted to a logical OR- combination and a linear adding operation. Rather, any suitable combination of the two phase-modulated signals can be employed to achieve a desired modulation mode.
  • a multi-mode modulation apparatus and a method of modulating a carrier signal by a baseband signal in at least two modulation modes have been described.
  • the phase of the carrier signal is modulated in response to a first control signal derived from the baseband signal to obtain a first phase-modulated signal
  • the phase of the carrier signal is additionally modulated in response to a second control signal derived from the baseband signal to obtain a second phase-modulated signal
  • combination of the first and second phase-modulated signals is controlled to select one of the at least two modulation modes.
  • information of different components (e.g. phase and envelope) of the baseband signal can be phase-modulated and combined in a suitable manner, so that over- sampling and highly linear triangular or saw-tooth signals are not required.
  • the controlled combination provides a flexible multi-mode modulation scheme.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Nonlinear Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Amplifiers (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

Appareil de modulation multi-mode et procédé de modulation d'un signal porteur par un signal en bande de base dans au moins deux modes de modulation. La phase du signal porteur est modulée en réponse à un premier signal de commande dérivé du signal en bande de base pour obtenir un premier signal à modulation de phase et la phase du signal porteur est de plus modulée en réponse à un deuxième signal de commande dérivé du signal en bande de base pour obtenir un deuxième signal à modulation de phase, une combinaison des premier et deuxième signaux à modulation de phase étant commandée pour sélectionner un desdits au moins deux modes de modulation. De cette façon, l'information des différentes composantes (par ex. la phase et l'enveloppe) du signal en bande de base peut être modulée en phase et combinée de manière appropriée, de telle sorte que le suréchantillonnage et des signaux triangulaires ou en dents de scie hautement linéaires ne soient plus nécessaires. De plus, la combinaison commandée donne un schéma de modulation multi-mode souple.
PCT/IB2006/054760 2005-12-16 2006-12-12 Appareil de modulation multi-mode WO2007069191A2 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
EP06842441A EP1969796A2 (fr) 2005-12-16 2006-12-12 Appareil de modulation multi-mode

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EP05112311 2005-12-16
EP05112311.5 2005-12-16

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WO2007069191A2 true WO2007069191A2 (fr) 2007-06-21
WO2007069191A3 WO2007069191A3 (fr) 2007-10-18

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CN (1) CN101375575A (fr)
WO (1) WO2007069191A2 (fr)

Cited By (5)

* Cited by examiner, † Cited by third party
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US8058927B2 (en) 2007-12-18 2011-11-15 Infineon Technologies Ag Amplifier modulation method and apparatus
CN101552759B (zh) * 2009-05-12 2012-03-21 四川虹微技术有限公司 一种传输模式检测装置
EP2573938A1 (fr) * 2011-09-22 2013-03-27 Alcatel Lucent Procédé d'amplification de signal basé sur une modulation à largeur d'impulsions
US8594724B2 (en) 2009-05-21 2013-11-26 Huawei Technologies Co., Ltd. Multi-mode convergence method, multi-mode combination method, and devices thereof
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EP2733846A1 (fr) * 2012-11-20 2014-05-21 Alcatel-Lucent Modulateur d'enveloppe et procédé de fonctionnement d'un modulateur d'enveloppe
WO2014079862A1 (fr) * 2012-11-20 2014-05-30 Alcatel Lucent Modulateur d'enveloppe et procédé de fonctionnement d'un modulateur d'enveloppe

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