WO2006038834A1

WO2006038834A1 - Method for remotely detecting body-worn weapons and explosives and device for carrying out said method

Info

Publication number: WO2006038834A1
Application number: PCT/RU2005/000496
Authority: WO
Inventors: Leonid Viktorovich Volkov; Alexandr Ivanovich Voronko; Natalya Leonidovna Berendakova
Original assignee: Leonid Viktorovich Volkov; Alexandr Ivanovich Voronko; Natalya Leonidovna Berendakova
Priority date: 2004-10-04
Filing date: 2005-10-03
Publication date: 2006-04-13
Also published as: RU2004128917A

Abstract

The invention relates to computer diagnosis. The inventive method for forming images in a millimetre and sub-millimetre wave range consists in producing a radiation in a wave range consisting of separate partial radiations, in orienting the thus formed radiations towards an observed object at different angles of incidence, in receiving the radiation reflected from said observed object, in converting the received radiation into electric signals and in forming a visually perceptible image of the observed object by means of said electrical signals. Each individual partial radiation is encoded by modulation and transmitted to a diffuser. The radiation reflected from the observed object is transmitted to a receiver. Said method also consists in decoding the partial electric signals, in forming partial images therefrom and in combining the partial images in such a way that a resulting visually perceptible image of the object is formed. The image is formed in the millimetre and sub-millimetre wave range by means of a system comprising a spatially dispersed radiation source, a focusing element, polarising lattices, processing and display devices.

Description

A method for remote detection of weapons and explosives hidden under the clothes of people, and a device for its implementation

Area of use

The present invention relates to the field of computer diagnostics in real time. In particular, to systems and methods for remote detection of weapons, explosives and drugs hidden under clothing on a person’s body or in his luggage, which are based on imaging of such objects, especially in the millimeter and submillimeter wavelengths. State of the art

In the field of remote detection of masked objects based on imaging of objects, millimeter and submillimeter radiation (hereinafter - MM / SMM) has advantages due to the high level of permeability of such radiation through various clothing fabrics, plastic, ceramic, wooden materials and other opaque in visible range of medium. Due to the relatively short wavelength of the MM / SMM radiation, it is also possible to create imaging systems (SFI) that provide the necessary spatial resolution in the images obtained by such systems. Such SFIs can be very effectively used in various crowded places and / or of high state significance (airports, courts, banks, places of emergence of high-ranking statesmen, etc.) in order to timely and covert remote detection of hidden weapons, drugs, smuggling and explosives, including in a rapidly changing environment.

Currently known and widely used methods (detection) for detecting weapons and smuggling carried by people through the outputs and entrances of security zones are based on the use of systems that are sensitive to induction changes in the field of inspection. Most of these methods are limited to binary. (“Yes” / “no”) by the nature of the detection of the presence of metal objects without the possibility of revealing any of their characteristic details, distinctive properties or even information about the location of such objects. Such systems cannot be used for covert, effective, and real-time detection with a low false alarm rate. The sufficient availability of plastic and ceramic weapons makes such traditional detection systems inoperative. In order to reliably visualize and identify weapons of this new class, as well as conventional weapons but with a high level of reliability, stealth and a low level of false positive in automatic mode, mines, as well as the detection and identification of drugs and explosives, fundamentally new methods and technical systems Using MM / SMMSFI for any objects reflecting or emitting MM / SMM radiation allows solving this problem. This is possible due to the fact that MM / SMM radiation penetrates clothing with very little attenuation, and without affecting human health, unlike x-ray and microwave radiation. The reflection and absorption characteristics for MM / SMM radiation for human skin differ significantly from the same characteristics for plastic and ceramic weapons and drugs, as well as the vast majority of materials used for the production of weapons and explosives. This allows you to create contrasting images of objects, made from materials that are hidden on a person’s body under clothing. Due to the transparency for MM / SMM radiation of most materials from which various bags, suitcases, etc. are made, such objects can also be contrastingly observed in baggage.

It is known that passive radiometric MM / SMM SFIs are extremely ineffective in enclosed spaces, where in most cases the remote search. This inefficiency is due to the lack of contrast in the illumination of objects indoors as compared to open spaces where the object is illuminated by a “cold” sky, whose brightness temperature is around T = 70 K and the “warm” surface of the Earth T = 300K. In open spaces, the radio-brightness contrast at the facility can exceed 200 K, while indoors, this contrast does not exceed at best 5-7 K. Since modern high-speed radiometric cameras have a sensitivity of about IK, radiometric images for any practically real systems have low visual quality due to high noise levels and correspondingly low contrast.

To realize the potential of active MM / SMM SFI, it is possible only under certain conditions, imposed mainly on the parameters of the radiation probing the observed object. This primarily relates to the formation of lighting with a low level of radiation coherence in the inspection area. Failure to comply with this condition leads to the acquisition by such MM / SMM SFI images with a high level of coherent noise and, accordingly, low visual quality and information content. Known imaging system in the millimeter and submillimeter wavelength range, containing at least one composite radiation source in the millimeter or submillimeter wavelength range, intended to illuminate the field of view of the specified imaging system and made in the form of a spatially distributed set of separate independent point sources of radiation, bearing the radiation frequency of each of which differs from the carrier frequency of the radiation of any other radiation source from bound set by a small amount, not exceeding the allowable manufacturing deviations fixed carrier frequency for different narrowband radiation sources of the same type produced in the same production conditions, an element for focusing the radiation reflected from the objects of observation located in the specified field of view on the receiving device, made with the function of independently receiving the specified focused radiation incident from various spatial parts of the specified field of view and converting it into the corresponding matrix set of electrical signals, the outputs of which are connected to a device designed to form an image of the field of view from the specified matrix array signals and displaying this image on the display, and each image element is formed by the corresponding electric signal from the specified matrix set, and each electric signal corresponds to radiation reflected from those parts of the observed objects that are located in one of the indicated parts of the field of view and different electrical signals correspond to different parts of this field of view (US patent N ° 5227800, GOlS 13/89, publ. 07/13/1993).

The specified source of information adopted as a prototype for the claimed devices.

From the same source of information, there is a known method of imaging in the millimeter and submillimeter wavelength range, which consists in generating radiation in the millimeter or submillimeter wavelength range, consisting of individual partial radiations that differ in physical parameters of radiation, the direction of the generated radiation toward the object of observation, reception through focusing element of radiation scattered from the zone of the object of observation, converting the received radiation into electrical signals ala and forming electrical signals according to the visually perceived image of the object. The specified source of information is also adopted as a prototype for the claimed objects. This method of active imaging and the corresponding active MM / SMM SFI are based on the original method of generating spatially incoherent quasimonochromatic radiation in the inspection area, which coincides with the SFI field of view. A feature of the method and system of image formation during the detection of an object is the use of a spatially distributed array (matrix) of point sources of MM / SMM radiation as a lighting device. The point sources of the grating are sources of quasi-monochromatic radiation with slightly different central frequencies of the emitted radiation (the frequency distribution is not greater than the standard tolerances for sources of industrial manufacture). Lattices are designed to illuminate an object with radiation with reduced spatial coherence. The image of the object is projected onto a multi-element receiving matrix (MPM) using a focusing lens. The set of electrical signals is generated by the MMM and processed (mixed, amplified, filtered, etc.) electronically so as to form an image of the object and visualize it on the screen of the corresponding display. A significant drawback of such a system is the fact that in the millimeter wave range it is impossible to obtain a high-quality image by simply destroying the spatial coherence of almost monochromatic radiation in the field of view of the SFI, as is done in optical systems. This is due to the almost specular reflection of millimeter-wave radiation from almost all objects of interest for remote detection, in contrast to the diffuse nature of the reflection of optical-band radiation from almost any object (except for a limited number of mirror-type objects). In the MM / SMM wavelength range, only a small number of predominantly fall into the entrance pupil of the focusing element radiation component from the entire wide angular spectrum of the components of a spatially incoherent radiation illuminating the object, which satisfy the condition of specular reflection. Therefore, the spatial coherence of radiation, which mainly focuses on the receiving matrix and is involved in image formation, has a fairly high coherence, even when the radiation illuminating the object is characterized by extremely low spatial coherence. Due to this, the generated images are characterized by a high level of coherent noise (speckles) and are subject to the influence of specular reflections that destroy the quality of the resulting images.

Disclosure of invention

The present invention is directed to solving the above problems, according to which the final (final) image of the SFI is obtained as a result of analysis and synthesis of a sufficient number of partial images of the observed object, obtained independently of each other and each of which is characterized by an independent (and different from each other) set of parameters radiation. Such physical parameters include the carrier frequency of illumination, its polarization state, angle of incidence, etc. The analysis and synthesis of such images (synthesis may be understood, for example, as a weighted accumulation of partial images) is carried out by means of analog or digital electronic (electron-optical) means or their combinations. Such an expanded set of partial images for various combinations of physical parameters allows a much better analysis of objects and interference in the final image, since it allows independent access to such components. Having access to the partial components of the images, for example, it is possible to optimize the weighted combination of such components according to the selected criterion (for example, to minimize the level of (interfering) components, destroying the visual quality of the final image and reducing its information content. Ultimately, unique opportunities open up to identify the distinctive features of the observed objects and significantly increase the likelihood of their correct recognition.

The technical result achieved in this case consists in the detection of masked objects on the human body or in its luggage, regardless of the material from which this object is made, based on the formation of its images with improved visual quality information content.

The specified technical result for the device is achieved by the fact that the device for remote detection of weapons and explosives hidden under clothing of people, containing at least one radiation source in the millimeter or submillimeter wavelength range, made in the form of a set of separate independent radiation elements, the physical radiation parameters of each of which made different from the physical parameters of the radiation of other radiation elements, an element for focusing radiation reflected from the object of observation, in the direction of the receiving device, which has the function of independently receiving radiation incident from the corresponding complementary parts of the area of the observation object and converting it into a matrix set of corresponding electrical signals, the outputs of which are connected to the processor to form an image of the observation object and its location zone and display this image on a display, each image element being formed by a corresponding electrical signal from this matrix set, which corresponds to a spatially defined part of the observed object and its location surrounding area, is provided with a diffuser, located at a distance from the radiation source for receiving the radiation and scattering it in toward the surveillance area, each individual independent radiation element the radiation source is configured to encode radiation by modulating the latter, different from modulation of other separate independent radiation elements, the diffuser is active with the possibility of implementing the function of reducing the spatial coherence of the incident radiation and / or with the possibility of implementing the scattering function of the incident radiation by spatially different parts of the diffuser with additional coding radiation by modulating the scattering properties of these parts of the diffuser, receiving The property is configured to independently receive each coded component of the radiation incident from the area of the observation object, and to convert each electric signal from the matrix set into a set of electrical signals, with each electrical signal from a set of electrical signals corresponding to a separate coded component of radiation, the processor unit is configured to independent reception of individual electrical signals, conversion of each matrix set of electrical signals fishing, obtained from electrical signals with the same coding, into a separate partial image corresponding to it, and forming the resultant image of the object of observation and its location by combining individual partial images or their fragments.

The specified result for the method is achieved in that in the method for remote detection of weapons and explosives hidden under the clothes of people, which consists in the formation of radiation in the millimeter or submillimeter wavelength range, consisting of individual partial radiations that differ in physical parameters, the direction of the generated radiations to the side object of observation, reception of radiation scattered from the object of observation through a focusing element, conversion of received radiation into electrical signal la and the formation of these electrical signals visually perceived image of the observation object, each individual partial radiation is additionally encoded by modulating it, which is different in parameters from the modulation of other partial radiation, directing partial radiation to the diffuser to reduce their spatial coherence and / or scattering them by the various spatial parts of the diffuser to create additional partial radiation with additional modulation, corresponding to the angle of incidence on the object of observation, after reflection of radiation from the object of observation carry out focus The transmission of this radiation and its transmission to a receiving device that receives this radiation independently from each part of the observed space in the area of the object under observation and translates the set of emissions into the corresponding matrix set of electrical signals, decodes the partial electrical signals corresponding to the specified partial emissions from each from the indicated electrical signals of the indicated matrix set, partial images are formed from the matrix sets are different x partial electrical signals, and then combine partial images or fragments thereof to form a visually perceived resulting image of the object.

The indicated features for each of the objects are significant and interconnected with the formation of a stable set of features for each of the objects.

Brief Description of the Drawings The present invention is illustrated by specific examples, which, however, are not the only possible, but clearly demonstrate the possibility of achieving the essential characteristics of the desired result by the given sets.

In FIG. 1 is a generalized block diagram of one of the possible implementations of the active system for the formation of synthesized images; FIG. 2 is a structural diagram of a system for generating synthesized images; FIG. 3 - point-like radiation source in a waveguide implementation; FIG. 4 - a device for frequency conversion and signal processing; FIG. 5 - the first partial image, characterized by the first position of a point-like radiation source relative to the observation area; FIG. 6 is a second partial image characterized by a second position of a point-like radiation source relative to the observation area; FIG. 7 - the third partial image, characterized by the third position of a point-like radiation source relative to the observation area; FIG. 8 is a fourth partial image characterized by a fourth position of a point-like radiation source relative to the observation area; FIG. 9 shows the curves of such partial images

(identical image cross-sections), the physical parameters of the radiation of which are practically close (for example, the frequencies are almost the same

(in the case of a change in the radiation frequency as a parameter), or the illumination angles are almost the same; FIG. 10 - partial images are shown whose physical parameters (the indicated angle of incidence of the components on the object) are different from each other by the amount at which these images for the observed object become statistically distinguishable; FIG. 11 - partial images are shown whose physical parameters (the specified angle of incidence of the components on the object) are different from each other by the amount at which these images for the observed object become statistically distinguishable, however, the average energy images are different due to differences in the "diffuse" and "mirror" reflections from the object of the corresponding radiation components; FIG. 12 - presents the first view of the results of numerical modeling of an object (in shape resembling a gun) having an external similarity in the shape and characteristic dimensions of parts with typical shapes and details for such objects; FIG. 13 - a second view of the results of numerical modeling of an object (in shape resembling a gun) is presented, having an external similarity in the shape and characteristic dimensions of parts with typical shapes and details for such objects; FIG. 14 - shows the gradation scale for the signal level in the corresponding image elements shown in Fig.12-13; FIG. 15 is a structural diagram of an imaging system using an unscannable multi-element spatially distributed radiation source and an unscanned multi-element receiving device; FIG. 16 is a detailed diagram of an adaptive MM / SMM imaging system based on the use of a multi-element spatially distributed radiation source and multi-element receiving device; FIG. 17 is a functional diagram of a generator of two mutually coherent signals, consisting of paired generators with a stabilized frequency of their difference signal; FIG. 18 is a device for receiving multi-component radiation, amplification, decoding and subsequent processing of difference signals of the first type of FIG. 19 - a device for receiving multicomponent radiation, amplification, decoding and subsequent processing of difference signals of the first type FIG. 20 - a device for receiving multicomponent radiation, amplification, decoding and subsequent processing of difference signals of the first type; FIG. 21 is a first example implementation of a mutually coherent signal generator of a BKC generator with a number of generated signals greater than two and with different difference frequency values; FIG. 22 shows phase diagrams of radiation components; FIG. 23 is a diagram of an image forming system illustrating a mechanism for generating strong “mirror” and weak “diffuse” signal components in a received signal; FIG. 25 is a diagram of the MPR of a radiation source; FIG. 26 - shows the spectrum of one of the side components of the resulting radiation in the observation zone; FIG. 27 - shows the fine structure of the spectrum of the signal received by one of the receiving elements of the receiving matrix when forming the image of the object; FIG. 28 shows the fine structure of the spectrum of the signal of FIG. 27 after reducing the level of the mirror components of the spectrum. FIG. 29 is a graphical representation of the distribution of spectral lines of decoded signals corresponding to the fine structure of the spectrum of FIG. 27, in the form of a two-dimensional matrix diagram. FIG. 30 is a graphical representation of the distribution of spectral lines of decoded signals corresponding to the fine structure of the spectrum of FIG. 28, in the form of a two-dimensional matrix diagram. Fig.Zl is an illustration of the features of radiometric and multicomponent image formation. FIG. 32 is an illustration of the position of an object on a person, indicating the arrows of possible reflections forming various partial images; FIG. 33 is an illustration of the process of generating the resulting synthesized image from a set of partial images, from which eliminates noise-like interfering partial images; FIG. 34 is a second example implementation of a mutually coherent signal generator of a BKC generator with a number of generated signals greater than two and with different values of the difference frequencies; FIG. 35 is an example implementation of a mutually coherent signal generator whose composite generators have substantially different frequencies; FIG. 36 is a generalized diagram of a receiving channel of an input node of a receiving device; FIG. 37 - shows the standard input path of the superheterodyne receiver, the first circuit of the input node of the receiving device; FIG. 38 is a second diagram of an input node of a receiving device; FIG. 39 is a third diagram of an input node of a receiving device; FIG. 40 is a fourth diagram of an input node of a receiving device.

BEST MODES FOR CARRYING OUT THE INVENTION FIG. Shows a generalized structural diagram of one of the possible implementations of the active system for the formation of synthesized images.

In this implementation, an active system for generating synthesized images may consist of:

1) Spatially distributed (PR) source 1 of multicomponent radiation of millimeter and / or submillimeter wavelengths, each component 2, 3, 4, 5 of which is characterized by a different set of values of physical parameters, while such components can be either distinctively encoded (for example, distinctively modulated ), or emitted at different points in time. PR source 1 is intended for illumination by multicomponent radiation of the observation zone 6 and the person 7 located in them and the object 8 hidden on his body under the clothes 9;

2) A focusing element 10 (for example, a lens) intended to focus the radiation reflected in the observation zone 6, which is a set of reflected radiation components 11,12,13,14, in the plane of the sharp image 15;

3) A receiving device 16, configured to receive multicomponent radiation at various spatial points on the surface (in particular the plane) of a sharp image (PRIZ), converting the radiation received at each of these PRIZ points into a corresponding primary electrical signal, converting each primary signal to the corresponding a set of separate secondary electrical signals corresponding to the indicated coded (e.g. modulated) radiation components emitted by the indicated PR source at the same time intervals, and / or components emitted at different time intervals, and which are part of the multicomponent radiation adopted at a given point in the PRIZ using decoding procedures (for example, by demodulation) of encoded (modulated) secondary electrical signals and / or time division procedures for the corresponding secondary electrical signals with temporary compaction,

4) The first polarizing grating 17, located between the lens 10 and the sharp image plane 15, which can rotate around the optical axis 18, for transmitting linearly polarizing radiation components with a certain selectable direction of polarization to the receiving device 16, by means of mechanically connected with the first polarizing grating 17 node rotation 19, controlled by external monitoring signals, 5) The second polarizing grating 20, located between the PR radiation source 1 and the observation zone 6, which is equipped with a rotation function around the axis, passed through the center of the PR source 1 and the center of the observation zone 6, through a mechanically connected rotation unit 21, under the control of external control signals for transmitting into the observation zone 6 linearly polarized radiation components, with a certain selectable direction of polarization,

6) a processor device 22 associated with the receiving device 16, the PR radiation source 1, the rotation unit 19 and the rotation unit 21, and is intended, inter alia, to control the operation of the receiving device 16, the PR radiation source 1 and the rotation units 19,21. The processor device has the function of receiving secondary signals and determining, by processing them, the radiation intensity of each of the respective radiation components received by the receiving device 16 at the corresponding points of PRIZ 15, as well as the formation of numerous partial images, the values of the elements (counts) of which correspond to the intensities of those radiation components which are received at various points of the sharp image plane (PRIZ) by the receiving device 16, and whose physical parameters either almost identical, or lie in certain ranges, or are selected based on the same selection criteria. Moreover, for the formation of each element of the partial image, only one component of the radiation components received by the receiving device in the corresponding spatial element of the spatial point of the sharp image plane is used. The processor device 22 is also intended to perform the function of synthesizing high-quality images, including by weighted summation of partial images or their limited fragments. Such fragments may include a small number of elements (counts) of images, up to one element.

The fraction of the value of the element value of each of the partial images used to generate the value of the corresponding element of the synthesized image is determined in accordance with the algorithm for achieving the best quality of the synthesized image and depends on the parameters of the radiation component responsible for the formation of this partial image and the reflection characteristics of this component the surface area of the object that is displayed by this pixel, as well as the characteristics neighboring areas of the surface.

The processor device 22 may also perform the function of automatically recognizing images and identifying a masked object 8 from this image. 7) The display device 23 is intended to visualize the obtained images by displaying them on the display screen of the display device 23, which is associated with the processor device 22.

The processor device can control the position of the polarization gratings 17, 20 by supplying the corresponding control signals to their control nodes 19,21, which allows the formation of polarization-dependent (in particular, formed by both co- and cross-polarized radiation components) partial images Under coding different radiation components hereinafter, we will understand the procedures for the distinctive marking of these radiation components or, in other words, the endowment of each component you (or more substantially identical components on physical parameters) feature. Such coding is carried out in a multi-component PR radiation source. The coding procedures for radiation components may be based on distinctive modulation (amplitude modulation, frequency modulation, phase modulation, etc.) of various radiation components by different modulating signals or, for example, on the formation of radiation, the distinctive radiation components of which are doublet radiation components, the spectral lines of each doublet (these two spectral lines in their physical properties can correspond to practically equivalent emissions) differ from each other in the carrier frequency by an amount that is times ichna for various doublets. (Components can be multiplet as well, and their spectral lines, including, correspond to various physical parameters, for example, different polarization states). Under the coding can be understood other procedures for endowing the hallmark of various components of the radiation. In this case, in the receiving device, from the primary electrical signals generated by the receiving device from the focused radiation received at various points of the PRIZ 15, numerous secondary electrical signals can be extracted by means of corresponding decoding devices (for example, demodulating devices), each of which corresponds to only one of them encoded (e.g. modulated) components. In this case, the coding (for example, modulating) procedures of the radiation components and decoding (for example, demodulating) of the electrical signals corresponding to them should be carried out in such a way that the intensity of each of the corresponding focused radiation components received by the receiving device in the specified spatial Prize points 15.

The processor device is configured to receive all secondary signals for all of these sets and determine, through their processing, the radiation intensity of each the corresponding radiation component, from the set of components received by the receiving device 16 at the corresponding points of PRIZ 15 and the formation of numerous partial images, moreover, the value of any element of each partial image is assigned the intensity value of only one of the secondary signals, and from that set of secondary signals that corresponds to radiation received at a certain spatial point in PRIZ 15. The position of the PRIZ point relative to other points of reception of radiation PU16 in PRIZ respectively tstvuet position corresponding element (frame) of the partial image with respect to its other components (samples). Each secondary signal from all sets of secondary signals is involved in the formation of only one image element (reference) for all of the generated partial images. If for the formation of a partial image for some reason the received secondary signals are not enough, then the corresponding elements are assigned some specific value (for example, equal to zero). The selection of secondary signals for the formation of each of the partial images is carried out according to a pre-selected selection criterion. Advantageously, each partial image is formed from secondary signals formed from the same radiation component, but received by PU 16, respectively, at different spatial points of PRIZ 15 (if a multi-element receiving device is used) or various radiation components (radiated at different points in time, which due to the scanning principle of reception of the used PU16), but with the same physical parameters or different radiation components with similar physical parameters (if some physical parameters of the radiation components of the PR source 1 are also scanned over time), etc. Next, the processor device 22 synthesizes a high-quality image of the observation zone 6 and those located in them objects, for example, a person 7 and hidden under the clothes 9 of the object 8 from the received partial images. Previously, each of the partial images can be subjected to one of the traditional image analysis procedures (for example, identifying image elements corresponding to areas of the surface of the object 8 that mirror this component of radiation, therefore, the magnitude of its intensity in which elements of the corresponding partial image is too large in comparison with the corresponding elements of other partial images) and partial image processing procedures (for example, spatial f filtering and / or reducing or removing (replacing a knowingly small value) the values of the elements corresponding to the mirror-reflected components of the radiation) in order to improve their quality. (In some cases, the traditional partial image processing procedures may also not be used at all.) After this, the procedure for generating the resulting image synthesis using the obtained set of partial images is initiated. These partial images are used in the synthesis procedure of the resulting (combined) image, while the synthesis procedure can use all of the formed partial images, so maybe only part of these images, or only fragments of part or all images (and fragments can consist of any number partial image elements, including from only one element). Further, the above image synthesis procedures will be called partial image combining procedures or also called partial image combining procedures. The procedures of such synthesis can be considered the procedures of weighted summation of partial images, and the values of each element of the synthesized image is equal to the weighted sum of the values of those elements of the partial images (taken from one of each partial image) whose position corresponds to the position of the specified element of the synthesized image. The weighting coefficients of the values of the values of the corresponding elements of various partial images forming the value of the same element of the synthesized image can be different, and this can be the case for any element of the synthesized image. As indicated earlier, any weighted coefficients are selected from the conditions for obtaining the best quality of the synthesized image and in accordance with the selected algorithm to achieve the required quality of the synthesized radiation.

To simplify the presentation of the principles of image formation and synthesis, we consider the simplest implementation of such an image formation system. The structural diagram of the simplest in execution (but not in functionality) synthesized image formation system is shown in FIG. 2. The system consists of a spatially distributed scanning (SPR) source 24, a focusing element (lens) 10, a polarization grating 17 and its associated rotation unit 19, a scanning receiving device 25, a display device 23 and a processor device 22. The processor device 22 is electrically connected with the display device 23, with the scanning spatially distributed source 24 through the control unit SPR source 26 and with the scanning receiving device 25 through the control unit of the receiving scanning device stvom 27.

SPR radiation source 24 in the simplest implementation consists of:

1) One (single) point-like (TP) radiation source 28 illuminating the observation zone 6;

2) The scanning device of the radiation source 29, performing spatial displacements of the indicated TS source 28 along the scanning path 30, thereby ensuring time-consistent illumination of the observation zone 6 by radiation with different angles of incidence into the observation zone 6 (due to a change in the spatial position of the TS of the source 28 relative to the observation zone 28 during its mechanical movement). When scanning the TS of the radiation source 28, in essence, the aperture of the SPR of the radiation source 24 is synthesized, which is determined by the dimensions of the scanning surface 31 (in the simplest case of the plane) (in which the indicated scanning path 30 of the TP of the source 28 is located), from spatial points of which, similar to points 32, 33, the observation zone 6 is sequentially lit throughout the entire scanning cycle.

The spatially distributed (PR) source described above will hereinafter be referred to as either a scanning PR (SPR) radiation source or a PR radiation source with a synthesized aperture.

In the general case, the TS source 28 consists of a block 34 for generating, controlling and coding radiation (GKKI block), which is radiated into free space by means of a transmit antenna 35 connected to the GKKI block 34. The TS source 28 can also be installed in the holder 36, moving together with the TP installed thereon by the source 28 along the above-described path 30 as described above, which is additionally equipped with an electronically controlled rotary device 37 capable of rotating the TP source of radiation 28 around an axis coinciding with the direction the highest antenna gain 35. The TP source can also be additionally equipped with a polarization grating 38 mechanically mounted on a holder 36, transmitting only linearly polarized radiation through itself towards the observation zone. The indicated electronically-controlled holder 36 and the polarization grating 38 provide the ability to illuminate the inspection area with linearly polarized radiation with controlled the position of the plane of polarization, varying sequentially in time.

A point-like (TP) radiation source 28 in the simplest waveguide implementation (Fig. 3) consists of series-connected radiation source MM or CMM of range 39, having an input for control signals 40 (for example, to change the frequency of its radiation), a gate 41, an electronically controlled attenuator 42, having an input for control signals 43, a p-i-p modulator 44, having an input for modulating signals 45, and a transmitting antenna 35. A series-connected radiation generator 39 of the MM or CMM range, valve 41, electronic control direct the attenuator 42, p-i-n modulator 44 form generating unit 34, the formation and emission of encoding (block GKKI).

As a source of MM or CMM band 39, generators of any type can be used (using the Gunn diode, LPD generators, any type of “generators”), characterized by wide “noise” spectral bands of the generated radiation (from 50 MHz to 40 GHz and higher) and etc.) provided that the receiver SPU 25 is designed with the possibility of optimal reception of radiation from the used radiation source 39.

The design of the scanned ITP radiation source can be complicated and functionally improved if a backward wave lamp (BWT) or any other radiation generator providing an electronically controlled change in the frequency of its radiation through the processor unit 22 is used as the source 39 of the TS of the source 28.

The radiation pattern of the transmitting antenna 35 is chosen wide enough and symmetrical to provide illumination of any point in the observation zone 6 with the same level of radiation intensity at any spatial position of the scanned transformer of the radiation source 28. If an antenna with a narrow symmetric radiation pattern is used, then the above the holder 36 can be additionally equipped with a two-axis rotary device 46, providing aiming of the maximum radiation pattern of the transmitting antenna 35 at the same point of the observation zone 6 for any spatial position of the TS of the radiation source 28.

Scanning receiving device 25 in the simplest implementation consists of:

1) A single-element receiver (OPR) 47 (Fig. 2) consisting, in turn, of a receiving element 48 and an associated unit 49 of amplification, frequency conversion and signal processing (UCHPOS) received by the receiving element 47;

2) The scanning device of the receiver 50, which provides mechanical scanning of a single-element receiver 47 in the plane of the sharp image of the focusing element 10 along the corresponding path of the scan 51 lying on the surface (for example, in the plane) of the scan 52.

The specified scanning device of the receiver 50 can also be designed with the ability to scan ODA 47 on any, including complex scanning surface 52, repeating the shape of the surface of a sharp image to ensure optimal reception of radiation from a focused non-planar image by the receiving element 48 even in the case of using a 10 s lens insufficient correction of its aberration distortions.

As the receiving element 48, any antenna can be used, including. including horn. The antenna performs the function of receiving radiation that has fallen into its input aperture (the spatial dimensions of which are much smaller than the dimensions of the synthesized aperture of the SPR source 24) and converting the received radiation into the corresponding electrical signal. As a unit of UCHPOS 49, receiving the indicated electrical signal, any combination of radio engineering devices can be used to ensure the appearance of the output of this signal block, either the amplitude of which is proportional to the intensity of the received antenna radiation, or this intensity can be determined by such a signal after its digitization and supply to the digital processor or in any other way.

For example, in the UCHPOS unit 49 (Fig. 4), a direct amplification and signal detection device can be used in which the input signal entering the UCHPOS unit 49 from the output of the antenna 48 is amplified at high frequency by a direct amplification amplifier unit 53, consisting of a filter 54 and UHF direct amplifier amplifier 55 to a sufficiently high level (with a gain of 50 dB or more) without any frequency conversion of this signal and then fed to the input of the amplitude detector 56 (which is functionally, in the general case, equivalent to inert an ionic nonlinear element) consisting of a nonlinear diode 57, which is rectifying in this circuit, and a low-pass filter 58, at the output of which 59 only the low-frequency (or time-constant) envelope of the amplified signal appears, the amplitude of which is directly proportional to the intensity of the received antenna radiation (or in other words, the radiation power averaged over time as a result of passing a low-pass filter 58). If the radiation of the TP of the source of the TP is modulated (for example, by applying rectangular pulses of a certain repetition rate to the input 45 of the modulator 44), then this envelope is modulated by such pulses. In order to obtain a value proportional to the amplitude of the output modulated signal, a synchronous detector 60 can be used, the input of which is connected to the output of the low-pass filter 59, while a signal containing the same ones mentioned above must be supplied to the synchronization input 61 (reference input) of the synchronous detector 60 modulating rectangular pulses, maybe with some phase delay to obtain the maximum signal at the output 62 of the synchronous detector 60. The output signal can then be digitized by an analog-to-digital converter (ADC) and loaded into the memory of the processor device for further processing. As a processor unit 22 and a display unit 23, a personal computer with built-in function boards providing digital control of the radiation source 24 through the control unit of the source 26 and the receiving device 25, through the control unit of the receiving device 27, as well as receiving the output signals of the receiving device, digitizing them by the ADC board and loading into the internal memory of such a processor device for further processing.

The system operates as follows: the processor device 22 supplies control signals to the SPR source 24 through its control unit 26, through which the TS source 28 moves from the current spatial point of its position along the path of movement 30 to an adjacent point 32 of the scanning surface 31. The antenna 35 of the TS of the source is directed 28 towards the observation zone 6 with a view to its uniform illumination. The radiation of the TS source 28 having, as a result of moving this source and changing its spatial position relative to the observation zone 6, a new direction of propagation in the observation zone, after scattering it in the observation zone 6, is received by the entrance pupil of the focusing element 10 and is focused on the surface through the polarization grating 17 (plane) sharp images of the focusing element 10.

The processor unit 22 sends a control signal to the scanning device 50 of the control system 25 through its control unit 27 with the aim of positioning the ODA 47 to the starting point 63 of the scanning path 51 of the ODA 47 along the scanning surface 52, accurate to the longitudinal distance from the antenna phase center to this plane coinciding with the surface of the sharp image PRIZ focal element 10. Def. 47 receives radiation focused into a receiving antenna 48 (or, which in this case is equivalent, into a receiving element 48) 47 located at a given point 63 of the scanning surface 52 (or the scanning path 51), while the received radiation is scattered by that portion of the surface 64 of the observed object 8 in the observation zone 6, which is optically coupled to the given position of the receiving antenna 48 OPR 47 by means of the focusing element 10. At the output of the block UCHPOS 49 OPR 47 appears almost constant signal proportional to the intensity received by the receiving antenna 48 OPR 47 radiation. This signal, through the control unit 27, is fed to the input of a noise-resistant analog-to-digital converter (ADC), which is part of the processor unit 22, which digitizes the specified output signal OPR 47 and loads it into the memory of the processor unit 22 as a digital value of the image element value corresponding to the current spatial position of the ODA 47 in the scan plane 52. Then, the processor unit 22 sends a new control signal to the scanning device 50 of the receiving device 25 to move the ODA 47 to the neighboring spatial point 65 of the scanning plane 52 along the scanning path 51 of the ODA 47 in order to determine the intensity of the received radiation at this 65 point and load the value of the new image element in the memory of the processor device 22. The procedure for moving OPR 47 and loading into the memory of the processor unit 22 of the corresponding values of the values of the image elements continues to until ODA 47 reaches the final spatial points 66 on its scan path 51, which means that the full raster pixel values of the quantities and the object 8 7 6 surveillance zone belonging to a field of view of the image forming system (or rather a focusing lens 10) formed completely. Moreover, this image is formed by the radiation of the TS of the radiation source 28, located in one of the spatial points 32 of the scanning surface 31 of the PR of the radiation source 24. Moreover, the image will also be characterized by other physical parameters (except the angle of incidence of this radiation in the observation zone) of the radiation forming it in depending on the type of radiation source used 39 TP source 28. For example, it can be a narrow-band radiation source of linearly polarized radiation with vertical polarization her and with a central frequency of 95.6 GHz. On the other hand, it can be a noise source of linearly polarized radiation and an emitted frequency band of 10 GHz, with a central frequency of 94 GHz and horizontal radiation polarization. It is important that in both cases the elements of OPR 47 were adapted for optimal reception of radiation from the TS of the radiation source 28. After the formation of the partial image corresponding to the position at point 32 for the TS of the source 28 in accordance with the procedure for synthesizing the aperture of the PR of the source 24 (more precisely, scanning of the TS of the source 28 along the scanning path 30) the processor unit 22 again sends control signals to the SPR source 24 through its control unit 26, along which the TS source 28 moves from the spatial point 32 along scanning paths 30 to the next neighboring point 33 of the scanning surface 31. Then, the processor unit 22 sends a control signal to the scanning device 50 of the receiving device 25 through its control unit 27 in order to position the Odr 47 at the starting point of the path 63 of the scanning path 51 Odr 47 along the scanning surface 52 and the procedure for generating a new partial image for the new position of the TS of the source 28 in the scanning surface 31 of the PR of the radiation source 24 is again completely repeated. The specified procedure is repeated again and again for the following spatial positions TP radiation source 28, until the TP source 28 passes the entire path of its scanning 30 along the surface 31 of the PR of source 24, having completed the synthesis of the aperture of the PR of the radiation source 24. As a result, various partial images, characterized by different positions of the TP of source 28 relative to the observation zone 6, will be loaded into the memory of processor 22 means different angles of incidence of the corresponding components 2,3,4 of the scanned PR source 24 on the surface of the observed object 8 (Fig.5 - Fig.8). Each of the corresponding partial images (more precisely, the identical sections of these images by the plane) is 67.68.69 due to the sufficiently high coherence of each of the radiation components 2,3,4 illuminating the object 8 will have poor quality due to the random distribution of speckles inside the corresponding coherent images. However, the nature of the speckle distribution depends on the angle of incidence of the radiation components 2,3,4 on the uneven surface of the object 8. Moreover, the necessary range of variation in the angle of incidence of the corresponding radiation component for the indicated change in the speckle distribution depends on the surface properties. A preliminary analysis of the various partial images obtained will make it possible to select partial images with substantially different spectral distributions and sum them up. Averaging the speckle of such distributions using the above procedure for summing partial images 67.68.69 will reduce the number of speckles and improve the quality of the synthesized image 70 of the object 8. This analysis procedure together with the summation operation or any other operation may be included in the synthesis (combination) procedures described above ) partial images.

When implementing the above procedures for summing partial images, it should be borne in mind that speckle structures in various partial images can be practically spatially similar (almost identical) if the corresponding radiation, their forming, have close values of the distinctive physical parameter (for example, the difference in the angles of incidence of components 2 and 3 on object 8 is negligible). FIG. Figure 9 shows the curves of such partial images (identical image sections) 71 and 72, the physical parameters of the radiation of which are almost similar (for example, the frequencies are almost the same (in the case of changing the radiation frequency as a parameter), or the illumination angles are almost the same (in the case of changing the illumination angle). the summarized image 73 practically repeats the original partial images and has the same poor quality and, accordingly, is dissimilar to the desired “ideal” image)) shown in FIG. 9- FIG. 10 by a dashed line. Figure 10 shows partial images 74, 75 whose physical parameters (the specified angle of incidence of the components on the object 8) are different from each other by the amount at which these images for the observed object 8 become statistically distinguishable. If the average energies of such images (or their distorted fragments) are the same (that is, there is no mirror effect), then the summation of such images (or their distorted fragments) leads to the resulting images of improved quality 76. However, even if the conditions for choosing the optimal value are satisfied of a changing physical parameter, but in the case of a specular reflection of one of the partial radiation components, the corresponding partial image 77 will predominantly be brighter m and, accordingly, with a higher average energy (or the energies of part of fragments containing specular reflections) compared to the partial image 78 of diffusely reflected radiation, while their total image 79 (or part of the fragment containing a specular fragment of one of the partial images) will repeat the mirror image 77 despite the presence in the total of other diffuse images. It is clear that in the case of separate reception of partial images, their summation (or summation of their fragments) should be carried out with different weights to obtain a high-quality total image of a type close in quality to ideal 74 (and in this case all elements of the mirror image 77 can have the same decreasing weighting coefficients. In this case, the system allows the transformation of the total “mirror” image 79 (that is, containing the dominant mirror component in all or part of fragments or even elements) of poor image quality in the total "diffuse" type 76 image is increased quality, which was previously not achievable (Fig. 11).

Moreover, the necessary range of variation of the angle of incidence of the corresponding radiation component necessary to achieve the indicated speckle distribution depends on the surface properties of the object 8. A preliminary analysis of the various partial images obtained will make it possible to select only partial images with significantly different spectral distributions and ultimately sum them up. Summation of all partial images, among which there may be a larger number of partial images containing statistically identical speckle images that do not contribute to improving the quality of the synthesized (obtained as their sum) image, can lead to a situation where the relative contribution of partial images with significantly different speckle distributions to this the synthesized image turns out to be insignificant in comparison with the contributions “not improving the quality)) of partial images. Therefore, preliminary analysis and selection of partial images is essential and should be included in most image synthesis procedures (or, which is the same, combination or, what is the same, combination of partial images or their fragments). The procedures for preliminary analysis of speckle distributions and their subsequent averaging by summation can be made separately for the same parts (fragments) of various partial images. These parts of the images may include any number of elements of the corresponding image up to one element. Analyzing the nature of the change in the intensity value in equivalent elements of different partial images (that is, elements of different partial images obtained by receiving the corresponding radiation component of the antenna 48 OPR 47 at the same point PRIZ or, what is the same, reflected in the observation zone 8 of one and the same part 64 of the surface of the object 8, provided that during the formation of partial images, the object retained almost the same position) depending on the angle of incidence of the corresponding component it is possible to identify the maximum and minimum value of the intensity of speckle distributions for a given element and using these values to calculate the rms value of the value of this element (reference value), which will be optimal (minimizing the influence of speckles) for this element of the synthesized image. The fact is that a change in the speckle distribution for a given element may slightly depend on the angle of incidence of the radiation components on the corresponding surface section of the object 64. Therefore, averaging all available values of quantities for a given element of partial images can give an incorrect value if these values are unevenly distributed relative to the true average value (when the statistics are not complete).

The computational capabilities of the processor unit 22 can also be effectively used in the case of glare reflections of the radiation components from a number of sections of the surface of the object 8. In this case, large values of the values of the elements of the “mirror” images can be reduced or even removed from the corresponding sums. The number of procedures for improving synthesized images, including including the described summation procedures, is quite large due to the increased amount of information about the object, which can be obtained thanks to the proposed imaging system.

If a backward wave lamp (BWT) or other frequency-sweeped radiation source is used as a radiation source 39 of the TS of source 47, then by means of a control signal from the processor unit 22, the frequency value of the BWW radiation can be changed. The above procedure for obtaining numerous partial images for various positions of the TS source 28 in the scanning plane 31, PR of the radiation source 24, but already for a new value of the frequency of the components incident at different angles, is repeated again. Then, the radiation frequency of the BWT changes again and a new set of partial images is generated again and so is repeated until the entire range of changes in the frequency of the BWT is exhausted.

The sources of radiation included in the specified TS source 47, as indicated, can have any origin from narrow-band (quasimonochromatic) generators on Gunn diodes or LPD generators to broadband noise generators, a harmonic generator can also be used (for example, a frequency multiplier implemented on a Schottky diode) the input of which through a flexible coaxial cable can be fed a signal from the microwave generator (which can be easily sweeped in the frequency range from 8 GHz to 16 GHz under external control x control signals), in this case, harmonics of radiation of various orders and, depending on the order of the harmonic of the radiation emitted in one way or another (equal to 4 or 5 or 6 order, etc.), for example, by means of a band-pass filter, will appear at the output of the harmonic generator connected to the output of the harmonic generator, the signal sweeped in frequency, for example, in the range from 48 GHz to 128 GHz, will be supplied from the output of such a generator device to the observation zone 8. In the general case, all harmonics can be fed into the observation zone 8 (and, moreover, even independently accepted by the corresponding control system or other type of control panel). A change in the radiation frequency can affect the noise distribution of coherent images. On Fig-13 presents the results of numerical simulation of an object (in shape resembling a gun), having an external similarity of the shape and characteristic sizes of parts with typical shapes and details for such objects, for the observation of which, mainly, millimeter-wave imaging systems are developed . During the simulation, all factors capable of causing a speckle structure in images were specially eliminated in order to demonstrate the destructive effect of only Gibbs oscillations (another type of noise caused by radiation coherence), as well as the ability to overcome their influence. In the millimeter range, in contrast to the optical range, the Gibbs spatial effect, due to the limited bandwidth of the spatial frequencies of the object by the focusing element, can seriously distort the resulting image. In FIG. 12 shows the intensity distribution obtained in a single-frequency spatially coherent image for a frequency of 70 GHz. (It was assumed that the wavefront falls normally on the surface of the object, while the various sections of the object are quasi-flat). This image is distorted by irremovable intensity oscillations typical of the Gibbs effect, which significantly distort its quality, while the distribution of brightness spots in Fig. 12 corresponds to the structure of spots in experimentally obtained poor quality images of real pistols. However, the synthesized image obtained by summing the partial images independently obtained for the five frequencies 68, 76, 84, 92 and 100 GHz (Fig. 13) makes such a five-frequency summary image possessing significantly improved quality, while increasing its information content sufficient for unambiguous recognition of an object. In FIG. 14 shows the scale gradations for the signal level in the corresponding image elements shown in Fig.12-13.

A simple increase in the number of frequencies cannot automatically increase image quality. The Gibbs effect appears when the spatial frequencies in the image of an object exceed the spatial frequency bandwidth during image formation. The frequency interval for effective speckle reduction in images, as you know, is determined by the depth of the inhomogeneities of the surface of the object and also predominantly amounts to 3-15 GHz or more. A further decrease in the frequency step will lead to the summation of almost identical distributions in the intensity of the partial images and to an increase in the absolute value of the signal, but not to a significant limitation of the oscillation constraints. Since the development of an imaging system (SFI) capable of operating in a very wide band of radiation frequencies seems expensive, the joint use of effects by changing the angle of incidence of the radiation components and their frequency seems preferable to further increase the possibility of improving the quality of the synthesized images obtained in such systems.

The processor unit can also control the intensity of the radiation components 2,3,4 sent to the observation zone 6 by the source 28 by programmatically sending the attenuation coefficient attenuator 42 control signal to its input 43, thereby weakening the level of the mirror components entering the receive antenna 48 OPR 47 for various provisions. This will prevent saturation of the amplification devices of the UCHPOS 49 unit and improve the conditions for the synthesis of improved quality images.

If the SPR source 26 is configured to change the polarization state of the radiation of the TS of the source 28, then the above procedures for the formation of new partial images can be repeated for different values of the polarization states illuminating the object 8 of the radiation component, for different positions of the polarization array 17 by sending control signals to a two-axis rotary device 46 (which makes it possible to obtain co- and cross-polarization partial images, which is important for identifying masked explosives and plastic weapons). Thus, the amount of information about the masked object is significantly increasing, while increasing the number of procedures for synthesizing high-quality images. A scanning PR source can contain two 28, 80, or several TS sources, each of which can emit simultaneously two or more independent radiation components. The components can be distinctively modulated (for example, by amplitude modulation using modulators such as modulator 44). On the other hand, the components emitted by one TP source can be grouped into doublet or multiplet radiation components that have the same (identical) coding feature. In both cases, different TP sources 28.80 can be scanned along their own non-intersecting paths of spatial scanning in their own spatial parts of the scanning surface 31. In this case, TP sources must be implemented with the function of independent and distinctive coding of their radiation (or even the radiation component), for example by amplitude modulation with modeling frequencies different for different TPs of 28.80 sources (or even their components). A single-element receiver (OP) must additionally contain decoding (demodulating) nodes, which make it possible to extract component secondary electrical signals corresponding to variously encoded radiation components received collectively by the OP receiving element and converted into a common primary electrical signal in the form of the sum of such component electrical signals. Highlight secondary electrical signals from the specified primary in this case can be done by adding another synchronous detector 60 to the synchronous detector 60 in the UCHPOS circuit 47 in figure 4, by connecting its input to the output of the low-pass filter 59, while being used as synchronizing signals (reference signals) for each of the synchronous detectors, different signals must be supplied, and only those that are used to modulate the corresponding ρ-in modulators of the corresponding TP sources 28, 80. Another way is to digitize by means of a fast analysis log-to-digital converter (ADC) of the signal from the output of the low-pass filter 59 with a frequency of time samples not less than the highest frequency contained in this signal, then loading the entire array of samples into the memory of the processor device 22, performing the Fourier transform on this array of samples to obtain the frequency distribution digitized temporary primary signal. Next, select the spectral components corresponding to the modulation frequencies of the respective radiation components and measure their amplitudes to obtain the intensities of the corresponding components received by ODA 47 at the current point on the scanning surface 52.

The latter method of spectral analysis is also applicable to the identification and measurement of practically any number of simultaneously emitted and different amplitude-modulated components of the PR source, which is performed, for example, in the case when modulators, such as modulator 44, associated with different TP sources of the PR source are supplied with frequency-different modulating signals . It is clear that the cutoff frequency of the filter 58 should be large enough to skip all modulation frequencies, and the ADC should be fast enough to provide the required digitization speed of the signals. Scanning receiving device 25 may contain a line of receiving elements, the outputs of which are associated with multi-channel block UCHPOS, and with the output of each receiving element connected to the input of one electronic channel of a multi-channel block UCHPOS (this channel can fully correspond to the corresponding block UCHPOS single-element receiver 47). Such a receiving element and the corresponding electronic channel of the UCHPOS multi-element block associated with it form an independent receiving channel, which can functionally and structurally fully correspond to the single-element OPR 47 receiver described in connection with FIG. 2. The combination of such channels can form a receiving device of any type: single-element, with a scanning ruler or an unscanned receiving device with a two-dimensional receiving matrix of receiving elements.

The frequency principle of coding of radiation components can be implemented when each radiation component is characterized by a characteristic associated with its own frequency spectrum and / or the frequency spectrum of such a component that occurs after its modulation or other type of coding. In this case, the most effective procedure for receiving, frequency converting, processing and measuring the intensity of each received radiation component can be based on the independent reception in each receiving channel (through its receiving element, for example, a receiving antenna) of the corresponding focused radiation, converting it into the corresponding primary electrical signal (which is spectrally equivalent to the received focused radiation received element) of the subsequent first frequency conversion the primary electric signal with a shift to the region of intermediate frequencies without violating the spectrum structure of this signal, amplification and band-pass filtering of the shifted signal by the first amplifier, second frequency frequency down-conversion of the signal without violating the structure of its spectrum, and its amplification and band-pass filtering in the corresponding second amplifier amp and output the second amplifier of the IF amplifier for inputting an analog-to-digital converter to digitize this signal with a frequency of time samples not less than the highest frequency contained in this signal, then load the entire array of samples into the memory of processor device 22, perform the Fourier transform on this array of samples to obtain the frequency ( spectral) distribution of the digitized signal. Further, programmatically, by means of a processor device 22, the measurement of the parameters of the spectral components corresponding to various partial differently coded radiation components (in case the coding is based on one or another of the above frequency separation of the various radiation components) that are part of the focused radiation received by the receiving element and determining the intensity of each of these radiation components by analyzing the parameters of the corresponding spectral components of the digitizer signal in particular (by measuring their amplitudes) to obtain the intensity of the corresponding radiation components received by the receiving channel of the receiving device at the corresponding spatial point of the sharp focus surface. The procedure described above for digitally measuring the intensities of various components can also be applied when the distinctive distribution of secondary signals corresponding to various radiation components appears only after processing the signal received by the receiving element in some decoding (demodulation) node. In this case, the digitization must be carried out for the signal that occurs at the output of the corresponding decoding device after its amplification and bandpass filtering. Further, the processing of the digitized signal can be carried out as described above. On Fig shows a structural diagram of an imaging system using not scanned multi-element a spatially distributed (MPR) radiation source 81 and an unscannable multi-element receiving device 82. The block diagram of FIG. 15 generally corresponds to the composition of the nodes and their functional purpose of the nodes to the generalized scheme depicted in FIG. 1, but clarifies the features of the used radiation source 81 and the receiving device 82. Such a system opens up wide possibilities in the high-speed synthesis of high-quality images, since the radiation from the spatially distributed (PR) source 81, consisting of a sufficiently numerous set (lattice) of stationary spatially distributed point-like (TP) radiation sources 28.83, the radiation of each of which is independently distinctively encoded (for example amplitude modulated), and all radiation components of the PR source radiation can be quickly and independently received by numerous receiving elements 48, 84, matrix of receiving elements 85 of the receiving device 82 and simultaneously processed by a multi-channel block 86 UCHPOS, each channel of which is associated with the corresponding receiving elements 48, 84, ... followed by the processing of the corresponding electrical signals, the formation of partial images and the subsequent synthesis of a high-quality resulting image on (or, in other words, the described about the above, combining (combining) these partial images) and displaying the synthesized image on the screen of the display device 23. Unscannable multi-element spatially distributed

The (MPR) radiation source 81, in the general case, consists of independent TS 28.83 radiation sources, which emit independent partial radiation components of the MPR radiation source that are phase-independent from each other, while such components are encoded (for example, are distinctively amplitude modulated ) in a distinctive way and therefore can be received by each receiving element 48.84 of the receiving matrix 85 and independently decoded (demodulated) in each independent channel of the multi-channel block UCHPOS 86.

In this case, the radiation of the MPR of the source 81 is directed to the observation region 7 and after it is scattered by the object 8, as well as by the clothes and skin of a person 7, from the observation zone 6 partially falls into the entrance pupil of the focusing element 10 of the imaging system. (The size of the entrance pupil in most cases coincides with the diameter of the used focusing element (lens)). A focusing element (PV) 10 (lens or mirror, for example) focuses the radiation scattered in the observation zone 6 on the surface of a sharp image (PRI), in which a multi-element receiving matrix (MPM) 85 is located, capable of receiving this radiation independently at different points of PRIZ , the size of the MPM 85 ultimately determines the field of view of a given imaging system. A polarization grating 17 can be placed in front of the receiving matrix to isolate co- and cross-polarizing components in the radiation of the focused lens 10 on the receiving matrix MPM 85. In this case, the focusing element 10 establishes a one-to-one correspondence between the receiving elements 48, 84 of the receiving matrix 85 and the corresponding portions field of view of the imaging system. Any radiation scattered by a certain point 87 of the object 8 is mainly focused at a specific receiving point and is received by the corresponding receiving element 48 of the matrix 85. Therefore, any partial radiation components of the TS sources 28, 83 reflected from the point 87 of the object 8 and entering the entrance pupil of the focusing element 10 can be received by said receiving element 48 of the receiving matrix 85 and independently decoded in the corresponding independent channel of the multi-channel UCHPOS unit of device 82 associated with this the reception element 48, and this is true for any receiving element MPM 85.

As the channel of the multi-channel block 82 amplification, frequency conversion and signal processing (UCHPOS) can be any radio channel capable of performing the necessary operations above amplification, conversion and signal processing, including single-channel UCHPOS described above in the description in connection with FIG. . 2, FIG. 3 and FIG. four.

As the sources of radiation 28.83 of a multi-element spatially distributed (MPR) source 83, any radiation sources can be used, including the sources of radiation described in connection with FIG. 2 and FIG. 3. The radiation sources that make up the indicated TS sources 28.83 can also be of any origin, from narrow-band (quasi-monochromatic) Gunn diodes or LPD generators to broadband noise generators. In particular, harmonic generators (for example, multipliers on Schottky diodes) can be used as generators, the inputs of which through the flexible coaxial cables can be used to transmit microwave generators (which are easily sweeped in frequency in the range from 8 GHz to 16 GHz) at the same time at the output harmonics generators will appear harmonics of radiation of various orders and depending on the order of the harmonic radiation emitted in one way or another (equal to 4 or 5 or 6 order, etc.), for example, using the appropriate technique device 82, sweepable for example in the range from 48 GHz to 128 GHz. LOB (s) can also be used as these generators, however, the matrix of such generators will be quite expensive. The most practical seems to be an MPR source in the form of a two-dimensional planar matrix of MM or CMM generators made by integrated technology, when both the radiating antenna (s) and, say, the associated Gunn diode of each of these TP sources are made in a single technological process or, more Moreover, the entire matrix is made in the indicated integral design. Such generators can be either narrow-band or rather broad-band (up to 2-3 GHz emission bands). In mass production, the cost of the matrices will be slightly more than the cost of one generator. Independent radiation modulation of individual generators can be accomplished by modulating the supply currents for each of the generators. A more elegant coding scheme for the radiation of generators of such matrices is based on the combination of narrow-band monolithic generators MM or CMM radiation in groups of two generators located next to each other, one of which, at least, should be a VCO - generator, the frequency of which is controlled within certain limits by external voltage . VCOs are created from conventional generators by adding a diode varicap to the generator circuit, the capacitance of which varies by the control voltage, which leads to a change in the generated radiation depending on the control voltage of the varicap. The use of two monolithic generators, the resonator antennas of which lead to the generation of radiation components with approximately similar radiation frequencies, one of which is a VCO, allows by supplying part of their radiation, for example, via microstrip lines to a planar diode mixer, which can also be performed integrally on one with the generators to the substrate and isolate by means of this mixer and integrally connected with it a strip amplifier a difference signal whose frequency is equal to the difference pilots at the signal generators. To do this, the indicated smaller part of one of the two generators should be an order of magnitude larger than the smaller part of the second generator in order to ensure the optimal operation of the mixer. Then, this difference signal must be phase-synchronized with a stable crystal oscillator signal (or its harmonic) through the corresponding PLL loop (the crystal oscillator and the PLL can be located outside the matrix of coupled generators, and the signal PLL loop mismatch (error signal of a discriminator, for example, a phase detector (or even a frequency detector, if it is necessary to stabilize only the difference frequency and not the phase) of the PLL loop), which is proportional to the phase difference (difference) of the difference signal from the phase of the crystal oscillator signal (or its harmonic ) apply to the control electrode of the VCO, to reduce the value of the mismatch signal, providing phase synchronization of the specified difference signal and the signal of the crystal oscillator (or its harmonic), (or the corresponding frequencies if a frequency detector is used as a discriminator) Due to this scheme, the frequency-phase changes of the VCO signal will repeat the frequency-phase changes of the second generator from the indicated pair of generators, while their difference signal in its spectral purity will be equivalent to the signal of the crystal oscillator, leaving whose frequency may be less than a thousandth of a percent of its central frequency. Most of the generated signals through planar antennas will be emitted into free space from almost one spatial point relative to the observation zone 6. After scattering in the observation zone, these components will be focused in the same way in the plane of the sharp image, forming spatially similar partial images, therefore, a multi-channel receiving device 82 having accepted spatially equivalent samples of these images by each of the receiving elements, 48.84 can form in the corresponding channels of the UCHPOS block, difference signals (for example, by supplying electrical signals corresponding to the radiation of the indicated generators to a nonlinear diode and a filtering circuit following the diode), which will be spectrally equivalent to the difference signal in the above-described generation scheme of the doublet TP of the source MM or even CMM radiation ( depending on the resonant frequency of the corresponding transmitting antennas used) .. Since each such pair 5 000496

44 MlIF generators of source 81 can have its own crystal oscillator with its own frequency value or can use its various harmonics, then difference frequency signals that differ from each other in difference frequency and which are formed from pairs of frequency shifted pairs can be generated in the corresponding receiving channels of receiver 82 relative to each other to the frequency of the crystal oscillator (or its harmonic frequency) of electrical signals corresponding to the doublet components of the radiation, taken in turn respectively Leica Geosystems receiver elements 48.82. The formation of their difference signal can be performed by applying them to a nonlinear element (for example, a diode). This leads to the distinctive decoding of various doublet signals by the receiving device 82. This can be performed independently in the block in different channels of the multi-channel UCHPOS 86, each of which is equivalent to the single-channel UCHPOS considered in connection with Fig. 4, when the received signal, after its amplification in a direct amplification amplifier unit 53 is supplied as a sum of various doublet signals to the input of a nonlinear diode 57; a signal comprising stabilized difference signals with different values and frequencies, this signal can be pre-filtered to store only the indicated difference signals in it, and then each difference signal can be extracted and its parameters determined in various radio engineering units based on frequency selection schemes, including by digitizing the filtered signal and applying various digital methods for determining the parameters of its components (as described above).

In this case, the intensity of the corresponding doublet component (or one of the lines included in the doublet) can be measured by measuring the average power of the corresponding difference signal, or its individual components. It is assumed that the multi-element receiving device 82 of the formation system images can be pre-calibrated by applying to the inputs of the receiving elements 48.84, radiation with a known radiation intensity). In some cases, such a calibration is not necessary, since relative changes in intensity in each of the partial images are important for identifying objects. On the other hand, if the sensitivity of the receiving system is dependent on the physical parameters of the received radiation components, and this is essential for a particular image synthesis algorithm, such a calibration can be performed for each or part of the variable parameters, and such calibration can be performed periodically during the operation of the system .

Each such pair of monolithic radiation generators will form a corresponding TS source 28, 83, MPR of the radiation source 81. From the point of view of the possibility of synthesizing images of such MPR, a source of doublet lines is preferable, since it can be inexpensive and provide a very high density of information channels in the corresponding MM bands and / or CMM radiation arriving at the inputs of the receiving device 82, significantly reducing the level of radiation of illumination in the observation zone 6, increasing the number of possible artsialnyh images that can be obtained by the receiver 82 and processed by the processing unit for synthesizing high-quality images in near real time.

In the ideal case, the point each point on the surface of the sharp image (in the plane of the sharp image) 48 should correspond to a certain point 87 in the observation zone 6 (plane of the object). However, due to the finite aperture of the used focusing element (PV), each point 48 (or a limited area) in the PV receiving zone uniquely corresponds to a limited observation region 6, or, accordingly, a limited, but quite spatially defined, part of the field of view of the formation system images, scattered (or radiated) radiation from which it is mainly focused at this point by a focusing element (lens) 10. In fact, we are talking about a limited volume of the sharp image observation area for the receiving element under consideration, which is achieved with the focusing element used, for focusing plane-parallel radiation beams and the position of which is determined from the condition of optical conjugation of the reception zone / plane and the observation zone / plane by means of PV. The transverse dimensions of this volume are determined by the radius of the image element resolved by the quasi-optical system, and the linear linear size by the corresponding depth of field for the focusing element (lens) 10. The indicated final dimensions of the resolved element determine the spatial dimensions of the speckles of noise and are proportional to the sizes of Gibbs oscillations characteristic of MM images and intensely destroying their quality.

A more detailed diagram of an adaptive MM / SMM imaging system (SFI) based on the use of a multi-element spatially distributed (MPR) radiation source and a multi-element receiving (MP) device is shown in FIG. 16.

Such an adaptive SFI consists of the following subsystems and nodes:

1) a wide-frequency focusing element (lens) 10, designed to form MM / SMM images;

2) a receiving device 82, including: a) a multi-element receiving matrix (MPM) of the receiving elements

85, intended for receiving by its receiving elements 48, 84 spatial samples in the radiation focused by the 10 MM / SMM lens in the surface of a sharp image PRIZ of the focusing element 10 and converting the radiation received by the elements of the receiving matrix 82 into the corresponding matrix (set) of independent electrical signals (independent matrix dimension electrical signals coincides with the dimension of partial and resultant images formed later), b) UCHPOS 87 multi-channel unit for amplification, frequency conversion and processing, including, as before, decoding (for example, demodulation) of partial or full specified signals received by the specified receiving matrix (each matrix element 48, 84 has its own specified channel 49.88 of the UCHPOS block 87, forming, together with the corresponding receiving element, the corresponding receiving channel of the receiving device 82. The outputs are indicated The channels of the UCHPOS 87 block are connected with the multiplexer 89. The UCHPOS 87 block includes a block of heterodyne generators 90 generating heterodyne signals for the reference signals of the mixers of the corresponding channels of UCHPOS 87, for the frequency downward frequency shift of the signals received by the receiving elements of the MPM 85 (for example, MPM antenna receivers) in gain bands of the corresponding IFA, each of which is associated with the corresponding specified mixer in the specified channel of the multi-channel unit 87 UCHPOS (if necessary, such a heterodyne frequency converter Azovans)

3) a processor unit 22 configured to control the various nodes included in the various units of this imaging system, with the function of digitally receiving signals from the output channels of the UCHPOS 87 unit (connected to the inputs of the multiplexer 89) from the output of the multiplexer 89 by connecting the output of the multiplexer unit to ADC input 91 as well as digital processing and visualization of matrix partial images generated by block 22, performing the function of preliminary numerical processing of the corresponding partial images signal imaging using an image preprocessor 92. The processor unit 22 also includes an interface unit 93 (providing signal transmission between the various nodes of the system), the main processor unit 94, which controls the operation of the entire system in general, and synthesizing high-quality result images), a visual display unit of the result images 95, having a display 96.

4) a multi-element spatially distributed radiation source 81, consisting of a two-dimensional matrix of point-like radiation sources, each of which consists of separate radiation generators 39, 97, 98, connected to its own valves, each of which is connected to its own electrically controlled attenuator 42, 99,100, the output of each of which is connected to the input of the corresponding radiation modulator 44,101, 102 whose outputs are connected to the inputs of the respective transmitting antennas 35, 103,104. Each generator, attenuator and modulator is electrically connected to its own control and modulation unit 105,106,107, and is controlled or modulated by its signals. Phase stabilization of the difference frequency of the spectrally shifted carriers of two or more of these signals allows us to solve the problem of high sensitivity of the receiving equipment, as well as to perform efficient coding of partial emissions.

The first is achieved at the maximum possible concentration of energy of the signal, which carries information about the properties of the reflecting surface of the object, in an extremely narrow frequency band of the difference signal allocated in the receiving part of the system for each element individually. This takes place despite the fact that the intrinsic stability of the generators of the singlet (from one spectral line) radiation of the MM / SMM bands does not allow, in principle, to achieve the required frequency stabilization and, accordingly, such spectral concentration. In this case, an ultrahigh concentration of the energy of the difference signal is achieved for frequencies in the region of which the spectral power of the excess noise of the electronic components (and this frequency is at least not less than 10-50 MHz, but it can be achievable above 1-3 GHz, etc. depending on the implementation of the doublet line generator) becomes minimal and is characterized only by the spectral power of thermal noise, which, although it cannot be eliminated for almost any spectral range, is characterized by a negligible value in the indicated range of difference frequencies (for a frequency band of 1 Hz it is characterized by a value of 10 ^"20 W).

Thus, there is a double approach, consisting in the maximum possible narrowing of the difference signal band (or, equivalently, the spectral energy concentration of the signal reflected by the object) and its frequency stabilization (up to 1 Hz of the difference frequency deviation), on the other hand, transferring its frequency to the range with extremely low noise level of electronic equipment (comparable or higher than 1 GHz) allows you to achieve extremely high sensitivity of the receiving equipment SFI (and hence the ultra-low level of active clothing illuminating radiation man - much less in comparison with the general level of the external natural background radiation in this spectral range), and on the other hand the increased dynamic range of the receiving equipment.

The latter is important in connection with the mirror nature of the reflection of radiation of this range from the objects of observation, which determines the large dynamic range of signals reflected at arbitrary angles from the surface of the object of observation and the angles of mirror reflection. It is obvious that if the dynamic range of the receiving equipment is not sufficient, only radiation components that are specularly reflected from the object will be visually selected, which obviously determines the extremely low quality of the generated images.

According to the present invention, the transceiver of the image forming system for obtaining complete information about the radiation scattered by the object under conditions of a low level of illumination power of the object according to the first embodiment includes a heterodyne receiver of millimeter and submillimeter radiation intended for receiving millimeter and submillimeter radiation of images of the indicated image forming system, a millimeter and submillimeter radiation source for illuminating an object, the heterodyne receiver including a receiving antenna connected to a subharmonic first mixer for receiving the first signal at the reference input thereof a radiation generator that performs the function of a local oscillator for the specified mixer, the first bandpass filter connected to the first mixer To isolate the intermediate frequency signal, a subharmonic second mixer, the signal input of which is electrically connected to the output of the first bandpass filter and, and the reference input is designed to receive the frequency signal multiplied by the first frequency multiplier of the reference signal generator, the second bandpass filter, the input of which is connected to the output of the second mixer , a high-frequency or low-frequency signal analyzer, the input of which is connected to the output of the second mixer, means for displaying and processing the signal associated with the output a of the signal analyzer, the radiation source is a second radiation generator, the output of which is connected to the input of the second frequency multiplier, the output of which is connected to the transmitting antenna, and includes a control unit for monitoring the radiation frequency of the second radiation generator by the frequency of the first radiation generator by generating a difference frequency signal of these generators and ensure phase synchronization of the specified differential signal by the signal generator of the reference signal by adjusting the hour the second generator, the reference signal generator is designed to activate the control unit and generate the reference signal for the specified signal analyzer, and the first and second frequency sources of the signal source and the first subharmonic mixer are made with the possibility of functioning on the harmonics of the same order. In this transceiver, the signal analyzer is two analog-to-digital converters that synchronously digitize the signal from the output of the second band-pass filter and the multiplied signal of the reference signal generator from the output of the first frequency multiplier; and a processor having a memory for loading digital arrays of digitized said signals, and configured to calculate amplitude and phase information of the received signal receivers.

In this transceiver, the control unit is a first directional coupler connected to the output of the first generator and dividing the signal of the first generator by power into smaller and larger parts, a second directional coupler connected to the output of the second generator and dividing the signal of the first generator by power by smaller and larger parts, a mixer, the inputs of which are designed to receive smaller parts of the signals of the first and second generators, and which implements extracting the difference frequency signal from these signals to supply this difference signal through a bandpass filter to one input of the phase detector, the other input of which is designed to receive the signal of the specified reference signal generator, and the error signal of the phase detector, which is the phase mismatch signal between the difference frequency signal of the signals of the first and the second generators and the signal of the reference frequency generator, is supplied to the control electrode of the second generator to change the frequency of the second signal th generator and reducing the indicated phase mismatch.

The heterodyne receiver of the transceiver can be mounted on a scanning device with the ability to receive radiation of the full image formed by the imaging system by scanning the heterodyne receiver in the sharp plane of this system. The heterodyne receiver of the transceiver can be made in the form of a matrix of heterodyne receivers arranged so that the phase centers of these antenna receivers of each heterodyne receiver coincide with the sharp image plane of the imaging system, and each heterodyne receiver is equipped with a directional coupler to transmit part of the power of the second generator to the heterodyne input of the corresponding first mixer, and the specified second generator is common to all heterodyne receivers , each of which is configured to receive part of its power through a corresponding directional coupler.

According to a second embodiment, the transceiver of the system for generating millimeter and submillimeter images for obtaining detailed information about the radiation scattered by the object under conditions of a low level of illumination power of the object contains a receiver for direct amplification and detection of millimeter and submillimeter radiation, designed to receive millimeter and submillimeter radiation images of the specified formation system images, the source of the compound millimeter and submillimeter is emitted An instrument intended for illuminating an object or, in this case, a direct amplification and detection receiver includes a receiving antenna connected to a high-frequency amplifier, the signal of which is supplied to a quadratic detector, a signal analyzer, the input of which is connected through a filter to the output of the specified quadratic detector, and display means and signal processing associated with the output of the signal analyzer, a composite radiation source consisting of a first radiation generator connected to the first directional coupler, dividing signal of the first generator in power to a larger and smaller part and a second radiation generator connected to the second directional coupler, dividing the signal of the second generator in power by a larger and smaller part of the output antenna system designed to transmit the indicated large parts of the power of the signals of the first and second generators into free space in the same way, in the control unit, to the inputs of which the indicated signals of lower power, respectively, of the first and second generators are supplied from the corresponding outputs of these directional couplers and, which is intended to control the radiation frequency of the second radiation generator by the frequency of the first radiation generator, the generator a reference signal ator designed to activate a control unit and generate a reference signal for said signal analyzer.

The signal analyzer for this example can be a band-pass filter with a central transmission frequency corresponding to the frequency of the specified reference signal generator, coupled to an analog-to-digital converter that digitally samples the signal and fills these samples with the processor’s memory, which processes these samples to obtain the spectral composition this signal. In addition, the analyzer may additionally consist of a mixer, the signal input of which is connected to the output of the specified band-pass filter, and the signal of the reference signal generator is supplied to the reference input of the specified mixer, and the output signal of the specified mixer is fed through the filter to the input of an analog-to-digital converter performing digital sampling signal and filling these samples with processor memory, while the processor digitally processes these samples in order to obtain the spectral composition of this signal ala.

The control unit for the transceiver according to this embodiment is a mixer, the inputs of which are designed to receive smaller parts of the signals of the first and second generators, and are connected to the corresponding outputs of the first and second directional couplers, and which implements extracting the difference frequency signal from these signals to supply this difference signal through a bandpass filter to one input of the phase detector, the other input of which is designed to receive the signal of the specified reference signal generator, and the error signal of the phase detector, which is the phase mismatch signal between the difference frequency signal of the signals of the first and the second generators and the signal of the reference frequency generator, is fed to the control electrode of the second generator to change the frequency of the second signal th oscillator and reduce the phase error. In this case, the direct amplification and detection receiver can be installed on a scanning device with the possibility of receiving the radiation of the full image generated by the imaging system by scanning the heterodyne receiver in the sharp image plane of this system. In the area of the sharp image of the focusing element, a matrix of these direct amplification and detection receivers can be located so that the antennas of these receivers are located near the plane of the sharp image of the focusing element.

When using a set of these sources of composite radiation, in which the frequencies of the signal generators of the reference signals of the corresponding sources are different from each other, several specified signal analyzers are connected in parallel to the output of the quadratic detector of the direct amplification and detection receiver, the number of which is equal to the number of these sources of composite radiation in the specified set, and the center frequency of the band-pass filter of the corresponding analyzer is equal to the frequency of the signal of the reference oscillator, respectively existing source of composite radiation.

And when using a set of these sources of composite radiation, at which the frequencies of the signal generators of the reference signals of the corresponding sources differ from each other, to the output of the quadratic detector of the receiver of direct amplification and detection several indicated signal analyzers are connected in parallel, the number of which is equal to the number of the indicated composite radiation sources in the specified set, and the center frequency of the band-pass filter of the corresponding analyzer is equal to the frequency of the reference generator signal of the corresponding composite radiation source, while the signal of the reference generator of the specified signal is supplied to the reference input of the mixer of the specified signal analyzer composite radiation source.

Moreover, different sources of composite radiation from a set (including TP sources of a spatially distributed source) sources are intended for lighting or an object. Different sources of composite radiation from a set of sources have substantially different average frequencies, calculated as the arithmetic mean of the frequencies of the corresponding paired generators.

The radiation propagating in free space of the indicated most of the signal of the first generator is mainly linearly polarized in the first spatial direction, and the radiation propagating in free space of the indicated most of the signal of the second generator is mainly linearly polarized in the second spatial direction. In this case, the first spatial direction coincides with the second spatial direction or the first spatial direction orthogonal to the second spatial direction.

The receiver may be equipped with polarizing means emitting radiation linearly polarized in the first spatial direction from the incident radiation, or the receiver may be equipped with polarizing means emitting linearly polarized radiation in the second spatial direction from the incident radiation.

The frequencies of the first and second generators of the composite radiation source simultaneously increase or decrease in frequency in a fairly wide frequency range, and the specified control the unit stores the specified control of the frequency and phase of the second generator by the frequency and phase of the first generator in the entire specified frequency range.

According to the following exemplary embodiment, the transceiver of the imaging system in the millimeter and submillimeter wavelength ranges for obtaining detailed information about the radiation scattered by the object under conditions of low illumination power of the object, comprising a receiver for direct amplification and detection of millimeter and submillimeter radiation, designed to receive millimeter and submillimeter radiation images of the specified image forming system in the sharp image plane, its focus element, a source of millimeter and submillimeter radiation intended for illumination of the object, the direct amplification and detection receiver includes a receiving antenna connected to a high-frequency amplifier, the signal of which is fed to a quadratic detector, a high-frequency or low-frequency signal analyzer, the input of which is connected through a filter with the output of the specified quadratic detector, the means of display and signal processing associated with the output of the signal analyzer, the radiation source consists of composite radiation source, the composite radiation source consists of a first radiation generator connected to the first directional coupler, dividing the signal of the first generator by power into larger and smaller parts, and a second radiation generator connected to the second directional coupler, dividing the signal of the second generator by power to large and a smaller part of the output antenna system for transmitting these large parts of the power of the signals of the first and second generators into essentially the same way, the control unit, to the inputs of which from the corresponding outputs of the indicated directional couplers the indicated signals of lower power, respectively, of the first and second generators and which are intended to control the radiation frequency of the second radiation generator by the frequency of the first radiation generator, a reference signal generator designed to activate the control unit and generate a reference signal for the specified signal analyzer. For this embodiment, the specified signal analyzer is a band-pass filter with a central transmission frequency corresponding to the frequency of the specified reference signal generator, coupled to an analog-to-digital converter, which digitally samples the signal and fills these processor samples with memory, which processes these samples to obtain a spectral composition of this signal. The specified analyzer may additionally consist of a mixer, the signal input of which is connected to the output of the specified band-pass filter, and the signal of the reference signal generator is supplied to the reference input of the specified mixer, and the output signal of the specified mixer is fed through the filter to the input of an analog-to-digital converter performing digital signal sampling and filling these samples with processor memory, while the processor digitally processes these samples in order to obtain the spectral composition of this signal and,

For this transceiver, the control unit is a mixer, the inputs of which are designed to receive smaller parts of the signals of the specified first and second generators, and are connected to the corresponding outputs of the first and second directional couplers, and which extracts the difference frequency signal from these signals to supply this a difference signal through a bandpass filter to one input of the phase detector, the other input of which is designed to receive the signal of the specified reference generator th signal and the error signal of the phase detector, which signal phase mismatch between the signal of the difference frequency signals of said first and second generators and signal generator reference frequency is supplied to the control electrode of the second generator to change the frequency of the signal of the second generator and reduce the specified phase mismatch.

A set of these sources of composite radiation can be used, while the frequencies of the signal generators of the reference signals of the corresponding sources must be different from each other, and several indicated signal analyzers are connected in parallel to the output of the quadratic detector of the direct amplification and detection receiver, the number of which is equal to the number of these sources of composite radiation in the specified set, and the center frequency of the band-pass filter of the corresponding analyzer is equal to the frequency of the signal of the reference oscillator and the corresponding composite radiation source.

For this embodiment example, a set of these sources of composite radiation can also be used, while the frequencies of the signal generators of the reference signals of the corresponding sources are different from each other, and several of the indicated signal analyzers are connected in parallel to the output of the quadratic detector of the direct amplification and detection receiver, the number of which is equal to the number of these sources composite radiation in the specified set, and the center frequency of the band-pass filter of the corresponding analyzer is equal to the frequencies e of the signal of the reference generator of the corresponding source of composite radiation, while the reference signal of the mixer of the specified signal analyzer receives the signal of the reference generator of the specified source of composite radiation. In FIG. 17 is a structural diagram of paired generators connected by a PLL loop, which allows generating two signals of the MM or CMM bands, the difference signal of which is phase-locked by the signal of a highly stable crystal oscillator or its harmonic. Such a generator circuit can be used both for generating the above-described doublet components for illuminating the observation zone 6 by them, and for implementing transceiver equipment An SFI with heterodyne bias in the control room 16 of the received signals that are generated by one of the paired generators and used to illuminate the observation zone 6, and the other is transmitted to the control room 16 via a flexible coaxial cable for use as a pump signal in a subharmonic mixer (s) and provides the formation of intermediate signals frequencies whose frequency is equal to the frequency of the indicated difference signals and is highly stable even if the frequencies of the signal of the generators themselves change randomly over time (due to phase noise or as a result of ate drift) or regular (due to a controlled sweep of frequencies in any technically achievable limit) images.

The device (Fig. 17) consists of two MM / SMM generators of ranges 108 and 109, operating at almost the same frequency, at least one of which 109 is a VCO (a generator whose frequency is controlled by external voltage). In a preferred embodiment, both generators are GUNs (s), since this makes it possible to change their frequencies through electronic sweeping. In the case of waveguide implementation of the generators, gates 110,111 are included at their outputs for decoupling the generators from the remaining parts of the circuit. By way of directional couplers 112 and 113, smaller parts of the power of the signals of the generators 108 and 109 are fed through their respective outputs to the inputs of the mixer (quadratic converter) 114, to form a difference frequency signal equal to the frequency difference of the signals of these generators, the specified difference signal from the output of the mixer 114 is fed to the input of the frequency selective circuit 115, consisting of a band-pass filter 116, (tuned to the center frequency of the difference signal), connected in series with the amplifier 117 and the output of the force The device 117 is fed to one of the inputs 118 of the phase detector 119 having an output 120, the signal of the generator of the difference signal 122, which is either a signal of the reference quartz oscillator included in the generator 122, or one of its harmonics formed in the frequency multiplier 123 connected in series with the indicated exemplary reference quartz oscillator (this oscillator can be quartz and thermally stabilized, therefore the phase noise of such an oscillator is negligibly small ) The error signal from the output 119 of the phase detector 119 is fed to the input of the amplifier 124 and from its output to the input of the filter 125 of the frequency selective amplifier unit 126, while the frequency band of the bandpass filter 125 is optimally selected to ensure proper (with a low level of phase noise and / or filtering the high-frequency information components of the difference signal.) the functioning of the PLL loop described above and then on the control electrode 127 of the VCO generator 109. With the correctly selected bandwidths of the filters 117 and 125, we produce passed by the phase detector 119, the error signal adjusts the frequency of the VCO 109 to reduce (eliminate) the phase differences between the specified difference signal, the frequency of which is equal to the difference of the signals of the two generators 108 and 109 and phase-synchronized by the stabilized signal of the generator 122. . Moreover, the indicated smaller part of the signal of one of the generators

(e.g., generator 108) should be an order of magnitude larger than the indicated smaller portion of another generator (e.g., 109) for optimal operation of mixer 114.

Large parts of the signals of the generators 108 and 109 from the corresponding outputs 128 and 129 of the directional couplers 112 and 113 can then be radiated into the open space (or used in another way), including after passing through the corresponding modulators 130, 131 (amplitude or phase) each of which connected in series with the corresponding radiating antenna 132 and 133, which can be either individual 132, 133 for each of the channels of passage of large parts of the signals of the generators 108, 109, and can be combined by means of directional couplers 134, 135 into a common waveguide 136 for radiation through a common antenna 137. The frequencies of such signals are shifted relative to each other by the frequency of the spectrally pure difference signal of the generator 122 (122,123) and their difference signal is phase-locked to the signal of the specified reference generator 122, however, the specified differential signal after the propagation of the signals of the generators 108, 109 to the receiving device SFI and subsequent reception by this device can be formed in the corresponding amplifier th channel of the receiving device and the newly allocated difference signal will have the spectral characteristics of the signal of the reference oscillator 122 stabilized.

The diagram above shows the functional relationships of a generator device implemented in a waveguide design. The same device can be integrated in the form of a monolithic semiconductor device, in this case, in accordance with the monolithic design of the generator devices, the antennas 132 and 133 are combined with the corresponding generators 108, 109 and serve as actual planar antennas to emit the generated signals into open space, and of the corresponding resonator systems in the composition of the corresponding generators (properly connected to the corresponding nonlinear element with a negative impedance to generate a signal - for example, to the Gunn diode). In this case, modulators 130, 131 are excluded from the composition of the composite generator (the difference frequency of such a generator can be modulated here). Directional software valves can also be excluded,

111. Directional couplers in planar (strip) design

112, 113 perform the same function of selecting smaller parts of the energies of the generated signals of planar generators lОδ, 109 and feeding them into a planar mixer 114. (which can be performed in a single manufacturing process together with generators). All other elements, including phase detector 119 and frequency amplifier blocks 115, 126 can be performed by integrated technology as well. The stabilized type reference signal generator 122 should preferably be external.

Such a paired generator can be extremely cheap (for mass production) and can be widely used in transceiver telecommunication MM / SMM systems (including for intercomputer communication). At the same time, several paired generators with different difference frequencies and even different natural frequencies of the generators (when changing the configuration of their antennas) can be located on the same substrate. Antennas can be different for different pairs and paired antennas can be differently oriented on the substrate (the same for antennas in a pair, but different for different pairs).

In FIG. 17 phase detector 119 and selective block 115 (the amplifier 125 filter 124 is combined into a block 138 having one output 139 matching the output of the amplifier 125 and two inputs, input 140 matching the signal input 118 of the phase detector 119 and input 141 matching with another (reference) input 121 of the phase detector 119; while the additionally specified first combined block 138 is combined with a mixer 114 and a frequency selective block 115 (amplifier 117 - filter 116) into a second combined block 142 (PLL1) having an output 143 matching (electrically connected) with output 139 of the block 138 and three inputs, the input 144 is simultaneously the first input of the mixer 114, and the second input 145 of the block 142 is the second input of the mixing element 114, and the third input 146 matching the reference input 121 of the phase detector 119

Finally, the PLL block 142 combined with the generators 108, 109, valves (non-reciprocal devices) 110, 111 and the corresponding directional couplers 112, 113 form a pair of mutually coherent signals generator (BKC generator) 147 or, in other terminology, a doublet (multiplet) line generator 147 (DL generator), the last term will be used if indicated the BKC generator is used specifically for emission into free space, the emission of both spectral components in the form of a doublet component through the combined output antenna 137 of FIG. 17, or two predominantly identically oriented antennas 132, 133 having predominantly the same radiation patterns. It is preferred that the amplitudes of the spectral components of the doublet component are substantially the same.

Block 147 has two outputs 128 and 129, which coincide with the outputs of the corresponding directional couplers 112, 113, which receive large parts of the signal energies of the generators 108, 109, respectively, one input 148, which coincides with the input of the phase detector 119, designed to supply the signal of the reference generator 122, two contact groups 149, 150, usually connected by a jumper 151, (the presence of a connection of a contact group 149, 150 by a jumper 151 provides an electrical connection to the output of the amplifier 125 and the control electrode of the VCO 109 with the corresponding by applying an error signal generated by the phase detector 119 directly to the control electrode 127 of the VCO 109).

If there is no jumper 151 (in the case of the above-described encoding of the doublet signal by means of a deterministic, time-independent relative shift of the carrier frequencies of the spectral components of the doublet component, the jumper must always be connected), the indicated error signal of the phase detector 119 can be applied to one of the inputs of the signal voltage adder 152 , a modulating signal (in the form of a change in the signal voltage over time, for example) for FM / FM coding (modulation ) of the differential signal of the generators 108, 109. The output of the modulating signal generator 153 in this case is electrically connected to one of the inputs of the adder 152 in the case .. As indicated above (Fig. 17), the pass bands of blocks 115, 126 must be selected so that the modulating appearing on the output of the mixer 114 as part of the total difference signal was suppressed to the maximum and did not pass to the output 143 of block 142. This ensures high stability of the frequency of the difference signal in the intervals between the absence of the modulating signal of the generator 151 and guarantees the stability of the corresponding FM / FM modulation of the difference signal, if FM / FM modulation performed.

Such designations associated in combining various elements into different blocks (by means of a jumper 151) are made for ease of presentation of the subsequent material. The BKC generator considered above and similar, based on the principle of radiation from practically one phase center (or several, but closely spaced) mutually coherent signals (two or more), with modulated difference frequencies can be of considerable practical interest in MM / SMM communication systems . Such systems can be widely used in wireless high-speed (broadband) intercomputer communication, relay broadband, for wireless communication of various life support systems inside buildings, for covert communication if the carrier frequencies of the generators are located in the absorption bands of the MM / SMM radiation by the atmosphere (secrecy is also ensured by forced deviation (maybe according to a random law) of the actual carrier frequencies while maintaining the indicated phasing of their difference frequencies), etc.

In this case, the corresponding transceiver systems can significantly compress the information communication channels (due to the temporal stability of the spectral localization of the corresponding difference frequencies), while expanding as the band of one such channel (the phase or frequency deviation or the frequency shift of the difference signal can be arbitrarily large), and the frequency range occupied by such channels (the absolute value of the difference signal can be arbitrarily large, while the carrier range MM (/ CMM) of the range is many times exceeds the ranges of radio frequencies and microwave frequencies.In this case, this device is a transmitting path of a transceiver with a double (or many) carrier, which can be used for telecommunication purposes with increased noise immunity and without additional restrictions on the band of the information signal. In this case, any modulation / demodulation methods based on the principle of coherent (increased noise immunity and selectivity) demodulation of the received signals can be used, since the difference frequency present in the signal spectrum has increased phase coherence (there are a huge number of approaches to make it discrete). Phase modulators can be used in antiphase to increase the depth or efficiency of phase modulation.

In such systems, the difference signal is modulated by the signal of the communication message (or the signals in the case of the number of mutually coherent signals in the composition of the common signal are more than two). To implement duplex communication, a frequency diplexer can be installed at the output of such a transceiver, and the difference in transmission and reception frequencies can be quite large due to the implementation principle of the device, which provides increased isolation of the transceiver channels. The isolation of the transceiver channels can be provided by the frequency difference of the corresponding difference signals (transmission and reception, respectively)

The difference signal itself can be modulated in various ways. Some are described above in connection with the discussion of the BKC generator of the implementation of FIG. 1, Modulators 130 and 131, which are part of the corresponding independent signal channels, can carry out both amplitude and phase modulation of carrier frequencies (in this case, both modulators 130, 131, or only one 131 can be used at the same time, the second carrier plays the role of a reference for creating a difference signal in the mixing diode of the receiving device by heterodyning).

Another approach to the implementation of the frequency (or phase) modulation of the difference signal is to add additional the amplitude-modulated signal of the message source 152 to the indicated error signal of the phase detector 119, at least by adding the two signals of the block 151 (for example, a summing operational amplifier or other faster device).

Another possibility for modulating a two-frequency carrier lies in the frequency-phase modulation of the signal of the reference oscillator 122 (the source of the differential frequency signal). Frequency (phase) modulation of the difference signal by the BKC generator is transferred to the corresponding difference signal. In this case, the speed of the device is determined by the frequency-phase implementation of the feedback loop

The advantage of the last two approaches is the simplicity of the integrated-planar design of such a transmitter, when the cost of the generators (say on the Gunn diode) is low due to the low requirements for stabilization of their absolute frequencies, while the MM mixer 114, as well as all the elements of the BKC generator can be located on the same substrate (and made by a single integrated technology as MM generators) As generators 108, 109 of the BKC generator can be generators of any range, starting from the YIG generator of the microwave range torches, easily tunable in the range of 8-18 GHz, (generation of millimeter-wave radiation using the YIG generator of the microwave range can be carried out by supplying a signal of such a generator to the input of the frequency multiplier, in particular, implemented on a Schottky diode by generating its harmonics of various orders) , Gunn diodes MM / SMM ranges, backward wave tubes tunable in the tens of GHz bands and produced for spectral ranges up to THz. In this case, the circuit of the BKC generator can be supplemented by frequency multipliers (harmonic generators), sequentially included one in each independent channel before or after modulators 130, 131 (in this case, the modulators must be tuned to the corresponding frequency range of operation).

Frequency multipliers can be implemented on Schottky diodes, allowing to obtain harmonics of the pump signal with a low level of conversion loss up to (depending on the frequency of the pump signal) THz range.

Each such multiplier can be equipped with a frequency-selective band-pass filter that selects harmonics of the desired frequency (in the future, the possibility of switching on the harmonics of the multiplier of the specified band-pass filter is assumed, but the filter may not be shown in further figures, as it may in some cases not be used). The use of multipliers makes it possible to use any part of the MM / SMM spectrum for carriers radiated into free space by antennas 132, 133 (137) (Fig. 17), using much lower frequency sources as the driving generators 108, 109 (for example, microwave radiation YIG generators can be transferred to the millimeter range by multiplying frequencies with a factor of 3-5). The real factor of multiplication should not exceed the value of 8-10 (otherwise the level of phase noise starts to increase rapidly and conversion losses increase).

The frequencies of the paired generators 108 and 109 can synchronously vary in magnitude, in principle, in any range, towards a simultaneous increase (or simultaneous decrease), for example, under the control of the corresponding control unit 106 of FIG. 16 in this case, due to the described PLL, the difference signal of these generators will still be phase-synchronized in the manner described above (with proper selection of the PLL loop element parameters) and will have the spectral purity indicated above (and the signals of the individual oscillators sweep in frequency in this pair will repeat the frequency phase changes of each other (the signal of one generator will control signal of another. The range of variable frequencies of the sweep paired generators can be quite large (in the case of BWT or YIG generators, it can cover up to several tens of GHz), which allows one to obtain partial images at an ultralow level of illumination of observation zone 6 in a wide frequency range, receiving fundamentally new information in the form of new partial spectrally excellent images.

In this case, the generator 108, as well as the generator 109, is a generator whose frequency is controlled by an external voltage supplied to the control input 154 of the master VCO 108, which controls the slave Hun 109 through the PLL block described above, which controls the voltage, and the corresponding BKC generator is characterized by an additional input 155, which coincides with the control input 154 of the generator 108. The BKC 147 generator can be effectively used to significantly increase the sensitivity of the receiving channels of a single-element 49 Whether multielement 82 UCHPOS blocks corresponding SFI receiving device substantially reducing the level of radiation, the illumination zone of observation. For this, microwave generators are preferably used, for example, the YIG generators described above (in particular, transistor ones) with a frequency of the generation signal that allows using a flexible coaxial cable as a transmission line for the generation signals (usually the signal frequency should not exceed 36 GHz). In this case, the signal of one of the paired generators 108 is supplied via a flexible coaxial cable 156 to the input of the harmonic multiplier 157 described above (or, in other words, the harmonic generator), the output of which is connected to the transmitting antenna 35, through which the harmonics of the signal of the generator 108 are emitted in the direction of the zone observations 8. In this case, the TS source 28 consists of a harmonic generator 157 and a transmitting antenna 35. Between these elements, a filter and / or the gate and / or attenuator and / or amplitude modulator, however, even without these elements, an SFI receiving circuit based on the principle of subharmonic heterodyning will be characterized by high sensitivity. To achieve high sensitivity, the signal of the second generator 109 from the output 129 of the BKC 147 generator is supplied (Fig. 18) through the flexible coaxial cable 158 to the heterodyne input 159 of the subharmonic diode mixer 160 in the corresponding channel of the UCHPOS single-element 47 or 82 multi-element receiver at the output of the subharmonic mixer of the mixer 160, harmonics of the difference signal of the corresponding signals of the generators 108, 109 appear. Harmonics of the difference signal of the required order (for example, the harmonic of the difference on the signal of the signals of the generators 108.109 of the fifth order) obtained at the output of the subharmonic mixer 160, is allocated by the frequency-selective amplifying unit 161 of the amplifier, which is connected to the output of the mixer 160, at the output 162 of the amplifier 161, the amplified difference signal of harmonics 162 will be frequency stable and phase-coherent with respect to to the corresponding harmonic (the order which is equal to the harmonic order of the signals of the generators 108, 109) of the signal of the differential frequency generator 122 of the BKC 147 generator and will contain information about the reflection coefficient Ia portion of the object surface from which the reflected signal generator 108 and which has been focused by the focusing element 10 on the receiving member corresponding to the reception channel used by the receiving device. The difference signal of harmonics (harmonics of the signals of the generators 108,109. The signal of the generator 108 is received by the receiving elements, and the signal of the generator 109 is supplied to the heterodyne input of the mixer 160 through a flexible coaxial input), which appears at the output 162 of the amplifier 161 is equal to the frequency of the generator signal differential signals 122 in the generator BKC 147 (Fig. 17) multiplied by the order of the selected harmonic (for example, an order of 5).

From the output 162 of the amplifier 161, the difference signal is supplied to the signal input of the subsequent synchronous detector 163, and the corresponding (for example, harmonic 5) harmonic of the signal of the generator of the differential signal 122 of the BKC generator, which is formed in series by a frequency multiplier 165 and a strip, is applied to the reference input 164 of the synchronous detector 163 a filter 166, the output of which is connected to the reference input 164 of the synchronous detector, while the input of the multiplier 165 receives the signal of the differential frequency generator 122 of the BKC 147 generator by means of flexible coaxial cable. At the quadrature outputs 167,168 of the synchronous detector 163, the quadrature components of the corresponding differential harmonic signal appear. After supplying these components by, for example, a multiplexer 89 to the input of the ADC 91, digitizing them by the ADC 91 and loading them into the memory of the processor device 22, information about the intensity of the received generator signal 108 (i.e., the corresponding radiation component) can be calculated in the corresponding processor unit 22. Not only can the components of the radiation of the generator 108, but also its amplitude and the change in its phase relative to the signal of the generator 109, which it acquired, propagating from the radiating antenna 35 to the scattering point in the observation zone and then to the corresponding receiving element of the receiving device (phase incursion of the signal of the generator 109 in the coaxial cable is deterministic and easily accounted for by appropriate calibration).

The simplest solution is to determine the parameters of the received (information) signal of the generator 108 associated with digital methods for spectral analysis of signals described in detail above. For their application, the differential signal from the output 162 of the amplifier 161 through the multiplexer 89 is fed directly to the input of the ADC 91 and the time samples of the difference signal are performed at a sufficient rate and with a duration of a series of samples inversely proportional to the required spectral resolution of the difference signal. Then the array is loaded into the memory of the processor device and digital Fourier transform is performed on this array in order to identify the spectral composition of the difference signal and the intensity of the signal of the generator 108 received by the corresponding receiving element of the corresponding receiving device is determined by the parameters of the spectral component of the corresponding frequency of the difference signal (e.g., its amplitude).

It is clear that a receiving channel based on digital spectral analysis of difference signals can identify (decode) and determine the intensity of a large number of difference signals and, accordingly, distinctively encoded radiation components simultaneously received by the receiving element. For the simultaneous emission of such components, any number of TP sources can be used, the generators of which are used the above-described scheme for generating harmonics of the pair signals of the BKC generator. The advantage of the above transceiver circuitry for the imaging system also lies in the fact that the microwave signals of paired generators can be transmitted to the PR radiation source and the receiver device by means of flexible coaxial cables of sufficient length, rather than by hard and long sections of waveguides (the latter is not practical from a practical point of view) .

Moreover, if, simultaneously with the digitization of the signal from the output 162, the amplifier 161 digitizes from the output 164 of the frequency multiplier 166 the signal of the corresponding (in our example 5th) harmonic of the signal of the differential signal generator 122 (it is assumed in this case that the blocks 165 and 166 in the digital circuit spectral analysis of signals saved) and as an array of information (difference) signal and reference (signal of the signal generator 122) (more precisely, their harmonics of the same order) are loaded into the memory of the processor unit 22, then both the amplitude and the relative phase of the difference signal can be determined by computation, and hence the radiation component of the generator 108 adopted by the corresponding receiving element PU. The phase characteristics of the radiation component transmitted through the observation zone can be used in a number of different applications.

In the case of using the BKC 147 generator as a generator of doublet lines, i.e. in this case, the signals of both paired generators 108,109 are equally radiated towards the observation zone 8, either through independent but closely spaced antennas 132, 133, or through a common antenna 137, the receiving channels of the corresponding UCHPOS units should be adapted accordingly for receiving, decoding, and subsequent processing of the corresponding difference signals of such doublet radiation components, for example, by using the circuit shown in FIG. 19. In such a scheme (Fig. 19), both radiation components (different in carrier frequency) doublet components are received by the receiving antenna 48 at the same time at the corresponding point of the sharp focusing surface of the focusing element 15 and their electrical signals are fed to the input of the mixer (mixing diode) 169 and independently from each other are converted downward in frequency, while the local oscillator 171 is fed to the heterodyne input 170 of the mixer 169. After amplification in the amplifier amplifier 161, the frequency-shifted doublet signals the remaining ones are fed to the input of a nonlinear element 172 (a quadratic detector, a diode) at the output of which their difference signal is generated, after filtering and amplification in the amplifier of the amplification amplifier 173 (whose frequency characteristics are selected taking into account the filtering of the difference signal itself, and not its harmonics), the difference signal, frequency which is equal to the frequency difference of the signals of the generators 108, 109, while the phase is synchronized with the phase the spectrally pure stabilized signal of the generator of the differential signal 122 of the BKC 147 generator, through the multiplexer 89, is fed to the input of the ADC 91 and digitized as a sequence of time samples of a certain duration. The resulting array of samples is loaded into the memory of the processor device 22 and then the corresponding Fourier transform is performed on this array to determine the spectral composition of the digitized signal. The intensity of the doublet components can be determined from the obtained spectrum in accordance with the algorithms of digital spectral analysis repeatedly described above. It is clear that a receiving device based on the circuit of FIG. 19 can detect a sufficient number of doublet components with different difference frequencies, which is determined by the duration of the samples and the operating frequency band of the receiving device as a whole. The density of independent information channels is high, due to the precision frequency grid of the difference signals arising at the output of the diode 172. At the same time, there are no essential requirements for the frequency stability of the generators 108, 109 and the local oscillator 171, since their phase noise does not affect the spectral frequency of the corresponding difference signals . Moreover, the number of channels of the preliminary frequency conversion of the doublet components can be more than one without affecting the quality of the difference signal generated after such transformations, after any phase distortions are introduced in the preliminary electronic stages in both doublet components in the same way.

The circuit of FIG. 19 can also be used to receive radiation components with different amplitude modulation.

Another signal receiving circuit, functionally equivalent to that discussed in connection with FIG. 19 is shown in FIG. In this case, an antenna-coupled non-linear element is used as the receiving element 174. Non-linear element 175 (usually a diode Schottky) is placed in the terminals of the receiving antenna, while the non-linear element 175 connects, as a rule, two metal parts 176, 177 of the receiving antenna.

In this case, the primary electrical signal induced on the antenna parts 176, 177 by incident radiation consisting of radiation components 178, 179 is quadratically detected on non-linear element 175 with the formation of their difference signal, which appears at the output 180 of such a receiving element 174. In this in the sense of point 180 of the circuit in FIG. 20 is equivalent to a point coinciding with the output of the nonlinear circuit element 172 in FIG. 19. Therefore, the series-connected amplifier 181, multiplexer 89 and ADC 91 of FIG. 20 in this case are functionally equivalent to amplifier 173, multiplexer 89 and ADC 91 in the circuit of FIG. 19, obtaining the same end result of processing the received signals as obtained in the circuit Fig.19. The receiving element 174 can convert the primary electrical signal induced on its antenna parts downward if the radiation of the heterodyne generator 182 is quasi-optically coupled to the same receiving element 174 together with the focused radiation 178 (as a rule, the radiation of the heterodyne generator 182 is incident on the receiving element 174 in the form plane wavefront). In the latter case, at the output 180 of the receiving element 174, partial electric signals offset in frequency downward corresponding to the radiation components 178,179 appear. In this sense, point 180 of the circuit in FIG. 20 is equivalent to a point coinciding with the output of the mixing diode 160 of the circuit of FIG. 18. Therefore, the series-connected amplifier 181, multiplexer 89 and ADC 91 of FIG. 20 in this case are functionally equivalent to amplifier 161, multiplexer 89 and ADC 91 in the circuit of FIG. 18, characterized by the same end result of processing the received signals as obtained in the circuit Fig.20. Among the advantages of such reception schemes (in accordance with FIG. 19, FIG. 20) is the possibility of integral (monolithic) execution of the multi-element matrix of receiving elements 174. In this case, planar antennas are usually used, which are technologically easy to implement, which does not limit the possibility of careful selection their parameters.

Highly stable difference signals responsible for various partial components of the radiation received by the receiving device can be obtained in other implementations of the receiving and transmitting SFI equipment, described below.

Highly stable difference signals responsible for various partial components of the radiation received by the receiving device can be obtained in other implementations of the SFI transceiver equipment described below. One of the implementations of the mutually coherent signal generator of the BKC generator with the number of generated signals greater than two and with different values of the difference frequencies is shown in FIG. 21. The BKC 182 generator includes individual signal generators 183, 108, 109, all or only 183 of which are VCOs. One of the generators 183 is selected as the master, the phase of the signal of which will be followed by the phases of the remaining generators - slave VCOs 108, 109 through the corresponding PLLs. To this end, a smaller part of the signal energy of the generator 183 is coupled into the waveguide channel 185 (waveguide or microstrip designs depending on the implementations of the generators 183, 108, 109), ending with a coordinated load 186 to minimize reflections, and a set of directional couplers 187, 188, each of which s energy supplies corresponding portion of the master oscillator signal generator 183 driven PLL control circuit 108, 109. The structure of the said control circuits includes blocks 189, 190, functionally corresponding to the second fully the combined block 142 (Fig. 17) having inputs 191, 192, 193 (block 189) and 194, 195, 196 (block 190) which are functionally equivalent to the corresponding inputs 144, 145 and 146 of block 142, and outputs 197 (block 189) and 198 (block 190) correspond to the output 143 of block 142; as well as blocks 199 and 200, which are differential frequency generators functionally equivalent to block 122 (Fig. 17), but having different frequencies of the corresponding generated signals. The circuits are also equipped with directional couplers 201, 202, each of which divides the signals of the corresponding generators 108,109 into smaller parts supplied to the inputs 192 and 195 of blocks 189, 190 and large parts to waveguide structures 203, 204, which can either multiply the frequency 157,205 times radiation (by generating harmonics) are sent to the observation zone 6 by means of transmitting antennas 35, 206 connected to these multipliers (the frequencies emitted by harmonic generators - multipliers are equal to the harmonics frequencies of the generators 108, 109), l for directly connected to the antennas 35, 206 (the directional valves necessary in this case are not shown in Fig. 21).

The principle of achieving phase synchronism of the difference signal of the slave generators 183 and one of the leading 108 (similarly to any other slave generator 109) with the signal of the differential frequency generator 199 is achieved as follows. At the input 191 of block 189 a smaller part of the signal of the generator 183 is supplied and at the input 192 of this block 189 a smaller part of the signal of the slave generator 108, block 189, by analogy with the operation of block 142 (Fig. 17), generates an error control signal proportional to the phase mismatch of the difference signal of the generators 183 and 108 and the signal of the reference frequency generator 199, which from the input 197 enters the control electrode 154 of the VCO 108 to reduce the indicated phase mismatch until the complete phase synchronism of the specified difference and specified th reference signals. Ratio between the above smaller parts of the generators 183 and 108 should be the same as for the ratio of the smaller parts of the generators 108, 109 discussed in connection with Figure 17. Thus, the synchronization of the difference signals of the slave 183 and the leading generators 108, 109 with the corresponding signals ( mainly with various parameters) reference generators 199, 200.

In other words, the procedure for generating multiple mutually coherent signals can be described as follows.

A smaller part of the signal energy of the leading generator 280 enters through the directional coupler 184 into the wave guide channel 185, from which part of the energy of this signal through the directional couplers 187, 188 to the blocks generating other mutually coherent signals. In each block, the corresponding signal from channel 185 is supplied to one of the inputs of mixer 93 of the second combined block 189 (equivalent to 142 of FIG. 17). At the other input of this mixer, a part of the energy of the slave generator 108 is supplied, and finally, at the input of the phase detector 95 of block 189, a differential frequency signal is supplied to the differential frequency generator 199, with a frequency different for different generator blocks. Due to the feedback loop provided by the PLL (the phases of the corresponding difference signals are captured by the phases of the signals of the corresponding reference generators), the outputs of the corresponding directional couplers 184, 187, through which most of the signal energies can be connected to the inputs of the frequency multipliers 157, 205, 207 for the formation of mutually coherent signals of a higher frequency and then sent to the observation zone 6, through antennas connected to the multipliers, 35.207 and 208, respectively. In this case, the object is illuminated by multiplet radiation, each component of which is shifted relative to the main one (emitted by the slave generator 183) by exact spectral values equal to the frequencies of the difference frequency generators 199, 200. In this case, the signal of one of the generators of the predominantly leading 183 can be used as a heterodyne source in the receiving circuit of FIG. 18, while its signal from the output 209 of the matching device 210 connected to the output of the main channel of the directional coupler 184 and intended to transform the signal energy from the waveguide transmission line to a coaxial transmission line with minimal losses and through which the signal of the generator 183 is transformed from its waveguide mode into the corresponding coaxial cable mode and can be further transmitted via a coaxial flexible cable to supply the signal of the generator 183 directly to the local input 159 (or several of these inputs, if a multi-channel UCHPOS is used)) of the mixer 160 (lei) of the corresponding channels of the corresponding UCHPOS block, while the signals of the generators 108, 109 are used to illuminate the observation zone 6. After reflection from the object and reception by each receiving element of the corresponding receiving device, these signals will be mixed in the corresponding mixing elements of the receiving channels of block 49 with the corresponding harmonic of the local oscillator signal 183. The difference signals formed at the output of such mixers will have a The phase and phase stability of differential signal generators 199, 200 will be frequency-separated in accordance with the selected harmonics of the corresponding differential frequency generators 199, 200 and will carry information as the intensities of the signals reflected by the object.

This approach significantly solves the problem of the flexibility of implementing various devices for lighting the observation zone and receiving the radiation components scattered in it, since the flexible coaxial cable allows you to easily move the light source TP unit consisting of a multiplier loaded with an antenna in the space of the illumination system and place it anywhere optimal for illuminating the object 8 by means of an appropriate scanning device. It is also significant that the various generators 108, 109 of mutually coherent signals individually and quite simply technically they can illuminate various parts of the object

The composition and the mutual sequence of the radio nodes included in each of the respective receiving channels of the receiving device 25 or 82, as well as the principle of their joint functioning when amplifying and decoding the radiation signals of the partial components reflected by that portion of the surface 87 (Fig. 15) of the object 8, on which “watches” the corresponding receiving element 48 of the receiving matrix 85 (associated with one of these channels), is determined by the peculiarity and sequence of the primary radiation coding, p different for various partial sources 3,4,7 and even secondary coding (if this is carried out by the corresponding PR radiation source). In the general case, the implementation of double (as well as greater multiplicity) decoding (demodulation) is not difficult and can be carried out using standard radio engineering units (including, along with amplifiers of the corresponding ranges, heterodyne mixers, amplitude (quadratic) detectors, synchronous (parametric) detectors , including scanning, also digital nodes, allowing a certain time sequence of amplified and shifted downward in frequency (can be partially odirovannyh) transfer signals in their digitized by ADC and implement methods of decoding by the digital signal processing. This can be done for any species (including many sufficiently known) modulation / demodulation MM / radiation HMM.

As indicated above in the MM / CMM bands, the reflection of radiation from most of the observed objects is carried out mainly in a mirror image. This fact determines the low quality level of images formed in the MM / SMM ranges, even if the spatial coherence of radiation in the field SFI vision is significantly reduced, by analogy with optical imaging systems.

We will explain the above by the example of changes in the phase diagrams for radiation components during their propagation from the site of the radiation-scattering surface 87 of object 8 (Fig. 15) to the point

Prize coinciding with the position of the corresponding element of the receiving matrix 48.

In FIG. 22 shows phase diagrams of 211,212,213 radiation components. The phasor diagram 188 corresponds to the state of the radiation components in the observation zone of the space point (Fig. 15), located near the point 87 of the surface of the object 8, at the moment preceding the scattering of these components by the indicated surface. Diagrams 212 and 213 correspond to the states of the radiation components at the spatial point near the element 48 of the receiving matrix 85 in the case when this radiation was scattered by the indicated point on the surface 87 of the object 8 (Fig. 15), respectively, mainly in a mirror image (diagram 212), or mainly in a diffuse way ( chart 213).

In FIG. 23 is a diagram of an image forming system illustrating a mechanism for generating strong “mirror” and weak “diffuse” signal components in a signal received by element 48 (FIG. 15). Each phasor (214, 215), FIG. 22, corresponds to a radiation component emitted by one of the point radiation sources, which is part of a multi-element spatially distributed source.

Such phasors have almost the same amplitude (length) and different mutual phases 216, 217 (the latter are insignificant since the signal processing circuit ultimately selects the squares of the phasor lengths) before the moment of scattering of the radiation components by the object. If these components are diffusely scattered by the surface area, then the corresponding indicatrixes of their scattering have wide angular distribution 218, 219, Fig.23, therefore, the relative parts of the wave fronts of the "diffuse components)) that fall into the entrance pupil of the lens 10 will be almost the same. The phasor lengths of the respective components 220,221 in the "diffuse" diagram 213 of FIG. 22, after focusing on the corresponding receiving element 48, they will be almost the same (in the case when speckle distortions are present in the generated partial images, the same phasors means the equality of the average statistical deviations in the distribution of speckle oscillations at this and the nearest receiving points for the partial images corresponding to the considered components ), therefore, the system will work as a scheme with ideally destroyed spatial coherence of the illuminating and receiving th receiving radiation device. In this case, spatially incoherent images of improved quality are formed if the object reflects the components in a diffuse way (due to the effect of statistical averaging of coherent speckles and another type of spatial noise). If the components are scattered by a surface portion in a mirror fashion, the corresponding scattering indicatrixes have narrow angular distributions 222, 223. Therefore, the relative parts of the wave fronts corresponding to different “mirror components)) will be different and such fronts will be intercepted in different ways by the entrance pupil of the lens. The mirror part 224 of the corresponding scattering indicatrix enters the entrance pupil of the lens 10 only for part of the point sources, like the TP source 83, the MPR of the radiation source 82, while for the other TP sources, like 28, only the diffuse (energetically relatively small) part 225 is intercepted by the input the pupil of the lens 10. Therefore, in the phasor diagram 212 the “mirror”) phasor 226 dominates in comparison with any “diffuse”> phasor like phasor 227. If the considered radiation components are not modulated, then the signal received by the receiving device is detected as an inseparable sum of squares of the corresponding phasors. Since only the signal dominates in this sum, formed only by a part of closely spaced point sources near the TP of the source 83 of the MPR of the radiation source 82, the millimeter image generated by these sources in PRIZ of the focusing element 10 will be spatially coherent with its speckle distortions, despite the fact that the object is illuminated spatially by incoherent light. Since each individual component of the radiation under consideration, both in the region of the object and in the region of the receiving matrix, has high spatial coherence (it is formed by a point radiation source), therefore, the partial image formed by such a component will be spatially coherent with its characteristic noise speckle distribution. Thus, with the mirror-like nature of the reflection of radiation from the object of observation (which is characteristic of MM / SMM radiation), no destruction of the coherence of radiation in the region of the object (in contrast to the optical range) will improve the quality of its image, making this image free from coherent speckles and from the influence Gibbs effect.

If the components are independently modulated (or encoded), then on the receiving side, after their independent reception, it is possible to change their relative contribution to the total signals for each element of the synthesized (or relative contribution to the value of each pixel) final (result) image by hardware or software. In this case, from a poor “mirror” image, “diffuse” images with high visual quality will be artificially obtained (the corresponding transformation of the states of phase diagrams is shown by arrow 228 in Fig. 22). The phase diagram formalism considered above remains true for the case of using a spatially distributed radiation source with a synthesized aperture, when various radiation components are generated at different times due to the mechanical movement (scanning) of a single radiation source over the surface formed by the preferred spatial position of such a source relative to the observed object (as a result of source movements aperture of a spatially distributed source). In this case, the squares of the amplitudes of the various phasors are accumulated sequentially in the receiver in time (the receiver must be suitably adapted for such a reception mode) in accordance with the rate of movement of the indicated source. Let us analyze the possibilities of the above correction of individual partial components of image signals. In accordance with the principle of superposition, the complex amplitude of the radiation at the receiving point (for example, in the area of the receiving element) can be represented as the sum of the complex amplitudes of the partial components of the components of this radiation (phasors), each of which was emitted by one of the independent elements of a spatially distributed (PR) source radiation and, after propagation towards the observation zone, was scattered by that part of the surface of the object of observation 87, which is optically coupled (by means of the lens formula 10) to matrivaemoy receiving point (point arrangement of the receiving element 48 in action), then during further propagation component partially has got in the entrance pupil SFI and focused at the point of reception, denoted by the indices (m, k)

β ^? V (V _m , _k ) Vtf ^k (y _{m> k} )) - exp (/ C ^fc (V _ra , _k )) (D

For simplicity of consideration, independent TP sources of the MPR source 82 are ordered in the form of a two-dimensional matrix set in which each TP source has its own serial number of row i and column j, which uniquely determine its position in space, including with respect to the surface of the illuminated object 8 in the point of observation of the object 87. In this case, the ordinal indices of the TS of the source (i, j) uniquely determine the angle of incidence 229 β of the partial radiation component created by it, passing through the object plane 230, onto the surface section 231 8 and the object 232 at the observation point 87. Alternatively, the portion 231 may be positioned in relation to the entrance pupil of the lens closer than the object plane.

It is clear that the summation in (1) is performed over all (phase) independent TP elements of the MPR source sources (I is the maximum number of TP sources of MPR elements of the radiation source along the rows, J is along the columns, respectively

In formula (2), φ ™ means the absolute value of the phase of the partial radiation component under consideration immediately after its emission by the PR element of the source (i, j) at one time, φf] i ^ _mk , β _t ^ is the average phase incursion of this radiation component at its propagation from the PR element of the source to the receiving element (since this factor does not change in time and does not affect the final result, it will be omitted in further formulas), finally фf _J (x _mk , β _{ι J} ) - additional random propagation phase shift s radiation in the recesses of the scattering object to the considered portion 229 surface observation object 8. This phase shift components during its further propagation from the object plane 230 of the focusing element 10 to the real location _d d a particular object of the scattering portion 231, and finally, ^α 'V ^{_y> k} (y _mk ) - that part of the partial component radiation, which was reflected by the considered site of the object (this site can be characterized by a point x _mk ), then fell into the entrance pupil of the focusing element 10 of the SFI and focused on the receiving element 48 at the point PRIZ y _mk . The amplitude of the phasor ^{^«,} ^d ^ ^{m, k} f _^) is determined by the portion of the wavefront corresponding component, which has got in the entrance pupil of the focusing element 10 and independent of the scattering function of this component is that portion of the surface of the object at x _mk, which is quasi-optically conjugate with the corresponding receiving element at the point at _mk by means of a lens (the indicated indicatrix largely depends on the nature of reflection - specular or diffuse). In general, for the phase of the indicated additional raid, we can write

F.L ^ β u) - 2π ^ _{cQs βm kj j} (3)

d _d is the distance (or optical distance, if the object is in the medium) from the scattering part of the surface (206) of the object to the object (input) plane 207) of the lens (the thin lens formula conjugated with the receiving plane) ^Fig . 24, β ^mJc i, j is the angle of incidence (229) of the partial radiation component of the TS of the PR source of the source (i, j) at the object surface point x _{m> k} , and f is the index characterizing the parameter of the radiation component highlighting the object, while t shows the type of distinctive physical property of this radiation (for example its carrier frequency, e about polarization, etc. (or both at the same time, etc.), and d is the specific value of its value (for example, 94 GHz for frequency or linear horizontal polarization, or even a joint set of such values, (if the index characterizes simultaneously several characteristic parameters of the illuminated radiation).

The signal at the output of the inertial quadratic amplitude detector (assuming that all harmonics of the carrier are filtered out, and the signal is normalized to the gain of the receiving channels of the receiving device) and at the considered point y _mjk in accordance with (1), (2) will have the form

(4), where T is the characteristic averaging time of the signal by the inertial part of the indicated detector. In the case where the phase difference component emitted by various elements of the PR source is constant (the case of elements OL source emitting phase-coherent radiation components), the output will consist of both terms will contain interference supplements, defined phase relations f '"j ^to - f ™ f between the various components of the radiation.

The second interference term can be removed from the sum (4) if the indicated phase differences "f 'ф ^ f f change in time randomly. This case corresponds to illumination of the object by spatially incoherent radiation and occurs when the phase difference for of the signal components corresponding to different angular partial radiation components takes all possible values equally in the range 2π. This situation also occurs if the radiation from all TP sources is not modulated or modulated one This makes it possible to distinguish between different components belonging to different TP sources of the PR of the radiation source. This case fully describes the case of the PR of the radiation source used in the prototype. Significant disadvantages of this source associated with the mirror-like reflection of the millimeter range were discussed earlier.

In the case of independent distinctive coding (for example, by means of amplitude modulation), each angular component of the radiation, as well as any other physically distinctive radiation components (among such components, a component characterized by different values of the carrier frequency and / or polarization state, etc.) it becomes possible

In another implementation of SFI, the components of TP sources (including the squares of the lengths of the phasors of their emissions or the lengths of the phasors) can be determined independently by selective coding (for example) of modulating the partial components of each TP of the source and, accordingly, by independent selective reception by each receiving element and subsequent decoding (for example, demodulation) of the partial radiation component of each TS source (i, j), which is part of the MPR source.

In both cases, the second term of the sum (4), which describes the effects of mutual interference of partial radiation from different radiation sources, is suppressed (in this case, the intermodulation noise correction in the detected signal is equal to zero), while the first term is only proportional to the accumulation time T, (it is assumed that all signal modulations were removed by previous demodulation schemes), which is not shown in the formulas in the text below, but its presence is implied. Thus, the signal at the output of the inertial amplitude detector is equal to

α ' ^d S _{m> k} (y _m , _k ) = ∑ ( ^{α /} V- ^k (У _m , _k )) ² (5)

T.O. the recorded signal in this case is the sum of the squares of the amplitude modules of the partial radiation components received by the receiving element 48 (the squares of the lengths of the corresponding phasors (see Fig. 22)) multiplied by the averaging time T (not shown in formula (5), as follows text) and is proportional to the sum of the time-averaged powers of these components (proportional to the powers of the corresponding radiation components at a given receiving point) accumulated over time T, without any noise effect of the mutual phase relations between these radiation components.

In essence, relation (5) means that the signal recorded at the output of the quadratic inertial detector is the sum of the integral powers (radiation densities, including spectral ones, for a given set of ranges of physical parameters characterized by the considered radiation components accumulated during the exposure time of the image) partial images formed by partial phase-independent radiation components (in accordance with (5), each of which was random and independent m is emitted by one of the independent TP sources of the PR of the radiation source and the corresponding components are phase-independent.

In the case when this radiation is encoded in a distinctive way, that is, various radiation components can be received by the receiver as a result of decoding procedures independently of each other and their characteristics (for example, average power) are determined independently, such a signal can be represented as a separable independent set of components,

α ^? Si _k ( _{V ra> k} ) = U ( ^α 'V _i f) ² (6)

which can be converted into a sum of type (5) (characterized by only one number, the value of the element

(m, k) together with an arbitrarily chosen weighting factor ^α 'R | " _j ^k for each such independent component included in such a set

α ^? S _{m, k} (y _{m, k} ) = ∑ ° ^< "R £ ^k • ( ^"<"V ^) ² (7)

Moreover, the resulting matrix result image can be represented as a matrix of elements of the resulting synthesized (combined image), each element is characterized by the position of the corresponding receiving point at _mk in PRIZ, where the corresponding components of the focused radiation were taken and the value of which is equal to "'S _mk (y _mk ).

In this case, the values of the weight coefficients ^a 'R _y ^{> k} will be selected from the conditions for obtaining a single image of the best visual quality and / or information content. Since these coefficients can be changed arbitrarily (for example, by the processor, when the signals are digitized and loaded into its memory), the number of such sums, as well as the change in the relative contribution of each component to the final value of the element value (equal to the indicated weighted sum) of the resulting (synthesized) image corresponding to this signal. This allows, for example, to suppress an excessively large signal of one of the components of the corresponding radiation component, characterized by specular reflection from a portion of the surface of the object, when the other components are reflected diffusely, which means that their signal level is low compared to the mirror signal. Moreover, this can be done for each element of the image thus formed and with the number of components in each element equal to the number of independently decoded signals from the signal received by the corresponding receiver. Independent TP sources 28, 80 SPU 24 or independent TP sources 28, 28, MPU 81 create independent spatial radiation components in the observation zone 6 that can either be emitted at the same time instants, while they are encoded in different ways (for example, have different frequency of their amplitude modulation), to be, after their reception in the Priz plane, the corresponding receiving device, independently decoded (demodulated) and processed in the corresponding receiving devices 25,82 in order to determine their intensity th (time-averaged power), or radiated sequentially in time, which allows you to use the principle of temporary demultiplexing them signals in the respective receiving devices 25, 82 so that they are independently processed in these devices. Different sets of these components can be emitted simultaneously and differently encoded, forming the corresponding group of radiation components, while various such groups can be emitted sequentially in time, which allows the principle of temporary demultiplexing in the UE to be used for component signals belonging to different indicated groups. In this case, to each distinctive angular direction of propagation of the radiation components in the observation zone, which unambiguously corresponds to a certain spatial position of one of the TS sources of the corresponding PR source (SPU or MPU), several physically different components can correspond (for example, several different components of the same direction of propagation components of different radiation frequencies (for example, 94 GHz, 105 GHz, 115, GHz, etc.), which in this case have the same type of polarization and / or different (for example, linearly polarized components in the vertical and / or horizontal directions and / or components with circular polarization), in any case, the corresponding receiving devices should determine the intensity distribution of each of these radiation components in the sharp focus plane PRIZ after they are focused by the focusing element 10 into this the PRIZ plane is independent for each component (by means of receiving PUs by the receiving elements and processing in their UCHPOS) and loading the value of the values of the elements correspondingly partial images to the memory of the processor device 22 for their subsequent processing. The distinctive propagation directions of the components of the (distinctive-angular) radiation are uniquely associated with the spatial positions of either the corresponding TS sources of an unscannable multi-element spatially distributed (MPR) radiation source, or with the spatial positions of any one TP of the source or several that it (or they) occupy during its mechanical scanning in the scanning plane 31 of the corresponding SNU 24 to form the corresponding partial image. The set of all possible distinctive spatial positions of TP sources form a spatial aperture of the corresponding spatially distributed radiation source, or a fixed aperture in the case of a multi-element spatially distributed (MPR) radiation source 82, or a synthesized aperture in the case of a scanned spatially distributed source (SPU) 24 of the radiation source , in the form of the corresponding two-dimensional matrix of spatial positions (shown in Fig. 25) of the corresponding TP Source.

In the case of using amplitude modulation to encode various components, the spectrum of each individual such partial radiation component will consist of at least a spectral component at the carrier frequency of the illuminating radiation and at least two additional spectral side components resulting from said modulation, which are shifted relative to the main component is the zero component by the value of the modulation frequency Ω ^mo . These shifts for the side spectral components turn out to be different for different TP sources and the corresponding radiation components. The diffuser is designed in such a way that the intensity of the indicated components — radiation components — after their reflection by this diffuser turned out to be equal in magnitude over the entire observation area (i.e., the condition for uniform illumination of the object by radiation by the specified component is fulfilled). In FIG. 25 is a schematic representation of a multi-element spatially distributed (MPR) radiation source characterized by spatially distributed TP sources 28.83 located on the aperture surface of this MPR source in the form a two-dimensional matrix such TP sources, geometrically rolnostyu corresponds discussed above two-dimensional array of spatial positions of its TA sources (GSHTPI) (structurally it can be TA sources of any of the above-discussed implementations), each of which has its own frequency AM modulation Ω ^mod emitted by them radiation (either corresponding difference frequency if doublet coding is used).

In FIG. 26 shows a spectrum 233 of one of the sidebands of the resulting composite radiation (emitted by the entire matrix of TP sources) in the observation zone when different components of the differential amplitude modulation are used for coding. This spectrum consists of an almost continuously filled (due to the appropriate choice of frequencies of the corresponding modulating signals) set of side spectral lines (234,235) of the corresponding partial radiation components, each of which is received by the same element

of the receiving matrix (m, k) and the value of each of which y ^a 'V ™ - ^k J corresponds to a time-averaged power (a factor proportional to the averaging time T is omitted hereinafter, but its presence is assumed as a result of time averaging) of one of the above partial the radiation component that was radiated towards the observation zone 6 of the object by the corresponding TS radiation source from the spatial point of the spatially distributed radiation source (SPU or MPU), characterized by indices (i, j). It is assumed that each such component, characterized by its propagation direction in the observation zone 6 (each such angular component has its own set of indices (ij)), is characterized by its own value of another distinctive physical feature or a set of values of additional physical features (as discussed above), where t is the index of the physical property (for example, t = l means the carrier frequency of the radiation) D is a serial number showing the value of a physical parameter or set of parameters, for example t = l, 1 = 1 can mean a frequency of 94 GHz, t = 2 1-1 component with vertical linear polarization). The number of spectral independent lines of type 235, 234, for each parameter a'i, can be equal to the number of positions of TP sources of type 28, 83 of their positions in the aperture of the corresponding PR of the radiation source (SPU or MPU) in the corresponding matrix of spatial positions of TP sources having dimension of spatial position elements (IxJ). Where I is the number of rows of elements of this matrix, J is the number of its columns .. The values of these spectral components in the observation zone before they interact with the object are preferably equal to each other (Fig. 26) due to the constructive PR of sources, and the intensity values in each wave surface the front of each component in the observation zone 6 is also almost the same, that is, the observation zone 6 is illuminated uniformly by the radiation of each indicated component.

Therefore, any of their relative changes after reflection from the object 8 and person 6 and falling into the corresponding elements 48 and / or 48.84 (in FIG. 2 and FIG. 15) of the corresponding receiving devices demonstrate differences in their reflection by different surface areas (in the case of plastic objects and internal points) of observed objects 8 and person 6. Each individual spatial component of radiation has its own propagation angle in the observation zone. Here, part (or all) of the spectral components is the component of the radiation scattered in the observation zone, decomposed by the angle of its propagation in the propagation zone, since such a component illuminates the object from the corresponding spatial point of the aperture of the radiation source PR. The spectral localization regions in the spectrum of such components and the spatial localization regions of the corresponding TP sources in the specified aperture the generation of these components are uniquely related to each other, which is crucial in the analysis of the processing of such signals received by the corresponding receiving devices.

In FIG. 27 shows the fine structure 236 of the signal spectrum in the form of a set of independent ordered and distinctive (i.e., mainly non-overlapping) spectral lines, including spectral lines 234, 235 received in one of the UCHPOS channels after receiving focused multicomponent radiation with the corresponding corresponding receiving element 48 at the corresponding spatial point of the Priz (after its reflection in the corresponding part of the observation zone 6 or, what is the same, in the corresponding portion of the SFI field of view). The magnitudes of the amplitudes of each spectral line are equal to the intensities of the corresponding different components of the received PUs at the considered PRIZ point. A set of all spatial positions of the receiving elements in the aperture of the receiving device in Priz, including the receiving (receiving) element (s) of the scanned receiving device or unscanned receiving elements of the receiving matrix of the multi-element receiving device, necessary for the formation of all the various elements of the corresponding partial image, forms a two-dimensional matrix spatial position of the receiving elements (PPE) in the aperture of the receiving device which is structurally equivalent to the corresponding two-dimensional th matrix of elements of the (corresponding) partial image (EPI). The system can transform the spectrum by suppressing the mirror components or by changing mutual amplitudes in accordance with the selected criteria. One of such transformed spectra is shown in FIG. 28, which is obtained from the spectrum shown in FIG. 27. Relationships The position of each image element in such an EPI matrix, as well as the corresponding spatial position of the corresponding receiving element in the PRIZ or, in other words, in the PES matrix, is characterized by indices (m, k), and the corresponding EPI and IJi SEM matrices have similar structures and equal dimensions (M ₅ K). In this case, the radiation components were taken by the receiving elements located at the point PRIZ characterized by the indices (1,4) of the matrix ШJilЭ and the same indices (1,4) of the EPI matrix. In the case of using a multi-element receiving matrix when forming partial images of objects of the observation zone 8, this receiving element has a fixed spatial position with indices (1, 4) i.e. located in 1 row and 4 column of the receiving matrix). In FIG. 27, for illustration, one intense “mirror” spectral component 234 is identified, associated with the TS source 28 (in the matrix representation of the PR source - this element has position (3, 3), i.e. it is located in the 3rd row and column 3 of the matrix of spatial positions of the TP sources ) and a weak “diffuse” spectral component 235 associated with the TP source 83, characterized by the position in the matrix of spatial positions (20.2). The maximum value of the magnitude of each of the spectral lines corresponds to (or is equal to, if the calibration procedure for the received signals is used to determine the absolute values of the intensity of the received radiation components) the intensity value of the corresponding distinctive received radiation component.

For a clearer graphic representation of the features, the distribution of 236 spectral lines of the decoded signals 234,235 (from the signal received by only one element 48 of the receiving device) introduced a two-dimensional matrix - a diagram 237 (Fig. 29) of these spectral lines is structurally similar to the PPTPI matrix for the corresponding PR radiation source TP sources which are responsible for the appearance of the corresponding spectral components. Spectrum 236 (Fig. 27) of the signal of the receiving element (with position (1, 4) in matrix notation) is transformed into a matrix diagram 237, so that each spectral line 234, 235 of of spectrum 236 occupy such a matrix position in the matrix of diagram 237, which is occupied by that element of the matrix of the PR of the PPTI source (which created this spectral line (created by means of distinctive radiation of radiation). Thus, the appearance of the matrix diagram 237 allows one to unambiguously assess the contribution of various TS sources in the formation of composite radiation for a given receiving element (1.4) and the elements of the corresponding partial images. Similar matrix diagrams arise for any and all elements of the receiving matrix . Thus the amount of multiparameter images received by the receiving matrices of dimension (M, N) when the subject 8 radiation ITP source with matrix PPTPI dimension (I ₅ J) ₅ a matrix (MxN) sets matritsdiagramm Najd having pazmepnoct (I, J). With the large dimensions of both matrices of the radiation source and receiver, this is a huge amount of information equal to the product MXNXIXJXY, where Y is the number of bytes corresponding to the digital representation of the spectral power in the computer's memory.

In essence, a matrix diagram is a set of independent signal

components C ^' _h y ^a ' V _y ' ^k j contained in the signal of the corresponding

receiving element (m, k) (or its spatial position if it is scanned in the image plane) generated by different sections of the diffuser with dimension. (I ₅ J) when it is illuminated by a radiation beam with a certain set of physical parameters af, and with a different value of the parameter af ^+1, a new matrix diagram is generated corresponding to the new value of the physical parameter (or their set) of the radiation illuminating the diffuser. The formation of partial images, each element of which is formed by radiation with a limited but characteristic set of physical parameters of the radiation illuminating the object, can be achieved by targeted selection of the appropriate components | ^α / ^ ^{rm, k} j _or weighted sums from the corresponding sets 238,239 for the corresponding image element (or corresponding receiving element) of such an image Depending on the choice made, partial images can be obtained spatially coherent and monochromatic, spatially incoherent and monochromatic, or for example spatially coherent but polychromatic, or finally “white”, or both, but highlighted mainly at a certain angle to their surface, etc. (the choice can be made in accordance with the formalism described above. Such partial images, each by itself, can provide additional distinctive information about the observed object (for example, different details of its surface can be emphasized at different frequencies or when highlighted at different angles, etc.). Moreover, such partial images can also be obtained by hardware, when the formation of the indicated sums from the group

the corresponding components ["'V _y ' ^k J, (as discussed above in each receiver-image element can be implemented at the hardware implementation level. Subsequent combination of the formed partial images (hardware or software) with the formation of their total image with elimination (or reduction of their high coefficient) of interfering partial images with a high noise level (or fragments of them up to individual pixels) from the total weighted sum of partial images can be considered as the simplest but effective implementation of combination procedures

Any relative changes in the amplitudes of the indicated radiation components that are scattered by each individual point on the surface (and / or internal point) of the object will be strictly determined by the scattering characteristics of this object at this point for each set of parameters of the illuminating radiation. Some of these components can be mirrored from this point (due to specular reflection at certain angles of incidence, the so-called glint effect) and represent very strong signals at the output of the receiving matrix element. From the spectrum, it can be easily determined that mirror reflections are caused by elements having corresponding modulation frequencies.

In the simplest version of the proposed methodology, such destructive signals can be simply removed or extracted on the signal processing ethane. The ability to selectively extract destructive signals without any effect on other image information signals (even for only one pixel of such an image) is a basic property of this latest MMV / SMMV SFI which creates new realities for image formation procedures.

In FIG. 28 and FIG. 30 shows the distribution of the spectral power of the encoded radiation signals in the composite signal of the receiving element 49 (or the composition of intensities for a given index of elements of the corresponding partial images) of the receiving matrix after removing interfering mirror values and some correction of other intensities for the corresponding angular components of the radiation (including 234) , which can be performed by the processor 22. The unevenness of the values of the spectral components is physically related due to the speckle structure of the observed corresponding partial ones, however, the deviations of such values about a certain average value turn out to be equal, which ensures high quality of the resulting image after using such spectral lines for its synthesis. If at the same time the observation zone 6 is highlighted by radiation in which one value of the spatial distribution in the zone observations can correspond to several additional components with distinctive values of their other physical parameters (different frequencies, types of polarization, etc.) and the components are encoded or emitted sequentially in time (or in any other way indicated above, then the amount of distinctive information about objects and a person in the observation zone 6 is rapidly growing and can be represented for each spatial position of the receiving element in PRIZ or, in each element, respectively , in matrices of PESE, in the form of a set of matrix diagrams 239, each of which is characterized by its new value of the value of the additional physical parameter of the distinguishing component (for example, for a radiation frequency of 94 GHz - one new matrix diagram is added, for a frequency of 95 GHz - the following diagram is added - matrix, etc.). Such a set appears for any element of the receiving matrix in any spatial position in Priz.

. Such a volume of information provides expanded computational capabilities for analyzing the parameters of an object and its surface, as well as for obtaining high-quality images of any type and physical embodiment (spatially incoherent monochromatic, quasi-monochromatic spatially coherent, “white”, etc.).

Unique properties of objects that are inaccessible from the analysis of ordinary images can be detected. For example, a large amount of visual information allows you to identify structural parameters of the surface from the analysis of composite coherent images. In particular, it is known that speckles “breathe” when the parameters are changed, the images are coherent with each image pixel differently depending on the depth of its irregularities at a given point. By analyzing the characteristics of such a change depending on the position of the point source — the diffuser element and the wavelength, it can be estimated as the angle of inclination (the depth of the irregularities) and even the direction of the inclination, if it is large scale. Using such statistical information over the entire multiparameter volume, it is possible to describe with high accuracy the surface relief of the object or even its internal structure (with transparency in the MM range of its material, for example, in the case of plastic firearms) It is important that changing the angle of illumination will change the speckle amplitude in different ways different points of the partial image, since the depth of the roughness of the corresponding sections of the surface of the object is different. That is why it is necessary to analyze partial images independently for each of the corresponding elements and summarize partial images in the general case differently for different elements of the synthesized radiation. The same is true for combining images of their fragments that differ in frequency, etc. It is clear that the number of possible procedures for optimal processing and subsequent synthesis of the resulting images is rapidly increasing with the growth of the amount of information that can be obtained on the basis of the proposed method.

To demonstrate the capabilities of the proposed approach in the synthesis of high quality images in FIG. Figure 31 shows the results of numerical modeling of the procedure for generating resultant images and improving their quality by minimizing the effect of interfering partial images in their accumulation in the resulting synthesized image. When modeling, the type of images is selected based on the probable type of the corresponding partial images, however, the procedures for their complete or partial accumulation are performed exactly by numerical simulation.

Seven partial images 240-246 (Fig. 31) can be obtained, for example, in a lighting scheme with seven independently coded radiation beams from seven points of the PR source aperture. In this case, each such beam forms its own partial image 240, 241 (characterized by its own average angle of illumination of the object), which can be obtained simultaneously by the receiving device PU due to their distinctive coding.

In this case, the possible resulting images are described by the formula (7) where the weighting coefficient can be fundamentally different for the components of the composite image (7) inside each element of the resulting (combined) image.

Conditionally noise-like interfering partial images 240 and 246 can occur when an object 8 is illuminated with partial radiation components 247 incident on the object at the corresponding illumination angles, due to strong reflections of these components from the surface of the clothing 8 masking the object 8 of the clothes of the individual 7 or for other reasons of FIG. 32.

The averaged matrix diagram 248 (obtained as a result of averaging the matrix diagrams described above for individual partial image elements over the entire set of these elements of the corresponding partial image conditionally demonstrates the difference in the average energies of the partial images 240-246. In this case, the matrix diagram element (1.1 ) 249 corresponds to the average energy of the images 240, and the element (3.2) in 250 the average energy of the image 246.

In FIG. 33 shows the classic result image 251, which will be obtained by a radiometric receiver that does not have a decoding electronic unit. The result image 251, using the formalism of formula (7), is obtained when the weighted coefficients for each partial image and each element inside separate partial images are the same the same ones (or in other words, by a direct, non-weighted summation of all partial images 240-246, including interfering 240 and 246 images). In this case, the noise in images 240 and 246 is additively added to the images of the object in partial images 241-245 (which in turn can also be distorted for other reasons (partial spatial coherence due to the limited width of the corresponding radiation beam), but when summed they will give a good image)

This is essentially classical imaging by any of the previously known methods using the classic radiometric approach of passive imaging or active, but with a simple destruction of the spatial coherence of the radiation. In other words, such an image will be observed in a classical radiometric imaging system. Thus, any radiometric system can receive and visualize only one-parameter images of the form 251, which under difficult masking conditions of the object 9 will produce images of obviously poor quality.

While the proposed system forms a set of many parametric images of the form 252 in the form of a set-stack of partial images, each of which is characterized by its parameter of the radiation forming it.

Finally, a synthesized, improved image will be obtained as a result of the formation of a new stack of 253 summable partial images by removing the “destructive” images 240 and 246 from the stack 252 (images 240-246). Summing a new stack leads to an image of a fundamentally new quality with a clearly recognizable image.

Finally, the circuit of the BKC generator of FIG. 34, in which the master (which can be used as a source of a heterodyne signal for mixer 160 (Fig. 18), which operates in its main mode (not in the mode of a subharmonic mixer), uses a relatively powerful source of MM radiation 183 (BWT, Gunn diode, etc.) .d.), and the slave generators that make up the BKC 255 paired generator (functionally equivalent to the unit (Fig. 17) are generators of a lower, for example, microwave frequency, which can be implemented by technology, for example, YIG generators, easily controlled and tunable in a wide range of 8-16 GHz. The signals of the lower frequency generators (UHF) are then transferred to the frequency range of the master oscillator by means of the corresponding frequency multipliers with the corresponding multiplication factor.

Therefore, in this case, the signals of paired coupled generators 108, 109 (Fig. 17) of the combined second block 255 (Fig. 34) (which functionally and schematically completely coincides with the block 147 of Fig. 17) through the outputs 256, 257 (Fig. 34) corresponding outputs 128, 129 of this block 147 shown in FIG. 17 are supplied respectively to the inputs of frequency multipliers 258, 259.

And their frequencies (signals of the generators 108, 109) are independently multiplied by the indicated multipliers 258, 259 to the frequency of the leading third generator 183, while one multiplied signal from the output of the multiplier 259 is used further for its purpose in the backlight circuit through radiation through the antenna 206; one part of the other multiplied signal separated by the directional coupler 260 can be used in the lighting circuit, while another part of the other after the directional coupler 260 is fed to the multiplier 258 and after multiplying the frequency with factor N (and also after filtering the multiplied signal with a band-pass filter to extract the multiplied frequency with the required multiplication factor - this filter is not indicated on the diagram, as such a filter will not be indicated below, although its presence will be implied) is fed to block 261, regulated the frequency of the VCO 108. Block 261 is functionally and schematically equivalent to block 142 of FIG. 17, while its inputs 262, 263, 264 are equivalent to the inputs 144, 145, 146 of block 142 of FIG. 17, and its output 267 corresponds to the output 143 of block 142 of FIG.

The smaller part of the signal of the multiplied frequency (through a filter, not shown in the diagram, emitting the signal of the multiplied frequency) from the corresponding output of the multiplier 258 is fed to block 261, (designed to control the phase of the signal of one of the generators 108 of block 255, which is an analog of block 147) of FIG. 34, to one of its inputs 262 (equivalent to one of the mixing inputs 145 of block 142 of FIG. 17). At the other input 263 (equivalent to the input 144 of the block 142 in Fig. 17), a smaller part of the signal energy of the master oscillator 183 is supplied through the directional coupler 265, and the signal 266 (an analog of the block) is input to the input 264 (corresponding to the input 145 of the block 142 in Fig. 17) 122 of Fig. 17). From output 267 (analogue 143 for block 142 of FIG. 17), an error signal proportional to the phase error between the signal of reference oscillator 266 and the difference signal of the multiplied signal of generator 108 of block 255 (analogue of block 147) and the signal of master generator 183 is fed to input 268 318 of block 255, which is the input of the control electrode of the VCO 108 (in this circuit both generators 108, 109 are VCOs) (see Fig. 17). The error signal after exposure to the control electrode of the VCO 108 leads to a decrease in the indicated phase mismatch between the indicated signals until the complete elimination of this mismatch and the achievement of their phase synchronism.

The frequency of the generator 108 is N times smaller than the frequency of the master oscillator 183, N is the factor of multiplying the frequency of the multipliers 258, 259 Since block 255 provides phase synchronism between the difference signal of the signals of the generators 108, 109 and the reference signal of the reference generator 122, then the Nth the harmonic of the signal of the generator 109 at the output of the multiplier 259 is in a phase synchronism state, in which the difference signal between the signals at the output of the multiplier 259 and the output of the generator 183 has a spectral purity of the signals of the reference generators 266 and 122 When the main part of the signal generator 183 through gate 270 is input to a radiating antenna 208, and further into the coverage area in a simpler diagram of Fig. 35, in which the place of block 261

(equivalent to block 142 of FIG. 17) placed block 138 (fully described in connection with Fig 17), while removed from the circuit as unnecessary blocks 266 and 269. The inputs 140, 141 of the phase detector of the block 138 which are the inputs of the phase detector included in the block 138 (or, which is equivalent to the inputs 118, 121 of the phase detector 119, which is part of the block 138 of FIG. 17) are supplied: respectively, the input of the multiplied signal of the generator 108 from the output of the multiplier 258 (through a filter not shown in the diagram), and to the input 141 the signal of the generator 183 is supplied through the directional coupler 265. At the output 139 of block 138, an error signal is obtained — a phase mismatch signal between the indicated signals supplied to the inputs 140, 141. The error signal from the output 139 of the block 138 is supplied to the control electrode 268 of the VCO located in the block 255 (completely equivalent to the block 147 of Fig. 17). In this simpler scheme, the difference signal between the signal of the master oscillator 183 and the signal at the output of the multiplier 259 is phase-synchronized (in phase with the signal of the generator 122) by the generator 122. Moreover, this phase synchronization is carried out by a pair of slave generators 108, 109 of a much lower frequency (which is technically simpler) than the more powerful master MM (or CMM) generator 183. The output of multiplier 259 (through a filter not shown in the diagram) is fed to the input antennas 206 and through it into free space. In this case, the main part of the signal of the generator 183 through the valve 270 is fed to the input of the radiating antenna 208 and then to the lighting zone

It is clear that in the circuit one more (not only one) pair generator of the form 255 can be added, the outputs of which are loaded with multipliers of type 258, 259 with a feedback loop with a PLL block of type 138. The indicated phasing of the signals of the pair generator by the signal of the master generator 183 can be arranged by analogies to the circuit of FIG. 21 (through directional couplers 184, 187, 188 and wave guide channel 185 282. The main advantage of the two variants of the last GKVS scheme considered is the possibility of supplying signals from microwave generators 108, 109 of FIG. 34 (or only one 109 in Fig. 35) from the block of generators, which in this circuit can be located in the area of the receiving device 82 (at the location of the local oscillator 90 in Fig. 16, which is the generator 183 in Fig. 34), to Lighting schemes by means of flexible coaxial cables (allowing transmission of microwave radiation up to frequencies of 36 GHz). In this case, the frequency multipliers 258, 259) will be located directly at the location of the associated antenna 206 (or 67), aimed to illuminate the object 8.

This approach significantly solves the problem of the flexibility of implementing various reception / illumination devices, since a flexible coaxial cable makes it easy to move a light unit consisting of a multiplier loaded with an antenna in the space of the illumination system and place it at any point that is optimal for illuminating the observation zone. It is also significant that the various generators 108, 109 of mutually coherent signals (FIGS. 21, 34, 35) individually and quite simply technically can illuminate different sections of the observation zone from different spatial points of the aperture of the PR of the radiation source, thus providing coding of the corresponding components, since in the receiving device after mixing their signals with the local oscillator signal of the generator 183 of FIG. 21 or FIG. 34, which is the local oscillator 90 52 for FIG. 16, the corresponding IF signals at the mixer output for the respective radiation beams will be shifted from the beginning of the frequency axis by the frequency of the corresponding reference generators 199, 200 (Fig. 21) or 122, 266. The latter ensures their frequency separation by frequency-selective circuits of the receiving device 82 ( Fig. 16). The composition and the mutual sequence of the radio nodes included in each of the respective amplification channels the receiving device 82 (Fig. 15), as well as the principle of their joint functioning when amplifying and decoding the signals of the radiation of the partial components reflected by that portion of the surface 87 of the object 8, on which the corresponding receiving element 48 of the receiving matrix 85 is “watched” (associated with one of these channels), is determined by the peculiarity and sequence of coding of radiation, different for different TP of partial sources). In the general case, the implementation of double (as well as greater multiplicity) decoding (demodulation) is not difficult and can be carried out using standard radio engineering units (including, along with amplifiers of the corresponding ranges, heterodyne mixers, amplitude (quadratic) detectors, synchronous (parametric) detectors , including scanning, also digital nodes that allow a certain time sequence of amplified and shifted downward in frequency (can be partially odirovannyh) transfer signals in their digitized by ADC and implement methods of decoding by the digital signal processing. This can be done for any species (including many sufficiently known) modulation / demodulation MM / radiation HMM.

BKC generators allow reaching fundamentally new frontiers for imaging and information transfer systems in communication systems in the MM / SMM ranges. The use of mutually coherent signal generators for both probing (lighting) objects and their decoding (with their mutually coherent heterodyning) in the channels of the receiving device allows one to achieve fundamentally new possibilities both in extracting information from such signals and in increasing the sensitivity of reception - transmitting equipment and its dynamic range. To understand the details of coding (modulation) / decoding

(demodulation) of mutually coherent signals consider the features the formation of their difference signals in one of the amplification channels of the receiving device after their propagation from the radiating antenna of the corresponding partial TS of the source 35 to the receiving matrix 85 and their reception by one of the elements 48 of this receiving matrix (Fig. 15).

The difference signal of the mutually coherent signals of the generators discussed above can be obtained at the receiver in at least two distinctive ways. In the first case, both components, which are, for example, part of the corresponding doublet communication signal, or the doublet signal used for illumination in the imaging system, after amplification are fed simultaneously to form their difference signal to the input of a quadratic detector (for example, a diode) into the amplifier channel associated with the corresponding receiving element 47 that received such a doublet signal. Moreover, the specified amplifier channel may contain any combination of amplifying and frequency converting units located up to the quadratic detector, if their effect on both components of the corresponding doublet signal is the same. In any case, the subsequent quadratic detector will be able to extract its difference signal with the corresponding spectral and phase composition from the indicated doublet signal. Moreover, the extracted difference signal can be further amplified in one or more local oscillator amplification with an appropriate choice of local oscillator sources.

In the second case, mixers (or parametric detectors - synchronous detectors, for example) are used, when the difference signal is extracted by applying to the signal input of the mixer components that have passed the path from the source 28 to object 8 and finally received by the receiving element 48, and the second component (phase-coherent first) is fed to the reference signal of the mixer (Fig.15). In this case, the second the component propagates through, for example, a coaxial cable, or in another similar manner, preserving its amplitude and deterministic phase delay associated with propagation in the cable). For a signal of one of the components of the electric signal generated in the receiving element 48 of the receiving matrix 85 by partial radiation, characterized by physical parameters ccf (in accordance with the notation introduced above for the ratios of the previously derived relations, except for replacing the designation of the index of the form of a physical parameter, which had the designation t, in the new notation, it has the designation 1), and the input block generating the difference signal between it and the phase-coherent signal with it can be written

a "S J (t AND Vj -K-exp (i • (* Ф ^ (θ)] (8)

wherein ι ^{J fb} _a f ^(a = l <- ^• * +% F ^s K _f ^(a ^{+ pr} ^<(a + ^'J K ^(of w in this case omitted index pair (m, n), indicating the position? of the receiving element 48 in the receiving matrix 85, instead of them the index b = l is entered, 2 showing the component number in the doublet (1 or 2) or demonstrates the fact that the component is supplied to the receiving device as a reference signal b = 0 (see below). is the total gain of the amplifier-transform blocks preceding the separation block of the specified differential signal (including the receiving antenna), the phasor amplitude of the partial signal received by the antenna where, (i, j) is the index of the TP of the source or its spatial position emitting a given component, ω _a ^b ,, - is the central frequency of the partial radiation

generator, and "f _a ^b _J (t) is its phase noise characterizing deviations

the real frequency of this generator from its ideally central value. If these amplifying conversion blocks contain In addition, the heterodyne mixer (s) (in the case of amplification of doublet radiation signals) with the local oscillator frequency D (t), then -TD (t) should also be taken into account in (9), however, such a replacement is not important, since the frequency of the difference signal is the local oscillator D (t) is not affected. This is due to the fact that the phase addition associated with the local oscillator frequency is equally subtracted from the frequencies of both signal components in the local oscillator mixer, therefore, they are self-subtracted in the future when generating the difference signal frequency. The latter is important because it allows the use of unstable low-cost heterodyne generators for converting a doublet signal in frequency to the frequency converter band without affecting the quality of their difference signal; mV * DO "the determinate component of the phase modulation of partial radiation (if any), which is added to the signal in any of the above methods described in the description of Fig.21, Fig.34; p ^r f _a ^b l (f) - phase the additive resulting from the propagation of radiation in any free space between the radiating antenna of the emitter and the receiving antenna of the receiving element 47; i ^J f _a ^b _ll (t) and the phase additive introduced into the signal by the corresponding TP source, while the PR source is characterized only by spatial radiation incoherence, then this function is a random function of time, if PR is a radiation source encoding, then this is a regular deterministic function.

An important factor in the formation of a difference signal of two phase-coherent signals is the fact that, thanks to the PLL principle of the BKC generator, the noise phases of its generators, non-changing in time, nevertheless follow each other (repeating each other), therefore, at any time % A0 = ⁿ Ф _a ² _f (0 =% (0 (10)

Since the difference signal accurate to the constant d arises from the relation

S _bg аt = di ⁴ SiJj (0) Г 'Sg ⁰⁾ (O) ^* (И) then the above noise additions are self-subtracted in the resulting difference signal, and the remaining phase components are either deterministic information functions of time or constants, and on this In fact, various highly sensitive receiving circuits can be constructed. So when using the BKC generator when illuminating the observation zone, when the slave generator 108 illuminates the observation zone b = l (or part of it), and the master generator 183 is used as the source of the heterodyne signal b = 0, the difference signal at the output of the mixer will be described by the following relation

where Aω _tJ = ω _a ^λ _d - ω ^ ⁰ is the stable frequency of the received differential signal equal to the frequency of the reference oscillator 122, due to this determinate term, the corresponding spectral component in the spectrum of the difference signal will occupy its spectral position accurate to the bandwidth of the quartz reference oscillator 122 ( with an accuracy of 1-10 Hz or less), which provides a small total bandwidth even if a BKC generator with a large number of slave generators of type 109 is used to illuminate the observation zone (Fig. 21). In this case, the corresponding generators of difference signals of type 199,200 should be selected from the condition that their frequencies (or corresponding harmonics) are located along the axis of the difference frequencies at discrete spectral points, the distances between which are slightly greater than half the widths of spectral lines adjacent along the spectral axis (taking into account their possible drift over time functioning) for corresponding differential frequency generators of type 122, in order to provide the maximum frequency density of the corresponding differential signals arising at the output of the respective decoders of the receiving device. It is clear that the filtering blocks following the decoding block should be narrow enough enough to ensure that only the indicated difference frequencies are allocated. Digital differential frequency analysis schemes should provide for the corresponding duration of the sequence of time samples of the ADCs described above in order to provide the necessary spectral resolution of the difference signals with the corresponding Fourier transform.

All of the above provides a high dynamic range of the SFI transceiver equipment and a low level of illumination of the object zone, the noise level of the equipment when developing the corresponding nodes narrowband in the calculation of the stability of the difference signals of their spectral components. In the case ^under consideration, ^aχ Vc — sopst for all elements of the receiving matrix for which the indicated master oscillator 183 is used as a local oscillator.

The view of the spectrum of the possible spectrum clearly shows the possible optimal sequence of demodulating (decoding) blocks, allowing extracting information about the corresponding spectral characteristics of the signal at the output of this sequence.

The simplest sequence of such radio nodes can be considered with the example of the device shown in FIG. 36, in which, from the receiving antenna 271, through the UHF amplifier 272 (consisting of a preselector filter 273 and the amplifier 274 proper), the signals of the generators 108,109 reflected by the object (mutually coherent with the signal of the master oscillator 183 discussed above in FIGS. 17, 21) are received by the antenna 271 , 34.35) to the signal input of the first mixing element 275, (these signals can be fed to the input of the mixer and directly from the antenna without the use of UHF), to the heterodyne input 276 of the first mixer 275, a signal is supplied from the master oscillator 183 (FIG. 21, FIG. 34, FIG. 35). (If the GKVS circuits shown in Figs. 34, 35 are used, then the corresponding microwave signal of the generator 109 of block 255 can be fed to the input 276 of the mixer 275, operating in this case on the N harmonic of this microwave signal or through a frequency multiplier with a factor N, located directly near mixer 275). Received at the output of mixer 275, signals of difference frequencies of the form are fed to the inputs of independent identical frequency channels 277, 278, which filter the formed signals to extract signals with frequencies located near the frequencies of the corresponding difference signal selected for processing, and in this channel 277 by frequency-selective blocks of type 279 (each of which has its own filter 280 and amplifier 281). Moreover, these blocks have corresponding center frequencies and passbands for transmitting only signals (a set of such differential signals) belonging to the signal frequency range associated with the corresponding partial radiation source. In the future, each of these independent frequency channels 277, 278 is parametrically detected the corresponding difference signals allocated in the channel 277, ... by supplying them from the output of block 279 to the signal input 282 of the second mixer 283, respectively of the existing frequency channel 277 (in this case, the difference signals correspond to the distinctive partial radiation of the illumination generator 108, and the reference (heterodyne) input 284 of the second mixer 283 is supplied via an adjustable phase shifter 285 from the corresponding reference generator from the BKC generator circuit (generator 122 of Figs. 17, 34 35 or 199, 200 of Fig. 21) by means of, for example, a coaxial cable, and in principle this signal can be any (depending on the signal of the corresponding reference generator 122, including FM modulated - the latter allows to reduce the requirements for the dynamic range of receiving circuits with preserving the narrow bandwidth of the instantaneous, in this case, bandwidth) In a preferred embodiment, the frequency of the reference oscillator is stabilized with an accuracy of 10 Hz or less by means of quartz and thermal stabilization. In the particular case, only one channel 277 can be used, and the difference signals formed at its output can be analyzed digitally after filtering and digitizing it (which will be described below).

In this case, the output of the second mixer 283 also generates decoded (or demodulated if the difference frequencies vary in frequency) signals with spectral amplitudes proportional to the amplitudes of the corresponding coded radiation components reflected by the corresponding section of the object surface 8 of FIG. 1, and with frequencies equal to the frequencies of the corresponding differential frequency generators 122 or 199,200, etc. (or their harmonics depending on the implementation). This allows after filtering them with a frequency selective amplifier 286 (filter 287, amplifier 288) to accurately measure their parameters (for example, spectral density or, equivalent to the square of the length of the corresponding phasor of the received radiation component (component intensity).

The time sequences of the total total signal from the output of the second mixer through the specified filtering unit 286 can be converted into a digital sequence of digital samples of this signal by supplying this signal through a multiplexer 89 to the input of an analog-to-digital converter 91 (performing time samples of such a signal for a certain time interval) , loading this sequence into the digital memory of the processor device 22 (FIG. 2, for example) and then the subsequent conversion of the Fur the obtained digital data set by digital methods in the digital processor device 22 (Fig. 2 for example) as a result of which the whole spectrum with the accuracy of the spectral resolution equal to the inverse time of the duration of the procedure for obtaining the indicated samples of the signal.

In the latter case, the amplitude-phase information can also be extracted, for this, the ADC 91 (or the second ADC operating synchronously with the ADC 91) must simultaneously digitize the signal from the output of the mixer 283 type, fed to the input of the ADC through the filter block type 286, and at the same time digitize the reference signal supplied to the reference input 284 of the specified mixer (type 283) (in this case, the type 285 phase shifter is not needed in the circuit), which should also be fed to the ADC input (via multiplexer 89 or fed to the input of the second specified ADC). In this case, the processor device 22 from the data loaded from the output (s) of the ADC into the memory can extract both amplitude and phase information about the signal at the input of the mixer 283 by digital methods. In the cases considered above, phase information about the signals is not used.

Separately, it is necessary to analyze the case when, for the purpose of lighting, the observation zone 6 and heterodyne reception, BKC generators are used, the slave generators of which (Figs. 34, 35) or even the master and slave generators (Fig. 21) operate at frequencies several times (N times ) lower operating frequencies of the imaging system, while the operating frequencies are formed from the frequencies of these generators by means of frequency multipliers with a multiplication factor N (such as 157, 205,207 of FIG. 21 or 258, 259 of FIG. 34, 35). In this case, the receiving circuit of FIG. 36 must be modified, and о if the operating frequency of the lead generator 183 (Figs. 35, 36) coincides with the operating frequency of the imaging system, then the signal of the generator 109 of block 255 should be directly supplied to the heterodyne input 276 of the mixer 275, however, the signal of the reference generator should be sent to the reference input 284 of the mixer 283 122, the frequency of which is previously multiplied by a frequency multiplier (not shown in the diagram) N times (in this case, block 285 can depict the specified multiplier in assumption that the corresponding phase shifter is not specified or is missing).

If in the BKC generator circuit of FIG. 21 all the generators operate at reduced operating frequencies, then the signal from the generator 183 of FIG. 21 is supplied to the reference input 276 of the mixer 275 (possibly through a valve and matching device to reduce reflections) or, however, the mixer 275 in this case is subharmonic, operating on the N harmonic of the reference signal of the generator 183. At the reference input of the mixer 283, as well as the circuit discussed above, the signal of the generator 122 multiplied in frequency by N times (i.e., the harmonic of the signal of the generator 122 of the Nth time order). The object is illuminated by signals from slave generators 108, 109, ... previously multiplied by frequency multipliers 157, 205 of FIG. 21. The signals of the generators 108,109, ... are fed to the inputs of the multipliers 157, 205 through flexible coaxial cables, the latter can be connected to the waveguide outputs of the generators 108,109 through the matching devices of the type 210 described above, FIG. 21. Such a device can be used everywhere for transferring without loss of energy a signal from a waveguide to a coaxial cable, where the use of a coaxial cable is used to transmit signals with a frequency that allows them to be transmitted through a coaxial cable. Flexible corrugated waveguides can also be used to transmit the signals of the generators to frequency multipliers located in the lighting zone and heterodyne mixers located in the receiving devices. In these cases, the high frequency for the transmitted signals may be higher than the signals transmitted over coaxial cables.

In FIG. 36 - FIG. 40 is a diagram of the input nodes of the receiving device 16 of FIG. 1, allowing to amplify the signals received by the antenna of the receiving element, convert them in frequency by heterodyning, and partially decode them (including doublet signals), highlighting the encoded (modulated) components, for example, in the terminal quadratic or mixing (parametric detector) elements. In this case, it is possible to decode, including frequency-stabilized difference signals, the envelopes of which contain all the information about the corresponding pixel of the corresponding partial image or about the communication message. Such partially decoded signals from the outputs of such blocks can be fed to the inputs of the blocks discussed above for their full decoding, by means of blocks, etc.

In FIG. 37 shows the standard input path of a superheterodyne receiver, consisting of a receiving antenna 271, electrically connected to a Dicke switch 289 (which can additionally amplitude-modulate the input signal. Element 289 is relevant for the use of the considered units in a radiometric system. For an active system, this is an optional element), the queue connected in series with the UHF amplifier 272 operating in the MM frequency band, which in turn is connected in series with the mixer 275, to the heterode another input of which 276 generates a local oscillator signal. The frequency of the local oscillator should differ from the possible difference frequency of the doublet signal (if the doublet signal is amplified in the circuit), and in the most general case this local oscillator can be local (and of poor quality) and not connected to the received signal generators 108, 109. Mixer output 275 electrically connected to the input of the intermediate frequency amplifier UPCH 279, which isolates and amplifies the signal shifted down in frequency by the frequency of the local oscillator signal. In principle, several cascaded input signal heterodyning cascades can be used (by means of a second mixer and a second amplification amplifier connected in series with it, which are not shown in Fig. 37). In this case, the first mixer 275 and the first amplifier UPCH 279 can be used to effectively suppress the mirror the conversion component and various intermodulation components, the second mixer and, accordingly, the second amplifier (not shown in Fig. 37) can have steeper frequency response drops and provide better rejection of input stage noise). Blocks 272, 275 and 279 form a typical radio engineering unit 290 for amplification and heterodyning of signals, and such a unit may not include UHF 272, and the antenna signal may be fed directly to the input of mixer 275. The output of UHF 279 is connected to the input of a quadratic signal converter (amplitude detector - diode) 291, which provides the separation of difference signals from doublet (or carries out the first carrier demodulation in the case of using singlet (from one spectral component) signals) due to the operation of multiplication imino-coherent signals, which were independently received by the antenna 271 and converted by the above stages of amplification and frequency shift.

As indicated above, the noise of the local oscillators does not add phase noise to the difference signal, since they are equally added to both components of the doublet signal and are mutually destroyed after quadratic transformation at the output of element 291. The latter is extremely important for telecommunication systems as well, since they do not require any stabilization of the local oscillators, Unlike standard transceiver equipment. Further, the generated difference signals can be processed by any of the decoding units 277 described above or even by their nodes depending on the use of the types and modulation levels of the original doublet signals.

It should be particularly noted that the circuit of FIG. 37 essentially corresponds to the input stage of a standard radiometric receiver, on the nonlinear diode of which 291 envelopes of thermal radiation can be extracted. Thus, such a receiver can be used to generate radiometric images along with the receipt of active encoded images in one system). The difference can only be in the bandwidth of the amplifiers, which for the radiometric case should be as wide as possible, but for signals the BKC generator, on the contrary, is as narrow as possible. However, when using such a receiver together, the condition of a narrow-band rejection can be imposed on subsequent stages following the quadratic device 291, which makes it possible to receive and process signals of passive and active images in one receiver.

In FIG. 38 shows a particular case of the reception circuit of FIG. 37, in which there is no UHF unit (usually a waveguide implementation), and the received signals by the antenna 271 are fed directly to the input of the mixer 275 (as indicated above).

As indicated, while the specified amplifier channel may contain any combination of amplifying and frequency-converting blocks located up to the quadratic detector, if their effect on both components of the corresponding doublet signal is the same. Then the subsequent quadratic detector will be able to extract from the specified doublet signal its difference signal with the stored spectral and phase composition. Moreover, the extracted differential signal can be additionally amplified in one or several cascades of heterodyne amplification (consisting of a mixer and a corresponding amplifier) with the corresponding choice of heterodyne sources for the corresponding mixers of the heterodyne cascades located after the quadratic detector, if the corresponding heterodyne signals are formed from the signal of the differential generator frequency generator BKC 122 by appropriate division of its frequency, the signal at the output of such mixers will also save litudno phase information in the difference signal.

The same heterodyne gain of the difference signal is possible in the circuit of Fig. 36, where the difference signal is extracted in the mixer 275 by a reference signal for which is the master oscillator 183 of the corresponding of the BKC generator of FIGS. 21, 34, 35, in this case additional cascades of the heterodyne gain of the differential signal, preserving the phase content of the original differential signal, should be used for the reference inputs of the mixers with the signal of the generator 122, divided by the frequency in the required number of times (depending on the number of such cascades).

The indicated approach for generating / receiving mutually coherent signals also allows implementing the receiving circuits of FIG. 39 functioning without signal heterodyning at a millimeter-wave frequency. Developed in recent years, the technology for manufacturing low-noise amplifiers of the MM range (up to 140 GHz and higher) allows the signal to be amplified to a value significantly higher than the noise level of non-linear converter 291, which allows the detection of amplified MM frequency signals without any application of any preliminary signal heterodyning cascades. In this case, the mutually coherent doublet signals received by the antenna 271 (Fig. 39) are amplified in the UHF 272 at a carrier frequency of 40 to 50 dB or higher and are fed directly to a non-linear converter (diode) 291, which distinguishes the corresponding difference frequency signals due to the squareness of its BAX.

The receiver circuit shown in FIG. 39, it is of considerable practical interest from the point of view of the quick and effective implementation of the approaches described above in the formation of multi-parameter highly informative images by means of real-time millimeter-wave radiometric multi-element cameras currently being developed. Such MM multi-element (up to 1024 independent independent elements and above) cameras, the amplification channels of which are built with integrated technology based on the principle of direct amplification and detection of signals described above, are capable of forming multi-element images with a speed of up to 17 frames per second and higher and IK sensitivity and higher (such a camera was developed in particular by TRW in the USA). The advantages of such a camera lies in the possibilities of increased density of the bulk packing of the channels for receiving and amplifying the signals of MM images, which ensures high spatial resolution of such a camera. This is achieved due to the absence of powerful heterodyne signals, the dissipation of energy of which always requires a decrease in the density of the gain channels and, accordingly, a decrease in the spatial resolution of the camera.

However, such cameras are designed to receive only passive images and implement the radiometric principle of receiving radiation.

It is known that the formation of radiometric images inside closed rooms (where all the procedures of hidden screening take place) is absolutely ineffective due to the low contrast of the brightness temperature of the objects of the observed scene (5-7 K), therefore, this camera can only work in open spaces under contrast lighting objects with a “cold” sky (77K) and a “hot” surface of the earth (300K).

Considering the operational features of the above-described signal decoding units 277 in accordance with FIG. 36 as well as the direct amplification and detection amplification circuit of FIG. 39, it can be argued that such MM television cameras can be technologically simply adapted for the active multi-parameter images discussed above and create such images in real time. At the same time, nodes 277 can be used as simple low-frequency blocks of the end stages of the amplifying channels of the receiving device of such a matrix following the allocation of differential signals by diode 291,

Thus, such a camera can be effectively applied not only for the formation of low-contrast radiometric images that do not carry any real information about objects in closed rooms, but also for the formation of active images with high information content. that can be obtained in any conditions.

The proposed principle of mutual coherence of the two signals makes it possible to efficiently use the direct amplification and detection circuit in the receiving part of any transceiver without any additional MM / SMM oscillators-local oscillators while maintaining high reliability and speed in data transmission / reception. The reception and decoding of doublet signals (signals consisting of a pair of mutually coherent signals) can also be effectively performed by receiving matrices of antenna-nonlinear elements (Schottky diodes) of FIG. 40. In such receivers, a nonlinear element (Schottky diode) 292 is mounted in the antenna input, thus connecting the paired conductive elements of the antenna 293, 294, the design of such receivers can also be schematically illustrated in FIG. 15 in the case of using an antenna-coupled non-linear element in FIG. 15 for the indicated reception and non-linear transformation (detection) of the input signals. Such an antenna-coupled nonlinear element can also be used for quasi-optical heterodyning of input signals (the heterodyne signal in the latter case quasi-optically falls on the conductive parts 293,294 of the receiving antenna along with the signals and the corresponding IF signal is extracted at the output of this element (at the antenna input / output point)) .In the case of using this element as a mixer, a planar bandpass filter must be additionally connected to the input / output of the antenna to isolate the generated IF signal, A non-linear element 292 in this case is also supplied by this filter. Another embodiment of the heterodyning of doublet signals on an antenna-coupled non-linear element of Fig. 40 is based on the implementation three-frequency heterodyning. In this case, the third strong heterodyne signal of the additional generator 295 is supplied to the antenna-coupled non-linear element together with the input mutually coherent doublet components, the frequency of which corresponds in order to the frequency of the difference signal of these doublet components (Fig. 40), and the subsequent band-pass amplifier UCH 279 is electrically connected to the specified antenna-related element has a finite passband (corresponding to the difference signal band) with a central frequency equal to the frequency difference oak etnogo difference signal and the third heterodyne signal generator 295. Such a mixing element as a result of three-frequency mixing provides a second difference signal, which lies in the band of said IF amplifier. Since the first difference signal (between the components of the doublet) can have a frequency of up to 1 GHz or higher, the frequency of the heterodyne signal can also be in the region of hundreds of MHz, which ensures a high frequency value of the second difference signal and, accordingly, provides all the advantages of a superheterodyne reception circuit. The conversion loss of such a heterodyne circuit will not be significantly higher than that of a harmonic heterodyne converter. The advantages of such a scheme is a significant simplification of the receiving-amplifying path, since heterodyne signals in the frequency domain up to several GHz can be generated by a standard transistor generator, and its signal is fed to the heterodyne (mixing) antenna element via a coaxial cable or a corresponding strip line with integrated decoupling elements amplifier block and input receiving node. In this case, the carrier frequencies of the doublet signal can vary in any range (corresponding to the operating frequency range of the antenna, and these can be bands up to 200 GHz and higher, while such elements can be easily implemented in the CMM range, everything is determined by the antenna manufacturing technology and the corresponding nonlinear element, the receiving circuit, including the local oscillator 295, can remain the same.

The above coding schemes and approaches for coding the radiation illuminating an object (by means of the considered BKC generators) 5 certainly do not limit the number of possible approaches for coding such radiation that can be implemented in any other alternative way (including well-known ones, for example, only by means of distinguishing amplitude modulation of AM radiation in channels corresponding partial radiation sources, etc.)

Industrial applicability

The present invention is industrially applicable, as it can be implemented using technologies, on the basis of which at present 15 computerized data processing systems are being created with their demonstration on a monitor.

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Claims

Claim

1. The imaging system in the millimeter and submillimeter wavelength range, containing at least one spatially distributed radiation source in the millimeter or submillimeter wavelength range, consisting of spatially distributed point-like simultaneously emitting radiation sources, made with the function of illuminating the field of view phase-independent radiation components, each of which is emitted by a corresponding point source, characterized by different angles of incidence of the shown radiation components in the field of view and the carrier frequency difference of which does not exceed the value required to ensure their indicated phase independence, an element for focusing the radiation scattered in the field of view onto a receiving device made with the function of independent reception of radiation scattered by various spatial parts of the field of view transforming it into a set of corresponding signals, with each signal of the specified set corresponds to radiation scattered by a spatially defined part of the observation signals, the outputs of the indicated receiving device are connected with the device for converting the indicated set of signals into the corresponding image of the monitoring zone and displaying this image on the display, each image element being formed from the corresponding signal of the specified set, characterized in that the said point radiation sources are made with the distinctive function encoding the radiation components emitted by them, by, for example, their amplitude modulation with different modulation frequencies, for The receiving device is configured to independently receive each encoded component of the radiation received from the specified observation area, and to convert each signal from the specified set of signals into an additional set of partial signals, and various partial signals for any but one of the same additional sets of partial signals correspond to distinctively encoded radiation components or identically encoded radiation components, but with distinctive values of these distinctive physical radiation parameters of the corresponding radiation element, the device is configured to independently receive individual partial electrical signals the formation of these partial signals of partial images of the zone observed for each of which a separate element of such an image corresponds to radiation scattered by a spatially defined part of the observation zone, and which is formed from a separate partial signal with the same coding and with the same and / or close values of the physical parameters of the radiation of these independent radiation elements, and the formation of the resulting image observation zones by combining these partial images and / or fragments thereof.

2. The system according to claim 1, characterized in that the source is additionally equipped with polarizing means that extract from its radiation mainly linearly polarized in the first spatial direction, and the receiver is equipped with polarizing means for isolating the radiation it receives that is linearly polarized in the second spatial direction .

3. The system according to claim 2, characterized in that the first indicated direction coincides with the second indicated direction.

4. The system according to claim 2, characterized in that the first indicated direction is orthogonal to the second indicated direction.

5. The system according to claim 1, characterized in that each independent point-like source is equipped with an adjustable attenuator to provide an acceptable reduction in the average power level of the corresponding component ..

6. The method of forming images in the millimeter and submillimeter wavelength range, which consists in generating radiation in the millimeter or submillimeter wavelength range, consisting of separate partial radiation components that differ from each other in angle of incidence into the observation zone, direction of the formed partial radiation components in the observation zone, reception through the focusing element of the radiation scattered in the observation zone, the conversion of the received radiation into signals, each signal radiation scattered by a certain spatial part of the observation zone, and the formation of a visually perceptible image of the observation zone from these signals, characterized in that each individual partial radiation component is additionally encoded differently from the encoding of other partial radiation components, after scattering of said radiation in the observation zone, this scattered radiation to a receiving device that receives this radiation independently from each the transient part of the observation zone by converting the indicated radiation into a corresponding set of signals, each of which corresponds to the radiation scattered in a certain spatial part of the specified observation zone, and forms an additional set of partial signals from each signal of the specified set of signals, and the encoded radiation components correspond to the specified partial signals form partial images, for each of which a separate image element corresponds to radiation, p to the seeded space of a spatially defined part of the observation zone, and which is formed from a separate partial signal of the corresponding additional set of partial signals, and then partial images and / or fragments thereof are combined to form the resulting image of the object and its visual display.