WO2005098635A2 - Systemes et procedes permettant de recevoir des donnees dans un reseau de communication sans fil - Google Patents

Systemes et procedes permettant de recevoir des donnees dans un reseau de communication sans fil Download PDF

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Publication number
WO2005098635A2
WO2005098635A2 PCT/US2005/009807 US2005009807W WO2005098635A2 WO 2005098635 A2 WO2005098635 A2 WO 2005098635A2 US 2005009807 W US2005009807 W US 2005009807W WO 2005098635 A2 WO2005098635 A2 WO 2005098635A2
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Prior art keywords
signal
flie
clocked
sub
ofthe
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PCT/US2005/009807
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English (en)
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WO2005098635A3 (fr
Inventor
Ismail Lakkis
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Pulse-Link, Inc.
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Priority claimed from US10/811,410 external-priority patent/US7321945B2/en
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Publication of WO2005098635A2 publication Critical patent/WO2005098635A2/fr
Publication of WO2005098635A3 publication Critical patent/WO2005098635A3/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0059—Convolutional codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0891—Space-time diversity
    • H04B7/0894—Space-time diversity using different delays between antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/10—Polarisation diversity; Directional diversity
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L7/00—Arrangements for synchronising receiver with transmitter
    • H04L7/04—Speed or phase control by synchronisation signals
    • H04L7/041—Speed or phase control by synchronisation signals using special codes as synchronising signal

Definitions

  • the invention relates generally to wireless communication and more particulariy to systems and methods for wireless ccmmumcation over awide bandwidth ( ⁇ annel using apluraUty of sub-channels.
  • I3ackground Wireless communication systems are proliferating at the Wide Area Network (WAN), Local Area Network (LAN), and Personal Area Network (PAN) levels. These wireless communication systems use a variety of techniques to allow simultaneous access to multiple users. The most common of these techniques are Frequency Division Multiple Access (FDMA), which assigns specific frequencies to each user, Time Division Multiple Access (TDMA), which assigns particular time slots to each user, and Code rJivision Multiple Access (CDMA), which assigns specific codes to each user. But these wireless communication systems and various modulation techniques are afflicted by a host of problems that limit the capacity and the quality of service provided to the users.
  • FDMA Frequency Division Multiple Access
  • TDMA Time Division Multiple Access
  • CDMA Code rJivision Multiple Access
  • Olieproblem to can exist mawirelesscorr ⁇ nura Multipaminterfe ⁇ ence,or multirjaih occurs because some of the energy in a transmitted wireless signal bounces offof obstacles, such as buildings or mour ⁇ ains, as it travels from source to destination
  • the obstacles in effect create reflections of the transmitted signal and the more obstacles mere are, the more reflections they generate.
  • the reflections then travel along their own transmission paths to the destination (or receiver).
  • the reflections will contain the same infbrmation as the original signal; however, because of the differing transmission path lengths, the reflected signals will be out of phase with the original signal As a result, they will often combme destructively with the caiginal signal in e receiver. This is referred to as fading
  • current systems typically try to estimate the multipa effects and then compensate for mem in the receiver using an equalizer.
  • a second problem mat can affect the operation of wireless cc ⁇ rnmunication systems is mterference from adjacent communication cells within the system
  • FDMA/TDMA systems is type of interference is prevented through a frequency reuse plan
  • available communication frequencies are allocated to cceimunicaticn cells within the communication system such mat the same frequency will not be used in adjacent cells.
  • F ⁇ ssentially the available frequencies are split into groups. The number of groups is termed the reuse factor.
  • the communication cells are grouped into clusters, each duster containing me same numr- ⁇ " of cefc Each frequency group is then assigned to a cell in each cluster.
  • each cell can only use l/V 1 of the available frequencies, ie., each cell is only able to use 1/7 81 of the available bat-dwidth.
  • Wireless communication systems can be split into three types: 1) line-of-sight systems, which can include point-to-point or point-to- multipoint systems; 2) indoor non-line of sight - ⁇ sterns; and 3) oi ⁇ do ⁇ r systems such as wireless WANs.
  • a method of (xanmuracating over a wicleba ⁇ -d-ccmmuracation channel divided into a plurality of -nib-channels comprises dividing a single serial message intended for one of the plurality of communication devices into a plurality of parallel messages, encoding each of the plurality of parallel messages onto at least some of the plurality of sub-channels, and transmitting the encoded plurality of parallel messages to the communication device over flie wideband communication channel "
  • the transmitters and receivers can be simplified to eliminate high power consuming components such as a local oscillator, synthesizer and phase locked loops.
  • a trarismitter comprises a plurality of pulse converters and differential amplifiers, to convert a balanced trinary data stream into a pulse sequence which can be filtered to reside in the desired frequency ranges and phase.
  • the use of the balanced trinary data stream allows conventional components to be replaced by less costly, smaller cornponents that consume less power.
  • a receiver cornprises detection of the magnitude and phase of the symbols, which can be achieved with an envelope detector and sign detector respectively.
  • conver ⁇ cnal receiv ⁇ components can be replaced by less costly, smaUercomponentstoc ⁇ nsume less power.
  • Figure 1 is a diagram illustrating an example embodiment of a wideband channel divided into a plurality of - ⁇ ib-channels in accordance with Ihe invention
  • Figure 2 is a diagram illustrating the effects of multipatti ma wireless cornmunication system
  • Figure 3 is a diagram illustiating another example embodiment of a wideband communication channel divided into a plurality of sub-channels in accordance with the invention
  • Figure 4 is a diagram iUustrating the appUcati
  • A is a diagram illustrating flie assignment of sub-channels for a wideband ccnimunication channel in accordance with the invention
  • the width of the symbols (or the symbol duration) Tis defined as 1/B.
  • a delay spread a is defined as the delay from reception of data stream 104 to the reception ofthe last multipath data stream 108 that interferes with thereception of data stream 104.
  • the delay spread d s is equal to delay d4.
  • the delay spread d will vary for dif-ferentenviror-ments. An environment wim a lot of obstacles will create a lot of multipalh reflections. Thus, the delay spread a will be longer. --Experiments have shown that for outdoor WAN type envtemments, the delay spread a can be as long as 20 ⁇ s. Using the 10ns symbol duration of equation (1), this translates to 2000 symbols.
  • the next sub-channel 200 is oflset by 3b/2, the next by 5 b/2, and so on
  • each sub ⁇ -hannel 200 is oflset by -b/s, -3b/s, - 5b/2,dtc.
  • s ⁇ ib-charmels 200 are r ⁇ n-overlapping as this allows each sub-channel to te processed inderxndentry in the receiver.
  • a roll-off factor is preferably applied to the signals in each sub-channel in a pulse-shaping step. The effect of such a pulse-shaping step is illustrated in figure3 by the r-on-rectangular shape ofthe pulses in each s channel200.
  • the time domain signal for a (sinx) ⁇ sgxa ⁇ 400 is shown in figure 4 in ordertoillustiate the problems associated wit ⁇ As can te seen, main lobe 402 comprises almost all of signal 400.
  • r must te selected so as to reduce tte number ofside lobes 404 to a suffiderl number, e.g, 15, while still rnaximizing the available bandwidth in each sub-channel 200.
  • M (l+r)N.
  • r is chosen so to in equa ⁇ integer. Choosing r so mat M is an integer allows for more efficient transmitters designs using, for example, Inverse Fast
  • figure ⁇ illustrates an example cornmumcation system 600 comprising a plurality of cells 602 that each use a common wideband communic ⁇ onctomel to communicate with ccmmura each cell 602.
  • the common cornmumcation channel is a wideband commimication charmel as desmTjed above.
  • Each communication cell 602 is defined as the coverage area of abase station, or service access point, 606 within the cell
  • One such base station 606 is shown for illustration in figure ⁇ .
  • base station will te used generically to refer to a device that provides wireless access to the wireless communication system for apiurality of communication devices, whe tiiesy ⁇ lemisaMe of sight indoor, or out o ⁇ Because each cell 602 uses the same communication charmeL signals in adjacent cells 602.
  • system 600 uses a syrxnronizaticn cede raise factor of 4, although the reuse factor can vary deperxling cm tiie application
  • the synchronization code is periodically inserted into a communication from a base station 606 to a communication device 604 as illust ⁇ iedm figure 7.
  • Afterapredetermmednumberofdatapackets7C2,inte particular synchronization code 704 is inserted into the information being transmitted by each base station 606.
  • a synchronization code is a sequence of data bits l ⁇ iown to torn me base station 606 and any cc ⁇ which it is communicating
  • the synchronization coo ⁇ aUows such a cornmunication device 604 to syn ⁇ toof oa- «sMon6O6,wl ⁇ icl ⁇ ,inturr ⁇ ,aUowsdevice604tod ⁇
  • incell l see lightly shaded cells
  • synebrorazation cocte l (SYNCl) is inserted into data sdream station 606 in cell 1, after every two packets 702; in cell 2 SYNC2 is inserted after eveiy two packets 702; m inserted; andincell 4 SYNC4 is inserted
  • SYNCl synebrorazation cocte l
  • FIG 5 an example wideband communication channel 500 for use in communication system 600 is divided into 16 sub-channels 502, centered at freque ⁇ transmits a single packet occupying Ihe wtelebarxlwidmRofwidebarxi channel 500. Such apacket is illustrated bypacket 504 in figure 5B.
  • Packet 504 comprises sub-packets 506 to are encoded with a frequency oflset cc ⁇ iesponding to one of sub-channels 502. Sub-packets 506 in effect define available time slots in packet 504. Si i y, sub-channels 502 can te said to define available fiequency bins in ccmmunication channel 500. Therefore, the resources available in cornmuricaticn cell 602 are time slots 506 and frequency bins 502, which cante assigned to different communication devices 604 within each cell 602. Thus, for example, frec ⁇ ency bins 502 and time slots 506 can te assigned to 4 different communication devices 604 within a cell 602 as shown in figure5.
  • Each cornmumcation device 604 receives the entire packet 504, but only processes those frequency bins 502 and/or timeslots 506 that are assigned to it Preferably, each device 604 is assigned non- adjacent frequency bins 502, as in figure 5. This way, if ulcererference corrupts the information in a portion of communication channel 500, then the effects are spread across aH devices 604 within a cell 602. Ultimately, by spreading out the effects of crizo--eda ⁇ the entire infoimationsert from the unaffected informatiori received in other frequency bins.
  • each user 1-4 loses one packet of data
  • each user poteritMy receives three unaffected packets from the other bins assigned to them Hence, the imaffected data in the other three bins provides enough information to recreate ftie entire message for each user.
  • bins to each of multiple users. Eri-a-tring mat the bins assigned to one user are separated by mcae than me coherence baridSvidth a diversity.
  • the coherence bandwidth is approxiinately equal to i -
  • whae ds is least 1 MHz
  • data block a can te repeated in the first and third sub-charmels 200 and data blc ⁇ -kb can te repeated in tte sub-channels 202, provided the sub-channels are sufficiently separated in frequency.
  • the system cante said tote usingadiversityla ⁇ gthfactorof2.
  • the system can similariyte configured to irnplementofl acfiversity lengths, e.g, 3,4, ..., /.
  • Spatial diversity can comprise transmit spatial diversity, receive spatial diversity, or both, transmit spatial drversity, the transmitter uses a plurality of separate transmitters and a plurality of separate ariterrnas to transmit each message. In other words, each transntittertrar)-5mits1hesamemessageinparalleL The messages are then received from the tiansnitters and combined in the receiver.
  • Receive spatial diversity uses a plurality of s- ⁇ paraterecdvers arxi a pluraHty of separate antennas to message.
  • each base station 6C)6transmitta can include two antennas, for transmit spatial diversity, and ea ⁇ ccnimunication device 6O4recaver can irr spatial diversity. If only trar-smit spatial diversity is implemented in system 600, then it can te implemented in base stations 606 or in communication devices 604.
  • niimber ' ⁇ fccmrrair ⁇ cation devices 604 assigned frequency bins 502 and/or time slots 506 in each cell 602 is preferably programmable in real time.
  • the resource allocation within a communication cell 602 is preferably programmable in the face of varying external conditions, i.e., multipalh or adjacent cell ir-terference, and varying requirements, i.e, bandwidth requirements for various users within the cell
  • varying external conditions i.e., multipalh or adjacent cell ir-terference
  • requirements i.e, bandwidth requirements for various users within the cell
  • bins assigned to a particular usre can te used for tethtte forward a ⁇ link
  • some bins 502 can te assigned as the forward lirik and some can te assigned for use on me reversely defending on the irnplementation
  • the entire bandwidthR is preferably reused in each ⁇ mmunication cell 602, with each cell 602 being differentiated by a unique syr Aranization code (see discussion below).
  • system 600 provides increased immunity to multipalh and fading as well as increasedtend width (i etomeelirnir-a ⁇ 3. Synchronization When a device 604 in cell 1
  • the device recdves an incoming commiinication from the cell 1 base station 606, it compares the incoming data with SYNCl in correlator 800. Essentially, the device scans the incoming data trying to correlate the data with the Once correlator 800 matches the incoming data to SYNCl itgeneratesa correlation peak 804 at the output Multipath versions ofthe data will also generate correlation peaks 806, although these peaks 806 are generafly smaller than co ⁇ elation peak 804. Thedevice can then use theco ⁇ elation peaks to perform charrnd estimation, which allows the device to adjust for Ihe multipalh using, eg., an equalizer.
  • correlator 800 receives a data stream comprising SYNCl , it will generate correlation peaks 804 and 806. I ⁇ on the other hand, the data stream comprises SYNC2, for example, then no peatewiflte generated arri the device wift ess ccnimunication Even though a data stream to comprises SYNC2 will not create any correlation peaks, it can create noise in correlator 800 that can prevent detection of co ⁇ elation peaks 804 and 806. Several steps can te taken to prevent this from occurring Cne way to minimize fl erioise created mccn ⁇ latOT
  • the ⁇ ync ⁇ nizaticn cedes can in such a ma ⁇ n ⁇ to only the synchronization codes 704 of -djacenl cell data streams, e.g., streams 708, 710, and 712, as opposed to packets 702 within those steams, will interfere with detection ofthe correct syrchronization code 704, e.g, SYNCl.
  • the noise or crizerference caused by an incorrect synchronization code is a function ofthe cross correlation of that synclironization code with respect to the correct code.
  • a preferred erntectiment of system 600 uses synchronization codes to exhibit ideal cross correlation, -.e, zero.
  • the ideal cross correlation ofthe synchronization codes covers aperiod 1 that is suffident to aflow accurate detecfim of mi ⁇ ipath ⁇ This is important so that accurate channel estimation and eqiializaticn can take place.
  • period 1 the noise level 908 goes up, because the data in packets 702 is random and will exhibit low cross correlation with the synchronization code, e.g., SYNCl .
  • the synchronization code e.g., SYNCl .
  • period 1 is actually slightly longer then the multipalh length in oid ⁇ toensuretothemultipatiicantedetected a Synchronization code generation
  • Conventional systems use orthogonal codes to achieve cross co ⁇ elation in correlator 800.
  • SYNCl, SYNC2, SYNC3, and SYNC4 corresponding to cells 14 (see lightly shaded cells 602 of figure 6) respectively, wiflaU need tote generated
  • the data streams involved comprise liigh and low data bits, thente bits and "-1" to the low data bits. Orthogonal data sequences are then those to produce a "0" output when they are exclusively ORed (XORed) together in correlator 800.
  • each code must have ideal, or zero, cross correlation with each ofthe other codes used in adjacent cells 602. Therefore, in one example embodiment of a method for generating syncliionization codes exhiDiting the properties clesciibedatevei the process begins by select ⁇ codes.
  • a perfect sequence is one that when correlated with itself produces a number equal to the iiumber of bits in the sequence.
  • ⁇ rrngenenc'torm y x(0)x(l)x(2)x(3)x(0)x(l)x(2)x(3)x(0Kl)x(2K3)x(0)x(lM2W3
  • y x(0Kl).. ⁇ (TK0)x(l).. ⁇ (LK0)xG).. ⁇ (L)x(0)x(l). ⁇ (L).
  • a sample 1002 is generated every fourth sample bin 1000.
  • Each sample bin is separated by l/(4LxT), where -Tis the symbol duration
  • E 4
  • each sample bin is separated by 1/(16x1) in the fiequency ck ⁇ nain
  • Traces 2-4 illustrate the next three synchronization codes.
  • the samples for each subsequent syrxhronization code are shifted by one sample bin relative to the samples for the previous sequence. Therefore, none of sequences interfere with each other.
  • each syr-chrom-_aticm ⁇ xteisto samples where is the length ofthe multipalh, to flie front of each code. This is done to make the convolution with flie multipath cyclic and to allow easier detection of fl e multipalh.
  • synchronization coo s rantegenerated from more than o methodology For example, a perfect sequence can te generated and repeated for times ard then a secxMl perfed sequent can te generated and repeated four times to gd a n factor equal to dght The resulting sequence can then te shifted as described above to create the synchronization codes.
  • ccnimunications from base station 1110 comprise synchronization code SYNCl and ccmmunications from base station 1112 and 1114 comprise SYNC2 and SYNC3 respectively
  • device 1108 will effectively receive flie sum of these three synchronization codes. This is because, as explamedatove, base sMcms 1110, 11 ⁇ tran-anit at the same time. Also, the synchronization codes arrive at device 1108 at almost the same time because they are generated in accordance with the description above.
  • the synchronization cxxles SYNCl, SYN ⁇ Therefore, when device 1108 correlates the sumx of codes SYNCl, SYN(-2, arid SYN(-3, the latta two wiU not int ⁇ with proper detection of SYNCl by device 1108.
  • flie SIR for each sah-channel 502 cante measured and communicated back to base station 1110.
  • s ⁇ ich an ⁇ nlxxliment therefore, sub ⁇ hannels 502 c ⁇ tectivided into gro
  • figure 12A shows a wideband cxmmunication channel 1200 segmented into sub-channels jo to fc.
  • m one emboctimeni, device 1108 and base station 1110 commum ⁇ teovaachannelsudi as channel 1200.
  • Sub-charmels in flie same group are preferably separated by as many sub-channels as possible to ensure diversity.
  • sub-channels within the same group are 7 sut ⁇ ha ⁇ nels apart, e.g., group GI coinprises ⁇ and/ 5 .
  • Device 1102 reports a SIR measurement for each of the grourxGl to G8. These SIR measurements are preferably ⁇ rnparedwifliaflin-stoldvatuetodeter ⁇ This comparison can occur in device 1108 or base station 1110. ffit occurs in device 1108, thendevice 1108 can ⁇ arrplyrepcrttobasestation 1110 whichsub-charmelgroupsareuseableby device 1108. SIR reporting will te samultaneously occurring for a plurality of devices within cell 1102.
  • figure 12B illustrates the situation where two communicaticn devices corresponding to u ⁇ erl and user2 report SIR levels above the threshold for groups GI, G3, G5, and G7.
  • Base station 1110 preferably then assigns sub-channel groups to useri and user2 based on the SIR reporting as illustrated in Figure 12B.
  • base station 1110 also preferably assigns them based on the principles of frequency diversity.
  • commumcation device 1108 is near the edge of cell 1102
  • device 1118 is near the edge of cell 1106, then flie two can interfere with each otha.
  • the SR measurements to device 1108 and 1118 report back to base stations 1110 and 1114, respectively, will indicate to the interference level is too high
  • Base station 1110 can then te configured to assign only the odd groups, i.e, GI, G3, G5, c ⁇ ., to device 1108, wMe base ⁇ on 1114 cante configured to assign the even groups to device 1118 a coordinated i -ion
  • the two devices 1108 and 1118 will then not interfere with each otha due to the ccoidinated assignment of sub-channel groups.
  • flie systems and methods for wireless communication over a wide bandwidth channel usingaplura ofsub-charmelsnotc ⁇ yimprov can also increase the available bandwidth agnificantly.
  • the sub-channels cantect ded by three.
  • device 1108, for example cante assigned groups GI, G4, etc.
  • device 1118 cante assigned groups G2, G5, etc.
  • device 1116 cante assigned groups G3, G6, etc.
  • fl e available bandwidth for these devices i.e., devices near flie eclges ofcells 1102, 1104, ar ⁇ l 1106, is reduced by a fad ⁇ still better than a CDMA system, for example.
  • G8. The SIRs reported are then coinpared, in step 1404, to a thresteM to determine tfthe SIR is group.
  • device 1108 can make the dete ⁇ ninati ⁇ n and simply report which groups are above or below the SIR threshold Ifthe SIR levels are good for each group, then base station 1110 can make each group available to device 1108, in step 1406. Periodically, device 1108 preferably measures the SIR level and updates base station 1110 in case the SIR as deteriorated For example, device 1108 may move from near the center of cell 1102 toward the edge, where interference from an adjacent cell may affect the SIR for device 1108. If the cornparison in step 1404 reveals to the SIR levels are not good, then base station 1110 can te preprogrammed to assign ⁇ thertheodd groups or the even groups only to device 1108, whichitwill do instep 1408.
  • Device 1108 then reports flie SIR measurements for the odd or even groi ⁇ s it is assigned in step 1410, and they are again compared toaSlRlhre ⁇ holdinstep 1412. It is assumed to the poor SIR level is due to the fad to device 1108 is operating at flie edge ofcell 1102 and is therefore being interfered with by a device such as device 1118. Butdevice 1108 will teiriterfering with device 1118 at flie same time. Therefore, the assignment of odd or even groups in step 1408 preferably corresponds with fl e assignment of flie opposite groups to device 1118, by base station 1114.
  • step 1410 when device 1108 reports flie SIR measurements for whicheva groups, odd or even, are assigned to it, the cornparison in step 1410 should reveal to flie SIR levels are now below the threshold level Thus, base station 1110 makes the assigned groups available to device 1108 in step 1414. Again, device 1108 prefer-hlyperiodically updates the SIR measurements byretumrng to step 1402. It is possible for flie cornparison of step 1410 to reveal that the SIR levels are still above the threshold, which should indicate that a third device, e.g, device 1116 is still interfering with device 1108. m fliis case, base station 1110 can te preprogrammed to assign everythird group to device 1108 in step 1416.
  • device 1108 should te able to operate on the sub-channel groups assigned, i.e., GI, G4, etc., wilhout undue interference. Again, device 1108 preferably periodically updates flie SIR measurements by returning to step 1402.
  • a third comparison step can te irnpleme ⁇ ted after step 1416, to ensu ⁇ an adequate SIR level for propa operation Moreover, if there are more act ⁇ acent cells, i.e, if it is possible for devices in a 4 th or even a 5°' adjacent cell to ' interfere ' witfr ⁇ vice 1108, then flie process offigure 14 would continue and the sub-channel groups would te divided even further to ensure adequate SIR levels en the s ⁇ jl>charmels assignd Even though the process of figure 14 reduces the bandwidh availabletodevices at the edge of cells 1102, ⁇ 1106, the SIR measurements can te used in such a manna as to in ⁇ ease the data rate and therefore resto ⁇ bandwidth To accomplish this, the transmitters and rec ⁇ versusedin base stations 1102, 1104, and 1106, and in devices in ccmmunication therewith, e.g, devices 1108, 1114, and 1116 respectively,
  • the base station eg, base station 1110
  • the base station can then determine what symbol mapping scheme can te supported for each sub-channel group and can change the modulation scheme accordingly.
  • Device 1108 must also change the symbol mapping scheme to correspond to that ofthe base stations. The change can te effected for all groups u ⁇ ifoimly, or it can te effected for individual groups.
  • the symbol mapping scheme can te changed cnjust flie forward link,jusi flie revere theemrxxiiment
  • the systems and methods described herein provide the ability to rnaintain higha available bandwidths with higha perfeirmance levels than conventional systems. To fully realize the benefits clescnted, however, the systems and methods described thus far must te capable of irnplementation in a cost effect and convenient manner.
  • the irnplementation must include ieconfigurability so that a single device can move between clifferent types of ccmmunicaticHi systems and still maintain optimum performance in accoidance with the systems and methods described herein
  • the following clesxripticns detail example high level embcxiime ⁇ ts ofhardware irnplementations configured to operate in accordance with fl e systems and methods described herein in such a manna as to provide flie capabilityjust described above. 5.
  • Transmitter 1500 is provided to illustrate logical ccmponents that can te ir ⁇ ludedm a transmitta configure described herein It is not intended to limit the systems and methods for wireless communication over a wide bandwidth channel using a plurality of sub-channels to any particular transmitter configuration or any particular wireless commixnication system.
  • transmitter 1500 comprises a serial-toparallel converter 1504 configured to receive a serial datastream l 502 ex ⁇ nprising a data iateR.
  • Serial-topara converter 1504 converts data stream 1502 intoN parallel data streams 1504, where Nis the number of sub-channels 200.
  • the datarate of each parallel data stream 1504 is flienRN.
  • Each data stream 1504 is then sent to a scrambla, encoder, and interleaver block 1506.
  • Scrambling, encciding, and interleaving are common techniques ir ⁇ plemented in many wireless ⁇ rnmumcaticn transmitters and help to provide robust, secure communication Examples of these teclmicfues will te briefly explained for illiistrativepurposes. Scrambling breaks up the data to te transmitted man effort to smooth oirtte For example, if the data comprises a long string of 'T 's, there will te a spike in the spectral density. This spike can cause greater interfaence within flie wireless communication system. By breaking up the data, the spectral clensity can te smoothed outto avcidany suchpeaks.
  • EEC sei ⁇ nblingisacHevedbyXOI ⁇ ingthedataw Encoeiirig,orcoelmgtheparaUelbitsu ⁇ arns 15M
  • the purpose of EEC is to improve the capacity of a communication channel by adding some carefully designed redundant irfomiatim to the data being 1ran-m ⁇
  • Evolutional codes operate on serial data, one or a few bits at a time.
  • Block codes operate on relatively large (typicaUy,uptoacoupleofhundred bytes) message blocks.
  • convo orial encoding or turto coding with Viterbi decocting is a FEC tcx imcruetoisparti ⁇ ilariysuitedto mainly by additive white gaussian noise (AWGN) or even a channel that simply experiences fading
  • Convolutional codes are usually described using two parameter: the cede rate ar l fl e con ⁇ rate, k/n, is expressed as a ratio ofthe numter ofbits into flie convolutional encoder (k) to the number of channel symbols (n) output by the corrvo onal ericoder ina given erccder cycle.
  • the constraint length parameter, K denotes the 'length" ofthe convolutional encoder, i.e. how many k-bit stages are available to feed the combinatorial logic to produces the output symbols.
  • Qosely related to ⁇ T is the parameter m, which indicates how many encoda cycles an input lit is retained and ⁇ s ⁇ it first appears at the input to the convolutional encoder.
  • the m parameter can te thought of as the memory length ofthe encoder. Interleaving is used to reduce flie effects of fading.
  • Interleaving mixes up flie order ofthe data so that if a fade interferes with a portion ofthe transmitted sagna the overafl message wifl not te effected This is because once the message is de-interleaved and decoded in the recdver, the data lost will comprise non-ccntiguous portions of flie overall message. In otha words, flie lade will interfere with a contiguous portion ofthe interleaved message, but when the message is de- interieaved, the interfered with portion is spread througteirt Are overaU message. Using t information can then te filled in, or the irnpad ofthe lost data may just te negligible.
  • each parallel data stream 1504 is sent to 1508.
  • Symbol mappers 1508 apply the requisite symbol mapping, eg, BPSK, QPSK, etc, to each parallel data stream 1504.
  • Symbol mappers 1508 are preferably programmable so to the mcdulation apptied to paraUel data streams can teetoiged, for e an ⁇ the SIR reported for each siib-channel 202. It is also preferable, to each ⁇ ymtelm-ipp l 508 tese so to the optimum symbol mapping scheme for each ⁇ aib-charmel cante selected and appKed to each pa ⁇
  • the transmitted signal occupies the entire ter-dwidth B of communication channel 100 and cornprises each ofthe discrete parallel data streams 1504 encoded onto their respective sub-channels 102 within bandwidth B. lE-ncoding parallel data streams 1504 onto the appropriate sub-channels 102 recjuires to each paraUel data stream 1504 by an appropriate offset This is acMeved modulator 1510.
  • FIG 16 is a logical block diagram of an example embodiment of a modulator 1600 in accordance with the systems and methods described herein Irnrxjrta ⁇ tly, modulator 1600 takes parallel data streams 1602 performs Time Division Modulation (TDM) or Frequency KvisicnMo ⁇ nlation (TOM) on each data stream 160 ⁇ 1612, and then shifts each data stream in frequency using frequency shifter 1614 so that they occupy the appropriate sub-channel Filters 1612 apply flie required pulse shaping, i.e, they apply the roll-off factor described in section 1.
  • the frequency shifted parallel data streams 1602 are then summed and transmitted Moctulator 1600 can also include rate controlla 1604, frecjuency encoder 1606, and interpolators 1610.
  • Rate control 1700 is used to control the data rate of each parallel data stream 1602.
  • rate ccntrolla forexar wltich ⁇ (( ⁇ isttes-measfl( ⁇ , ⁇ t7 ⁇ isfl ⁇ esameas ⁇ ( ⁇ ),etc.
  • Figure 17 illustrates that flie effed of repeating the data streams in this manna is to take the data streams that are encoded oritotte first 8 sub-(-harrnels 1702, and duptieateth sulKhannels 1702.
  • 7 siib-channels separate sub-channels 1702 cxmprising the same, or duplicate, data streams.
  • tffMng effects one sub-channel 1702,fc ⁇ exarnpleitteo1h ⁇ wb-channels 1702 carrying the same data will likely not te effected, i.e, there is frecjuency diversity between the duplicate data ⁇ rtrearns.
  • the data rate cante reduced by more than half eg, by four or more.
  • the data rate can also te reduced by an amount otha than half For example if crizbrmation from n data stream is encoded onto m sub ⁇ hannels, where m >n.
  • rate controlla 1700 is programmable so that the data rate can te changed responsive to certain operational factors.
  • rate controller 1700 can te programmed to provicle mere robust transmission
  • different types of wireless communication system e.g, indoor, outdoor, line-of-sight, may require varying degrees of robustness. communication system.
  • FIG. 18 illustrates an alternative example emrxxlrme ⁇ t of a rate controlla 1800 in accordance with the systems and methods dctscrited In rate controller 1800 flie data rate is increased instead of decreased This is accornplished using serial-to-parallel converters 1802 to convert each data streams d(0) to d(15), for exarnpte, into two data streams.
  • Delay circuits 1804 then delay one ofthe two data streams generated by each s ⁇ rial-to-parallel converter 1802 by l A a symbol, period
  • data streams d(0) to d(15) are transformed into data &em ⁇ (0) to ⁇ (31).
  • rate controlla 1604 is preferably programmable so that the data rate can te increased, as in rate controller 1800, or decreased, as in rate controller 1700, as required by a particular type of wireless cornmumcation system, or as required by the communication channel conditions or sub-channel conditions.
  • filters 1612 are also preferably programmable so to they can te configured to apply pulse shaping to data streams ⁇ (0) to ⁇ (31), for example, and then sum flie appropriate streams to generate the appropri to frequency shifter 1614.
  • FIG. 19 illustrates one example emboctimc ⁇ of a frequency encxida 19 ⁇ methods clescribed herein Similar to rate encoding, frequency encoding is preferably used to provide increased communieation robustness.
  • data streams a(0) to a(15) generated by adders 1902 and 1904 comprise information related to more than one data streams d ⁇ ) to d(15).
  • a(0) comprises the sum of d ⁇ ) and d(8), i.e, d ⁇ ) + d(8), while a(8) ccnprises d(8) - d ⁇ ).
  • frequency encoder 1900 is programmable, so to it can te enabled and disabled in order to provided robustness when required
  • adders 1902 and 1904 are programmable also so that diflere ⁇ t matrices cante applied to -/(Q) to d(15) .
  • Afta frequency erxxxling ⁇ TDM/FDM blocks 1608 perform TDM or FDM on flie data streams as required by the particular embcxliment
  • Figure 20 illustrates an exanpleen ⁇ rxxiimentofaTDM/FT Mblock2000configure ⁇ TDM/FDM block 2000 is provided to illustrate the logical components to can teirrlud d a TDM/FDM block configured to perform data strea
  • Sub-block repeater 2002 is configured to rec ⁇ ve a sub-block of data, such as block 2012 comprising bits a ⁇ ) to a(3) for example. Sub-block repeater is then configured to repeat block 2012 to provide repetition, which in turn leads to more robust communication Thus, sub-block repeater 2002 generates block 2014, which comprise 2 blocks 2012. Sub- block scrambla 2004 is then configured to receive block 2014 and to scramble it, thus generating block 2016. One method of scrambling can te to invert half of block 2014 as illustrated in block 2016. But other scrambling methods can also te implemented defending on the embodiment Siib-block terminator 2006 takes block 2016 generated 2034 to the front of block 2016 to form block 2018. Termination block 2034 ensures that each block can te processed independently in the receiver.
  • termination block 2034 Without termination block 2034, some blocks may te delayed due to multipath, for example, and they would therefore overlap part of flie next block of data But by including termination block 2034, the delayed block canteprevented frcmoveriapping any ofthe actual data in the next block 1 errntnation block " 2034 can be a cy iC prefix termin-ition 2036.
  • a cyclic prefix terminaticn 2036 simpfy repeats the last few symbols ofblock 2018. Thus, for example, if cyclic prefix termination 2036 is three symbols long, then it would simply repeat the last three symbols ofblock 2018.
  • terminaticn block 20254 can comprise a sequence of symbols that are known to both the transmitter and recdver.
  • TDM/FDM block 2000 can include a sub-block repeater 2008 configured to perform a second block repetition step in which block 2018 is repeated to form block 2020.
  • TDM/FDM block 2000 comprises a SYNC inserter 210 configured to periodically insert an appropriate synchronization code 2032 after a predetermined ⁇ umba of blocks 2020 and/or to insert known symbols into each block.
  • SYNC inserter 210 configured to periodically insert an appropriate synchronization code 2032 after a predetermined ⁇ umba of blocks 2020 and/or to insert known symbols into each block. The purpose of synchronization code 2032 is discussed in section 3.
  • Figure 21 illustrates an example embcdime ⁇ tofaTDM/FDMblock2100cor ⁇ figuredforFDM which exjmprises sub-block repeater 2102, sub-block scrambla 2104, block coda 2106, saib-blcck transformer 2108, sub- block terminator 2110, and SYNC inserter 2112.
  • Sub-block repeater 2102 repeats block 2114 and generates block 2116.
  • Sub-block coder 2106 takes block 2118 and codes it generating block 2120. Coding block correlates the data symbols togeflia and generates symbols b.
  • Sub-block transforma 2108 then performs a transformation on block 2120, generating block2122.
  • the transformation is an IFFT ofblock 2120, which allows for more effidait equalizers to te used in flie recdver.
  • sub-block terminator 2110 terminates block 2122, generating block 2124 and SYNC inserter 2112 periodically inserts a synchronization code 2126 after a certain number ofblocks 2124 and/or insert known symbols into each bloc
  • sub-block terminator 2110 only uses cyclic prefix te-mination as described above. Again this allows for more effident receiva designs.
  • TDM/FDM block 2100 is provided to illustrate the logical components to cante irc ⁇ configured to perform FDM on a data stream, --- ⁇ pending on the actual iinplcrnentaticn, some ofthe logical components may or may not te included Moreover, TDM/FDM block 2000 and 2100 are preferably programmable so to the appropriate logical components can te included as l ⁇ quired by a particular implementation This allows a device to incorporates one ofblocks 2000 or 2100 to move between elifferent systems with different reqt ⁇ ements.
  • TDM/FDM block 1608 in figure 16 te programrnable so to it cante programmed to perfo ⁇ n TDM, such as described in conjunction with block 2000, or FDM, such as described in conjunction with block 2100, as required by a particular communicaticn system.
  • theparaUeldatastreamsarepass ⁇ dtofilters 1612 which apply the pulse sh ⁇ ingefcscribed in c»rgurx ⁇ c wifl ⁇ the roU-off factor of equation (2) insecticn 1.
  • FIG 22 illustrates an example emboclimerit of a frequency shifter 2200 in acccadance with the systems and methods described herein
  • frequency shifter 2200 comprises mi ⁇ ipHers 2202 configured parallel data stream by tiie appropriate exponents to achieve flie required frequency sh ⁇
  • Each exponential is of flie for e ⁇ ( 2 ⁇ 7 ⁇ -9, where c is the corresponding sub-channel ⁇ in figure 16 is programmable so to various channel/sub-channel cxnfiguraticns can te acccmmoclated for various different systems.
  • an 1FFT block can replace shifter 1614 and filtering can te done after the JJ bT block Thistypeof implementation can te more effident depending on the ir ⁇ plementaticn
  • the parallel data streams are shifted, they are summed eg, in summa 1512 offigure 15.
  • the summed data stream is then transmitted ii ⁇ ing the enlire barx ⁇ stream also comprises each of the parallel data streams shifted in frequency such to they occupy flie appropriate s ⁇ ibcharmeL
  • each sub-charmel may te asag ⁇ different users.
  • the assignment of sub-channels is described in section 3b.
  • Sample Receiver Embodiments Figure 23 illustrates an example embodiment of a receiver 2300 to can te configured in acccadance with the present invention Recdva 2300 ⁇ mprises an antenna 2302 configured to rec ⁇ e a message transrnitted by a to such as transmitter 1500. Thiis,antenrra23CCisccnfiguredtoreceiveawi&
  • the wide band message comprises a plurality of messages each encoded onto each of a corresponding sub-channel All ofthe sub-channels may or may not te assigned to a device to includes recdver 2300; therefore, receiva 2300 rnaycrir ⁇ y riot te re all ofthe ⁇ ur ⁇ ha ⁇ nels.
  • ⁇ o recdver 2304 is corifigured to remove the carrier associated with the wide band communication channel and extrad a baseband signal comprising the data stream transmitted by flie transmitter.
  • Exarnple radio recdva embodiments are elescrited in more detail telow.
  • the baseband signal is then sent to correlator 2306 and demodulator 2308.
  • Qjrrelator 2306 is configured to correlated with a syrxhranization code inserted in the data stream as clescnted in section 3. It is also preferably configured to perform SIR and multipalh estimations as -Demodulator 2308 is configured to extrad the parallel data streams from each sub-channel assigned to the device comprising recdva 2300 and to generate a single data stream therefrom.
  • Figure 24 illustrates an example crnbcK ⁇ rmentofa demodulator 2400 in ac the baseband data stream so that parallel data streams corrprisang the baseband data siteam can teinde ⁇ m receiva 2400.
  • the output of frequency shifter 2402 is a plurality of parallel data streams, which are then preferably filtered by filters 2404.
  • Filters 2404 apply a filter to each paraflel data stream to correspcncls to Ihe pirlse shape ap ⁇ transmitter, eg, transmitter 1500.
  • an IFFT block can replace shifter 1614 and filtering can te done after the IFFTblock.
  • recdva- 2400 preferably includes dedmators 2406 configured to decimate the data rate ofthe parallel bit streams. Sampling at higha rates helps to ensure accurate recreation of Ihe data But the higher the data rate, the larger and more complex equalizer 2408 becomes. Thus, the sampling rate, and therefore the number of samples, can te reduced by Equalizer 2408 is configured to reduce the effects of multipath in receiva 2300. Its operation will te discussed more fully telow.
  • equalizer 2408 After equalizer 2408, the parallel data streams are sent to de-scrambler, decoder, and de-interieaver 2410, which perform the opposite operations of scrambla, axoda, and interleaver 1506 so as to leproduce the original data generated in the transmitta.
  • the parallel data streams are then sent to parallel to serial converter 2412, which generates a single serial data stream from the parallel data streams.
  • lE iualizer 2408 uses flie multrpath estimates provided by co ⁇ elator 2306 to equalize the effects of multipath in recdva 2300.
  • SBO Single-In Single-Out
  • each SISO equali-- comprisir ⁇ g equalizer 2408 rec ⁇ and generates a single equalized output Alternativdy
  • each ecjualizer can te a Multiple-In Multiple-Out (MMO) or a Multiple-Si Single-Out (MISO) equalizer.
  • MMO Multiple-In Multiple-Out
  • MISO Multiple-Si Single-Out
  • frequency encoder 1900 encodes information from more than one parallel clata stream onto each sub ⁇ harm ⁇ to equalize more than one s xhanneL
  • equalizer 2408 will need to together.
  • Equalizer 2408 can then generate a single output correspcndingto ( ord(8) (MISO) or it can generate both d(l) zt ⁇ d ) (MMO).
  • ⁇ ualizer 2408 can also te a time domain eq ⁇ alizer(TDE) era frequency dom the en ⁇ odiment
  • equalizer 2408 is aTDE ffthe modulator in the transmitter paforms TDM on the parallel data streams, and a FDE if the rno ⁇ ⁇ lator performs FDM
  • equalizer 2408 can te an FDE even if TDM is used in the toansrnitter. Therefore, the preferred equalizer type should te taken into consideration when deciding what type ofblock termination to use in flie transmitta.
  • a device moves from one system to anotha, it preferably reconfigures the har ⁇ ⁇ receiver, as required and switches to a protocol stack con spcnding to the new syste
  • An impcrtart part of reconfiguring the recdva is leconfiguring, ca-prograrnming, the equalizer bexause multipalh is a main problem for each type of system
  • the multipalh varies expending on the type of system, which previously has meant that a different equaliza is required for different types of communication systems.
  • the channel access protocol described in the preceding sections allows for equalizers tote used that need ⁇ rilyterecorifiguredsHghtfyfOT operatic ⁇ systems.
  • a San ⁇ lelE ⁇ ualiz ⁇ rIEri ⁇ bc ⁇ iiment Figure 25 illustrates an example embodiment of arecdva 2500 illustrating cnewayto configure equals acccadance with the systems and methods described herein
  • equalizers 2506 are to simply include one equalizer per channel (for the systems and methods described herein, a channel is flie equivalent of a s ⁇ hannel as described above).
  • a correlator such as correlator 2306 (figure 23), can then provide equalizeis 2506 with an estimate ofthe number, arrplitude, and phase of any mult-paths present, up to some maximum nurnba.
  • CIR Channel Impulse Response
  • Thernoremultipalhsirxluded in the CIR the more path diversity the receiva has and the more ⁇ cb ⁇ stcxn ⁇ municatimm the system discussed a little mere fully telow.
  • the QR is preferably provided directly to equalizers 2506 from the correlator (not shown), ffsuch a cc ⁇ relator configuration is iised equalization process is relatively fast For systems with a relatively small number of channels, such a configuration is therefore preferable.
  • each equalizer 2506 can share each equalizer 2506.
  • each equalizer can te shared by 4 channels, e.g, CH1-Ch4, Ch5-CH8, etc, as illustrated in figure 25.
  • receiver 2500 preferably comprises amemory25Q2ccnfiguredtostoreir ⁇ formatimamvingonea ⁇
  • Memory 2502 is preferably divided into sub-sections 2504, which are each configured to store iriforrnation for a particular subset of channels.
  • Mcnnation for each channel in each subset is then alternately sent to the appropriate equalizer 2506, which equalizes the information based on the CIR provided for that channel Si this case, each equalizer must run much faster than it would if fliere was simply one equalizer pa channel For example, equalizers 2506 would need to run 4 ormoretimesasfast cadertoeflec ⁇ haddMcn,extramemo ⁇ 2502isrequiredto buffer the channel information But overall, flie complexity of recdva 2500 is reduced, because there are fewer equalizers. This should also lower the overall cost to implement receiva 2500.
  • recdva 2500 can te reconfigured for the most optimum operation for a given system.
  • receiver 2500 were moved lrom an outdcor system to m indoor system so that there are ' fewer, evefl as low as " l, ciia el per equalizer.
  • the rate at which equalizers 2506 are run is also preferably programmable such that cquatizeis 2506 can te run at fl e optimum rate for the num ⁇
  • each equalizer 2506 is equalizing multiple channels, then flie CIR for those multiple paths must alternately te provided to each equalizer 2506.
  • a memory (not shown) is also ii luded to buffer the QR information for each channeL The appropriate QR information is then sent to each equalizer from the CIR memory (not shown) when the corresponding channel information is being equalized
  • the QR memory (not shown) is also preferably programmable to ensure optimum cperation regardless ofwhat type of system receiver Rduming to the issue of path ctiversity, the numba of paths used by equalizers 2506 must account for the delay spread 4 in the system.
  • fl e commiinication channel can comprise a bandwidth of 125MHz, e.g, the channel can extend from 5.725GHz to 5.85GHz
  • flie channel is divided into 512 sub-charmels with a roll-off factor r of .125, Ihcri each subchannel will teve a ban ⁇ 215KHz, which provides approximately a4.6 ⁇ s symtel duration Sirxe the worst case ofpaths ⁇ sedbyequalize ⁇ s2504cantesettoamaximumof5.
  • fliere would tea first path PI at O ⁇ s, a second path P2 al4.6 ⁇ s,afl ⁇ dpathP3 at92 ⁇ s,afour1hpathP4al 13.8 ⁇ s,arrifii1h path P5 at 18.4 ⁇ s, which is close to ⁇
  • a sixth path can te irxluded so as to co ⁇ pletely cover the efelay spread ⁇ the worst case.
  • equalizers 2506 are preferably configurable so that they can te reconfigured for various ccmmunication systems.
  • the numba of paths used must te suffident regardless of flie type of commiimcaticn system.
  • recdva 2500 can preferably te reconfigured for 32 subchannels and 5 paths. Assuming the same overall bandwidth of 125 MHz, the bandwidth of each sub-charrnel is approximatefy4Mf ⁇ andttesymtelciu ⁇ Therefore, there will be a first path PI at O ⁇ s and subsequent paths P2 to P5 at 250ns, 500ns, 750ns, and l ⁇ s, respectively.
  • the delay spread shouldte covered for tte indoor environment
  • the l ⁇ sds is worst case so flie lus ds provided in tte above example will often te more than is actually required
  • This is preferable, however, for indoor systems, because it can allow operation to extend outside ofthe inside environment, e.g, just outside the building in which the inside environment operates.
  • this can te advantageous. 7.
  • Sample Embodiment of a Wireless Commimicaticn Device Figure 26 illustrates an example embodiment of a wireless communicaticn device in acccttdance with flie systems aidmedTOC-sdescnted herein
  • Device 2600 is, for example, a portable communication device configured for oper ⁇ c m plurality of indoor and oiitdoOT communication systems.
  • device 2600 comprises an anter ⁇ r ⁇ 26O21br transmitting and receiving wireless communication signals ova a wireless cornmumcation channel 2618.
  • Duplexa 2604, or switch can te included so that transmitta ' 2606 and receiva 2608 can both use antenna 2602, while being isolated from each otha.
  • Transmitter 2606 is a configurable transmitter configured to implement the channel access protocol c-escribed above.
  • transmitter 2606 is capable of transmitting and encoding a wideband c ⁇ mmunicaticn signal ⁇ mprising a plurality of subchannels. Moreova, transmitter 2606 is configured such that flie various subcorriponents to comprise transmitter 2606 can te leconfigured, or programmed, as descnted in section 5.
  • recdver 2608 is configured to implement the channel access protocol described above and is, therefore, also configured such that flie various sub- n cnents coinprising receiva 2608 canteieccnfigured, orreprogrammed, as descnted in section 6.
  • Transmitter 2606 and recdva 2608 are intei-faced with processor 2610, which can comprise various prrxessing, controller, and or Digital Signal Processing (DSP) drcuits.
  • DSP Digital Signal Processing
  • Processor 2610 controls flie operation of device 2600 including cricxxiirig signals tote transmit ⁇
  • Device 2610 can also include memory 2612, which can te ccnfigured to store operating instructions, e.g, firmware/software, used by processor 2610to control the operation of device 2600.
  • Processor 2610 is also preferably configured to lEprogramtiHismitter 2606 arid rer ⁇ va 26 ⁇ 2614and2616,respextivdy,asreq ⁇ iredbyttewire ⁇
  • device 2600 cante configured to periodcaflyaaertamflx availability Ifthe system is detected, then processor 2610 can te configured to load the ⁇ rrespcnding operating instruction from memory 2612 and reconfigure tiansmitta 2606 and receiva 2608 for operation in the preferred system. For example, it may preferable for device 2600 to switch to an indoor wireless LAN if it is available.
  • So device 2600 may te operating in a wireless WAN where no wireless LAN is available, while periodically searching for the availability of an appropriate wireless LAN. Once the wireless LAN is detected, processor 2610 will load the operating ir-structions, e.g, the appropriate protocol stack, for the wireless LAN environment and wifl reprogram transmitta 26C)6 and receiver 2608 accordingly. In this manner, device 2600 can move from one type of ccmmunicati(-n system to another, while maintaining sa ⁇ ericrperfoimance.
  • operating ir-structions e.g, the appropriate protocol stack
  • a base station configured in acccadar ⁇ «wifl the systems ardmemodsheremwffl similar manner as device 2600; however, because tte base station does not move from one type of system to another, fliere is generally no need to configure processor 2610 to reconfigure transmitter 2606 ard recdver 2608 IOT with the cperating instruction for a clifferent type of syste But processor 2610 can still te configured to reconfigure, or reprogram the of tiansmitta 2606 an ⁇ Vcriecdv ⁇ 2608 as reqi ⁇ ed by the operating co system as reported by cc mimication devices m communication with flie base station Moreova, such abase station cante ccnfigured m accordance with the systems a ⁇ which case, controlla 2610 cante configured to reprogram transnitta 2606 and receiv ⁇ 2608 to rrnplement Ihe appro mode of operation As described above in relation to
  • device 1118 will report a low SIR to base station 1114, which wifl cause base ⁇ taticm 1114 to reduce the numb ⁇ of subchannels assigned to device 1118.
  • Asexplamedmre ⁇ ntofig ⁇ es l2a ⁇ dl3,fl-isred 1114 assigning oriy wen snibcharmels to Prelerably,bases cm lll2iscxnespondir ⁇ sub-channels to device 1116.
  • base station 1112 and 1114 perform ccn-plernentaryreciucticns in tte channels assigned 1116 and 1118 o ⁇ d to prevc ⁇ tf int ⁇ fcrence ai 1116 and 1118.
  • step 2702 basestatic lll4recdvesS!Rrepcrtsfcffcliff ⁇ e ⁇ Ifthegroup
  • base station 1114 can assign all subchannels to device 1118 in step 2704. If, howev ⁇ , some of the group SIR reports received in step 2702 are poor, then base s ⁇ on 1114 can reduce the numter of sur>charmelsas ⁇ to device 1118, e.g, by assigning only even subcfiannels, in step 2706.
  • base station 1112 is preferably perfcnning a complementary reducticn in the subchannels assigned to device 1116, e.g, by assigning only odd subchannels. At this point, each base station has unused bandwidth wifli respect to devices 1116 and 1118.
  • base station 1114 can, in step 2708, assign flie unused odd ⁇ ub- ⁇ -h- ⁇ rmels to device 1116 a ⁇ It should te noted that even though cells 1102, 1104, and 1106 are illustrated as geometrically shaped, non-oven ⁇ pping coverage areas, the actual coverage areas do not resemble these shapes. The shapes are essentially fictions used to plan and describe a wireless commumcaticn system 1100. Therefore, base station 1114 can in fad ccmmunicate with ⁇ evice 1116, even though it is in adjacent cell 1104.
  • base station 1114 has assigned flie odd sub harmels to device 1116, in step 2708, base s c lU ⁇ communicate with device 1116 s ⁇ nidtaneously ova the odd sub-channels in step 2710.
  • base station 1112 also assigns the unused even sub-channels to dewce lll8mord ⁇ torecov ⁇ the unused here
  • spatial diversity is achieved by having toth base station 1114 ard 1112 communicate with (levice 1116 (and 1118)ovathesame ⁇ ub ⁇ hannels. Spatial diversity occurs when flie same message is transmitted s-muttaneously ova statistically independent cornmunication paths to the same recdva.
  • each base station in system 1100 is configured to transmit sdmultaneously,
  • system 1100 is a TDM system with synchrcnized base stations.
  • Base stations 1112 and 1114 also assigned flie same sub-channels to device 1116 in step 2708. Therefore, all to is left is to ensure that base stations 1112 and 1114 send flie same information Accordingly, the information commumcatedtodevice lll ⁇ bybasestaticns i ⁇ coordinated so to fl e same information is transmitted at flie same time.
  • the mexharasm for enabling this coordination is discussed mere fully telow.
  • Such coordination, howev ⁇ , also allows encoding to can provide furth ⁇ perforrnanee enhancements withm system 1100 ard aflow a gteat ⁇ p
  • One example coordinated encoding scheme that can teirnplcrnerited between base stations 1112 and 1114 wifli respect to ccmmunications with device 1116 is Space-Time-Coding (ST diversity.
  • ST diversity Space-Time-Coding
  • STC is illustrated by system 2800 in figure 28.
  • Si system 2800 transmitta 2802 transmits a message ov channel 2808 to recdva 2806.
  • trananitter 2804 transmits amessage ova channel 2810 to recdva 2806.
  • channels 2808 and 2810 are independent, system 2800 will have spatial diversity with resped to communications from transmitters 2802 and 2804 to recdva 2806.
  • the data transmitted by each transmitta 2802ard2804 canteencocledtoalsor ⁇
  • Block 2814a is the negative inverse ccnjugate ofblock 2812b and can flierefbre te described as -b*(N-l:0).
  • Block 2814b is the inverse conjugate ofblock 2812a and can therefore te described as a*(N-l:0). It should te noted that each block of data in the forgoing description will preferably comprise a cyclical prefix as ⁇ esxribed above.
  • blocks 2812a, 2812b, 2814a, and 2814b are received in receiva 2806, they arecx ⁇ nbmedandeiecodedinthe following manna
  • the symbol ⁇ 8> represents a cyclic convolution
  • Wliich can te rewritten as: Signals- ⁇ andR M cantedetermined ⁇ s- ⁇ It should te noted, that the processjust described is not the only way to implement STC. Otha methods can also te implem ⁇ -ted in acccadance with the systems and methods described herein BnrxMtantly, howev ⁇ , by adding time diversity, such as described in the preceding equations, to flie space diversity already achieved byusing base stations 1112 and 1114 to ccnm unicate with device 1116 samultaneouslytheBER can te reduced even furfh ⁇ to recova even more bandwidth
  • An example transmitter 2900 configured to communicate using STC in acccarJancewifl ⁇ fl ⁇ s stem described herein is illustrated in figure 29.
  • Transmitter 2900 irxludes a block storage device 2902, a serial-toparallel converter 2904, encod ⁇ 2906, and antenna 2908.
  • Encoda 2906 then encodes the bit streams as required, eg, encod ⁇ 2906 can generate -bge* and ⁇ wish* (see blocks 2814a and 2814b in figure 28).
  • the mcoded blocks are then combined into a sang-etrans-nitagrial as decribed ⁇
  • Transmitter 2900 preferably uses TDM to transmit messages to recdv 2806.
  • Figure 31 illustrates an alternative system 3100 to also uses roMbirt to elimm ⁇ with transmitters 2900 and 3000.
  • transmitta 3102 transmits ova channel 3112 to recdv 3116.
  • Transmitta 3106 transmits ova channel 3114 to receiv ⁇ 3116.
  • transmitters 3102 and 3106 implement an encoding scheme designed to recov ⁇ tendwidfh in system 3100.
  • transmitter 3102 can transmit bloe ⁇ 3104 cornprisirig symtels OQ, « / , 2 , and ⁇ J.
  • tiHi-anitt ⁇ 3106 wifl transmit a block 31C ) 8 comprising symbols - ⁇ /*, «o* - ⁇ , and ⁇ .
  • base stations 1112 and 1114 are preferably interfaced with a cornir network i ⁇ serv ⁇ .
  • base stations 1112 and 1114 which would actually te service access points in the case of a LAN
  • a common network interface serv ⁇ to ⁇ nnects the I-A ⁇
  • PSTN Switched Telephone Network
  • base stations 1112 and lll4 are typically interfaced with a common base station control center or mobile switching center.
  • coordination of flie encoding can te enabled via the common connection with flie network interface serv ⁇ .
  • Bases station 1112 and 1114 can then te configured to share information
  • This common connection related to communications with devices at flie edge of cells 1104 and 1106.
  • delay diversity can preferably te achieved in acccffdance with flie systems and methods described herein by cyclical shifting the trarisrnitted blocks.
  • one transmitter can transmit a block comprising A ⁇ A ⁇ A ⁇ and A 3 in that or ⁇ er, while the otter transmitter transmits the symbols in the following ord ⁇ A ⁇ Ac A 1 ⁇ and A 2 . Therefore, it cante seen to the second transmitta transmits a cyclically shifted version of flie block transmitted by the first transmitter.
  • Transmitter Radio Module Figure 32 is a diagram In certain crnbodiments, such a conventional radio transmitta module can, for example, te used to implement radio transmitta module 1514. As can te seen, baseband carcuitry 3202 can te configured to provide a digital transmit signal to radio trar-smitta module 3200 for transmission Baseband circuitry 3202 can, for example, comprise the components ciescribed above in relation to figures 15- 23.
  • the digital transmit data provided by baseband drcdtiy 3202 cante separated into a pluraHty as the -hphase (I) and Quadrature phase (Q) data streams illustrated in figure 32.
  • the I and Q data streams can then te encoded onto two orthogonal waveforms.
  • the divisicn of baseband data stream 1518 to I and Q channels can take on a variety of schemes.
  • flie I-( ⁇ annel) can represent the real part of data stream 1518ardtheQ hannelcan ⁇ eprescntfl ⁇ eimagjnaryt ⁇ Separation of digital tr-tn ⁇ mit data into I and Q data streams is well known and will not te discussed in furflia detail here.
  • flie digital I and Q data stoeams are converted to analog signals by digital to analog (D/A) converters 3204 and 3254 respectively.
  • the resultant analog signals can each te filtered with low- pass filters 3206 and 3256, respectively.
  • the filtered signals can then te mexlulated by modulators 3208 and 3258 with a local oscillator (LO) signal centered at flie carria frequency COQ.
  • LO local oscillator
  • the modulated sagriak supplied by flie mixers cante ccml- ⁇ riedbyccmbin ⁇ 3212.
  • the corrihined signal cante filtered throiigh band pass filter 3214.
  • the filtered signal is then ampMedbypow ⁇ arnplifi 3216 and broadcast with antenna3218.
  • the irnplementation illustrated in figure 32 is commonly referred to as a dired conversion transmitta, because the baseband carria frequency c- ⁇ Inofl ⁇ emlxx_iments, astaged approach to frequency conversden in which the baseband signal is first stepped up to one pr more intermediate fiequendes before being converted to an RF signal can te implemented
  • Such multi-staged transmitters often comprise adciitional mixers, synthesizers, local oscillators, etc.
  • the synthesizers, local oscillators, and ⁇ /A converters required by ccnveritional radio transmit modules cante large and expensive and can have relative large pow ⁇ requirements, especially when they are run at higha data rates.
  • Radio transmit module 3300 iflustrates an example embodiment of a radio transmit module 3300 configured in accordance with the systems and methods described herein Unlike radio Iransmit module 3200, radio transmit module 3300 does not include D/As, synthesizers, local osdllators or modulators. As a result, radio transmit module 3300 can avoid the expense, size constraints, and pow ⁇ constraints that are inherent in cx venticnal radio Iransmit module designs.
  • baseband ciuritiy 3202 can, fOTexarnp ⁇ "0", and "-1" for both the I and Q data By using two signals for each data stream, howev ⁇ , radio transmit module 3300 onfyseesaseriesoflsandOs.
  • the 1+ data stream can teccxledsaieh to it goes high when a "1" is bang transmitted and stays low when eith ⁇ a 'V' or a "-1" is bdiig transmitted
  • the I- data stream cante coded such that it goes high when a "-1" is being trarismitted and stays low when erth ⁇ a' ⁇ 'ora"! is being tran ⁇
  • the Q andQ- data streams can tecoded in flie same mann ⁇ .
  • the data streams can then te passed through puls ⁇ s 3322- 3328, whi ⁇ canteccnfiguredtocxnvcrttheeiatabitsin each data stream into natrow ⁇ pulses.
  • the combined signals can then te band pass filtered using band pass filters 3334 and 3336, which in addition to confining the signal to a narrow bandwidth for transmission, can also shape the pulse sequences in effect mochilating the signals.
  • the resultant shaped signals are flienready for trari-mi-sicmm the appropriate freqi ⁇
  • the shaped signals can then te combined in add ⁇ 3338, amplified by arnplifi ⁇ 3340, and transmitted via antenna 3342.
  • Band-pass filters 3334 and 3336 can also te configured to control phase, mord toiriai ⁇ lamorttegonalwavefo configured to only allow sin coot components to pass and band-pass filter 3336 can te configured to allow cos ⁇ tf coinponents to pass which are orthogonal waveforms.
  • FIG. 35 is a diagram illustrating an example ernboctimeritofapiils ⁇ configured m accords and methods ciescribed herein In the example offigure 35, ttepuls cornprises an AND gate 3506 and a delay module 3504.
  • a data stream 3502 is coupled to oneinputofAND gate 3506 as well as to flxcte ymcx e3504,wHchproclucesa delayed version 3508 of data stream 3502. Delayed data stream 3508 is then coupled to the oflia input of AND gate 3506. As cante seen on the right side of figure 35, when data stream 3502 is ANDedwiftictelayed data stoeam 3508, a data stream 3510 comprising narrow ⁇ pulses can be created The amount of delay applied by delay module 3504 must, of course, te controlled so as to produce satisfactory pulse wiclthsmdata stream 3510.
  • an inverted output can te used to generate outouls fcr the I- ardQ- data ⁇ toearns so to they can te combined with the 1+ and Q+- data streams in acxx lance wifli equations (1) and (2).
  • exnibiners 3320 and 3322 can te passive combiners such as flie one illustrated in figure 36.
  • the combin ⁇ illustrated in figure 36 sirrpfy comprises fliree res ve components R1,R2, and R3.
  • the resistive value ofcornponentsRl,R2, and R3 can te selected on an irnplementation by iinplementation bases.
  • Figure 37 illustrates an alternative emlxxlmert of a piils ⁇ to In this embodiment a (-apadtorCl ard resisted
  • a data stream 3708 is passed through the capacitcff-res-stor combination, the rising and felting edges ofthe various bits will create narrowa positive and negative pulses as illustrated by waveform 3710.
  • a diode DI can te irxluded so to waveform 3710 is converted into waveform 3712, which comprises a narrow pulse for each "1" in data stream 3708.
  • the decay rate ofthe pulse cornprising waveform 3712 is deteimined by the capadtance of capadtor Cl and flie resistance of resistor Rl.
  • the circuit decay rate 1/RC ⁇ teddte much less than the data rate.
  • the puls ⁇ offigure 37 can also te referred to as a differentiator detector.
  • an active combin ⁇ can te used to combine 1+ and Q+- with I- and Q-, respectively, in accordance wifli equations (1) and (2).
  • An active cornhin ⁇ can comprise an Operational Amplifi ⁇ (OP-AMP) 3802 as illustrated in figure 38.
  • Radio Recdva Figure 39 is diagram illust ⁇ ating an exemplary ra&o recdv ⁇ to cante used, for example, to implement radio receiv ⁇ 2304.
  • a radio signal is first received by anterma 3902 ard filtered by bard-pass filt ⁇ 3904.
  • the filtered signal can then te amplified by amplifi ⁇ 3906, which can comprises a low noise amplifi ⁇ ( NA) and in some embodiments include additional amplifiers.
  • the amplified signal can then te split into I and Q ccmponents and down converted by mixers 3910 and 3960 which have an LO signal supplied to them by the combination of sy ⁇ thesiz ⁇ 3908 and local oscillator 3970. Or e the signals are cbwr ⁇ xmvcrte4 low pass fitters 3912 ard artifacts from the downconverted signals.
  • the resultant filter signals can then, for example, te converted to digital signals by analog-to-digital (A/D) converters 3914 and 3964.
  • the digital I and Q signals can then te supplied to baseband circuit 3920 for furfl aprrxessing.
  • FIG. 40 is a diagram of an example radio receiv ⁇ 4000 that can te configured to work, for example, with the radio transmit module offigure 33.
  • a signal is received by antenna 4002, filtered by band ass filter 4004, and amplified by amplifi ⁇ 4006, in amann ⁇ samilar to that ofthe recdv described in figure 39.
  • the signal can fliente processed in two ccncurrentprrxesses.
  • the envelope for example, ofthe signal can tedetected using detector 4010.
  • cletecto 4010 can bean envelop detector or apow ⁇ cletector.
  • Envelope eletectors are wellknownand can, for exan le ⁇ teirnplementedasasiiTpledodeor a tricde with the prop ⁇ biasing
  • the output of e ⁇ vel ⁇ detector 4010 can then tefilt ⁇ ed by filt ⁇ 4012 ard converted to a digital signal
  • Filter 4012 can te implcrnented as a low pass filter with DC removal, e.g, a single pole notch filter.
  • the conversion process can te achieved, for example using A/D converter 4014, wliich then forwards the digital signal to base band circuitry 4018.
  • Sign detector 4020 can then te used to detect flie sign ofthe bit being decoded
  • flie original "1", “0", “4" values can te recovered by baseband circuitry 4018.
  • Sign detecticncan depending on the embodima ⁇ t,te irnplana-ted ⁇ sdngalimita ar ⁇ configured to deted adoublepositive, or doublenegative, in the resulting bit stream.
  • Figure 41 is a diagram illustrating an alternative emrxx-iment of a radio receiv ⁇ 4100 that can te used in cxn-juncticn,fOT example ⁇ mradiorecdv ⁇ 4100,ansigma-dellaA Dccnvert ⁇ isfcranedby combin ⁇ 4102, band pass filter 4104, precision, clocked comparator 4110, and D/A converter 4106.
  • the output of comparator 4110 is then fed to D/A converter 4106, the output of which is then subtracted form the incoming signal by combin ⁇ 4102.
  • the incoming signal is ova sampled
  • the table in figure 42 illustrates the effective numb ⁇ ofbits for each san ⁇ lingfreqiiency, Le, the rate at which cxmparafor 4110 is clocked, the filter carter for band pass filter 4104, and fl e ova sampling factor, for a parti ⁇ ilar implementation
  • ova sampling can te achieved iisang a pl ⁇ ra of comparator different phase of a clock signal Tteoiitoulofttecomparatcascanthentec filtenrigadedmaticncarcuitry4108.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Circuits Of Receivers In General (AREA)
  • Dc Digital Transmission (AREA)
  • Mobile Radio Communication Systems (AREA)

Abstract

L'invention porte sur un procédé qui permet de communiquer sur un canal de communication à large bande divisé en une pluralité de sous-canaux, de la manière suivante : on divise en une pluralité de messages parallèles un message sériel unique destiné à un dispositif parmi une pluralité de dispositifs de communication ; on code chaque message de la pluralité de messages parallèles sur au moins certains des sous-canaux de la pluralité de sous-canaux ; et on transmet la pluralité de messages parallèles codés au dispositif de communication sur le canal de communication à large bande.
PCT/US2005/009807 2004-03-26 2005-03-23 Systemes et procedes permettant de recevoir des donnees dans un reseau de communication sans fil WO2005098635A2 (fr)

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US10/811,410 US7321945B2 (en) 2003-03-28 2004-03-26 Interrupt control device sending data to a processor at an optimized time
US10/811,410 2004-03-26

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4632124A (en) * 1984-07-30 1986-12-30 Siemens Aktiengesellschaft Method and apparatus for delaying an ultrasound signal
US5235326A (en) * 1991-08-15 1993-08-10 Avid Corporation Multi-mode identification system
US6142946A (en) * 1998-11-20 2000-11-07 Atl Ultrasound, Inc. Ultrasonic diagnostic imaging system with cordless scanheads
US6748025B1 (en) * 1999-02-02 2004-06-08 Technoconcepts, Inc. Direct conversion delta-sigma receiver
US6833767B1 (en) * 2003-03-28 2004-12-21 National Semiconductor Corporation Frequency synthesizer using digital pre-distortion and method

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4632124A (en) * 1984-07-30 1986-12-30 Siemens Aktiengesellschaft Method and apparatus for delaying an ultrasound signal
US5235326A (en) * 1991-08-15 1993-08-10 Avid Corporation Multi-mode identification system
US6142946A (en) * 1998-11-20 2000-11-07 Atl Ultrasound, Inc. Ultrasonic diagnostic imaging system with cordless scanheads
US6748025B1 (en) * 1999-02-02 2004-06-08 Technoconcepts, Inc. Direct conversion delta-sigma receiver
US6833767B1 (en) * 2003-03-28 2004-12-21 National Semiconductor Corporation Frequency synthesizer using digital pre-distortion and method

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