WO2003077440A1

WO2003077440A1 - Adaptive antenna receiver and its receiving method

Info

Publication number: WO2003077440A1
Application number: PCT/JP2003/002798
Authority: WO
Inventors: Masayuki Kimata
Original assignee: Nec Corporation
Priority date: 2002-03-13
Filing date: 2003-03-10
Publication date: 2003-09-18
Also published as: JP2003273774A; AU2003211887A1

Abstract

An adaptive antenna receiver having an arithmetic unit the load on which is lightened by greatly reducing the computational complex of an adaptive update algorithm for calculating the antenna weighting factor. The antenna weight is controlled by allowing each finger to independently use an adaptive update algorithm so that the mean square of the common error signal after Rake combining is minimum, thus greatly reducing the computational complexity. If the transmission line fluctuation is quick, the function of compensating the transmission line distortion is separated from MMSE control circuits (5-1 to 5-L) for generating the antenna weight. The transmission line distortion of a desired signal is not compensated by using the antenna weight generated by the adaptive update algorithm, and control is so made that the direction of arrival of the signal and the average SIR may be maximum and that the instantaneous SIR may be maximum by Rake combining. Therefore, the characteristic degradation is reduced.

Description

TECHNICAL FIELD The present invention relates to an adaptive antenna receiving apparatus and its receiving method.

The present invention relates to an adaptive antenna receiving apparatus and method, and more particularly, to an adaptive antenna receiving method in which a CDMA transmission signal is received from a plurality of antenna elements constituting an adaptive antenna. Background art

The CDMA (Code Division Multiple Access) system is attracting attention as a wireless transmission system that can greatly increase the subscriber capacity. Conventionally, CDMA adaptive antenna receivers used in the CDMA system include, for example, “TDL adaptive array antenna using spreading processing gain for spread spectrum multiple access” by Wang, Kono, and Imai. J. Vol. J 75-BII, No. 11, p. 815-825, 1992) and Tanaka, Miki, and Sawahashi, “Characteristics of Decision Feedback Coherent Adaptive Diversity in DS-CDMA” (The Institute of Electronics, Information and Communication Engineers, As described in the Technical Report of the Radio Communication Systems RCS 96-102, January 1996), adaptive control is performed by using the weight control error signal extracted after despreading in antenna weight control. The antenna directivity pattern that maximizes the received SIR (Signal to Interference Ratio) is used for interference cancellation.

FIG. 1 is a configuration diagram showing an example of a conventional CDMA adaptive antenna receiving apparatus when a common error signal is used. The number of receive antennas is N (N is an integer of 2 or more), the number of multipaths is L (L is an integer of 1 or more), and the CDMA adaptive antenna reception for the kth user (k is an integer of 1 or more) The device will be described.

Conventionally, this type of CDMA adaptive antenna receiving apparatus has a multiplicity of Ni receiving antennas 1-1 to 1—N and L paths for the kth user, as shown in FIG. L signal processing means 30 0 to 1 30 to L corresponding to paths, MMSE (Minimum Mean Square Error) control circuit 5, adder 10, subtractor 11, and reference signal It is composed of a generation circuit 12. The L signal processing means 30-1 to 30-L corresponding to each multipath have the same configuration, respectively, and include delay units 2-1 to 2-L and N despreading circuits 3-1-11-1 to 3—L—N and antenna weighting / synthesizing circuit 4-1-1-4L.

The N receiving antennas 11-1 to 1-N are arranged close so that the respective received signals have a correlation. The delay units 2-1 to 2-L are configured to delay the signals received by the N receiving antennas 1-1 to 1-1N in accordance with each of the L multipaths. Are distinguished by The received signals output from the delay units 2-1 to 2—L are despread by the despreading circuits 3-1 to 1-3—L1N, and then the antenna weighting and combining circuit 4—! 4 to L—Sent to MMSE control circuit 5.

Figure 2 shows the antenna weighting synthesis circuit. 4 is a block diagram showing a configuration of each of L to L. FIG. Each of the antenna weighting / synthesizing circuits 4-1 to 4-L has the same configuration, and the multiplier 13-:! ~ 13-N and adder 1.4. For the sake of simplicity, the configuration of the signal processing means 30-1 will be described below as an example.

The antenna weighting / synthesizing circuit 4-1 receives the signal despread by the despreading circuits 3-1-1-3-1-N. The received signal is multiplied by the antenna weights generated by the MMSE control circuit 5 by the multipliers 13-1 to 13 -N in the antenna weighting and combining circuit 4-1, and further added by the adder 14. , Weighted synthesis, and sent to the adder 10 in FIG. The antenna weighting / synthesizing circuit 4-1 controls the amplitude and phase of the reception signals of the reception antennas 11-1 to 1-N so that the reception signal has a gain and the interference is suppressed so that the reception is performed. It forms the directionality of the array antenna.

Rake combining is performed by adding the outputs of the antenna weighting and combining circuits 41 1 to 41 L by the adder 10, and the result is input to the subtractor 11. The subtracter 11 converts the output of the reference signal generation circuit 12 from the rake (RAKE) composite output of the adder 10. The common error signal is generated by subtraction, and the common error signal is sent to the MMSE control circuit 5. The MMSE control circuit 5 uses the common error signal obtained from the subtractor 11 and the antenna reception signal corresponding to each multipath output by the despreading circuits 3-1-1 to 3-L-N, The antenna weight is controlled so that the root mean square of the common error signal is minimized. Here, since the adaptive update algorithm used in the MMSE control circuit 5 also makes the instantaneous transmission line fluctuation follow the antenna weight, an algorithm as fast as possible, for example, an RLS (Recursive Least Square) algorithm can be used.

The processing operation of the mth symbol (time mT when the symbol period is T) received through the 1 (1 = 1 to L) multipath channel for the kth user will be described as follows. The despread signals y _k , l, _n (m) received by the (l ~ N) th receiving antennas are given by the multipliers 13-1 to 13-N in the antenna weighting / synthesizing circuit 4-1-4-1 L The antenna weights generated by the MMSE control circuit 5 are multiplied, and weighted and combined by the adder 14.

_Assuming that the antenna weight of the n-th receiving antenna is w _k , _l5n (m), the antenna combined output z _k i (m) of the first path for the k-th user is

N

zk, l ^(m) = m. Yk, n (m) w _k , _£ , _n * (m) (1)

n = 1 '

It is expressed as Here, * represents a complex conjugate (the same applies hereinafter).

RAKE combining is performed by adding the outputs of the antenna weighting combining circuits 41 1 to 41 L by the adder 10 in FIG. The rake composite output z _k (m) for the _kth user is i) = II zn (m) (2)

£ = 1 ', and this rake composite output z _k (m) is input to the subtracter 1 1 _c The RLS (Recursive Least Square) algorithm used in the MMSE control circuit 5 controls the antenna weights so as to directly minimize the sum of squares of the exponential weighting error using all input samples up to the present. Where the sum of squares of the exponential weighted error is

It is expressed as Here, ο; is a weighting constant of 0 to ≤1, and e _k (m) is a common error obtained by subtracting the rake combined output of the adder 10 from the output of the reference signal generating circuit 12 by the subtractor 11. Represents a signal.

The subtracter 11 subtracts the rake combined output of the adder 10 from the output of the reference signal generation circuit 12 to generate a common error signal, and outputs the common error signal to the MMSE control circuit 5. The common error signal e _k (m) is e _k (m) = Zk (m) _ Z m) (4)

(Z _k (m) is the reference signal for the k-th user.)

It is represented as

In the RLS (Recursive Least Square) algorithm, the correlation matrix R _xxk is calculated by exponentially weighted time average based on the above equation (3).

Rxxk (0) = <5U (m = 0) …… (5)

Rxxk, m) = a R _YX v (m— 1) + Xk (m) (m)

(m = 1, 2, 3, ...) ... (6)

Is calculated. Where (5 is a positive constant, H is a complex conjugate transpose, and U is an identity matrix. X _k (m) is a despreading circuit 3-1:! ~ 3—L—N It represents the despread signal vector of the output despread signal, where Xk (m) is defined as follows.

k ( ^m ) ⁼ [yk, i, i ( ^m ) 'yk, i, 2 (m), ..., yk'i'N ( ^m ),

Yk.2,1 ( ^m ), k, 2,2 ( ^m ), ... 'Vk, 2, N (m), yk'L'l (m), Yk, L, 2 (m), ..., Yk, L, N (m)] ^T

…… (7) where T represents transpose (the same applies hereinafter).

The adaptive update algorithm used in the MMSE control circuit 5 includes a common error signal e _k (m) obtained from the subtractor 11 and the despreading circuit 3-1 1 1 to 3—L-N. The antenna weight is updated using the signal. In this process, the antenna weight is adaptively controlled based on the MMSE criterion so that the common error signal e _k (m) is minimized.

W _k (m) = W _k (m— 1)

+ Tk Rxxk " ¹ Xk (m) ek * (m) (8)

1

(9) expressed as _{a + X k (m) R} ^ Cm-DX k (m).

Here, W _k (m) represents the antenna weight vector of the antenna weight generated by the MMSE control circuit 5, and

W¾- (m) = [Wk, i 1 (m), w¾. _{> 1) 2} (m), ···, Wk, i,] sr (m),

wk, 2, l (m), Wk, 2,2 (m), · '·, w _{k? 2} , N (m), wk, L, l (m), w _{k; L; 2} (m) , ···, w _k , _L , _N (m)] T

...... Defined as (10).

Equations (8) and (9) must calculate the inverse matrix of the correlation matrix R _xxk , so if the matrix is inverted using the matrix formula, R ^ i ¹ becomes

Rxxk " ¹ (0)

(m = 0) …… (11) R "xxk ^(m) ^ xxk (m-1) — '

a ^ + a X k mi R xxi ^ Cm-DX ^ dn) (m = 1, 2, 3, ……)

(12).

However, this conventional technique has the following problems. The first problem is that the amount of operation of the adaptive update algorithm used in the MMSE control circuit 5 becomes large. Since the amount of calculation is large, a processing load is applied to the calculation circuit. The reason is that since the common error signal is used, the adaptive update algorithm that controls the antenna weights so that the root mean square of the common error signal is minimized must calculate the (NXL) _-order correlation matrix R _xxk. Because it must be.

The second problem is that the adaptive update algorithm used in the MMSE control circuit 5 follows the instantaneous transmission line fluctuation with the antenna weight, so that the characteristics deteriorate when the transmission line fluctuation is fast. is there. The reason is that when the fluctuation of the transmission line is fast, the weighting constant must be set small, and the effect of reducing noise is reduced. Disclosure of the invention

An object of the present invention is to provide an adaptive antenna receiving apparatus and a receiving method thereof, in which the amount of operation of an adaptive updating algorithm for calculating an antenna weight coefficient is significantly reduced, and the processing load of an arithmetic circuit is reduced. .

Another object of the present invention is to provide an adaptive antenna receiving device capable of improving characteristic degradation when transmission line fluctuation is fast and a method thereof.

An adaptive antenna receiving apparatus according to the present invention comprises: despreading means for despreading a received signal from a plurality of antenna elements for each finger; multiplying a despread signal output from each of the despreading means by a weight coefficient. Weighting factor multiplying means, channel distortion estimating means for estimating channel distortion based on each output from the weighting factor multiplying means, and complex conjugate means for generating each complex conjugate of the estimated channel distortion. Each of these complex conjugates is multiplied by each output from the weighting coefficient multiplying means to obtain transmission path distortion. Multiplying means for compensating for the above, combining means for adding the respective outputs of the multiplying means and performing rake combining, generating a common error signal between the combined output and the reference signal, and adding the common error signal to the transmission path. Error signal generating means for deriving by multiplying each of the distortions; and using each output of the error signal generating means and each of the despread signals, for each finger, the root mean square of the common error signal is minimized. Control means for controlling the weighting coefficient so that

Another adaptive antenna receiving apparatus according to the present invention comprises: despreading means for performing despreading processing on received signals from a plurality of antenna elements for each finger; and weighting the despread signals output from the despreading means, respectively. Weight coefficient multiplying means for multiplying coefficients; transmission path distortion estimating means for estimating transmission path distortion based on each output from the weight coefficient multiplying means; and complex conjugate for generating each complex conjugate of the estimated transmission path distortion Means for multiplying each of the complex conjugates and each output from the weighting coefficient multiplying means to compensate for transmission line distortion; and Synthesizing means for multiplying each of the transmission line distortions and a reference signal; and using each output of the second multiplying means and each of the despread signals for each finger. The weight And a control means for controlling the coefficients.

Still another adaptive antenna receiving apparatus according to the present invention includes: despreading means for performing despreading processing on received signals from a plurality of antenna elements for each finger; and a weighting factor for a despread signal output from the despreading means. Weighting factor multiplying means, a channel distortion estimating means for estimating channel distortion based on each output from the weighting factor multiplying means, and a complex conjugate hand for generating each complex conjugate of the estimated channel distortion. A multiplying means for multiplying each of the complex conjugates and each output from the weighting coefficient multiplying means to compensate for transmission path distortion; a combining means for adding the respective outputs of the multiplying means to perform Rake combining; Error signal generating means for generating a common error signal between the combined output and the reference signal and multiplying the common error signal by each of the transmission line distortions to derive the common error signal; And control means for controlling the weighting coefficient so as to minimize the root mean square of the common error signal using each output of the error signal generation means and each of the despread signals.

Another adaptive antenna receiving apparatus according to the present invention is provided for receiving from a plurality of antenna elements. Despreading means for despreading the signal for each finger; weighting coefficient multiplying means for multiplying the despread signal output from the despreading means by a weighting coefficient; and Channel distortion estimating means for estimating channel distortion based on the output; complex conjugate means for generating each complex conjugate of the estimated channel distortion; and each complex conjugate and each output from the weight coefficient multiplying means. A first multiplication unit that compensates for transmission line distortion by multiplying each of the transmission line distortions; a combining unit that adds the outputs of the first multiplication unit to perform Rake combining; A second multiplying means for multiplying, and a control means provided in common to the fingers and controlling the weight coefficient using each output of the second multiplying means and each of the despread signals. .

The receiving method according to the present invention comprises: a despreading step of despreading a received signal from a plurality of antenna elements for each finger; and a weight for multiplying the despread signal output from the despreading step by a weight coefficient. A coefficient multiplying step; a channel distortion estimating step of estimating a channel distortion based on each output from the weighting coefficient multiplying step; a step of generating each complex conjugate of the estimated channel distortion; A multiplication step for compensating for transmission line distortion by multiplying the output from the weighting coefficient multiplication step with each output from the weighting coefficient multiplication step; An error signal generating step of generating a common error signal with the signal and multiplying the common error signal by each of the transmission line distortions to derive the error signal; A control step of controlling the weighting coefficient such that the root mean square of the common error signal is minimized for each finger using each output of the signal generation step and each of the despread signals.

Another receiving method according to the present invention includes a despreading step for despreading a received signal from a plurality of antenna elements for each finger, and assigning a weight coefficient to the despread signal output from each of the despreading steps. A weighting factor multiplying step for multiplying, a channel distortion estimating step for estimating a channel distortion based on each output from the weighting factor multiplication step, and a step for generating each complex conjugate of the estimated channel distortion. A first multiplication step of multiplying each of these complex conjugates and each output from the weight coefficient multiplication step to compensate for transmission line distortion; A combining step of rake combining by adding outputs, a second multiplying step of multiplying each of the transmission path distortions by a reference signal, and each output of the second multiplying step and each of the despread signals. And controlling the weighting coefficient for each finger using the control method.

Still another receiving method according to the present invention is a despreading step of despreading a received signal from a plurality of antenna elements for each finger, and weighting the despread signal output from the despreading step. A weighting coefficient multiplying step for multiplying the coefficients; a transmission path distortion estimating step for estimating transmission path distortion based on each output from the weighting coefficient multiplication step; and a step for generating each complex conjugate of the estimated transmission path distortion. A multiplication step of multiplying each of these complex conjugates and each output from the weight coefficient multiplication step to compensate for transmission line distortion; a combining step of adding the respective outputs of the multiplication step to perform rake combining; An error signal generating step of generating a common error signal between the combined output and the reference signal, and multiplying the common error signal by each of the transmission path distortions to derive the error signal; A control which is provided in common with the fingers and controls the weighting coefficient so as to minimize the root mean square of the common error signal using each output of the error signal generation step and each of the despread signals. Step.

Another receiving method according to the present invention includes a despreading step of despreading a received signal from a plurality of antenna elements for each finger, and assigning a weight coefficient to the despread signal output from each of the despreading steps. A weighting factor multiplying step of multiplying, a channel distortion estimating step of estimating channel distortion based on each output from the weighting factor multiplying step, and a step of generating each complex conjugate of the estimated channel distortion. A first multiplication step of multiplying each of the complex conjugates and each output from the weighting coefficient multiplication step to compensate for transmission line distortion, and a synthesis step of adding the respective outputs of the first multiplication step and performing rake synthesis A second multiplication step of multiplying each of the transmission line distortions by a reference signal; and a second multiplication step provided common to the fingers; By using the respective force and the despread signal, and a control step of controlling the weighting coefficients.

The operation of the present invention will be described. It is possible to separate multiple paths using a common error signal. If there is no correlation between the paths, the adaptive update algorithm calculates the antenna weight using the N-order correlation matrix independently for each path, and calculates the (NXL) -order correlation matrix This is equivalent to the adaptive update algorithm, and therefore the antenna weight coefficient is controlled using the adaptive update algorithm so that the root mean square of the common error signal after rake combining is independently minimized for each finger. . As a result, the amount of operation of the adaptive update algorithm used in all MMSE control circuits can be greatly reduced from (NL) to N2L, and the processing load on the operation circuit can be reduced.

Furthermore, when the transmission line fluctuation is fast, the function of compensating the transmission line distortion and the MMSE control circuit that generates the antenna weight are separated separately, so that the antenna weight generated by the MMSE control circuit is Without compensating for signal transmission path distortion, control can be performed to maximize the signal arrival direction and average SIR, and control can be performed to maximize instantaneous SIR by rake combining. Can be improved. BRIEF DESCRIPTION OF THE FIGURES

FIG. 1 is a configuration diagram of an example for explaining a conventional technique.

FIG. 2 is a diagram illustrating a configuration of an antenna weighting synthesis circuit.

FIG. 3 is a configuration diagram of one embodiment of the present invention.

FIG. 4 is a diagram illustrating the configuration of the antenna weighting and combining circuit.

FIG. 5 is a diagram comparing B ER characteristics between the conventional example and the present invention.

FIG. 6 is a configuration diagram of another embodiment of the present invention.

FIG. 7 is a configuration diagram of still another embodiment of the present invention.

FIG. 8 is a configuration diagram of another embodiment of the present invention.

FIG. 9 is a configuration diagram of still another embodiment of the present invention.

FIG. 10 is a configuration diagram of another embodiment of the present invention. BEST MODE FOR CARRYING OUT THE INVENTION

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings. FIG. 3 shows the present invention. FIG. 2 is a diagram showing a configuration of an embodiment of the present invention, and portions equivalent to those in FIG. 1 are denoted by the same reference numerals. In Fig. 3, the number of receiving antennas is N (N is an integer of 2 or more), the number of multipaths is L (L is an integer of 1 or more), and the CD for the kth user (k is an integer of 1 or more) The MA adaptive antenna receiving device will be described.

As shown in Fig. 3, the C-DMA adaptive antenna receiving apparatus transmits L signals corresponding to multi-paths with N receiving antennas 1-1 to 1-N and L paths to the k-th user. Processing means 20 _ 1 to 20 _L, adder 10, subtracter 11, and reference signal generation circuit 12. Each of the signal processing means 20 0-1 to 20-L corresponding to each multipath has the same configuration, and includes delay units 2-1 to 2-L and N despreading circuits 3-1 to 1- 3—L—N, antenna weighting / synthesizing circuit 4-1 1 to 4-1 L, MMSE (Minimum Mean Square Error) control circuit 5-1 to 5—L, channel estimation circuit 6-1 Up to 6—L, complex conjugate circuit 7-1 to 7—L, multiplier 8— :! ~ 8-L, and a multiplier 91-1 ~ 9_L.

The N receiving antennas 11-1 to 1-N are arranged close so that the respective received signals have a correlation. Delay devices 2 _ 1 to 2 — L is N receiving antennas

By delaying the signal received at 1-1-1-N in accordance with each of the L multipaths, the signals are distinguished from the first path to the Lth path. Delay device 2— 1 to

2—Received signal output from L is despreading circuit 3-1— :! After being despread by LN, they are sent to the antenna weighting / synthesizing circuit 41-1 to 4_L and the MMSE control circuit 51 to 1-5-L.

In each of the L antenna weighting / synthesizing circuits 4-1 to 4-L, as shown in FIG. 4, a despreading circuit 3-1 to 3-1 to 3-1 ^-^^ The signal is multiplied by the antenna weights generated by the L MMSE control circuits 5-1 to 5-L in accordance with multipliers 13-1 to 13-N and added by the adder 14. The weights are combined and sent to the transmission path estimation circuits 6-1 to 6-L and multipliers 8-1 to 8-L in Fig. 3.

In the transmission path estimation circuit 6-1 to 6-L, the transmission path distortion is estimated using the output of the antenna weighting and combining circuit 4-1 to 4-1 L, and the estimation result is converted to a complex conjugate circuit 7- 1 to 7—L and multiplier 9-1 1 to 9-1 L are sent to L. The complex conjugate circuits 7-1 to 7-L generate complex conjugates of the transmission line distortion estimated by the transmission path estimation circuits 6-1 to 6-L. Complex conjugate circuit 71 The complex combination of transmission line distortion generated by 1-7-L is used by multipliers 8-1-1-8-L for antenna weighting and combining circuit 41 :! By multiplying the output of ~ 1 L, the transmission line distortion is compensated.

The outputs of the multipliers 8-1 to 8 _L in which the transmission line distortion has been compensated are added by the adder 10 to perform rake combining and input to the subtractor 11. The function of compensating for the transmission line distortion is as follows. When the transmission line fluctuation is fast, the update speed of the antenna weight by the adaptive update algorithm used in the MMSE control circuit 5-1 to 5-L Therefore, by separately separating the compensation function of the channel distortion, control is performed so that the instantaneous SIR is maximized by the rake combining by the adder 10. At this time, the antenna weights generated by the MMSE control circuits 5-1 to 5_L do not compensate for the transmission path distortion of the desired signal, but control so that the signal arrival direction and the average SIR are maximized. I do.

The subtracter 11 subtracts the rake combined output of the adder 10 from the output of the reference signal generation circuit 12 to generate a common error signal. The common error signal is divided into L respective multipliers 9 — 1−9−1 L is multiplied by the transmission line distortion estimated by the transmission line estimation circuit 6−1−6−L, and sent to each of the L MMSE control circuits 5-1-5−L. In each of the L MMSE control circuits 5_1 to 5—L, a multiplier 9-1 to 9—1L and a common error signal multiplied by the transmission line distortion and a despreading circuit 3—1-1—1 33—Using antenna received signals corresponding to each multipath output by L1-N, the antenna weight is controlled so that the root mean square of the common error signal is minimized.

Here, the adaptive update algorithm used in each of the L MMSE control circuits 5-1 to 5-L uses a high-speed RLS (Recursive Least Square) algorithm, and is independent for each finger. By using an algorithm that controls antenna weights using an N-order correlation matrix, the amount of computation can be greatly reduced, and the processing load can be reduced.

The configuration of the embodiment of the present invention will be described in more detail with reference to FIGS. I will tell. FIG. 3 is a configuration diagram showing a CDMA adaptive antenna receiving apparatus according to the present invention when a common error signal is used. The number of receiving antennas is N (N is an integer of 2 or more), the number of multipaths is L (L is an integer of 1 or more), and a CDMA adaptive antenna receiving device for the kth user (k is an integer of 1 or more) Will be described.

As shown in FIG. 3, the CDMA adaptive antenna receiving apparatus of the present invention supports multi-paths with N receiving antennas 11 1 to 11 N and L paths for the k-th user. It is composed of L signal processing means 20-1 to 20-L, an adder 10, a subtractor 11, and a reference signal generation circuit 12.

The L signal processing means 20 0-1 to 20-L corresponding to each multipath have the same configuration, and include a delay device 2-1 to 2-L and N despreading circuits 3-1-1 to 3—L—N, antenna weighting / synthesizing circuit 4-1 1 to 4-L, MM SE control circuit 5-1 to 5—L, channel estimation circuit 6_1 to 6_L, complex conjugate circuit 7-1 to 7 — L and multipliers 8—1 to 8—L and 9—1 to 9—L.

Each of the N receiving antennas 11 1 to 11 N receives a signal in which a desired signal and a plurality of interference signals are multiplexed, and is located close to each other so that the received signals are correlated. Are located. Delay device 2— :! 2 to L are distinguished from the 1st path to the Lth path by delaying the signals received by N reception antennas 1-1 to 1-N according to each of the L multipaths Is done. The received signals output from the delay units 2-1 to 2 _ L are despread by the despreading circuit 3-1 1 to 3 _ L-N, and then the antenna weighting and combining circuit 4-! ~ 4-L and MMSE control circuit 5-1 to 5-L are sent.

FIG. 4 is a block diagram showing a configuration of the antenna weighting / synthesizing circuits 411 to 4-1L. Each of the antenna weighting / synthesizing circuits 4-1 to 4-L has the same configuration, and includes multipliers 13_1 to 13-N and an adder 14. In order to simplify the description, the following description will be made taking the signal processing means 20-1 as an example. In the antenna weighting / synthesizing circuit 4-1, the received signal despread by the despreading circuit 3-1-1-3-1-N is converted into the MMSE control circuit by the multiplier 13-1-1-3-N The antenna weights generated in 5-1 are multiplied, added by an adder 14 and weighted and combined, and sent to the transmission path estimating circuit 6-1 and the multiplier 8-1 in FIG. The antenna weighting / synthesizing circuit 4-1 controls the amplitude and phase of the received signals of the receiving antennas 11-1 to 11-N to provide a gain to the desired signal, and to suppress the interference to receive the array antenna. To form a directivity. The transmission path estimation circuit 6-1 estimates the transmission path distortion using the output of the antenna weighting / synthesizing circuit 4-1 and sends the estimation result to the complex conjugate circuit 7-1 and the multiplier 9-1. . The complex conjugate circuit 711 generates a complex conjugate of the transmission path distortion estimated by the transmission path estimation circuit 6-1.

The complex conjugate of the transmission path distortion generated by the complex conjugate circuit 7-1 is multiplied by the output of the antenna weighting / synthesizing circuit 411 by the multiplier 8-1, thereby compensating the transmission path distortion. The outputs of the multipliers 8-1 to 8 _L whose transmission line distortion has been compensated are added by an adder 10 to perform rake combining, and input to a subtracter 11. The function of compensating for this transmission line distortion is based on the MMSE control circuit 5— :! In the update rate of the antenna weights by the adaptive update algorithm used in 5-L, it is not possible to compensate for the transmission path distortion in time. Control to maximize the instantaneous SIR. At this time, the MM SE control circuit 5— :! With the antenna weights generated by ~ 5-L, the transmission path distortion of the desired signal is not compensated, and the signal arrival direction and the average SIR are controlled to be maximum.

The transmission path estimation circuits 6-1 to 6-L provided for the transmission path distortion compensation function are, for example, V o 1. J 72-BII, N o. 1, pp. 7-15, 1989, as described in the “16 QAM phasing distortion compensation scheme for land mobile communications” By estimating the characteristics of the transmission line distortion from the symbols and interpolating the time series thereof, a known configuration in which the transmission lines of all the symbols are estimated can be used. As described above, when the transmission line fluctuation is fast, the antenna weight updating circuit 4-1 to 4—L cannot update the antenna weight in the MM SE control circuit 5-1 to 5—L in time. Each output has a large phase difference with each other. For this reason, even if an output having a large phase difference is supplied to the adder 10 for rake combining as in the conventional configuration shown in FIG. 1, accurate rake combining is not possible. It is difficult to maximize the instantaneous SIR by combining.

Therefore, in the present invention, a function for compensating for transmission line distortion, specifically, a transmission line estimation circuit 6-1 to 6-L and a complex conjugate circuit 7-1 to 7-L are further provided to provide a transmission path fluctuation. When the speed is fast, the function of compensating for the transmission line distortion is used to control the phase difference between each finger output to be small, perform accurate rake combining, and maximize the instantaneous SIR by rake combining. It is. If the transmission line fluctuation is slow,? ^ 1 ^ 3 £ Control circuit 5 _ 1-5-L In order to keep up with the update speed of the antenna weight sufficiently, the phase difference of each output of the antenna weighting and combining circuit 4-1-4-1 L is controlled to be sufficiently small. Therefore, there is no need to have a function of compensating for transmission line distortion, but it is clear that it may be.

As described above, by separately providing a function for compensating for the transmission line distortion and controlling the instantaneous SIR by rake combining when the transmission line fluctuation is fast, the present invention provides a solid line 1 shown in FIG. As shown in the BER (Bit Error Rate) characteristic of 00, good characteristics are exhibited regardless of the speed of transmission line fluctuation. In Fig. 5, the horizontal axis is Eb / No (signal power to noise power ratio) per bit of data symbol. In the conventional example shown in FIG. 1, the faster the fluctuation of the transmission line, the more the characteristic deteriorates as indicated by the one-dot chain line 200.

The subtracter 11 subtracts the rake combined output of the adder 10 from the output of the reference signal generation circuit 12 to generate a common error signal. The common error signal is divided into L respective multipliers 9 one:! 9L is multiplied by the transmission path distortion estimated by the transmission path estimation circuits 6-1 to 6-L and sent to the L MMSE control circuits 5-1 to 5-L. In each of the L MMSE control circuits 5-1 to 5-L, a common error signal multiplied by the transmission line distortion and a despreading circuit 3-1 to 1-3 are applied to the multipliers 9_1 to 9-L. — Antenna weight is controlled so that the root mean square of the common error signal is minimized using the antenna reception signals corresponding to each multipath output by L−N.

Here, the adaptive update algorithm used in each of the L MMSE control circuits 5-1 to 5_L is independently controlled for each finger using the RLS (Recursive Least Square) algorithm, which is a fast algorithm. Using the Nth order correlation matrix -Use an algorithm that controls the weight.

The operation of the embodiment of the present invention will be described with reference to FIGS. Here, the RLS (Recursive Least Square) algorithm used in each of the L MMS E control circuits 5-1 to 5-L will be described. The processing operation of the mth symbol (time mT when the symbol period is T) signal received through the first (1 = :! to L) th multipath channel for the kth user will be described.

Each of the L MMS E control circuits of the present invention 5— :! The R LS (Recursive Least Square) algorithm used in L is the correlation matrix, R _xx k, i (0) '= δυ (m = 0) "…-(13)

^{Rxxk, l (m) = a} xx k, l (m- 1) + Xk, l (m) X k) i H (m) (m = 1, 2, 3, ......) ...... (14)

Is calculated. Where <5 is a positive constant, H is a complex conjugate transpose, U is a unit matrix, and is a weighting constant of 0 <«≤1.

X _{k) 1} (m) is the despread signal of the despread signal output by the despreading circuit 3-1-1-1 to 3-1-N (1 = 1 to L) corresponding to the first multipath Represents the vector,

^{^{xk, i (m) = [}} y k, i, i (m), yk, i, 2 (m),, yk, l, N (m)] T

…… (15)

Is defined as Here, T represents transposition.

Each of the L MMS E control circuits 5— :! RL S (Recursive Least Square) algorithm used in ~ 5-L is by the multiplier 9 1-9 one L, channel distortion h _k, a common error signal i is multiplied e _kJ (m) (= h _{k) 1} e _k (m)) and the respective antenna reception signals output by the despreading circuit 3-1-1-1 to 3_1-N (1 = 1 to L) corresponding to multipath. Update antenna weights.

In this process, the antenna weight is adaptively controlled based on the MMSE criterion so that the common error signal e _k (m) is minimized.

W _{k) 1} (m) = W _{k> 1} (m-1) + Tk'lRxxk'r ¹ (m-1) Xk, l (m) e _{k> 1} * (m)

…… (16)

It is expressed as

Here, W _{k> 1} (m) represents the antenna weight vector of the antenna weight generated by the MMSE control circuit 5-1 (1 = 1 to L) corresponding to the first multipath,

wk '〗 ^{(m) = [Wk, i} , i (m), Wk, i, 2 (m), ···, Wk, i, N r

... Defined as (18).

Since equations (16) and (17) must calculate the inverse matrix of the correlation matrix R _xxkil , both equations (13) and (14) can be used to reduce the computational complexity of this inverse matrix calculation. Inverting the edges using the matrix formula gives

Is

R _{xxk you} -1 (0) = δ-lU (m = 0) "…-(19)

Rxxk, ^{(m) =} ^^ xxk ^(m " ¹⁾

(ΓΠ = 1'2,3, "" ") (20)

In the CDMA system, the multipath signal is separated by the spreading code, and the correlation between each finger is almost eliminated. Therefore, each finger independently calculates the antenna weight using the Nth-order correlation matrix RLS (Recursive Least Square) Algorithm and

(NXL) This is equivalent to the RLS (Recursive Least Square) algorithm that calculates the next correlation matrix. In the following, the RL S used in each of the L MM SE control circuits 5-1 to 5-L in the CDMA adaptive antenna receiving apparatus of the present invention is described.

(Recursive Least Square) algorithm and conventional CDMA adaptive antenna It proves that it is equivalent to the RLS (Recursive Least Square) algorithm used in one MMSE control circuit 5 in the communication device.

Here, for the sake of simplicity, consider the case where the number of multipaths is 2, that is, two fingers. When the correlation matrix Rxx in the case where a common error signal is used for all fingers in the conventional CDMA adaptive antenna receiver is represented by a division matrix,

Rii R12

R XX (21)

Expressed as R ₂₁ R22.

Where R _{1] L} is the autocorrelation matrix of finger 1, R22 is the autocorrelation matrix of finger 2, R ₁₂ is the cross correlation matrix of finger 1 and finger 2, R ₂₁ is the cross correlation of finger 1 and finger 1 Each represents a correlation matrix.

In the CDMA system, since the paths separated by the despreading operation are almost uncorrelated, the correlation between the fingers can be set to R ₁₂ = R 21 = 0. Therefore, the correlation matrix x is

Rii 0

R (22)

XX

0 R ₂

It is represented as

Then, the inverse matrix of the correlation matrix R _xy having only diagonal components is

It is represented as

In the conventional CDMA adaptive antenna receiver, RLS when one MMS E control circuit 5 uses a common error signal e (m) for all fingers

The (Recursive Least Square) algorithm is expressed by the following equation.

W (m) = W (m— 1) + r Rxx ' ¹ (m-1) X (m) E * (m)… (24) W (m) = [Wi (m), W ₂ (m) ] T ...... (25)

X (m) = [Xi (m), X ₂ (m)] T …… (26)

r: / _m .-i ^hie ( ^m ) ^: finger 1

h ₂ e (m): Finger 2

Where W (m) is the weight vector of finger 1 and finger 2 of the m symbol, W _T (m) is the weight vector of finger 1 of the m symbol, and W 2 (m) is the finger of the m symbol. Weight vector, X (m) is the despread signal vector of finger 1 and finger 1 of the mth symbol, and d (m) is the despread signal vector of finger 1 of the mth symbol, X ₂ (m ) Represents the despread signal vector of the m-th symbol's finger 1-2, and E (m) is multiplied by the transmission path distortion of the finger m-1 and the transmission path distortion h _{2 of} finger 2. Each represents a common error signal.

Expressing the above equation as a partition matrix,

i (m) (m-1)

+ r

W ₂ (m) W ₂ (m-1) R ₂₂ (m-1) X ₂ (m) h2 e ( _m ) _

. (27)

Becomes If there is no correlation between the fingers, the RLS (Recursive Least Square) algorithm calculated from the (NXL) -order correlation matrix and the RLS (Recursive Least Square) calculated from the N-order correlation matrix independently for each finger ) Algorithms are equivalent.

Next, each of the L M MSE control circuits 5— :! to 5—L in the CDMA adaptive antenna receiving apparatus of the present invention and one MMSE control in the conventional CDMA adaptive antenna receiving apparatus. We prove that the optimal weights obtained in circuit 5 are equivalent.

Optimal weight

Thus, if expressed by a partition matrix,

(28)

W = [Wi W ₂ ] T (29)

s ₂ ] ^T (30)

Becomes

Where W is the weight vector of finger 1 and finger 1, W _x is the weight vector of finger 1, W ₂ is the weight vector of finger 2, S is the correlation vector of finger 1 and finger 2, Si is The correlation vector of finger 1 and S ₂ represent the correlation vector of finger 2 respectively.

The above equation shows that if there is no correlation between the fingers, the optimal weight calculated from the (NXL) -order correlation matrix and the optimal weight calculated independently from the N-order correlation matrix for each finger are equivalent. ing. Here, we consider the case of two fingers for simplicity of explanation, but it is clear that the proof holds for any number of fingers. In this way, by using the fact that the cross-correlation of each path of the correlation matrix becomes almost uncorrelated, the order of one (NXL) -order correlation matrix is reduced to L N-order correlation matrices. The amount of calculation can be greatly reduced from (NL) 2 to N2L, and the processing load on the calculation circuit can be reduced.

In addition, when the transmission line fluctuation is fast, the function of compensating for the transmission line distortion and the MM SE control circuit 5-1 to 5-L for generating the antenna weight are separated from each other so that the MM SE control circuit 5— The antenna weights generated by 1 to 5—L do not compensate for the transmission path distortion of the desired signal, but control so that the signal arrival direction and the average SIR are maximized. Rake combining by adder 10 Can be controlled to maximize the instantaneous SIR. As a result, in the conventional adaptive update algorithm used in the MMSE control circuit 5, the effect of reducing the noise caused by following the transmission path variation with the antenna weight is reduced, and the problem of deteriorating characteristics is improved. be able to.

FIG. 6 is a configuration diagram showing another embodiment of the present invention. 6, the same components as those in FIG. 3 are indicated by the same reference numerals. The difference between the configuration shown in FIG. 6 and the configuration shown in FIG. 3 is that a decision unit 15 that decides the symbol data of the rake combined output that is the output of the adder 10, and that the decision output and the reference signal generation circuit 1 That is, a switch 16 provided between the second output and the second output is added. Hereinafter, differences between the configuration shown in FIG. 6 and the configuration shown in FIG. 3 will be described.

The rake combined output of the adder 10 is input to the decision unit 15, and the output of the decision unit 15 is not only output as the reception symbol of the k-th user, but also the reference signal during reception other than the known pilot signal. It is also sent to Switch 16 because it is used as The reference signal generation circuit 12 generates a known pilot signal, and the switch 16 selects the output of the reference signal generation circuit 12 when receiving a pilot signal. 15 Select the output of the receive symbol of 5 and send it to the subtractor 11. As a result, the subtractor 11 uses not only the output of the reference signal generation circuit 12 but also the output of the decision unit 15 to calculate a common error signal, and each of the L MMSE control circuits 5-1 to 5—Adaptive update used in L

Weights can converge more quickly. This embodiment has a new effect that the antenna weight of the adaptive update algorithm used in each of the L MMSE control circuits 5-1 to 5-L can be converged more quickly.

In the adaptive update algorithm used in each of the L MM SE control circuits 5-1 to 5-L, similar effects can be obtained by applying another high-speed algorithm, the SMI (Sample Matrix Inversion) algorithm. Can be demonstrated. FIG. 7 shows another CDMA adaptive antenna receiving apparatus of the present invention when this SMI algorithm is used as an adaptive update algorithm used in each of the L MMSE control circuits 5-1 to 5-L. FIG.

A subtractor for calculating a common error signal by subtracting the rake combined output of the adder 10 from the output of the reference signal generation circuit 12 is removed, and a signal output from the reference signal generation circuit 12 is used instead of the common error signal. Is multiplied by a transmission path estimation circuit 6-1 through 6_L by the L multipliers 9-1 through 9_L, respectively; L each of the MMSE control circuits 5— 1 to 5—Send to L. In each of the L MMSE control circuits 5-1 to 5-L, the reference signal multiplied by the transmission line distortion and the despreading circuit 3-1-1-1-1 to The antenna weight is controlled using the antenna reception signals corresponding to each multipath output by 3-LN.

The processing operation of the signal of the mth symbol (the time mT when the symbol period is T) received through the first (1 = 1 to L) multipath channel for the kth user will be described. The SMI algorithm used in each of the L MMSE control circuits 5—;! To 5—L calculates the correlation matrix R _xxk j as in the following equation.

R _xxk j (1) = Xk, l (1) Xk, l ^H (1) (m = l) …… (31)

R _X xk, l (m) = β R _xx k, l (m-1)

+ (1— ^) X _k; i (m) X _kj iH ( _m )

(m = 2, 3, ……) …… (32) where j3 is a forgetting factor satisfying the condition 0 <ι8 <1, and RLS (Recursive

Least Square) It has the same characteristics as the weighting constant α used in the algorithm. Also, calculate the correlation vector Skj as follows. s _k , i) = Xi (i) 2 _k * (i) ()

(m = 2,3, ……) (34)

(However, the output of the reference signal generation circuit is assumed to be 2 _k (m).) Therefore, the antenna weights generated by the L MMSE control circuits 5_1 to 5-L are:

W _k) i (m) = R _xx k ₎ r ¹ (m) S _{k> 1} (m) ... (35) Since equation (35) must calculate the inverse of the correlation matrix R _xxk ji, both sides of equation (32) are inversely calculated using a matrix formula in order to reduce the computational complexity of this inverse matrix calculation. Matrixized, Rxxk ¹ is

(m = 2,3, ……〉 --- ---- (36)

Even if the S Ml algorithm is applied to the adaptive update algorithm used in each of the L MMSE control circuits 5-1 to 5-L, the cross-correlation of each path in the correlation matrix becomes almost uncorrelated. By reducing the order of one (NXL) -order correlation matrix to L N-order correlation matrices, the amount of computation can be significantly reduced from (NL) 2 to N2L, and the processing load on the computation circuit Can be reduced.

In addition, when the transmission line fluctuation is fast, the MM SE control circuit that compensates for the transmission line distortion and generates the antenna weight 5— :! -5-L is separated separately, so that the antenna weights generated by the MMSE control circuits 5-1-5-L do not compensate for the transmission path distortion of the desired signal. Control can be performed to maximize the instantaneous SIR by the rake combining by the adder 10, and the same effect can be obtained that can improve the characteristic deterioration. can do.

FIG. 8 is a configuration diagram showing another CDMA adaptive antenna receiving apparatus of the present invention when an RLS (Recursive Least Square) algorithm is used as an adaptive updating algorithm used in one MMSE control circuit 5. Another configuration of the CDMA adaptive antenna receiving apparatus according to the present invention is a transmission channel estimating circuit having a function of compensating for channel distortion to signal processing means 30-1 to 30-L of the conventional CDMA adaptive antenna receiving apparatus. 6-1 to 6-L, complex function circuit 7-1 to 7-L and multipliers 8-1 to 8_L, 9-1 to 9-L are further provided.

Therefore, the L signal processing means 25-1 to 25-L corresponding to each multipath are provided with a delay device 2— :! ~ 2—L, N despreading circuits 3-1—1 to 3—L—N, antenna weighting synthesis circuit 41 :! 4 _L, channel estimation circuit 6-1-6 _L, complex conjugate circuit 7-1-7-L and multipliers 8-1-8 -L, 9-1-9-L . Thus, when the transmission line fluctuation is fast, the function of compensating for the transmission line distortion and the MM SE control circuit 5 that generates the antenna weight are separated separately, so that the antenna weight generated by the MM SE control circuit 5 is different. , Without compensating for the transmission line distortion of the desired signal, controlling to maximize the signal arrival direction and average SIR, and controlling to maximize the instantaneous SIR by rake combining by the adder 10. It is possible to improve the characteristic deterioration.

FIG. 9 is a configuration diagram showing another CDMA adaptive antenna receiving apparatus of the present invention when an RLS (Recursive Least Square) algorithm is used as an adaptive updating algorithm used in one MMSE control circuit 5. Referring to FIG. 9, a determinator 15 is provided at the rake combined output of the calorie calculator 10, and a switch 16 is provided between the output of the determinator 15 and the output of the reference signal generation circuit 12. . In addition, the signal processing means 25-1 to 25-L include a transmission path estimation circuit 6 _ 1 to 6 _L, a complex conjugate circuit 7-1 to 7 _L, and a Containers 8-1 to 8-L, 9-1 to 9-1 L are provided.

As a result, the subtractor 11 calculates the common error signal using not only the output of the reference signal generation circuit 12 but also the output of the decision unit 15, and calculates the antenna weight of the adaptive update algorithm used in the MMSE control circuit 5. Can be converged more quickly. Also, when the transmission line fluctuation is fast, the function of compensating for the transmission line distortion and the MMSE control circuit 5 that generates the antenna weight are separated separately, so that the antenna weight generated by the MMSE control circuit 5 is: Control to maximize signal arrival direction and average SIR without compensating for transmission path distortion of desired signal, and to maximize instantaneous SIR by rake combining by adder 10 And characteristic deterioration can be improved. This embodiment has a new effect that the antenna weight of the adaptive update algorithm used in the MMSE control circuit 5 can be converged more quickly.

FIG. 10 is a configuration diagram showing another CDMA adaptive antenna receiving apparatus of the present invention when the SMI algorithm is used as the adaptive update algorithm used in one MMSE control circuit 5. The signal processing means 25-1 to 25-L have a transmission path estimating circuit 6-1 to 6-L, a complex conjugate circuit 7-1 to 7-1 L and a multiplier 8 _, which are functions for compensating for transmission path distortion. 1-8-L, 9-1-9-L are provided.

As a result, when the transmission line fluctuation is fast, the function of compensating for the transmission line distortion and the MMSE control circuit 5 that generates the antenna weight are separated separately, and the antenna generated by the MMSE control circuit 5 is separated. The weight does not compensate for the transmission path distortion of the desired signal, but controls so that the arrival direction of the signal and the average SIR are maximized, and maximizes the instantaneous SIR by rake combining by the adder 10. It can be controlled, and the characteristic deterioration can be improved.

Although the above embodiment has been described based on the CDMA system, the TDMA (Time Division Multiple Access) system and the FDMA (Frequency Division Multiple Access) system can also be used for multiple arriving waves. Therefore, the present invention can be applied to an adaptive antenna receiver other than the CDMA system. Industrial applicability

As described above, according to the present invention, an adaptive updating algorithm is used independently for each finger so that the root mean square of the common error signal after rake combining is minimized.

-Since the weight coefficient is controlled, it can be used in all MMSE control circuits. The amount of operation of the adaptive update algorithm used can be greatly reduced from (NL) 2 to N2L, which has the effect of reducing the processing load on the arithmetic circuit.

Further, according to the present invention, when the transmission line fluctuation is fast, the function of compensating for the transmission line distortion and the MMSE control circuit for generating the antenna weight are separated separately, so that the antenna generated by the MMSE control circuit is separated. The weight does not compensate for the transmission path distortion of the desired signal, but can be controlled to maximize the signal arrival direction and average SIR, and to control the instantaneous SIR by rake combining. However, there is an effect that characteristic deterioration can be improved.

Claims

The scope of the claims

1. An adaptive antenna receiving apparatus configured to receive a transmission signal by a plurality of antenna elements constituting an adaptive antenna,

Despreading means for despreading the received signals from the plurality of antenna elements for each finger,

Weight coefficient multiplying means for multiplying the despread signal output from the despreading means by a weight coefficient,

Transmission line distortion estimating means for estimating transmission line distortion based on each output from the weight coefficient multiplying means,

Complex conjugate means for generating each complex conjugate of the estimated transmission path distortion; multiplication means for multiplying each of the complex conjugates and each output from the weight coefficient multiplying means to compensate for the transmission path distortion;

Combining means for rake combining by adding the outputs of the multiplying means,

Error signal generating means for generating a common error signal between the output after the rake combining and the reference signal, multiplying the common error signal by each of the transmission line distortions, and deriving each output of the error signal generating means Control means for controlling the weighting coefficient so as to minimize the root mean square of the common error signal using the despread signal and each of the despread signals.

2. The adaptive antenna receiving apparatus according to claim 1, wherein the control means is provided for each of the fingers, and controls the weight coefficient for each of the fingers.

3. The adaptive antenna receiving apparatus according to claim 1, wherein the control means is provided commonly to each of the fingers, and controls the weight coefficient commonly to each of the fingers.

4. The adaptive antenna receiving apparatus according to claim 1, wherein the control means uses an RLS (Recursive Least Square) algorithm as an adaptive updating algorithm for controlling the weight coefficient.

5. It further includes: a determination unit that performs data determination of an output of the combining unit; and a switch unit that selectively switches between the determination output of the determination unit and the reference signal.

When the determining means determines that the received signal is a pilot signal, the switching means selects the reference signal and inputs it to the error signal generating means, and the determining means converts the received signal to the pilot signal. 2. The adaptive antenna receiving apparatus according to claim 1, wherein when it is determined that the data signal is other than the data signal, the switch means selects the determination output and inputs the selected output to the error signal generating means.

6. An adaptive antenna receiving apparatus configured to receive a transmission signal by a plurality of antenna elements constituting an adaptive antenna,

Complex conjugate means for generating each complex conjugate of the estimated transmission line distortion; first multiplication means for multiplying each of the complex conjugates and each output from the weight coefficient multiplying means to compensate for the transmission line distortion When,

Combining means for performing rake combining by adding the outputs of the first multiplying means; second multiplying means for multiplying each of the transmission path distortions by a reference signal;

An adaptive antenna receiving apparatus comprising: control means for controlling the weighting coefficient using each output of the second multiplying means and each of the despread signals.

7. The adaptive antenna receiving apparatus according to claim 6, wherein the control means is provided for each of the fingers, and controls the weight coefficient for each of the fingers.

8. The control means is provided commonly to each of the fingers, and each of the fingers is 7. The adaptive antenna receiving device according to claim 6, wherein the weighting factor is controlled in common to the antennas.

9. The adaptive antenna receiving apparatus according to claim 6, wherein the control means uses an SMI (Sample Matrix Inversion) algorithm as an adaptive updating algorithm for controlling the weight coefficient.

10. A receiving method in an adaptive antenna receiving apparatus configured to receive a transmission signal by a plurality of antenna elements forming an adaptive antenna,

A despreading step of despreading the received signals from the plurality of antenna elements for each finger, and generating a despread signal for each finger;

A weighting factor multiplying unit that multiplies the despread signal by a weighting factor to generate each multiplication output. Channel distortion estimation for estimating each channel distortion based on each of the multiplication outputs: Each complex of the estimated channel distortion estimated A step of generating a conjugate; and a step of multiplying each of the complex conjugates and each of the multiplied outputs to compensate for each of the transmission line distortions. When,

An error signal generating step of generating a common error signal between the output of the synthesis and a reference signal, multiplying the common error signal by each of the transmission line distortions, and generating each error signal;

A control step of controlling the weight coefficient so as to minimize the root mean square of the common error signal using each of the error signals and each of the despread signals.

11. The receiving method according to claim 10, wherein the control step is performed for each of the fingers, and the weight coefficient is controlled for each of the fingers.

12. The control step is performed in common for each of the fingers, and 10. The receiving method according to claim 10, wherein the weight coefficient is controlled in common for the lingers.

13. The receiving method according to claim 10, wherein the control step uses an RLS (Recursive Least Square) algorithm as an adaptive updating algorithm for controlling the weighting coefficient.

1 4. Judgment 2 which makes data judgment of the output of the above-mentioned synthesis step

A selection step of selecting the reference signal when the received signal is the pilot signal, and selecting a determination output of the determination step when the received signal is a data signal other than the pilot signal; 10. The receiving method according to claim 10, further comprising: before the error signal generating step.

15. A receiving method in an adaptive antenna receiving apparatus configured to receive a transmission signal by a plurality of antenna elements constituting an adaptive antenna,

Despreading a received signal from the plurality of antenna elements for each finger to generate a despread signal for each finger;

A weighting factor multiplication step for multiplying the despread signal by a weighting factor to generate each multiplication output;

A channel distortion estimation step of estimating each channel distortion based on each of the multiplied outputs, and a step of generating each complex conjugate of the estimated channel distortion,

A first multiplication step of multiplying each of the complex conjugates and each of the multiplication outputs to compensate for each transmission line distortion;

A synthesizing step for performing rake synthesis by adding the multiplied outputs from the first multiplying step;

A second multiplication step of multiplying each of the transmission path distortions and a reference signal,

A control step of controlling the weighting coefficient using each of the multiplied outputs in the second multiplying step and each of the despread signals.

16. The control step is performed for each of the fingers, and each of the fingers is 16. The receiving method according to claim 15, wherein the weighting coefficient is controlled for each one.

17. The receiving method according to claim 15, wherein the control step is performed commonly for each of the fingers, and the weight coefficient is controlled commonly for each of the fingers.

18. The receiving method according to claim 15, wherein the control step uses an SMI (Sample Matrix Inversion) algorithm as an adaptive update algorithm for controlling the weight coefficient.