WO2001082464A1 - Controlling a brushless dc motor - Google Patents

Controlling a brushless dc motor Download PDF

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Publication number
WO2001082464A1
WO2001082464A1 PCT/US2001/013571 US0113571W WO0182464A1 WO 2001082464 A1 WO2001082464 A1 WO 2001082464A1 US 0113571 W US0113571 W US 0113571W WO 0182464 A1 WO0182464 A1 WO 0182464A1
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WO
WIPO (PCT)
Prior art keywords
motor
meter
output value
signal
meter output
Prior art date
Application number
PCT/US2001/013571
Other languages
French (fr)
Inventor
Michael P. Copeland
Original Assignee
Infineon Technologies North America Corp.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Infineon Technologies North America Corp. filed Critical Infineon Technologies North America Corp.
Priority to EP01930838A priority Critical patent/EP1284044A4/en
Priority to JP2001579437A priority patent/JP2003532363A/en
Priority to AU2001257336A priority patent/AU2001257336A1/en
Publication of WO2001082464A1 publication Critical patent/WO2001082464A1/en

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H02P6/182—Circuit arrangements for detecting position without separate position detecting elements using back-emf in windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
    • H02P29/60—Controlling or determining the temperature of the motor or of the drive
    • H02P29/67—Controlling or determining the motor temperature by back electromotive force [back-EMF] evaluation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/08—Arrangements for controlling the speed or torque of a single motor
    • H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2209/00—Indexing scheme relating to controlling arrangements characterised by the waveform of the supplied voltage or current
    • H02P2209/07—Trapezoidal waveform

Definitions

  • This invention relates to systems and methods for controlling a brushless DC (direct-current) motor.
  • Brushless DC motors also known as self-synchronous or electronically commutated motors, may be used in a variety of mechanical systems, including motor vehicles and aerospace systems.
  • brushless DC motors may be found in automotive engine cooling systems and in heating, ventilation and air-conditioning (HNAC) equipment.
  • a brushless DC motor typically includes a plurality of windings (or coils) wound about a stator, and a plurality of permanent magnets mounted on a rotor.
  • An electronic control system switches current in the stator windings in a process known as commutation.
  • the control system senses the position of the rotor and applies a coordinated sequence of control signals to electronic switches (e.g., transistors) that control the flow of current through the stator windings.
  • the sequential switching of current through the motor windings produces a magnetic flux that rotates the rotor.
  • Drive currents may be applied to the motor windings continuously in a linear mode of operation, or discontinuously in a nonlinear mode of operation using, e.g., pulse width modulation (PWM) techniques.
  • PWM pulse width modulation
  • the position of the rotor with respect to the conducting (or active) stator windings must be known.
  • Various techniques may be used to detect the position of the rotor. For example, some systems derive rotor position information from sensors (e.g., Hall-effect sensors and optical sensors) coupled to the motor shaft. Other systems derive rotor position information from the back electromotive force (EMF) voltages generated in the windings as the motor rotates.
  • EMF back electromotive force
  • the invention features systems and methods for controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals.
  • DC direct current
  • EMF back electromotive force
  • the invention features a system comprising a meter coupled to a motor terminal and adapted to produce a range of digital output values representative of a motor terminal signal from which a back EMF signal may be derived.
  • the invention features a system comprising a meter, and a controller coupled to the meter and operable to monitor the range of meter output values and to compute a motor commutation time based upon a monitored local minimum meter output value and a monitored local maximum meter output value.
  • the invention also features a system comprising a pulse width modulation (PWM) circuit, and a meter coupled to a motor terminal, synchronized with the PWM circuit and configured to produce an output representative of a motor terminal signal from which a back EMF signal may be derived.
  • PWM pulse width modulation
  • the meter may include an analog-to-digital (A/D) converter.
  • a buffer may be coupled between the motor terminal and the meter.
  • the buffer preferably is configured to scale the terminal signal values to a selected range.
  • the buffer may include a voltage divider.
  • the motor commutation time preferably is computed based upon an identified phase-to-phase zero crossing in a back EMF signal.
  • the controller may be configured to store a local minimum meter output value and a local maximum meter output value every motor terminal driving cycle. The zero crossing preferably is identified when the meter output value is substantially equal to one-half of the difference between the local maximum meter output value and the local minimum meter output value.
  • the meter When the meter is synchronized with a PWM circuit, the meter preferably is adapted to sample motor terminal voltages in a non-conducting motor phase at times when each conducting motor phase is being driven.
  • the invention features a method of controlling a polyphase brushless direct current (DC) motor.
  • a range of signal values representative of a motor terminal signal from which a back EMF signal may be derived is monitored. Over the range of monitored signal values, a local maximum signal value and a local minimum signal value are stored. A motor commutation time is computed based upon the stored local maximum signal value and the stored local minimum value.
  • the invention determines when zero crossings in the back EMF signals occur based upon direct measurements of the motor terminal signals. In this way, the invention avoids the sensors and complex circuitry, such as an ASIC or a plurality of comparators, that typically are used to determine when zero crossings occur. Furthermore, because the local maximum back EMF signal values and the local minimum back EMF signal values may be measured periodically (e.g., once every driving cycle), the invention readily accommodates component drifts and temperature variations.
  • FIG. 1A is a block diagram of control system and a driver for a polyphase brushless DC motor.
  • FIG. IB is a plot over time of a voltage signal at a terminal of a motor in a linear mode of operation.
  • FIG. 1C is a plot over time of a voltage signal at a terminal of a motor in a PWM mode of operation.
  • FIG. 2 is a block diagram of a control system, a driver and a buffer coupled between the control system and a polyphase brushless DC motor.
  • FIG. 3 is a schematic diagram of the buffer of FIG. 2.
  • FIG. 4A shows plots over time of signals applied to the transistors of a three- phase inverter driving circuit and the voltages at the terminals of a brushless DC motor in a linear mode of operation.
  • FIG. 4B is a plot over time of digital output values of an A/D converter in the control system of FIG. 2.
  • FIG. 5 is a flow diagram of a method of controlling a polyphase brushless DC motor.
  • FIG. 6 A shows plots over time of output signals of two timers configured to implement the method of FIG. 5.
  • FIG. 6B is a flow diagram of a method of controlling a polyphase brushless DC motor implemented using two timers.
  • a system 10 for controlling a polyphase brushless DC motor 12 includes a meter 14, a control circuit 16, a memory 18, and a driver interface 20.
  • Driver interface 20 supplies control signals 22 to a driver 24, which includes a plurality of switching transistors for driving the terminals A, B, C of motor 12.
  • a driver 24 which includes a plurality of switching transistors for driving the terminals A, B, C of motor 12.
  • two of the terminals e.g., terminals B and C
  • the third terminal e.g., terminal A
  • the terminal drive currents are commutated to operate the motor in a stable, substantially jirterless way.
  • the motor coils are commutated based upon information derived from back EMF voltages (VEMF) that are measured during a floating (non-conducting) driving phase of each terminal A-C.
  • VEMF back EMF voltages
  • the back EMF voltages may be measured between terminals A, B, C and a reference voltage (e.g., the voltage at the center tap N of the motor windings).
  • control system 10 is configured to identify "zero crossings" in the back EMF voltages based upon direct measurement of the terminal voltages.
  • zero crossings are identified when the floating terminal voltage is halfway between a local minimum back EMF voltage and a local maximum back EMF voltage.
  • the time span between adjacent zero crossings corresponds to the driving voltage phase delay.
  • the motor coils preferably are commutated at a time corresponding to one half of a phase delay after each identified zero crossing; although the motor coils may be commutated at other times.
  • Meter 14 is coupled to terminals A, B, C of motor 12 and is configured to produce a range of output values representative of terminal voltages from which the back EMF signals may be derived.
  • meter 14 is synchronized with a PWM driving circuit 26 and samples voltage values from the non-conducting phase terminal at times when the switching transistors driving the conducting phase terminals are active. Zero crossings in the back EMF signals are computed from direct measurements of the voltages at the motor terminals.
  • Control circuit 16 preferably stores in memory 18 a local minimum meter output value and a local maximum meter output value, and computes motor commutation times based upon the stored meter output values. Referring to FIGS. IB and 1C, in a linear mode of operation (FIG.
  • each cycle of the terminal voltage has a characteristic "trapezoidal" profile over time.
  • the measured motor terminal voltages range between a local minimum value N and a local maximum value N H - Zero crossings in the back EMF signals are identified at times when the terminal voltage reaches a value that is equal to one half of the difference between the local maximum value and the local minimum value.
  • the terminal voltage includes a plurality of voltage spikes that are the result of the PWM switching.
  • a trapezoidal profile 30 may be recovered from the back EMF signal by sampling the minima of the spike voltages, which correspond to the times when the on-phase switching transistors of driver 24 are active (i.e., when the conducting phases are active).
  • a motor control system 40 includes an analog-to-digital (A/D) converter 42 that samples the voltages at terminals A- C of motor 12 and produces a digital output 44 that is representative of the sampled voltage values.
  • An input buffer 46 is coupled between terminals A-C of motor 12 and the input of A/D converter 42. Buffer 46 scales the motor terminal voltages to a range (e.g., 0 volts to 5 volts) that is suitable for the inputs of A/D converter 42.
  • buffer 42 includes a voltage divider 48, 50, 52 for each motor terminal A, B, C, respectively.
  • buffer 46 may include an operational amplifier or other circuit components that are configured to scale the motor terminal voltages to appropriate voltage range.
  • Driver 24 includes a three-phase inverter 54 with a plurality of transistors 56 configured to drive the terminals A-C of motor 12 high (i.e., transistors A+, B+, C+) and low (i.e., transistors A-, B-, C-). Referring to FIG.
  • control system 40 choreographs the application of drive currents to motor terminals A, B, C, as follows: from times ti to t 3 , transistor A+ drives terminal A high, and from times t to t 6 , transistor A- drives terminal A low; from times t 3 to t 5 , transistor B+ drives terminal B high, and from times to to t 2 , transistor B- drives terminal B low; and from times to to ti and from times t 5 to t 6 , transistor C+ drives terminal C high, and from times t 2 to t 4 , transistor C- drives terminal C low.
  • the resulting voltages at terminals A, B and C have the characteristic trapezoidal profiles VAN, VB N and V C N, respectively.
  • control system 10 may identify the zero crossings by detecting when the A/D converter output reaches a value that is equal to one-half of the difference between the local maximum (N H ) and the local minimum (N L ). From the zero crossing information, control system 10 may determine the proper times to commutate the motor winding.
  • control system 10 controls a polyphase brushless DC motor as follows.
  • the back EMF voltage (V EMF ) produced at a floating motor terminal is measured (step 60). If the measured voltage corresponds to a local minimum (step 62), the local minimum (VL) is stored in memory 18 (step 64). If the measured voltage (VE MF ) is equal to one-half of the difference between a previously measured local maximum and a previously measured local minimum (step 66), control system 10 determines that a zero crossing has occurred. Control system then sets Ti to the time (T 2 ) of the previous zero crossing, and sets T 2 to the current time (T), which corresponds to the most recent zero crossing (step 68).
  • step 70 If the current time (T) follows the time (T 2 ) of the most recent zero crossing by one half of the time span between the last two zero crossings A (T 2 - Tj . )) (step 70), the motor is commutated (step 72). If the back EMF voltage (V EM F) corresponds to a local maximum (step 74), the local maximum (N ⁇ ) is stored in memory 18 (step 76). The process (steps 60-76) is repeated for each motor terminal and each motor commutation driving cycle.
  • control system 10 By updating the values of the local maximum ( ⁇ H) and the local minimum ( ⁇ L ) every cycle, control system 10 readily accommodates component drifts that might be caused by aging or temperature variations.
  • the control method of FIG. 5 may be implemented using two timers (TI, TO), as follows. After an initial zero crossing is detected (step 78), the timers TI, TO are reset and timer TI is started (step 80). When the next zero crossing is identified (step 82), the value of timer TI corresponds to the period ( ⁇ t) between two adjacent zero crossings. At this time, a commutation phase delay (Y ⁇ At) is computed (step 84), timer TI is reset (step 86), and timer TO is started (step 88).
  • step 90 When the value of timer TO is equal to the computed phase delay (step 90), the appropriate motor winding is commutated (step 92) and the timer TO is stopped and reset (step 94). The process (steps 82-94) is repeated every motor commutation cycle.
  • Other embodiments are within the scope of the claims. For example, although the above embodiments have been described in connection with three-phase brushless DC motors, these embodiments easily may be extended to operate with any polyphase brushless DC motor.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)

Abstract

Systems and methods for controlling a polyphase brushless direct current 'DC' motor are described. One system includes a meter (14) coupled to a motor terminal and adapted to produce a range of digital output values representative of a motor terminal signal from which a back EMF signal is derivable. The system also may include a controller (16) that is coupled to the meter (14) and is operable to monitor the range of meter output values and to compute a motor commutation time based upon a monitored local minimum meter output value and a monitored local maximum meter output value. A pulse width modulation 'PWM' circuit (26) may be provided, and the meter (14) may be synchronized with the PWM circuit (26). Zero crossing in the back EMF signals are identified based upon direct measurements of the signals at the motor terminals. In this way, sensors and complex circuitry, such as an ASIC or a plurality of comparators, typically are used to determine when zero crossings occur are avoided. Furthermore, because the local maximum values and the local minimum values may be measured periodically, e.g., once every driving cycle, the invention readily accommodates component drifts and temperature variations.

Description

CONTROLLING A BRUSHLESS DC MOTOR
TECHNICAL FIELD
This invention relates to systems and methods for controlling a brushless DC (direct-current) motor.
BACKGROUND
Brushless DC motors, also known as self-synchronous or electronically commutated motors, may be used in a variety of mechanical systems, including motor vehicles and aerospace systems. For example, brushless DC motors may be found in automotive engine cooling systems and in heating, ventilation and air-conditioning (HNAC) equipment. A brushless DC motor typically includes a plurality of windings (or coils) wound about a stator, and a plurality of permanent magnets mounted on a rotor. An electronic control system switches current in the stator windings in a process known as commutation. The control system senses the position of the rotor and applies a coordinated sequence of control signals to electronic switches (e.g., transistors) that control the flow of current through the stator windings. The sequential switching of current through the motor windings produces a magnetic flux that rotates the rotor. Drive currents may be applied to the motor windings continuously in a linear mode of operation, or discontinuously in a nonlinear mode of operation using, e.g., pulse width modulation (PWM) techniques. In order to apply the proper drive currents to the stator windings, the position of the rotor with respect to the conducting (or active) stator windings must be known. Various techniques may be used to detect the position of the rotor. For example, some systems derive rotor position information from sensors (e.g., Hall-effect sensors and optical sensors) coupled to the motor shaft. Other systems derive rotor position information from the back electromotive force (EMF) voltages generated in the windings as the motor rotates.
SUMMARY
The invention features systems and methods for controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals. In one aspect, the invention features a system comprising a meter coupled to a motor terminal and adapted to produce a range of digital output values representative of a motor terminal signal from which a back EMF signal may be derived.
In another aspect, the invention features a system comprising a meter, and a controller coupled to the meter and operable to monitor the range of meter output values and to compute a motor commutation time based upon a monitored local minimum meter output value and a monitored local maximum meter output value.
The invention also features a system comprising a pulse width modulation (PWM) circuit, and a meter coupled to a motor terminal, synchronized with the PWM circuit and configured to produce an output representative of a motor terminal signal from which a back EMF signal may be derived.
Embodiments may include one or more of the following features. The meter may include an analog-to-digital (A/D) converter. A buffer may be coupled between the motor terminal and the meter. The buffer preferably is configured to scale the terminal signal values to a selected range. The buffer may include a voltage divider.
The motor commutation time preferably is computed based upon an identified phase-to-phase zero crossing in a back EMF signal. The controller may be configured to store a local minimum meter output value and a local maximum meter output value every motor terminal driving cycle. The zero crossing preferably is identified when the meter output value is substantially equal to one-half of the difference between the local maximum meter output value and the local minimum meter output value.
When the meter is synchronized with a PWM circuit, the meter preferably is adapted to sample motor terminal voltages in a non-conducting motor phase at times when each conducting motor phase is being driven.
In another aspect, the invention features a method of controlling a polyphase brushless direct current (DC) motor. In accordance with this inventive method, a range of signal values representative of a motor terminal signal from which a back EMF signal may be derived is monitored. Over the range of monitored signal values, a local maximum signal value and a local minimum signal value are stored. A motor commutation time is computed based upon the stored local maximum signal value and the stored local minimum value.
Among the advantages of the invention are the following. The invention determines when zero crossings in the back EMF signals occur based upon direct measurements of the motor terminal signals. In this way, the invention avoids the sensors and complex circuitry, such as an ASIC or a plurality of comparators, that typically are used to determine when zero crossings occur. Furthermore, because the local maximum back EMF signal values and the local minimum back EMF signal values may be measured periodically (e.g., once every driving cycle), the invention readily accommodates component drifts and temperature variations.
Other features and advantages of the invention will become apparent from the following description, including the drawings and the claims.
DESCRIPTION OF DRAWINGS
FIG. 1A is a block diagram of control system and a driver for a polyphase brushless DC motor.
FIG. IB is a plot over time of a voltage signal at a terminal of a motor in a linear mode of operation. FIG. 1C is a plot over time of a voltage signal at a terminal of a motor in a PWM mode of operation.
FIG. 2 is a block diagram of a control system, a driver and a buffer coupled between the control system and a polyphase brushless DC motor.
FIG. 3 is a schematic diagram of the buffer of FIG. 2. FIG. 4A shows plots over time of signals applied to the transistors of a three- phase inverter driving circuit and the voltages at the terminals of a brushless DC motor in a linear mode of operation.
FIG. 4B is a plot over time of digital output values of an A/D converter in the control system of FIG. 2. FIG. 5 is a flow diagram of a method of controlling a polyphase brushless DC motor.
FIG. 6 A shows plots over time of output signals of two timers configured to implement the method of FIG. 5.
FIG. 6B is a flow diagram of a method of controlling a polyphase brushless DC motor implemented using two timers. DETAILED DESCRIPTION
Referring to FIG. 1 A, a system 10 for controlling a polyphase brushless DC motor 12 includes a meter 14, a control circuit 16, a memory 18, and a driver interface 20. Driver interface 20 supplies control signals 22 to a driver 24, which includes a plurality of switching transistors for driving the terminals A, B, C of motor 12. In operation, during each driving cycle, two of the terminals (e.g., terminals B and C) are energized (one terminal is driven high and one terminal is driven low) and the third terminal (e.g., terminal A) is floating. The terminal drive currents are commutated to operate the motor in a stable, substantially jirterless way. The motor coils are commutated based upon information derived from back EMF voltages (VEMF) that are measured during a floating (non-conducting) driving phase of each terminal A-C. The back EMF voltages may be measured between terminals A, B, C and a reference voltage (e.g., the voltage at the center tap N of the motor windings).
As explained in detail below, control system 10 is configured to identify "zero crossings" in the back EMF voltages based upon direct measurement of the terminal voltages. In particular, zero crossings are identified when the floating terminal voltage is halfway between a local minimum back EMF voltage and a local maximum back EMF voltage. The time span between adjacent zero crossings corresponds to the driving voltage phase delay. The motor coils preferably are commutated at a time corresponding to one half of a phase delay after each identified zero crossing; although the motor coils may be commutated at other times.
Meter 14 is coupled to terminals A, B, C of motor 12 and is configured to produce a range of output values representative of terminal voltages from which the back EMF signals may be derived. In a PWM mode of operation, meter 14 is synchronized with a PWM driving circuit 26 and samples voltage values from the non-conducting phase terminal at times when the switching transistors driving the conducting phase terminals are active. Zero crossings in the back EMF signals are computed from direct measurements of the voltages at the motor terminals. Control circuit 16 preferably stores in memory 18 a local minimum meter output value and a local maximum meter output value, and computes motor commutation times based upon the stored meter output values. Referring to FIGS. IB and 1C, in a linear mode of operation (FIG. IB), each cycle of the terminal voltage has a characteristic "trapezoidal" profile over time. The measured motor terminal voltages range between a local minimum value N and a local maximum value NH- Zero crossings in the back EMF signals are identified at times when the terminal voltage reaches a value that is equal to one half of the difference between the local maximum value and the local minimum value. In a PWM mode of operation (FIG. 1C), the terminal voltage includes a plurality of voltage spikes that are the result of the PWM switching. A trapezoidal profile 30, however, may be recovered from the back EMF signal by sampling the minima of the spike voltages, which correspond to the times when the on-phase switching transistors of driver 24 are active (i.e., when the conducting phases are active).
Referring to FIGS. 2 and 3, in one embodiment, a motor control system 40 includes an analog-to-digital (A/D) converter 42 that samples the voltages at terminals A- C of motor 12 and produces a digital output 44 that is representative of the sampled voltage values. An input buffer 46 is coupled between terminals A-C of motor 12 and the input of A/D converter 42. Buffer 46 scales the motor terminal voltages to a range (e.g., 0 volts to 5 volts) that is suitable for the inputs of A/D converter 42. As shown in FIG. 3, in one embodiment, buffer 42 includes a voltage divider 48, 50, 52 for each motor terminal A, B, C, respectively. In other embodiments, buffer 46 may include an operational amplifier or other circuit components that are configured to scale the motor terminal voltages to appropriate voltage range. Driver 24 includes a three-phase inverter 54 with a plurality of transistors 56 configured to drive the terminals A-C of motor 12 high (i.e., transistors A+, B+, C+) and low (i.e., transistors A-, B-, C-). Referring to FIG. 4A, in one motor driving sequence, control system 40 choreographs the application of drive currents to motor terminals A, B, C, as follows: from times ti to t3, transistor A+ drives terminal A high, and from times t to t6, transistor A- drives terminal A low; from times t3 to t5, transistor B+ drives terminal B high, and from times to to t2, transistor B- drives terminal B low; and from times to to ti and from times t5 to t6, transistor C+ drives terminal C high, and from times t2 to t4, transistor C- drives terminal C low. The resulting voltages at terminals A, B and C have the characteristic trapezoidal profiles VAN, VBN and VCN, respectively. In FIG. 4A, the winding commutation times are labeled to through t6; the zero crossings preferably occur midway between the commutation times. As shown in FIG. 4B, A/D converter 42 produces digital outputs (NADC) that are representative of the relative voltages produced at terminals A-C while motor 12 is being driven. The digital A/D converter output tracks the characteristic trapezoidal profile of the terminal voltages (VAN, AN, VAN)- AS explained above, control system 10 may identify the zero crossings by detecting when the A/D converter output reaches a value that is equal to one-half of the difference between the local maximum (NH) and the local minimum (NL). From the zero crossing information, control system 10 may determine the proper times to commutate the motor winding.
Referring to FIG. 5, in one embodiment, control system 10 controls a polyphase brushless DC motor as follows. The back EMF voltage (VEMF) produced at a floating motor terminal is measured (step 60). If the measured voltage corresponds to a local minimum (step 62), the local minimum (VL) is stored in memory 18 (step 64). If the measured voltage (VEMF) is equal to one-half of the difference between a previously measured local maximum and a previously measured local minimum (step 66), control system 10 determines that a zero crossing has occurred. Control system then sets Ti to the time (T2) of the previous zero crossing, and sets T2 to the current time (T), which corresponds to the most recent zero crossing (step 68). If the current time (T) follows the time (T2) of the most recent zero crossing by one half of the time span between the last two zero crossings A (T2 - Tj.)) (step 70), the motor is commutated (step 72). If the back EMF voltage (VEMF) corresponds to a local maximum (step 74), the local maximum (Nπ) is stored in memory 18 (step 76). The process (steps 60-76) is repeated for each motor terminal and each motor commutation driving cycle.
By updating the values of the local maximum (ΝH) and the local minimum (ΝL) every cycle, control system 10 readily accommodates component drifts that might be caused by aging or temperature variations.
Referring to FIGS. 6 A and 6B, in one embodiment, the control method of FIG. 5 may be implemented using two timers (TI, TO), as follows. After an initial zero crossing is detected (step 78), the timers TI, TO are reset and timer TI is started (step 80). When the next zero crossing is identified (step 82), the value of timer TI corresponds to the period (Δt) between two adjacent zero crossings. At this time, a commutation phase delay (Y∑At) is computed (step 84), timer TI is reset (step 86), and timer TO is started (step 88). When the value of timer TO is equal to the computed phase delay (step 90), the appropriate motor winding is commutated (step 92) and the timer TO is stopped and reset (step 94). The process (steps 82-94) is repeated every motor commutation cycle. Other embodiments are within the scope of the claims. For example, although the above embodiments have been described in connection with three-phase brushless DC motors, these embodiments easily may be extended to operate with any polyphase brushless DC motor.

Claims

WHAT IS CLAIMED IS:
1. A system for controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals, comprising a meter coupled to a motor terminal and adapted to produce a range of digital output values representative of a motor terminal signal from which a back EMF signal is derivable.
2. The system of claim 1 , wherein the meter comprises an analog-to-digital (A/D) converter.
3. The system of claim 1 , further comprising a buffer coupled between the motor terminal and the meter and configured to scale terminal signal values to a selected range.
4. The system of claim 3, wherein the buffer comprises a voltage divider.
5. The system of claim 1 , further comprising a controller coupled to the meter and operable to monitor the range of meter output values and to compute a motor commutation time based upon a local minimum meter output value and a local maximum meter output value.
6. The system of claim 5, wherein the motor commutation time is computed based upon an identified phase-to-phase zero-crossing in a back EMF signal.
7. The system of claim 6, wherein the zero crossing is identified when the meter output value is substantially equal to one-half of the difference between the local maximum meter output value and the local minimum meter output value.
8. The system of claim 5, wherein the controller is configured to store a local minimum meter output value and a local maximum meter output value every motor terminal driving cycle.
9. The system of claim 1, further comprising a pulse width modulation (PWM) circuit, wherein the meter is synchronized with the PWM circuit.
10. A system for controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals, comprising: a meter coupled to a motor terminal and adapted to produce a range of output values representative of a motor terminal signal from which a back EMF signal is derivable; and a controller coupled to the meter and operable to monitor the range of meter output values and to compute a motor commutation time based upon a monitored local minimum meter output value and a monitored local maximum meter output value.
11. The system of claim 10, wherein the motor commutation time is computed based upon an identified phase-to-phase zero-crossing in a back EMF signal.
12. The system of claim 11 , wherein the zero crossing is identified when the meter output value is substantially equal to one-half of the difference between the local maximum meter output value and the local minimum meter output value.
13. The system of claim 10, wherein the controller is configured to store a local minimum meter output value and a local maximum meter output value every motor terminal driving cycle.
14. The system of claim 10, further comprising a pulse width modulation (PWM) circuit, wherein the meter is synchronized with the PWM circuit.
15. A system for controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals, comprising: a pulse width modulation (PWM) circuit; and a meter coupled to a motor terminal, synchronized with the PWM circuit and configured to produce an output representative of a motor terminal signal from which a back EMF signal is derivable.
16. The system of claim 15, wherein the meter is adapted to sample motor terminal voltages in a non-conducting motor phase at times when each conducting motor phase is being driven.
17. The system of claim 15, further comprising a controller coupled to the meter and operable to monitor the range of meter output values and to compute a motor commutation time based upon a local minimum meter output value and a local maximum meter output value.
18. The system of claim 17, wherein the motor commutation time is commutated based upon an identified phase-to-phase zero crossing in a back EMF signal.
19. The system of claim 18, wherein the zero crossing is identified when the meter output value is substantially equal to one-half of the difference between the local maximum meter output value and the local minimum meter output value.
20. The system of claim 17, wherein the controller is configured to store a local minimum meter output value and a local maximum meter output value every motor terminal driving cycle. -
21. A method of controlling a polyphase brushless direct current (DC) motor having a plurality of phase windings energizable by timed application of drive voltages to a plurality of motor terminals resulting in back electromotive force (EMF) conditions at the motor terminals, comprising:
monitoring a range of signal values representative of a motor terminal signal from which a back EMF signal is derivable; storing a local maximum signal value and a local minimum signal value over the range of monitored signal values; and computing a motor commutation time based upon the stored local maximum signal value and the stored local minimum value.The method of claim 21, wherein the motor commutation time is computed based upon an identified phase-to-phase zero crossing in a back EMF signal.
22. The method of claim 22, wherein the zero crossing is identified based upon the difference between the stored local maximum signal value and the stored local minimum signal value.
23. The method of claim 23, wherein the zero crossing is identified when the monitored signal value is substantially equal to one-half of the difference between the stored local minimum signal value and the stored local maximum signal value.
24. The method of claim 21 , wherein a monitored local minimum signal value and a monitored local maximum signal value is stored every motor terminal driving cycle.
PCT/US2001/013571 2000-04-25 2001-04-25 Controlling a brushless dc motor WO2001082464A1 (en)

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US6661192B2 (en) 2003-12-09
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JP2003532363A (en) 2003-10-28
AU2001257336A1 (en) 2001-11-07
EP1284044A4 (en) 2006-01-04
US20020195982A1 (en) 2002-12-26

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