WO2000031862A2 - Method for controlling a rectifier circuit and corresponding rectifier circuit - Google Patents
Method for controlling a rectifier circuit and corresponding rectifier circuit Download PDFInfo
- Publication number
- WO2000031862A2 WO2000031862A2 PCT/DK1999/000651 DK9900651W WO0031862A2 WO 2000031862 A2 WO2000031862 A2 WO 2000031862A2 DK 9900651 W DK9900651 W DK 9900651W WO 0031862 A2 WO0031862 A2 WO 0031862A2
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- load
- voltage
- rectifier
- switch
- phase shift
- Prior art date
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the invention relates to a method for controlling a rectifier circuit with a rectifier and a load, in which at least one switch for controlled maintenance of a current flow through the rectifier is actuated and the signal necessary for actuation is generated with the aid of a DC voltage signal which is generated from the voltage above the Load is determined.
- the invention further relates to a rectifier circuit with a rectifier in series with an inductor, a diode and a load, in which a capacitor is arranged in parallel with the load and a controlled switch is connected in parallel with the series connection of diode and load, which switch is connected to a control device which generates a control signal with the aid of the voltage across the load, and a rectifier circuit with a rectifier which is arranged in parallel with a capacitance and with a load and whose input is connected to an inductor, a switch arrangement being connected to the inductor, which has at least one controlled switch which is connected to a control device which generates a control signal using the voltage across the load.
- the voltage across the load ie a smoothed DC voltage
- This DC voltage is divided and then compared with a reference voltage.
- the difference between the reference voltage and the voltage applied to the load or the corresponding part is a criterion for when the switch must be actuated.
- At the input of the rectifier there is a current profile that is approximately trapezoidal, i.e. the current remains constant outside of a rising edge and a falling edge. This reduces the harmonics in the current and increases the efficiency.
- the object of the invention is to further improve the efficiency.
- This object is achieved in a method of the type mentioned at the outset by superimposing an AC voltage signal on the DC voltage signal, the frequency of which corresponds to the frequency of the ripple at the output of the rectifier and which has a phase difference to the ripple that is smaller than a predetermined measure .
- the stationary case is first considered, in which there is no large changes.
- the voltage signal used to control the switch is therefore constant.
- the current at the input of the rectifier is then constant except for short sections at the beginning and end of each half-wave. If one superimposes an alternating voltage signal on the direct voltage obtained from the load voltage, the frequency of which corresponds to the ripple at the output of the rectifier and the phase position of which also, if not exactly, corresponds to the phase position of the ripple at the output of the rectifier, then one obtains one Control signal which has a ripple in synchronism with the ripple of the rectifier output voltage.
- the AC voltage signal is preferably obtained with the aid of the voltage across the load.
- the load voltage is used twice, namely on the one hand to obtain a criterion for when the switch should be actuated and on the other hand to obtain the AC voltage signal. A second voltage tap is therefore no longer necessary.
- the voltage across the load is preferably inverted and subjected to a further phase shift by 90 degrees.
- the load is usually connected in parallel with a capacitance, which contributes to smoothing the output voltage of the rectifier.
- This capacitance for example a capacitor, leads to a phase shift of the ripple by 90 degrees. If you invert the voltage across the load, there is a further phase shift of 180 degrees. With a further phase shift of approximately 90 degrees, a phase shift of 360 degrees is achieved overall, or in other words, the phase positions match.
- the deviation from one period is in any case irrelevant in the stationary case. In the case of - load changes, there are usually no major negative effects to fear.
- the phase shift is preferably determined by a
- the switch is kept open in predetermined operating states. This configuration also leads to an improvement in the efficiency if no AC voltage signal is superimposed on the DC voltage signal for controlling the switch. If the switch is kept open, no current flows "unused" past the load. The efficiency increases accordingly.
- the capacitor or the capacitance which is connected in parallel with the load, already causes a phase rotation of the ripple by 90 degrees. If you add another 270 degrees, you get a phase shift of 360 degrees or - in steady operation - a phase shift of zero. The phase positions do not have to match exactly here. It is sufficient if a predetermined difference, for example 15 degrees, is not exceeded. Within such limits, the current profile of a sinusoidal shape is similar enough to keep the harmonic content low. This procedure is largely independent of the specific type of rectifier circuit used.
- the phase shift device preferably has an inverter and a filter.
- the inverter causes a phase shift of 180 degrees.
- the filter is used for the 90 degrees still required. This can be achieved in a simple manner in that the cutoff frequency or the cutoff frequency of the filter is matched to the frequency of the ripple or the alternating component of the voltage across the load in such a way that the corresponding phase shift results.
- the filter is preferably designed as an RC filter.
- Such a filter can be conveniently accommodated, for example, in the feedback of an amplifier that is used as an inverter.
- a load measuring device is provided which deactivates the switch when the load falls below a predetermined value. This load measuring device can also be used without the phase shift device. It has the effect that when the current amplitudes and thus also the amplitudes of the harmonics of the current are small, the power factor correction is switched off.
- Fig. 2 different curves to illustrate current and voltage profiles
- Fig. 3 is a schematic representation of a modified circuit arrangement.
- FIG. 1 shows a circuit arrangement 1 with a rectifier 2, which in the present case is designed as a full-wave rectifier.
- the rectifier 2 is fed by a network 3, for example an AC network with a frequency of 50 Hz and a voltage U1 of, for example, 230 V.
- the current of the network 3 is accordingly an AC II.
- the output of the rectifier 2 is connected to a load 6 via a coil 4 or a corresponding inductor and a diode 5.
- a capacitor 7 or another capacitance is arranged parallel to the load 6.
- the load 6 can be designed more or less arbitrarily. It can also be formed, for example, by an inverter, which in turn feeds an electric motor in a frequency-controlled manner, wherein the motor can be used, for example, to drive a compressor of a small refrigerator.
- the current would charge the capacitor 7 up to the voltage U2. Since the diode 5 only allows the current to pass when the voltage U2 is greater than the voltage U3 across the load or the capacitor 7, there is no uniform flow of the current 12 without additional measures. Rather, this only becomes in the middle of each Half wave flow, which can have negative effects on the mains current II. There are then undesirably high harmonic contents.
- a switch 8 is arranged in parallel to the series connection of diode 5 and the parallel connection of load 6 and capacitor 7, which is controlled by means of a control device 9, i.e. the control device 9 opens and closes the switch.
- a control device 9 opens and closes the switch.
- EP 0 669 703 A2 known. Such a circuit is also referred to as a “boost converter” or “boost converter”.
- the control device 9 has a current detection device 10, which is equipped with an evaluation device 11 connected is.
- the current detection device 10 detects the current through the switch 8.
- control device 9 has a voltage detection device 12 which determines the voltage U3.
- the voltage detection device has a voltage divider 13, which is formed, for example, by two ohmic resistors 14, 15. Accordingly, a voltage U4 is present at the center tap 16 of the voltage divider 13 and is supplied to the inverting input of an amplifier 17.
- the non-inverting input of the amplifier 17 is connected to a reference voltage source 18, which emits a DC voltage.
- a voltage U5 is then established between the inverting input and the non-inverting input of the amplifier 17.
- 2 shows individual voltage and current profiles in different representations.
- 2a shows the line voltage U1 and the line current II over a full period, which is 20 ms at a frequency of 50 Hz.
- the output voltage U2 of the rectifier 2 is also entered, which corresponds to Ul in the first half period.
- Figure 2b shows the voltage U3, i.e. the voltage across the load 6. It can be seen that the voltage U3 is a DC voltage with a ripple which has a frequency twice as high as the voltage U1. The ripple of the voltage U3 is phase-shifted by approximately 90 degrees compared to the ripple of the voltage U2, which is not shown in any more detail. This phase shift results in particular from the capacitance 7.
- Fig. 2c now shows the voltage U5, i.e. the difference between the voltage of the reference voltage source 18 and the voltage U3. This difference is shifted by 180 degrees with respect to the ripple of the voltage U3. 2c shows the voltage U6 at the output 19 of the voltage detection device 12. Because of the RC element, the voltage U6 is again 90 degrees out of phase with the voltage U5. The voltage U6 is thus in phase with the voltage U2 at the output of the rectifier 2.
- the mains current II takes on a shape which, from a rectangular block or trapezoidal block, as is known from EP 0 669 703 A2, more closely approximates a sinusoidal shape, as is the case with this 2a can be seen. It is not absolutely necessary here that the current II is exactly in phase with the voltage Ul. Accordingly, it is not necessary derlich that the voltage U6 is exactly in phase with the voltage U2. Smaller deviations of 15 degrees, for example, are entirely permissible. However, by approximating the current II to a sinusoidal curve, the harmonic content of the current II can be further reduced.
- a further current detection device 21 is arranged in the line between the load 6 and the rectifier 2. If the current detector 21 determines that the load drops below a predetermined value, then the switch 8 can be deactivated, i.e. it remains permanently open. This has the advantage that no electricity is wasted. The resulting higher harmonic content of the mains current II can be accepted, because with low amplitudes of the mains current II the amplitudes of the harmonics also remain correspondingly small.
- Fig. 3 shows an alternative embodiment in which the same parts as in Fig. 1 are provided with the same reference numerals and corresponding parts with deleted reference numerals.
- the coil 4 ' is arranged in front of the rectifier, which can be formed, for example, by two diodes D1, D2.
- the switch 8 has been replaced by two switches 8 ', 8 ", which are also controlled by the control device 9', in the same way as the switch 8 in the circuit arrangement according to FIG. 1. 3, the rectifier and the step-up converter are therefore combined. This requires fewer components and a more compact design. In addition, the advantages of this circuit are that there are fewer line losses. In the circuit arrangement according to FIG. 3 there are only two diode sections in the rectifier, and the diode 5 is omitted. Furthermore, the coil 4 'can now be designed for alternating current. A design for direct current with ripple, as in the embodiment according to FIG. 1, is not necessary.
- switches 8 ', 8 are connected to diodes Da, Db in parallel.
- switches with diodes are available on the market as ready-made MOSFETs. These diodes are often already in the form of parasitic diodes.
- the comparator device 20 should now have two outputs in order to be able to control both switches 8 1 , 8 ".
- the two switches 8 ', 8" can be clocked synchronously.
- sequential control is also possible: If the first half-wave D1 is made conductive, the switch 8 'is switched. In the other half-wave, which acts on D2, the switch 8 "is clocked.
- the current sensor 21 ' can be used as the current sensor.
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
Abstract
Description
Claims
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
AU13755/00A AU1375500A (en) | 1998-11-26 | 1999-11-25 | Method for controlling a rectifier circuit and corresponding rectifier circuit |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE19854567A DE19854567A1 (en) | 1998-11-26 | 1998-11-26 | Method of controlling a rectifier circuit and rectifier circuit |
DE19854567.3 | 1998-11-26 |
Publications (2)
Publication Number | Publication Date |
---|---|
WO2000031862A2 true WO2000031862A2 (en) | 2000-06-02 |
WO2000031862A3 WO2000031862A3 (en) | 2000-08-17 |
Family
ID=7889093
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/DK1999/000651 WO2000031862A2 (en) | 1998-11-26 | 1999-11-25 | Method for controlling a rectifier circuit and corresponding rectifier circuit |
Country Status (3)
Country | Link |
---|---|
AU (1) | AU1375500A (en) |
DE (1) | DE19854567A1 (en) |
WO (1) | WO2000031862A2 (en) |
Families Citing this family (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5834217B2 (en) * | 2009-04-13 | 2015-12-16 | パナソニックIpマネジメント株式会社 | DC power supply device and application system |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4789818A (en) * | 1985-06-18 | 1988-12-06 | Fuji Electric Co., Ltd. | DC voltage converter |
EP0387435A1 (en) * | 1988-01-11 | 1990-09-19 | Farnell Instruments Limited | Control arrangement for a switched mode power supply |
EP0599000A1 (en) * | 1992-11-20 | 1994-06-01 | Matsushita Electric Works, Ltd. | Power supply |
EP0669703A2 (en) * | 1994-01-28 | 1995-08-30 | Matsushita Electric Industrial Co., Ltd. | AC-DC converter |
US5751567A (en) * | 1996-01-12 | 1998-05-12 | Fuji Electric Co., Ltd. | AC-DC converter |
Family Cites Families (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5235504A (en) * | 1991-03-15 | 1993-08-10 | Emerson Electric Co. | High power-factor converter for motor drives and power supplies |
DE69525441T2 (en) * | 1995-03-16 | 2002-07-11 | Franklin Electric Co Inc | Power Factor Correction |
US5747977A (en) * | 1995-03-30 | 1998-05-05 | Micro Linear Corporation | Switching regulator having low power mode responsive to load power consumption |
US5912549A (en) * | 1997-08-01 | 1999-06-15 | Lucent Technologies Inc. | Current mode controller for continuous conduction mode power factor correction circuit and method of operation thereof |
-
1998
- 1998-11-26 DE DE19854567A patent/DE19854567A1/en not_active Withdrawn
-
1999
- 1999-11-25 AU AU13755/00A patent/AU1375500A/en not_active Abandoned
- 1999-11-25 WO PCT/DK1999/000651 patent/WO2000031862A2/en active Application Filing
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4789818A (en) * | 1985-06-18 | 1988-12-06 | Fuji Electric Co., Ltd. | DC voltage converter |
EP0387435A1 (en) * | 1988-01-11 | 1990-09-19 | Farnell Instruments Limited | Control arrangement for a switched mode power supply |
EP0599000A1 (en) * | 1992-11-20 | 1994-06-01 | Matsushita Electric Works, Ltd. | Power supply |
EP0669703A2 (en) * | 1994-01-28 | 1995-08-30 | Matsushita Electric Industrial Co., Ltd. | AC-DC converter |
US5751567A (en) * | 1996-01-12 | 1998-05-12 | Fuji Electric Co., Ltd. | AC-DC converter |
Also Published As
Publication number | Publication date |
---|---|
AU1375500A (en) | 2000-06-13 |
WO2000031862A3 (en) | 2000-08-17 |
DE19854567A1 (en) | 2000-06-08 |
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