US9219317B1 - Delivering both sum and difference beam distributions to a planar monopulse antenna array - Google Patents
Delivering both sum and difference beam distributions to a planar monopulse antenna array Download PDFInfo
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- US9219317B1 US9219317B1 US13/556,348 US201213556348A US9219317B1 US 9219317 B1 US9219317 B1 US 9219317B1 US 201213556348 A US201213556348 A US 201213556348A US 9219317 B1 US9219317 B1 US 9219317B1
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- 238000009826 distribution Methods 0.000 title claims abstract description 62
- 239000011159 matrix material Substances 0.000 claims abstract description 29
- RYGMFSIKBFXOCR-UHFFFAOYSA-N Copper Chemical compound [Cu] RYGMFSIKBFXOCR-UHFFFAOYSA-N 0.000 description 4
- 238000003491 array Methods 0.000 description 4
- 238000005253 cladding Methods 0.000 description 4
- 229910052802 copper Inorganic materials 0.000 description 4
- 239000010949 copper Substances 0.000 description 4
- 238000000926 separation method Methods 0.000 description 3
- 238000013459 approach Methods 0.000 description 2
- 238000010276 construction Methods 0.000 description 2
- 238000007796 conventional method Methods 0.000 description 2
- 238000013461 design Methods 0.000 description 2
- 238000003780 insertion Methods 0.000 description 2
- 230000037431 insertion Effects 0.000 description 2
- 239000000463 material Substances 0.000 description 2
- 241000321453 Paranthias colonus Species 0.000 description 1
- 230000003321 amplification Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 238000005457 optimization Methods 0.000 description 1
- 238000007493 shaping process Methods 0.000 description 1
- 238000012546 transfer Methods 0.000 description 1
- 230000007704 transition Effects 0.000 description 1
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
- H01Q25/02—Antennas or antenna systems providing at least two radiating patterns providing sum and difference patterns
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/0006—Particular feeding systems
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/0006—Particular feeding systems
- H01Q21/0075—Stripline fed arrays
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
Definitions
- the present work relates generally to monopulse radar systems and, more particularly, to feed networks driving monopulse radar antenna arrangements.
- Monopulse radar functionality is implemented with parabolic reflector antennas having waveguide comparators at their feed locations.
- planar patch antenna arrays rather than relying solely on dish antennas.
- Low SLLs on the order of 30 dB, have been realized with planar patch array technology over a 20% fractional bandwidth.
- planar patch arrays are typically single port antennas with only a boresighted sum beam based on Taylor weights.
- FIG. 1 diagrammatically illustrates a monopulse radar system according to example embodiments of the present work.
- FIG. 2 diagrammatically illustrates the distribution network of FIG. 1 in more detail according to example embodiments of the present work.
- FIG. 3 diagrammatically illustrates a conventional example of the crossover components of FIG. 2 .
- FIG. 4 diagrammatically illustrates the comparator components of FIG. 2 according to example embodiments of the present work.
- FIG. 5 diagrammatically illustrates the distribution network of FIG. 2 , constructed with the stripline components of FIGS. 3 and 4 according to example embodiments of the present work.
- FIG. 6 is a cross-sectional view showing a laminar structure used according to example embodiments of the present work to realize a planar stripline network such as shown in FIG. 5 .
- FIG. 7 diagrammatically illustrates a network, according to example embodiments of the present work, which is similar to that of FIG. 2 , but with more ports and correspondingly more crossover and comparator components.
- FIG. 8 is similar to FIG. 5 , diagrammatically illustrating the distribution network of FIG. 7 , constructed with the stripline components of FIGS. 3 and 4 according to example embodiments of the present work.
- FIG. 9 diagrammatically illustrates a network, according to example embodiments of the present work, which is similar to that of FIG. 7 , but with more ports and correspondingly more crossover and comparator components.
- FIG. 10 is similar to FIG. 8 , diagrammatically illustrating the distribution network of FIG. 9 , constructed with the stripline components of FIGS. 3 and 4 according to example embodiments of the present work.
- Example embodiments of the present work provide a planar monopulse radar apparatus including a distribution matrix coupled to an antenna array.
- the distribution matrix receives weights (e.g., Taylor weights) associated with a sum pattern and weights (e.g., Bayliss weights) associated with a difference pattern, and delivers both sum and difference beam distributions across the antenna array.
- the distribution matrix includes a plurality of 0°/180° comparator components, and a plurality of crossover components. These components collectively form a passive, planar network that distributes the sum and difference pattern weights in-plane to the antenna array.
- the capability of delivering either the sum or difference distribution to the antenna array advantageously allows the antenna array to achieve low SLLs in both its sum and difference beam patterns.
- FIG. 1 diagrammatically illustrates a monopulse radar system according to example embodiments of the present work.
- a feed network is coupled between two input ports (port 1 and port 2 ) and an arrangement of N antennas.
- the feed network includes a 1 ⁇ N/2 Taylor splitter, a 1 ⁇ N/2 Bayliss splitter, and a distribution matrix (also referred to herein as a distribution network) having N inputs and N outputs.
- the distribution matrix provides channels that transfer Taylor and Bayliss weights from the respectively associated splitters to the N antenna elements.
- the Taylor and Bayliss splitters, and the antenna arrangement are provided with planar constructions, as is known in the art.
- the distribution matrix is also provided as a planar structure, as described in detail below.
- the splitters and the distribution matrix are provided as stripline constructions.
- FIG. 2 diagrammatically illustrates the distribution matrix (also referred to herein as distribution network) of FIG. 1 in more detail according to example embodiments of the present work.
- two crossover components 21 and two 0°/180° comparator components 23 collectively deliver two Bayliss weights (B 1 and B 2 ) and two Taylor weights (T 1 and T 2 ) from four input ports at 25 to a linear antenna array of four antenna elements A 1 -A 4 associated with four output ports at 27 .
- all ports of FIG. 2 are matched to 50 ⁇ .
- the arrangement of FIG. 2 operates as follows.
- the B 1 weight propagates to A 2 and A 3 , where A 2 and A 3 have the same magnitude but are 180° out of phase; and the B 2 weight propagates to A 1 and A 4 , where A 1 and A 4 have the same magnitude but are 180° out of phase.
- the T 1 weight propagates to A 1 and A 4 , where A 1 and A 4 have the same magnitude and are in-phase; and the T 2 weight propagates to A 2 and A 3 , where A 2 and A 3 have the same magnitude and are in-phase.
- FIG. 3 An example of the crossover 21 is diagrammatically illustrated in FIG. 3 .
- the crossover of FIG. 3 is a planar stripline component, constructed with two double-box 90° branchline couplers cascaded as shown.
- the double-box configuration is known in the art and commonly used in order to obtain wider bandwidths. (Some embodiments have a bandwidth of 9.2 GHz to 10.5 GHz.)
- Power input at ports 1 , 2 , 3 , and 4 (ideally) exits at ports 4 , 3 , 2 and 1 , respectively.
- power input at port 1 crosses with power input from port 2 in-plane, without requiring any vertical transition.
- FIG. 4 diagrammatically illustrates an example of the 0°/180° comparator 23 according to the present work.
- the comparator of FIG. 4 is a planar stripline component, constructed with a conventional double-box 90° branchline coupler 41 , cascaded with a phase shifter 43 that includes a conventional Schiffman loop 45 .
- Power input at port 1 exits at port 2 and port 4 , as does power input at port 3 .
- the double-box coupler configuration supports relatively wider bandwidth operation.
- the Schiffman loop structure 45 has an electrical path length that is 90° less than that of the meandering line section shown at 47 .
- the Schiffman loop 45 contains highly-coupled lengths of transmission line that create an S-shaped phase response, as is conventional.
- the 180°-differing phase delay profiles of both the Schiffman loop branch 48 and the meandering line branch 49 may be maintained substantially parallel to one another, thus enabling operation over relatively wide bandwidths.
- the trace widths of the stripline components illustrated in FIGS. 3 and 4 may be tailored to the desired range of frequency operation, as is conventional.
- Various embodiments include design features associated with conventional techniques. For example, FIG. 4 shows that a small section of line with significantly narrowed width (near port 2 ) may be provided according to conventional techniques to achieve a desired matching characteristic.
- the comparator component of FIG. 4 (minus the chamfered 90° bends at each port) has the same length as the crossover component of FIG. 3 , namely 33.5 mm.
- the legs of the comparator (adjacent the chamfered bends near each port in FIG. 4 ) are separated by a leg separation distance of 6.7 mm, which is the same as the leg separation distance of the crossover component of FIG. 3 .
- the four ports of the comparator component of FIG. 4 fit into the same-sized footprint as the four ports of the crossover component of FIG. 3 . This characteristic provides network creation simplicity.
- FIG. 5 shows at 51 the distribution network of FIG. 2 , constructed with the stripline components of FIGS. 3 and 4 , according to example embodiments of the present work.
- the crossovers 21 are oriented to extend generally transversely to the direction of power propagation. This orientation minimizes the various path lengths in order to decrease the insertion losses.
- the Bayliss weights B 1 and B 2 are respectively applied to port 1 and port 2
- the Taylor weights T 1 and T 2 are respectively applied to port 3 and port 4 .
- the separation between adjacent ports, on both the input side (port 1 -port 4 ) and the output side (port 5 -port 8 ), is set to 20.915 mm, to avoid grating lobes during X-band operation.
- FIG. 6 is a cross-sectional view showing a laminar structure used according to example embodiments of the present work to realize a planar stripline network such as shown at 51 in FIG. 5 .
- the network is constructed with stripline components such as shown in FIGS. 3 and 4 according to example embodiments of the present work.
- first and second identical layers each constructed of 31 mil thick RT/Duroid 5800 material between one ounce copper cladding on its opposite surfaces
- the copper cladding is stripped completely from one surface of the first layer, and the copper cladding on one surface of the second layer is etched to produce the distribution network (e.g., the network 51 of FIG. 5 ).
- the first and second layers are bonded together with the stripped surface of the first layer facing the etched surface of the second layer.
- Some embodiments use a 1.5 mil Arlon bonding film as shown in FIG. 6 .
- Copper cladding is provided respectively on the opposite outer surfaces of the laminar structure to define ground planes as shown.
- FIG. 7 diagrammatically illustrates a distribution network similar to that of FIG. 2 , but with eight input ports and eight output (antenna) ports. Here twelve crossovers 21 are needed to accomplish the proper phasing at the antenna ports.
- FIG. 8 is similar to FIG. 5 , but shows the larger network of FIG. 7 constructed with the stripline components of FIGS. 3 and 4 .
- port 1 -port 4 are respectively driven with the Bayliss weights B 1 -B 4 shown in FIG. 7
- port 5 -port 8 are respectively driven with the Taylor weights T 1 -T 4 shown in FIG. 7
- port 9 -port 16 respectively correspond to the antenna outputs shown at A 1 -A 8 in FIG. 7 .
- FIG. 8 One advantage of the aforementioned matching footprints of the FIG. 3 crossover and the FIG. 4 comparator is demonstrated clearly in FIG. 8 . More particularly, along any insertion path in FIG. 8 , the number and type of components that the power traverses are either the same or equivalent.
- power that propagates from port 1 to port 12 traverses a long line 81 , transverse adjuster 82 , three consecutive crossovers 21 , a comparator 23 , and another transverse adjuster 82 , in that order.
- power that propagates from port 3 to port 15 traverses a medium length line 83 , a transverse adjuster 82 , a crossover 21 , a comparator 23 , two consecutive crossovers 21 , a transverse adjuster 84 , and another medium length line 83 , in that order.
- Both paths contain three crossovers, one comparator, and two transverse adjusters.
- the port 1 ⁇ port 12 path contains one long line 81
- the port 3 ⁇ port 15 path contains two medium-length lines 83 .
- the sum of the lengths of two medium-length lines 83 is equal to the length of a long line 81 .
- the two paths are equivalent in phase length. This is true for any of the other paths as well.
- power input at any of port 1 -port 4 traverses two different paths having respectively different phase lengths that respectively correspond to the branches 48 and 49 .
- power input at port 1 in FIG. 8 exits at both port 12 and port 13 , where port 12 and port 13 are 180° out of phase with one another.
- the footprint match between the FIG. 3 crossover and the FIG. 4 comparator becomes increasingly important with larger networks such as FIG. 8 , inasmuch as they are difficult to simulate accurately or, in some cases, at all.
- FIG. 9 diagrammatically illustrates a distribution network similar to those of FIGS. 2 and 7 , but with 16 input ports and 16 output (antenna) ports.
- 56 crossovers 21 are required to accomplish the proper phasing at the antennas A 1 -A 16 .
- FIG. 10 is similar to FIGS. 5 and 8 , but shows the larger network of FIG. 9 constructed with the stripline components of FIGS. 3 and 4 .
- the Bayliss weights B 1 -B 8 of FIG. 9 are respectively applied to port 1 -port 8 of FIG. 10
- the Taylor weights T 1 -T 8 of FIG. 9 are respectively applied to port 9 -port 16 of FIG. 10
- the network examples described above according to the present work use crossover components similar to those found in conventional Butler matrices commonly used for discrete beam steering.
- the phasings for the Bayliss/Taylor networks of the present work are different from those of a Butler matrix.
- a linear phase front is achieved across the antenna elements for proper beam pointing.
- a network such as shown in FIGS. 9 and 10 provides an equal-phase front over A 1 to A 16 when the T 1 -T 8 Taylor weights are excited and the B 1 -B 8 ports are terminated to 50 ⁇ .
- some embodiments use a two-dimensional antenna array, wherein the N antennas shown in FIG. 1 are replaced by N linear antenna arrays, respectively.
- the Bayliss and Taylor aperture distributions can be realized along both orthogonal dimensions of the resulting two-dimensional antenna array by providing: (1) N distributors (i.e., N Bayliss/Taylor distribution networks), one for each of the N linear antenna arrays; and (2) one additional distributor to combine the N combinations of linear antenna array/distributor.
Abstract
Description
Similarly, the number of crossover components 21 (also referred to as simply, crossovers) needed is
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Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
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CN111428428A (en) * | 2020-04-17 | 2020-07-17 | 无锡威孚高科技集团股份有限公司 | Design method of weighted linear array antenna |
Citations (5)
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US4595926A (en) * | 1983-12-01 | 1986-06-17 | The United States Of America As Represented By The Secretary Of The Army | Dual space fed parallel plate lens antenna beamforming system |
US4618831A (en) * | 1984-09-25 | 1986-10-21 | Nippon Telegraph & Telephone Corporation | Power amplifying apparatus |
US5612702A (en) * | 1994-04-05 | 1997-03-18 | Sensis Corporation | Dual-plane monopulse antenna |
US20050035825A1 (en) * | 2003-07-18 | 2005-02-17 | Carson James Crawford | Double-sided, edge-mounted stripline signal processing modules and modular network |
US20110248796A1 (en) * | 2010-04-09 | 2011-10-13 | Raytheon Company | Rf feed network for modular active aperture electronically steered arrays |
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2012
- 2012-07-24 US US13/556,348 patent/US9219317B1/en active Active
Patent Citations (6)
Publication number | Priority date | Publication date | Assignee | Title |
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US4595926A (en) * | 1983-12-01 | 1986-06-17 | The United States Of America As Represented By The Secretary Of The Army | Dual space fed parallel plate lens antenna beamforming system |
US4618831A (en) * | 1984-09-25 | 1986-10-21 | Nippon Telegraph & Telephone Corporation | Power amplifying apparatus |
US4618831B1 (en) * | 1984-09-25 | 1997-01-07 | Nippon Telegraph & Telephone | Power amplifying apparatus |
US5612702A (en) * | 1994-04-05 | 1997-03-18 | Sensis Corporation | Dual-plane monopulse antenna |
US20050035825A1 (en) * | 2003-07-18 | 2005-02-17 | Carson James Crawford | Double-sided, edge-mounted stripline signal processing modules and modular network |
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Non-Patent Citations (3)
Title |
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M. Alvarez-Folgueiras et al., Synthesising Taylor and Bayliss Linear Distributions with Common Aperture Tail, Electronics Letters Jan. 1, 2009, vol. 45, No. 1 (2 pages). |
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Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN111428428A (en) * | 2020-04-17 | 2020-07-17 | 无锡威孚高科技集团股份有限公司 | Design method of weighted linear array antenna |
CN111428428B (en) * | 2020-04-17 | 2023-09-08 | 无锡威孚高科技集团股份有限公司 | Design method of weighted linear array antenna |
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