US8971450B2 - Transmission device, reception device, transmission method and reception method for wireless communication system - Google Patents
Transmission device, reception device, transmission method and reception method for wireless communication system Download PDFInfo
- Publication number
- US8971450B2 US8971450B2 US13/297,862 US201113297862A US8971450B2 US 8971450 B2 US8971450 B2 US 8971450B2 US 201113297862 A US201113297862 A US 201113297862A US 8971450 B2 US8971450 B2 US 8971450B2
- Authority
- US
- United States
- Prior art keywords
- symbol
- bit
- phase rotation
- complex variable
- number part
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active, expires
Links
Images
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/20—Modulator circuits; Transmitter circuits
- H04L27/2032—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner
- H04L27/2053—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases
- H04L27/206—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers
- H04L27/2067—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers with more than two phase states
Definitions
- the present invention relates to wireless communication and, more particularly, to a transmission device, a reception device, a transmission method, and a reception method for a wireless communication system.
- a communication system such as a wireless body area network (WBAN) for radio communication between an implant device implanted in a human body and a device outside the human body increasingly requires to have high sensitivity and consume less power.
- WBAN wireless body area network
- phase shift keying having excellent spectrum efficiency and reception performance is commonly used for a recent communication scheme.
- This method is disadvantageous in which it can hardly obtain low power consumption due to a spectrum distortion generated from a non-linear element and has a limitation in realizing a high speed data transmission between implant devices within a human body due to a limitation in a reception performance.
- an object of the present invention is to provide a transmission device and transmission method having high power efficiency and a reception device and reception method capable of providing high reception performance.
- a transmission device including: a serial-to-parallel converter configured to convert an input serial bit stream into a parallel bit stream having three bits; and a phase rotation symbol mapper configured to map the parallel bit stream to a symbol having phase rotation characteristics, wherein when the parallel bit stream includes first to third bits, the phase rotation symbol mapper sequentially maps the second and third bits to a complex variable and sequentially maps a real number part and an imaginary number part of the complex variable to the front part and the rear part of a symbol in this order or to the rear part and the front part of the symbol in this order.
- the phase rotation symbol mapper may map the real number part of the complex variable to the front half of the symbol and the imaginary number part of the complex variable to the rear half part of the symbol.
- the phase rotation symbol mapper may map the real number part of the complex variable to the rear half of the symbol and the imaginary number part of the complex variable to the front half of the symbol.
- the transmission device may further include: an upsampler configured to receive a symbol having the phase rotation characteristics and it performs upsampling from the received symbol; a transmission filter configured to filter the upsampled symbol; a digital-to-analog converter (DAC) configured to convert the filtered symbol into an analog signal; and a quadrature modulation unit configured to quadrature-modulate the converted analog signal.
- an upsampler configured to receive a symbol having the phase rotation characteristics and it performs upsampling from the received symbol
- a transmission filter configured to filter the upsampled symbol
- DAC digital-to-analog converter
- quadrature modulation unit configured to quadrature-modulate the converted analog signal.
- the transmission filter may include a square root raised cosine filter.
- a transmission method of a transmission device in a wireless communication system including: receiving an input bit stream; grouping the input bit stream into a parallel bit stream having three bits; and mapping the parallel bit stream into a symbol having phase rotation characteristics to generate a phase rotation symbol, wherein, in the generating of the phase rotation symbol, when the parallel bit stream includes first to third bits, the second and third bits are mapped to a complex variable, and a real number part and an imaginary number part of the complex variable are sequentially mapped to the front part and the rear part of a symbol in this order or to the rear part and the front part of the symbol in this order.
- the real number part of the complex variable may be mapped to the front half of the symbol and the imaginary number part of the complex variable may be mapped to the rear part of the symbol.
- the real number part of the complex variable may be mapped to the front half of the symbol and the imaginary number part of the complex variable may be mapped to the front half of the symbol.
- the transmission method may further include: receiving the phase rotation symbol and upsampling the symbol; filtering the upsampled symbol; converting the filtered symbol into an analog signal; and quadrature-modulating the converted analog signal.
- a reception device including: a synchronization unit configured to sample first and second sample values at a time interval of 1 ⁇ 2 of a symbol period with respect to one symbol from a reception signal in which three bits are mapped to one symbol; an exchanging unit configured to exchange imaginary number parts of the first and second sample values; a comparison unit configured to compare absolute values of the first and second sample values whose imaginary number parts have been exchanged by the exchanging unit; and a signal detection unit configured to restore the three bits on the basis of the results of the comparison unit.
- the signal detection unit may restore the first bit among the three bits into 0.
- the signal detection unit may restore the first bit among the three bits into 1.
- the signal detection unit may restore the second and third bits among the three bits on the basis of a sample value having a greater absolute value among the first and second sample values whose imaginary number parts have been exchanged.
- the reception device may further include: a quadrature demodulator configured to quadrature-demodulating a reception signal; an analog-to-digital converter (ADC) configured to convert the quadrature-demodulated reception signal into a digital signal; a matching filter configured to filter the converted digital signal and transmit the filtered signal to the synchronization unit; and a parallel-to-serial converter configured to receive a plurality of bits in parallel from the signal detection unit and convert the received parallel bits into serial bits.
- ADC analog-to-digital converter
- a reception method including: sampling first and second sample values at a time interval of 1 ⁇ 2 of a symbol period with respect to one symbol from a reception signal in which three bits are mapped to one symbol; exchanging imaginary number parts of the first and second sample values; comparing absolute values of the first and second sample values whose imaginary number parts have been exchanged; and restoring the three bits on the basis of the comparison results.
- the first bit among the three bits may be restored into 0.
- the first bit among the three bits may be restored into 1.
- the second and third bits among the three bits may be restored on the basis of a sample value having a greater absolute value among the first and second sample values whose imaginary number parts have been exchanged.
- a signal distortion due to non-linear characteristics generated from phase shift keying in a wireless communication system can be reduced.
- QPSK quadrature phase shift keying
- 1.3 dB reception performance can be improved in terms of performance and power back-off characteristics of about 0.6 dB can be improved in terms of transmission power.
- the reception device having such advantages can be implemented without increasing complexity compared with the structure of the existing reception device.
- FIG. 1 is a schematic block diagram of a transmission device according to an exemplary embodiment of the present invention.
- FIG. 2 is a view for explaining a phase rotation symbol modulation (generation) method performed in a phase rotation symbol mapper.
- FIG. 3 is a flow chart illustrating the process of a transmission method in a wireless communication system according to an exemplary embodiment of the present invention.
- FIG. 4 is a view showing constellation points according to a transmission output signal of a transmission device according to phase rotation shift keying (PRSK).
- PRSK phase rotation shift keying
- FIG. 5( a ) is a graph of a transmission output signal of quadrature phase shift keying (QPSK) by using a scatter diagram
- FIG. 5( b ) is a graph of a transmission output signal according to PRK by using PRSK according to an exemplary embodiment of the present invention.
- QPSK quadrature phase shift keying
- FIG. 6 is a graph of locus of transmission output signals of APSK through a signal trajectory diagram on a complex number plane.
- FIG. 7 is a graph of locus of transmission output signals of PRSK through a signal trajectory diagram on a complex number plane according to an exemplary embodiment of the present invention.
- FIG. 8 is a graph showing the comparison of a frequency spectrum distortion phenomenon by a non-linear device through a spectrum diagram.
- FIG. 9 is a schematic block diagram of a reception device of a PRSK scheme according to an exemplary embodiment of the present invention.
- FIG. 10 is a flow chart illustrating the process of a reception method according to an exemplary embodiment of the present invention.
- FIG. 11 is a graph showing the comparison between bit error rate (BER) performance according to white noise between the PRSK scheme according to an exemplary embodiment of the present invention and other schemes such as the existing QPSK, MSK and DQPSK.
- BER bit error rate
- FIG. 1 is a schematic block diagram of a transmission device according to an exemplary embodiment of the present invention.
- the transmission device includes a serial-to-parallel converter 100 , a phase rotation symbol mapper 110 , upsamplers 120 - 1 and 120 - 2 , transmission filters 130 - 1 and 130 - 2 , digital-to-analog converters (D/As) 140 - 1 and 140 - 2 , and a quadrature modulation unit 150 .
- serial-to-parallel converter 100 the transmission device includes a serial-to-parallel converter 100 , a phase rotation symbol mapper 110 , upsamplers 120 - 1 and 120 - 2 , transmission filters 130 - 1 and 130 - 2 , digital-to-analog converters (D/As) 140 - 1 and 140 - 2 , and a quadrature modulation unit 150 .
- D/As digital-to-analog converters
- the serial-to-parallel converter 100 performs parallel processing to map an input bit stream ⁇ a n ⁇ to a symbol.
- the phase rotation symbol mapper 110 receives the three grouped bits (which will be indicated as ⁇ a 3n , a 3n+1 , a 3n+2 ⁇ ) and generates (or modulates) a symbol having phase rotation characteristics.
- a phase rotation symbol modulation method performed by the phase rotation symbol mapper will now be described.
- FIG. 2 is a view for explaining a phase rotation symbol modulation (generation) method performed in a phase rotation symbol mapper. Such a method may be called phase rotation shift keying (PRSK).
- PRSK phase rotation shift keying
- the input bit stream input to the serial-to-parallel converter 100 is, for example, “010111100001111001100010”, as mentioned above, the input bit stream is grouped into three bits through the serial-to-parallel converter 100 .
- the lower two bits among the grouped bits are mapped to a gray-coded complex number secondary plane having four phases so as to be generated as a complex variable ⁇ A n ⁇ .
- Complex variables and phase values according to the pattern of the lower two bits may be set as shown in Table 1 below.
- the phase rotation symbol mapper 110 generates mutually differentiated symbols according to the first bit ⁇ a 3n ⁇ among the three bits ⁇ a 3n , a 3n+1 , a 3n+2 ⁇ . Namely, the phase rotation symbol mapper 110 determines which of a real number part and an imaginary number part of the complex variable ⁇ A n ⁇ is to be disposed on a front part or a rear part in a time domain on the basis of the center (namely, ⁇ T s /2 ⁇ ) of a time period of a symbol according to the first bit value of the three bits.
- the phase rotation symbol mapper 110 positions the real number part of the complex variable ⁇ A n ⁇ at the front part of the symbol based on ⁇ T s /2 ⁇ of the symbol and the imaginary number part of the complex variable ⁇ A n ⁇ at the rear part of the symbol.
- the phase rotation symbol mapper 110 positions the imaginary number part of the complex variable ⁇ A n ⁇ at the front part of the symbol based on ⁇ T s /2 ⁇ of the symbol and the real number part of the complex variable ⁇ A n ⁇ at the rear part of the symbol.
- the symbol generated through this process is called a phase rotation coded symbol.
- the phase rotation coded symbol will be indicated as ⁇ d n ⁇ .
- phase rotation coded symbol ⁇ d n ⁇ is upsampled by the upsamplers 120 - 2 and 120 - 2 .
- the transmission filters 130 - 1 and 130 - 2 receive the upsampled signal and generates filtered signals ⁇ d i,k , d q,k ⁇ .
- a transmission filter and a roll-off factor ⁇ which may be able to minimize intra-symbol interference must be selected.
- the transmission filter 130 for example, a square root raised cosine (SRRC) filter may be used.
- the roll-off factor ⁇ for minimizing intra-symbol interference 1 may be set.
- time period characteristics of the transmission filter 130 must be performed as a half period T p of the symbol as represented by Equation 2 shown below, rather than the symbol period T s .
- T p T s /2 [Equation 2]
- the transmission filters 130 - 1 and 130 - 2 may be represented by Equation 3 shown below:
- the D/A 140 converts the digital signals into analog signals. Namely, the D/A 140 converts the ⁇ d 1,k , d q,k ⁇ having a digital signal form into analog signals having waveforms of ⁇ d i (t), d q (t) ⁇ as shown in FIG. 2 .
- the quadrature modulation unit 150 quadrature-modulates the analog signals to generate a transmission signal.
- Equation 4 Re ⁇ c ⁇ indicates a real number part of the complex variable c and Im ⁇ c ⁇ indicates an imaginary number part of the complex variable c.
- ⁇ a 3n ⁇ is the first bit among the three bits input to the phase rotation symbol mapper 110
- ⁇ f c ⁇ is a radio carrier frequency
- ⁇ (t) ⁇ is a transmission filter defined in Equation 3
- FIG. 3 is a flow chart illustrating the process of a transmission method in a wireless communication system according to an exemplary embodiment of the present invention.
- the transmission device groups an input bit stream into 3-bit units (step S 110 ). Two lower bits of the grouped three bits are mapped to a complex number plane to generate a complex variable (step S 120 ). The real number part and imaginary number part of the complex variable are mapped to a front or rear part of a symbol according to the initial first bit of the grouped three bits to generate a phase rotation coded symbol (step S 130 ). The phase rotation coded symbol is upsampled (step S 140 ) and then transmission-shaping-filtered (step S 150 ). The filtered signal is converted into an analog signal (step S 160 ), and the converted analog signal is quadrature-modulated (step S 170 ).
- the transmission device implementing this transmission method has been described above with reference to FIGS. 1 and 2 .
- FIG. 4 is a view showing constellation points according to a transmission output signal of a transmission device according to phase rotation shift keying (PRSK).
- PRSK phase rotation shift keying
- the phase is rotated by ( ⁇ /2) or ( ⁇ /2) ⁇ from a real number axis or an imaginary number axis at every symbol.
- the phase is rotated by ⁇ ( ⁇ /2) ⁇ from a positive direction of the real number axis (I axis) to a negative direction of the imaginary number axis (Q axis).
- the phase is rotated by ⁇ ( ⁇ /2) ⁇ from the negative direction of the imaginary number axis to a negative direction of the real number axis.
- FIG. 5( a ) is a graph of a transmission output signal of quadrature phase shift keying (QPSK) by using a scatter diagram
- FIG. 5( b ) is a graph of a transmission output signal according to PRSK according to an exemplary embodiment of the present invention.
- the four constellation points on an I-Q space can be checked.
- constellation points of symbols are generated in a space rotated by ⁇ /4 ⁇ with respect to a transmission output signal of the QPSK.
- FIG. 6 is a graph of locus of transmission output signals of QPSK through a signal trajectory diagram on a complex number plane.
- zero-crossing according to phase shifting of 180 degrees causes spectrum distortion by a non-linear element such as an amplifier in a radio frequency domain.
- the spectrum distortion results in a power loss through back-off of an operation area of the amplifier in order to compensate for the degradation of the non-linear characteristics.
- FIG. 7 is a graph of locus of transmission output signals of PRSK through a signal trajectory diagram on a complex number plane according to an exemplary embodiment of the present invention.
- FIG. 8 is a graph showing the comparison of a frequency spectrum distortion phenomenon by a non-linear device through a spectrum diagram.
- the PRSK scheme according to the present exemplary embodiment can considerably reduce power of an adjacent channel due to the non-linear characteristics compared with the existing QPSK scheme. This can be confirmed even through numerical values of PAPR (Peak-to-Average Power Ratio).
- Table 2 below comparatively shows numerical values of the PAPR with respect to a transmission signal of the QPSK scheme and that of the PRSK scheme when a roll-off factor of the square root raised cosine filter is 1.
- the transmission signal of the PRSK scheme has a power efficiency of approximately 0.6 dB with respect to back-off compared with the transmission signal of the QPSK scheme.
- FIG. 9 is a schematic block diagram of a reception device of a PRSK scheme according to an exemplary embodiment of the present invention.
- the reception device includes a quadrature demodulation unit 200 , analog-to-digital converters (A/Ds) 210 - 1 and 210 - 2 , matching filters 220 - 1 and 220 - 2 , a synchronization unit 230 , an exchanging unit 240 , a comparison unit 250 , signal detection units 260 , 270 , and 280 , and parallel-to-serial converter 290 .
- A/Ds analog-to-digital converters
- ⁇ (t) ⁇ is a phase signal synthesized by inconsistency due to an error of a local oscillator
- ⁇ n(t) ⁇ is complex Gaussian white noise having a power spectrum density ⁇ N 0 /2 ⁇ .
- the quadrature demodulation unit 200 quadrature-demodulates the signal ⁇ r(t) ⁇ received by the reception device.
- the quadrature demodulation unit 200 corresponds to the quadrature modulation unit 150 of the transmission device.
- the A/Ds 210 - 1 and 210 - 2 convert the quadrature-demodulated signal into digital signals.
- the matching filters 220 - 1 and 220 - 2 receive the converted digital signals and output maximum output values of the input signals.
- the matching filters 220 - 1 and 220 - 2 may use the same filter factor as that of the transmission filters 130 - 1 and 130 - 2 of the transmission device.
- the synchronization unit 230 estimates and obtains timing synchronization and initial phase offset by using correlation characteristics of a preamble, and samples the same at a time interval of ⁇ T s /2 ⁇ . Namely, the synchronization unit 230 performs sampling twice in the signal symbol.
- a complex expression of the sampled and averaged reception signal is represented by Equation 7 shown below.
- ⁇ f ⁇ is a parameter due to the influence of a carrier frequency offset
- ⁇ is an initial phase offset uniformly distributed from 0 to 2 ⁇ .
- the exchanging unit 240 receives the reception signal ⁇ r i,k , r q,k ⁇ sampled by the synchronization unit 230 and exchanges the sample values of the sampled reception signals. Namely, as shown in Equation 8 below, imaginary number parts of the first and second sample values within the single symbol are exchanged.
- the comparison unit 250 obtains a signal size (namely, an absolute value), as represented by Equation 9 shown below, of the exchanged sample values as represented by Equation 8, compares the sizes of an even numbered signal (r 2n ) and an odd numbered signal (r 2n+1 ), and outputs the results to the signal detection units 280 , 270 , and 260 which restore respective bits of the grouped three bits.
- ⁇ square root over ( r i,2n 2 +r q,2n 2 ) ⁇
- ⁇ square root over ( r i,2n+1 2 +r q,2n+1 2 ) ⁇ [Equation 9]
- the signal detection unit 280 restores the first bit of the grouped three bits (the restored bit will be called Z p,n ). For example, the sizes of the two sample signals of the single symbol calculated as represented by Equation 9 are compared, and when the first sample value is greater, the first bit ⁇ z p,n ⁇ of the demodulated signal is determined as 0, and when the second sample value is greater, the first bit ⁇ z p,n ⁇ of the demodulated signal is determined as 1. This can be represented by Equation 10 shown below:
- both the real number part and the imaginary number part of the transmission signal can exist in the front or rear part of the symbol.
- Both the real number part and the imaginary number part of the transmission signal can exist in the front part of the symbol when the first bit of the group three bits is 0, and both the real number part and the imaginary number part of the transmission signal can exist in the rear part of the symbol when the first bit of the group three bits is 1.
- the signal detection unit 280 can restore the first bit of the grouped three bits by comparing the sizes of the sample values whose imaginary number parts have been exchanged as shown in Equation 10.
- the comparison unit 250 In order to restore the other remaining two bits of the grouped three bits, the comparison unit 250 outputs a symbol ⁇ w n ⁇ determined through a signal having a greater size (namely, the absolute value) as represented by Equation 11 shown below:
- w n ⁇ r 2 ⁇ n , ⁇ r 2 ⁇ n ⁇ > ⁇ r 2 ⁇ n + 1 ⁇ r 2 ⁇ n + 1 , ⁇ r 2 ⁇ n ⁇ ⁇ ⁇ r 2 ⁇ n + 1 ⁇ [ Equation ⁇ ⁇ 11 ]
- Equation 11 r 2n , r 2n+1 are signals after the imaginary number parts are exchanged by Equation 8.
- the signal detection units 270 and 260 perform final decoding (Z i,n , Z q,n ) on the other remaining two bits among the grouped three bits through a demodulation table as shown in Table 3 below.
- Table 3 corresponds to Table 1 as described above.
- the signal restored through the demodulation table is restored into an information signal Z n through the parallel-to-serial converter 290 .
- FIG. 10 is a flow chart illustrating the process of a reception method according to an exemplary embodiment of the present invention.
- the reception device quadrature-demodulates a reception signal (step S 210 ), and converts the quadrature-demodulated signal into a digital signal (step S 220 ).
- the digital signal is matching-filtered (step S 230 ) and then sampled at an interval of a half of a symbol (step S 240 ).
- Imaginary number parts of two sample values sampled for the one symbol are exchanged (step S 250 ), and the sizes (namely, the absolute values) of the signals whose imaginary number parts have been exchanged are compared to restore the grouped three bits (step S 260 ).
- the restored three bits are serially converted (step S 270 ).
- the device implementing this method has been described in detail with reference to FIG. 9 , and a repeated description thereof will be omitted.
- FIG. 11 is a graph showing the comparison between bit error rate (BER) performance according to white noise between the PRSK scheme according to an exemplary embodiment of the present invention and other schemes such as the existing QPSK, MSK and DQPSK.
- the PRSK scheme has a gain of an approximately 1.3 dB over the QSPK scheme having the best performance among the existing schemes at BER 10 ⁇ 6 .
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
Description
TS=3Tb [Equation 1]
TABLE 1 | ||
Pattern of | ||
{a3n+1, a3n+2} | complex variable {An} | Phase value {φ} |
00 | 1 + j | π/4 |
01 | −1 + j | 3π/4 |
10 | 1 − j | 7π//4 |
11 | −1 − j | 5π/4 |
T p =T s/2 [Equation 2]
S n(t)=Re{[{ā 3nα(t)+a 3nβ(t)}·Re{exp(jφ n)}+j{a 3nα(t)+ā3nβ(t)}·Im{exp(jφ n)}]·exp(j2πc t)} [Equation 4]
β(t)=α(t−0.5T s) [Equation 5]
TABLE 2 | ||||
Modulation scheme | QPSK | PRSK | ||
PAPR (dB) | 3.48 | 2.88 | ||
r(t)=e jθ(t) s(t−τ)+n(t) [Equation 6]
r k =e j{2πkΔf(T
r 2n =Re{r 2k }+jIm{r 2k+1}
r 2n+1 =Re{r 2k+1 }+jIm{r 2k} [Equation 8]
|r 2n|=√{square root over (r i,2n 2 +r q,2n 2)}
|r 2n+1|=√{square root over (r i,2n+1 2 +r q,2n+1 2)} [Equation 9]
TABLE 3 | |||
Sign of (wi,n, wq,n) | Detection data (zi,n, zq,n) | ||
+, + | 00 | ||
+, − | 10 | ||
−, + | 01 | ||
−, − | 11 | ||
Claims (9)
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
KR10-2010-0123413 | 2010-12-06 | ||
KR1020100123413A KR20120062231A (en) | 2010-12-06 | 2010-12-06 | Transmitting device, receiving device, transmitting method and receiving method for wireless communication system |
Publications (2)
Publication Number | Publication Date |
---|---|
US20120177141A1 US20120177141A1 (en) | 2012-07-12 |
US8971450B2 true US8971450B2 (en) | 2015-03-03 |
Family
ID=46455232
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US13/297,862 Active 2032-12-08 US8971450B2 (en) | 2010-12-06 | 2011-11-16 | Transmission device, reception device, transmission method and reception method for wireless communication system |
Country Status (2)
Country | Link |
---|---|
US (1) | US8971450B2 (en) |
KR (1) | KR20120062231A (en) |
Families Citing this family (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN104813590B (en) * | 2012-11-06 | 2018-01-05 | 加利福尼亚大学董事会 | Expansible serial/serial the I/O of solution connected for the chip based on multifrequency QAM schemes to chip |
KR102134421B1 (en) * | 2015-10-22 | 2020-07-15 | 삼성전자주식회사 | Method of processing and recovering signal, and devices performing the same |
KR101968389B1 (en) * | 2016-11-30 | 2019-04-11 | 성균관대학교산학협력단 | Method of pahse rotation shift keying based on probability of bit sequence and apparatus for performing the same, and method of quadrature amplitude pahse rotation modualtion and apparatus for performing the same |
KR102047367B1 (en) | 2016-12-27 | 2019-12-04 | 주식회사 제노코 | High Speed Phase Shift Keying Modulation |
KR101981013B1 (en) * | 2018-10-15 | 2019-05-21 | 성균관대학교산학협력단 | Method of quadrature amplitude pahse rotation modualtion and apparatus for performing the same |
Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20020097810A1 (en) * | 2001-01-22 | 2002-07-25 | Tetsuya Seki | Power control apparatus and power control method |
US6473506B1 (en) * | 1998-10-13 | 2002-10-29 | Telefonaktiebolaget Lm Ericsson (Publ) | Signaling using phase rotation techniques in a digital communications system |
US20040260985A1 (en) * | 2001-02-14 | 2004-12-23 | Abraham Krieger | Synchronization of a communications system |
US20100135431A1 (en) * | 2008-12-02 | 2010-06-03 | Electronics And Telecommunications Research Institute | Modulating device and method, demodulating device and method |
US20110122969A1 (en) * | 2009-11-23 | 2011-05-26 | Electronics And Telecommunications Research Institute | Transmission apparatus, reception apparatus, transmission method, and reception method of wireless communication system |
US20110150124A1 (en) * | 2009-12-17 | 2011-06-23 | Electronics And Telecommunications Research Institute | Modulation apparatus, modulation method, demodulation apparatus, and demodulation method |
US20130044841A1 (en) * | 2011-08-19 | 2013-02-21 | Kabushiki Kaisha Toshiba | Wireless receiving apparatus and method |
-
2010
- 2010-12-06 KR KR1020100123413A patent/KR20120062231A/en not_active Application Discontinuation
-
2011
- 2011-11-16 US US13/297,862 patent/US8971450B2/en active Active
Patent Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6473506B1 (en) * | 1998-10-13 | 2002-10-29 | Telefonaktiebolaget Lm Ericsson (Publ) | Signaling using phase rotation techniques in a digital communications system |
US20020097810A1 (en) * | 2001-01-22 | 2002-07-25 | Tetsuya Seki | Power control apparatus and power control method |
US20040260985A1 (en) * | 2001-02-14 | 2004-12-23 | Abraham Krieger | Synchronization of a communications system |
US20100135431A1 (en) * | 2008-12-02 | 2010-06-03 | Electronics And Telecommunications Research Institute | Modulating device and method, demodulating device and method |
US20110122969A1 (en) * | 2009-11-23 | 2011-05-26 | Electronics And Telecommunications Research Institute | Transmission apparatus, reception apparatus, transmission method, and reception method of wireless communication system |
US20110150124A1 (en) * | 2009-12-17 | 2011-06-23 | Electronics And Telecommunications Research Institute | Modulation apparatus, modulation method, demodulation apparatus, and demodulation method |
US20130044841A1 (en) * | 2011-08-19 | 2013-02-21 | Kabushiki Kaisha Toshiba | Wireless receiving apparatus and method |
Non-Patent Citations (6)
Title |
---|
Jaehwan Kim, Jung Yeol Oh, Cheolhyo Lee, Hyung Soo Lee and Jae Young Kim, "PSSK Proposal for High-data-rate In-body WBA# PHY", IEEE-15-09-0179-03-0006, ETRI, Jul. 16, 2009. * |
Jung Yeol Oh, et al. International Conference on ICT Convergence 2010 under the title "Phase Rotation Shift Keying for Low Power and High Performance WBAN In-body systems" Nov. 18, 2010, 32pages. |
Jung-Yeol Oh , Jae-Hwan Kim , Hyung-Soo Lee and Jae-Young Kim, "A pi/4-shifted Differential 8PSSK Modulation for High Data Rate WBAN System", ETRI, Korea, ICIS 2009, Nov. 2009. * |
Jung-Yeol Oh , Jae-Hwan Kim , Hyung-Soo Lee and Jae-Young Kim, "A π/4-shifted Differential 8PSSK Modulation for High Data Rate WBAN System", ETRI, Korea, ICIS 2009, Nov. 2009. * |
Jung-Yeol Oh, et al., "Phase Rotation Shift Keying for Low Power and High Performance WBAN In-body systems" 2010 IEEE, pp. 28-32. |
Jung-Yeol Oh, Jeong-Ki Kim, Hyung-Soo Lee, Sang-Sung Choi and Dong S. Ha, "Phase Rotation Shift Keying for Low Power and High Performance WBAN In-body systems", ETRI and Virginia Tech, Nov. 17-19, 2010, IEEE. * |
Also Published As
Publication number | Publication date |
---|---|
KR20120062231A (en) | 2012-06-14 |
US20120177141A1 (en) | 2012-07-12 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US8503546B1 (en) | Multiple layer overlay modulation | |
US9001948B2 (en) | Pulse shaping in a communication system | |
US7450628B2 (en) | Processor, modulators and transceivers for spread spectrum, CDMA, CSMA, OFDM, TDM, TDMA cross correlated and filtered systems | |
Barnela et al. | Digital modulation schemes employed in wireless communication: A literature review | |
US20050185699A1 (en) | Spread spectrum, cross-correlated and filtered modulated systems | |
WO2021249139A1 (en) | Bluetooth-low-energy constant envelope phase modulation and demodulation methods and devices | |
CN112398770B (en) | Bluetooth low-power consumption multiphase frequency shift keying modulation and demodulation method and equipment | |
US20070268978A1 (en) | Carrier offset estimator | |
US7072411B1 (en) | Computation reduction in OFDM system using frequency domain processing | |
US8971450B2 (en) | Transmission device, reception device, transmission method and reception method for wireless communication system | |
EP2262159A2 (en) | Apparatus and method for digital wireless communications | |
JP3166705B2 (en) | Wireless device and transmission method | |
CN111901269B (en) | Gaussian frequency shift keying modulation method, device and system with variable modulation index | |
Gao | Energy and bandwidth-efficient wireless transmission | |
KR20130073528A (en) | Phase rotation modulation apparatus and method | |
US6373903B1 (en) | Apparatus and method for increasing the effective data rate in communication systems utilizing phase modulation | |
US8514977B2 (en) | Transmission apparatus, reception apparatus, transmission method, and reception method of wireless communication system | |
CN112600781B (en) | Variable envelope frequency shift keying modulation and demodulation method and equipment | |
KR20130022286A (en) | Offset phase rotation shift keying modulation apparatus and method, phase silence rotation shift keying modulation apparatus and method, and phase silence rotation shift keying demodulation apparatus and method | |
CN113169949B (en) | Symbol constellation diagram for data transmission | |
Galvão et al. | Bandwidth efficient gaussian minimum frequency-shift keying approach for software defined radio | |
US12119967B2 (en) | Method and transmitter for constant envelope phase modulation and demodulation | |
CN114629763B (en) | OFDM system IQ signal demodulation method and device based on neural network | |
Zafar et al. | Implementation and analysis of QPSK & 16QAM modulator & demodulator | |
Udawant et al. | Digital image processing by using GMSK |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
AS | Assignment |
Owner name: ELECTRONICS AND TELECOMMUNICATIONS RESEARCH INSTIT Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:OH, JUNG YEOL;LEE, HYUNGSOO;CHOI, SANG SUNG;SIGNING DATES FROM 20111111 TO 20111114;REEL/FRAME:027242/0169 |
|
FEPP | Fee payment procedure |
Free format text: PAYOR NUMBER ASSIGNED (ORIGINAL EVENT CODE: ASPN); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY |
|
STCF | Information on status: patent grant |
Free format text: PATENTED CASE |
|
MAFP | Maintenance fee payment |
Free format text: PAYMENT OF MAINTENANCE FEE, 4TH YR, SMALL ENTITY (ORIGINAL EVENT CODE: M2551); ENTITY STATUS OF PATENT OWNER: SMALL ENTITY Year of fee payment: 4 |
|
FEPP | Fee payment procedure |
Free format text: ENTITY STATUS SET TO UNDISCOUNTED (ORIGINAL EVENT CODE: BIG.); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY |
|
MAFP | Maintenance fee payment |
Free format text: PAYMENT OF MAINTENANCE FEE, 8TH YEAR, LARGE ENTITY (ORIGINAL EVENT CODE: M1552); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY Year of fee payment: 8 |