US5504781A - Process for the recovery of data transmitted over a transmission path for digital data streams using decoding by cross-correlation of a data sequence coded by cyclic shifting and inversion - Google Patents

Process for the recovery of data transmitted over a transmission path for digital data streams using decoding by cross-correlation of a data sequence coded by cyclic shifting and inversion Download PDF

Info

Publication number
US5504781A
US5504781A US08284402 US28440294A US5504781A US 5504781 A US5504781 A US 5504781A US 08284402 US08284402 US 08284402 US 28440294 A US28440294 A US 28440294A US 5504781 A US5504781 A US 5504781A
Authority
US
Grant status
Grant
Patent type
Prior art keywords
data
code
word
code words
binary
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Fee Related
Application number
US08284402
Inventor
Andreas Wolf
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Tektronix Inc
Original Assignee
Siemens AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Grant date

Links

Images

Classifications

    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/38Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40Transmitting circuits; Receiving circuits
    • H04L25/49Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/4906Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems using binary codes

Abstract

A process for recovering, at the reception end, data transmitted over a transmission path for digital data streams. A code-word generator for generating a binary code word producing a Dirac pulse is provided. The binary code word is cyclically shifted to create further binary code words. The binary code word and further binary code words are inverted to create still further binary code words. The data is coded, on the transmission end of the transmission path, with the binary code word, with the further binary code words, and with the still further binary code words. On the reception end of the transmission path, the data is recovered by cross-correlating the data and by utilizing the position of the main maximum of the cross-correlation functions. To increase the number of code words, a second code-word generator and a third codeword generator, having different generator polynomials, are used for coding binary code words, further binary code words, and still further binary code words, by cyclical shifting and inversion in a manner similar to that above. On the reception end of the transmission path, second and third cross-correlators are additionally used. The main maximum of each of the resulting three cross-correlation functions is detected and the data word transmitted is recovered based on a main maximum with a value above a predetermined value and from the position of this main maximum.

Description

BACKGROUND OF THE INVENTION

The present invention relates to a process for recovering, at a reception end of a transmission path for digital data streams, data transmitted over the transmission path from a transmission end to the reception end.

In the present invention, various data are coded at the transmission end of the transmission path by means of a binary code word. The binary code word is generated by a code-word generator. The auto-correlation of the binary code word produces a Dirac Pulse. The various data at the transmission end of the transmission path are also coded with further binary code words produced by cyclically shifting the code word and by inverting the code word and further code words.

Further, in the present invention, the code word received is cross-correlated at the reception end of the transmission path by means of a cross-correlator to decode the code word. The relative position and the sign of the main maximum of the corresponding cross-correlation function is used to recover the data sent over the transmission path.

In a known process of this type ("telcom report" 14 (1991), No. 2, pages 104 to 107), a 25 -m sequence is used as binary code word. This 25 -m sequence has the property that the auto-correlation of this 25 -m sequence produces an ideal Dirac impulse. From the 25 -m sequence, further binary code words are produced by cyclically shifting the binary code word. These further binary code words are characterized by phases which differ from each other. In this way, 31 different data words can be coded on the transmission end, and thus 4-bit data words can be coded. 5-bit data words cannot be coded since only 31 code words are available. One embodiment of the known process, which constitutes an improvement with respect to the number of codable data words, uses inverted binary 25 -m sequences on the transmission end in addition to the coding. In this way, coding a maximum of an additional 31 different data words is possible. As a whole, 5-bit data words can thus be transmitted and recovered on the reception end of a transmission path by cross-correlation, despite disturbances on the transmission path, if not more than 7 bit errors occur upon the transmission.

The object of the present invention is to develop the above process so that a comparatively large number of data present on the transmission end can be reliably recovered on the reception end.

SUMMARY OF THE INVENTION

To achieve the above mentioned object, the present invention provides that a second supply of code words is used on the transmission end of the transmnission path, a second code word being generated by a second code-word generator. The auto-correlation of the second code word produces a Dirac pulse. Further second binary code words are produced by cyclically shifting the second code word and by inverting the second code word and further second code words to produce second inverse code words.

The second code-word generator can be defined by a generator polynomial of the same degree as the code-word generator.

The present invention further provides that a number of data are coded with data polynomials of the seventh order such that the code words of the two code-word generators are associated with data polynomials formed therefrom having, in each case, the five lowest binary places of tile seven order data polynomial as a function of two combinations of values of the two highest binary places of the seven data polynomial.

A further number of data are coded with data polynomials of the seventh order such that the inverse code words of the two code-word generators are associated with data polynomials formed therefrom having the five lowest binary places of the seven order data polynomial as a function of two further combinations of values of the two highest binary places of the seven order data polynomial. Further, an additional number of data are coded with data polynomials of the seventh degree such that code words of an additional code-word supply are associated with data polynomials which have been formed therefrom having zero at the five lowest binary places of the seven order data polynomial as a function of four combinations of values of the two highest binary places of the seven order data polynomial. The additional code-word supply is produced by a third code-word generator which corresponds to the two other code-word generators with respect to the degree of its generator polynomial and with respect to its code words.

The present invention provides that three cross-correlation functions are formed on the reception end of the transmission path by means of a cross-correlator, a second cross-correlator and a third cross-correlator, each having different correlation references. The height of the amounts of the main maxima of the cross-correlation functions are examined. If a height of the amount of a main maximum lies above a predetermined value, its relative position is determined and the datum transmitted in each case is recovered therefrom, considering also the sign of the corresponding main maximum.

One essential advantage of the process of the present invention is that more than twice as many code words are made available at the transmission end than in the known process. The number of bit errors must not exceed 5 to assure the dependable recovery of the data sent on the transmission end onto the transmission path on the reception end by cross-correlation.

In the process of the present invention, the code words of the second code supply can be formed in different manners. For example, four different code words produced by cyclically shifting the binary code word of the second code-word generator can be used. However, using two code words of the second code supply and forming the further code words therefrom by inversion is particularly advantageous.

As is also the case in the known process described above, the height of the main maximum of the cross-correlation functions can be advantageously utilized as a measure for the number of bit errors.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows an embodiment of a shift register suitable for producing a code word for the process of the present invention.

FIG. 2 shows a binary code word.

FIG. 3 shows further code words obtainable by cyclically shifting of the binary code word of FIG. 2.

FIG. 4 shows an embodiment of a bipolar coder.

FIG. 5 is a table showing coding or decoding.

FIG. 6 is an embodiment of an arrangement for implementing the process of the present invention.

FIG. 7 shows a cross-correlation function.

FIG. 8 shows three cross-correlation functions.

DETAILED DESCRIPTION

FIG. 1 shows a shift register 1 which contains 5 stages, 2, 3, 4, 5 and 6, each stage being a D flip-flop in the embodiment shown. The shift register 1 includes a feedback coupling from the output of stage 6 to an exclusive-OR gate 7 arranged between stages 3 and 4 and to another exclusive-OR gate 8 arranged in front of the stage 2. This feedback coupling can be described by a generator polynomial GKKF (x):

G.sub.KKF (x)=x.sup.0 +x.sup.2 +x.sup.5 =x.sup.5 +x.sup.2 +1(1)

This generator polynomial GKKF (x) is an "irreducible" polynomial of order g=5. The period of a 25 -m sequence which can be produced with the generator polynomial is 2g -1=31.

An input 9 of the shift register 1 can be provided with an input sequence E(x). A binary output sequence A(x) is provided at an output 10. The output signal A(x) is described with the input signal E(x) and the generator polynomial GKKF (x) by

A(x)=E(x)/G.sub.KKF (x)                                    (2)

The first 31 values of the output signal A(x) in the case of a stimulant with an input sequence E(x)=x31, which is a 100 00 sequence, is determined by the polynomial division ##EQU1## the result of which is identical to the sequence of numbers cO (n) of 25 -m sequency:

C.sub.O (n)={0000100101100111110001101110101}              (4)

the division remainder R(x), which furthermore is identical to the content I(x) of the five stages 2 to 6 after 31 cycles, indicates the periodic behavior of the 25 -m sequence generator. This sequence of numbers cO (n) is used, as will be further described below, as a code word cO (n) in the process of the invention.

If x31 +1 is selected as input signal, there is obtained ##EQU2## as output signal the polynomial HKKF (x) which is perpendicular to GKKF (x) and which represents only one period of the 25 -m sequence and is thus the polynomial representation of cO (n).

In the customary representation, the output signal of the shift register can be obtained from the table in FIG. 2, which has been compiled considering the fact that the contents of the individual stages 2 to 6 of the shift register of FIG. 1 can be described by the polynomial I(x), namely:

I(x)=x.sup.4 ·i.sub.5 +x.sup.3 ·i.sub.4 +x.sup.2 ·i.sub.3 +x.sup.1 ·i.sub.2 +x.sup.0 ·i.sub.1(6)

or, in general, by the relationship (7)

x.sup.i mod G.sub.KKF (x),                                 (7)

if a "1" is entered for i=0 in the first stage 2 and E(x)=0. As from x31, the conditions in the individual stages are repeated based on the period of 31 of the 25 -m sequence. The content i5 of the register 6 indicates the 25 -m sequence or cO (n) as binary sequence of numbers. If the code word cO (n) is shifted cyclically in accordance with equation (4) or in accordance with equation (5), one then receives 31 different code words C(x) with respect to their phase s, as can be noted from FIG. 3. These different code words C(x) can be described by the following equation (8):

C.sub.s (x)= x.sup.s.H.sub.KKF (x)!mod(x.sup.31 +1)        (8)

These code words have a length of 31 and make 31 different phase positions "s" of the 25 -m sequence possible, so that in this way 31 different codes words are available.

By way of further explanation of equation (8), cyclic codes generally have, as characteristic, an irreducible generator polynomial G(x) with the degree g. Code words C(x) are generally now produced such that the so-called cyclic supplementation R(x) is appended to a data word D(x), so that the code-word polynomial C(x) is divisible by G(x) without remainder. For this purpose, D(x) is first multiplied by xg and R(x) is then obtained by the division of the product D(x).xg by G(x). R(x) has the degree g-1 and is thus precisely g places long. The code words obtained are described by

C(x)=x.sup.g.D(x)+R(x)                                     (9)

this code word is then divisible without remainder by G(x). We therefore have ##EQU3## from which we obtain ##EQU4## The cyclic supplementation can now be obtained by inserting a data value for D(x) in equation (12) and dividing it by G(x). The result can then be separated into the result coefficient E(x) and the remainder R(x). Only the result for R(x) in equations (11) and (12) is essential for the calculation of the code word. E(x), on the other hand, is of no importance for the code word.

The store of a total of 31 code words can be doubled by inversion using a bipolar coder such as shown in FIG. 4, thereby obtaining 31 inverse code words. The code-word generator shown here has a feedback-coupled shift register 20 with the generator polynomial G1 (x) with several stages 21 to 24 (a total of 26 stages) and exclusive-OR gates 25 and 26. Another exclusive-OR gate 27 is arranged on an output side of the shift register 20. An input 28 of the exclusive-OR gate 27 is directly coupled to the input of the exclusive-OR member 26 and is adapted to be connected, via a switch contact 29 in its "a" position, to the output of stage 24. In the "b" position of the switch contact 29, the one input 28 is acted on by the signals of the lower five places d1 to d5 of the data word D(x). The further input 30 of the further exclusive-OR member 27 is acted on by the signal of the highest (sixth) place of the data word D(x). The sixth place controls the inversion so that 62 different code words are available here if one furthermore starts from a 25 -m sequence as example.

The 62 different code words forming a first code-word supply are thus obtained. Only half of the 62 code words are obtained by means of a code-word generator with the generator polynomial according to equation (5) while the other half of the 62 code words are obtained by inverting the first 31 code words to form inverse code words.

Based on the above, a second code-word supply can be produced by means of a second code-word generator having a generator polynomial G2 (x) and by inverting the code words thus obtained. A third code-word supply can be obtained by means of a third code-word generator having a generator polynomial G3 (x), which polynomials can be described by the following equations (13) and (14): ##EQU5##

In these equations (13) and (14), B3 (x) and B5 (x) represent the irreducible polynomials of fifth degree:

B.sub.3 (x)=x.sup.5 +x.sup.4 +x.sup.3 +x.sup.2 +1          (15)

B.sub.5 (x)=x.sup.5 +x.sup.4 +x.sup.2 +x+1                 (16)

In the table of FIG. 5, the code word supply C (x) produced with the bipolar code in accordance with FIG. 4 is described by indication of the generator polynomial G1 (x) with reference to the inversion, where "b" indicates either "0" or "1". The second code-word supply is characterized in the table by indication of the generator polynomial G2 (x), while G3 (x), with the additions a to d, designates code words of the third code-word supply.

As can furthermore be noted in detail from FIG. 5, in this way data words D(x) can be coded as test data to be transmitted which represent 7-bit words with the binary places d1 -d7. In this connection, one proceeds such that a shortened data word Dk (x) of the fifth order is obtained, in each case, from the data words D(x) of the seventh order, it having the five lowest places of the data word D(x) of seventh order. Inverted or non-inverted code words of the one code-word supply and of the further code-word supply are associated with this shortened data word Dk (x) of fifth order as a function of the combination of values at places d6 and d7 of the data word D(x) of seventh order. In this way, a total of 124 different test data can be coded. Therefore, four additional code words are still lacking to be able to transmit test data of a length of 7 bits. These additional code words are obtained such that two noninverted code words of the generator polynomial G3 (x) and the inverse code words from an additional code-word supply are used for this, again as a function of the combination of values d6 and d7. Thus a total of 128 code words are available, so that data words of a width of 7 bits can be transmitted.

As shown in FIG. 6, the code words formed by means of the above-described code-word generators with the generator polynomials G1 (x), G2 (x) and G3 (x) are deposited in a coding device 40, which may be an addressable memory. In this connection, the code words produced in accordance with the generator polynomial G1 (x) are present, for instance, at storage positions 41 the inverse code words of which are present on storage positions 42, and the code words produced in accordance with the generator polynomial G2 (x) are present at storage positions 43, the inverse code words at storage positions 44 and the additional code words at storage positions 45 and their inverse code words at storage positions 46. Data words shown in block 47 which are to be coded are coded in the coding device 40 in a manner such as described above and transmitted as coded data (block 48) over a transmission path 49 where they are present as coded data (block 50). The coded data in block 50 includes any errors introduced by the transmission path 49. The coded data are fed to three cross-correlators 51, 52 and 53.

The cross-correlators 51 to 53 have different 25 -m sequences as correlation references:

M.sub.1 (x)=x.sup.26 +x.sup.26 mod G.sub.1 (x)             (17)

M.sub.2 (x)=x.sup.26 +x.sup.26 mod G.sub.2 (x)             (18)

M.sub.3 (x)=x.sup.26 +x.sup.26 mod G.sub.3 (x)             (19)

These correlation references are produced with the generator polynomials G1 (x), G2 (x) and G3 (x). The cross-correlator 51 thus has the correlation reference M1 (x), the cross-correlator 52 has the correlation reference M2 (x), and the cross-correlator 53 has the correlation reference M3 (x).

If the generator polynomial for the generated code word C'(x) is identical to the correlation reference, then a course of the function with a maximum of the height 31, as shown in FIG. 7, results for the cross-correlation function KKF(n) between the code word and the correlation reference. The value "n", at which the main maximum is detected in the cross-correlation function is associated unambiguously to the phase "s" of the code word received. Furthermore, all considerations with regard to the cross-correlation are made with a bipolar sequence of numbers in which, therefore, in view of equation (4), all "0" values are replaced by the value "-1". For the example, it was assumed that D(x) =0 and M1 (x) is the correlation reference. The code words produced with a given generator polynomial produce an evaluatable maximum with the value 31 only in one of the three cross-correlators. In the two other cross-correlators only smaller maxima are produced, as can be noted from FIG. 8. In this connection, the unambiguity of the maximum in the plot of KKF.sub. 1 (n) is true also for falsified code words (i.e., code words including transmission errors). The value of the main maximum in KKF1 (n) drops by the value 2 per bit error in the code word. At the same time the maximum values of the secondary maxima in KKF2 (n) and KKF3 (n) increase at most by 2 per bit error in the code word. To obtain a maximum error tolerance upon the correlative decoding, the recognition threshold for a maximum in the course of the function of the cross-correlation is set at

|KKF(n)|≦21

This means that the code words transmitted can have up to 5 bit errors and still be recognized correctly.

From the position of the main maximum, from the polarity of the main maximum (positive or negative), and from the cross-correlator which provides the main maximum, the data word D(x) can be directly determined by means of a memory following the cross-correlators 51-53 (not shown), using the table shown in FIG. 5. In this connection, upon the occurrence of a positive main maximum in the cross-correlator 51 with the correlation reference M1 (x) it is determined that C(x) has been generated with G1 (x). In this way, in accordance with FIG. 5, places d6 to d1 of the data word D(x) are determined as 0. The position of the main maximum is now determined by the value of d7.

In the same way as in the known process which was described at the beginning hereof, the number of bit errors can be determined in suitable manner by also evaluating the height of the main maximum in the process of the present invention.

Furthermore, the process of the present invention is not limited to the use of 25 -m sequences as code words but that the Barker code, the Gordon Mills and Welsh sequence, and the Gold code can also be used.

The process of the present invention is not limited to the use of code words of a given length, a given number of cross-correlators, or a given number of generator polynomials. However, the number of cross-correlators must agree with the generator polynomials.

Claims (6)

I claim:
1. A process for recovering, at a reception end, data transmitted over a transpission path for digital data steams from a transmission end to the reception end, in which various data are coded at the transmission end of the transmission path using a first code word generated by a first code-word generator, which can be described by a generator polynomial of degree five, an autocorrelation of said first code word producing a Dirac pulse and also using a first plurality of additional code words, including a first subset of code words generated by the first code-word generator by cyclic shifting of the first code word and including a first subset of inverted code words obtained by inverting the first subset of code words, and in which a cross-correlation of a code word received in each case is performed at the reception end of the transmission path for decoding by means of a first cross-correlator, using a relative position and a sign of a main maximum of a corresponding cross-correlation function for recovery of the data, said process comprising the steps of: using a second plurality of code words at the transmission end, a first additional code word of the second plurality of code words being generated by a first additional code-word generator, and an autocorrelation of the first additional code word produces a Dirac impulse, said second plurality of code words including a second subset of code words generated from the first additional code word by cyclic shifting of said first additional code word and also including a second subset of inverted code words obtained by inverting the second subset of code words,
wherein the first additional code-word generator is describable by a generator polynomial (G2 (x)) of a same degree as that of the first code-word generator,
coding a first set of data (D(x)) with data polynomials of a seventh degree so that code words (G1 (x) not inverted; G2 (x) not inverted) from the first and first additional code-word generators are associated with data polynomials (DK (x)) formed therefrom having in each case the five lowest binary places of a data polynomial (D(x)) of the seventh degree, as a function of two combinations of values of the two highest binary places (d6, d7) of the data polynomial (D(x)) of seventh degree, coding a second set of data (D(x)) with data polynomials of a seventh degree so that the first and second subset of inverted code words (G1 (x) inverted; G2 (x) inverted) from the first and first additional code-word generators, respectively, are associated with data polynomials (D(x)) formed therefrom having in each case the five lowest binary places of the data polynomial of seventh degree, as a function of two further combinations of values of the two highest binary places (d6, d7) of the data polynomial (D(x)) of seventh degree, and coding a third set of data with data polynomials of a seventh degree so that code words (G3 (x); a, b, c, d) of an additional code-word supply are associated with data polynomials formed therefrom each having a null at the five lowest binary places (d1 -d5) of the data polynomial (D(x)) of seventh degree, as a function of four combinations of values of the two highest binary places d6, d7, of the data polynomial (D(x)) of seventh degree
wherein the additional code-word supply is produced by a second additional code-word generator which agrees with the first and first additional code-word generators with respect to a degree of its generator polynomial (G3 (x)) and its code words,
forming three cross-correlation functions on the reception end by means of a first additional cross-correlator and a second additional corss-correlator having different correlation references (M2 (x), M3 (x)), which are examined as to a height of their main maxima, and if a height of a main maximum lies above a value predetermined in view of maximum fault tolerances in decoding, its relative position is determined and datum transmitted ine ach case is recovered therefrom with due consideration of a sign of the corresponding main maximum.
2. The process according to claim 1, wherein
for coding of the third set of data (D(x)), in addition to code words (G3 (x); a, c) of the additional code-word supply, code words (G3 (x); b, d) formed by their inversion are used.
3. A process according to claim 1, wherein
the height of the main maxima of the corss-correlation functions (KKf(n)) is utilized as measure of a number of bit errors.
4. In a system having a transmission path for digital data streams, the transmission path having a transmission end and a reception end, a process for recovering, at the reception end, a data block transmitted over the transmission path, the process for recovering comprising steps of:
a) generating a first group of binary code words comprising substeps of:
i) generating, with a code word generator, a binary code word having an auto-correlation function that produces a Dirac pulse, wherein the code word generator can be described by an n-degree generator polynomial;
ii) cyclically shifting the code word generated in step (a)(i) to generate further binary code words;
iii) inverting the binary code word generated in step (a)(i) and the further binary code words generated in step (a)(ii) to generate still further binary code words;
b) generating a second group of binary code words comprising sub-steps of:
i) generating, with a second code word generator, a second binary code word having an auto-correlation function that produces a Dirac pulse, wherein the second code word generator can be described by an n degree generator polynomial;
ii) cyclically shifting the second binary code word generated in step (b)(i) to generate further second binary code words;
iii) inverting the second binary code word generated in step (b)(i) and the further second binary code words generated in step (a)(ii) to generate still further second binary code words;
c) coding the data block, at the transmission end of the transmission path, by means of the binary code word generated in step (a)(i), the further binary code words generated in step (a)(ii), the still further binary code words generated in step (a)(iii), the second binary code word generated in step (b)(i), the further second binary code words generated in step (b)(ii), and the still further second binary code words generated in step (b)(iii), including sub-steps of:
i) coding a number of data of the data block with seven degree data polynomials having five lowest binary places and two highest binary places such that the binary code word of the first code word generator and the second binary code word of the second binary code word generator are associated with data polynomials formed therefrom having, in each case, the five lowest binary places of the seven degree data polynomial, as a function of two combinations of values of the two highest binary places of the seven degree data polynomial;
ii) coding a further number of data of the data block with seven degree data polynomials having five lowest binary places and two highest binary places such that the inverted code words and the second inverted code words are associated with data polynomials formed therefrom having, in each case, the five lowest binary places of the seven degree data polynomial, as a function of two further combinations of values of the two highest binary places of the seven degree data polynomial; and
iii) coding an additional number of data with seven degree data polynomials having five lowest binary places and two highest binary places such that code words of an additional code word supply, being produced by a third n-degree code word generator, are associated with data polynomials formed therefrom, each having a null at the five lowest binary places of the seven degree data polynomial, as a function of four combinations of values of the two highest binary places of the seven degree polynomial;
d) cross-correlating the code word at the reception end of the transmission path with a first cross-correlator having a first correlation reference to obtain a first main maximum, with a second cross-correlator having a second correlation reference to obtain a second main maximum, and with a third cross-correlator having a third correlation reference to obtain a third main maximum, each of the first, second, and third main maximums having a relative position and a sign;
e) determining whether any of the first, second, and third main maximums exceed a predetermined value; and
f) recovering the data block using the relative position and the sign of any of the first, second, and third main maximums which exceed the predetermined value.
5. The process of claim 4 wherein the step of (c)(iii) further includes steps of:
inverting the code words of the additional code word supply; and
using the inverted code words for coding the additional number of data.
6. The process of claim 5 further comprising a step of determining a number of bit errors based on a height of at least one of the first, second, and third main maximums.
US08284402 1992-01-31 1993-01-26 Process for the recovery of data transmitted over a transmission path for digital data streams using decoding by cross-correlation of a data sequence coded by cyclic shifting and inversion Expired - Fee Related US5504781A (en)

Priority Applications (3)

Application Number Priority Date Filing Date Title
DE19924203301 DE4203301C1 (en) 1992-01-31 1992-01-31
DE4203301.2 1992-01-31
PCT/DE1993/000082 WO1993015574A1 (en) 1992-01-31 1993-01-26 Decoding by cross-correlation of a data sequence coded by cyclic shifting and inversion

Publications (1)

Publication Number Publication Date
US5504781A true US5504781A (en) 1996-04-02

Family

ID=6451022

Family Applications (1)

Application Number Title Priority Date Filing Date
US08284402 Expired - Fee Related US5504781A (en) 1992-01-31 1993-01-26 Process for the recovery of data transmitted over a transmission path for digital data streams using decoding by cross-correlation of a data sequence coded by cyclic shifting and inversion

Country Status (4)

Country Link
US (1) US5504781A (en)
EP (1) EP0624294B1 (en)
DE (1) DE4203301C1 (en)
WO (1) WO1993015574A1 (en)

Cited By (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5727018A (en) * 1993-05-28 1998-03-10 Siemens Aktiengesellschaft Process for obtaining a signal indicating a synchronization error between a pseudo-random signal sequence from a transmitter and a reference pseudo-random signal sequence from a receiver
US5966403A (en) * 1996-07-19 1999-10-12 Trimble Navigation Limited Code multipath error estimation using weighted correlations
US6141373A (en) * 1996-11-15 2000-10-31 Omnipoint Corporation Preamble code structure and detection method and apparatus
US6154486A (en) * 1995-06-05 2000-11-28 Omnipoint Corporation Preamble code structure and detection method and apparatus
US6356607B1 (en) * 1995-06-05 2002-03-12 Omnipoint Corporation Preamble code structure and detection method and apparatus
US6791960B1 (en) 1999-03-15 2004-09-14 Lg Information And Communications, Ltd. Pilot signals for synchronization and/or channel estimation
US20050018754A1 (en) * 1999-03-15 2005-01-27 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20060002453A1 (en) * 1999-03-15 2006-01-05 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US6987746B1 (en) * 1999-03-15 2006-01-17 Lg Information & Communications, Ltd. Pilot signals for synchronization and/or channel estimation
US20060126765A1 (en) * 2004-12-09 2006-06-15 Eun-Jeong Shin Apparatus and method for detecting timing error based on cyclic correlation
US20060256850A1 (en) * 2003-01-12 2006-11-16 Wolf Andreas C Method for the transmission of a data word
US20080123763A1 (en) * 2004-07-01 2008-05-29 Zarbana Digital Fund Llc Systems and methods for rapid signal detection and identification
US20080192867A1 (en) * 2007-02-14 2008-08-14 Wilinx Inc. Cross correlation circuits and methods
US20090196271A1 (en) * 1999-03-15 2009-08-06 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20090196278A1 (en) * 1999-03-15 2009-08-06 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US9645249B2 (en) * 2011-06-28 2017-05-09 Nextnav, Llc Systems and methods for pseudo-random coding
US9801153B2 (en) 2011-06-28 2017-10-24 Nextnav, Llc Coding in a positioning system

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4833470A (en) * 1986-07-15 1989-05-23 Matsushita Electric Industrial Co., Ltd. Code conversion apparatus
US5025455A (en) * 1989-11-30 1991-06-18 The United States Of America As Represented By The Administer, National Aeronautics And Space Administration Phase ambiguity resolution for offset QPSK modulation systems

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4833470A (en) * 1986-07-15 1989-05-23 Matsushita Electric Industrial Co., Ltd. Code conversion apparatus
US5025455A (en) * 1989-11-30 1991-06-18 The United States Of America As Represented By The Administer, National Aeronautics And Space Administration Phase ambiguity resolution for offset QPSK modulation systems

Non-Patent Citations (4)

* Cited by examiner, † Cited by third party
Title
A. Wolf, "Messprazision auf breitem Band," Telecom Report, vol. 14, No. 2, pp. 104-107 (Mar./Apr. 1991).
A. Wolf, Messpr zision auf breitem Band, Telecom Report, vol. 14, No. 2, pp. 104 107 (Mar./Apr. 1991). *
H. W. Atweiler, et al., "Bitfehler-Strukturanalyse in der Breitband-ISDN- Messtechnik," Messtechnik, vol. 44, No. 8, pp. 548-557 (1991).
H. W. Atweiler, et al., Bitfehler Strukturanalyse in der Breitband ISDN Messtechnik, Messtechnik, vol. 44, No. 8, pp. 548 557 (1991). *

Cited By (30)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5727018A (en) * 1993-05-28 1998-03-10 Siemens Aktiengesellschaft Process for obtaining a signal indicating a synchronization error between a pseudo-random signal sequence from a transmitter and a reference pseudo-random signal sequence from a receiver
US6154486A (en) * 1995-06-05 2000-11-28 Omnipoint Corporation Preamble code structure and detection method and apparatus
US6356607B1 (en) * 1995-06-05 2002-03-12 Omnipoint Corporation Preamble code structure and detection method and apparatus
US5966403A (en) * 1996-07-19 1999-10-12 Trimble Navigation Limited Code multipath error estimation using weighted correlations
US6141373A (en) * 1996-11-15 2000-10-31 Omnipoint Corporation Preamble code structure and detection method and apparatus
US20090196278A1 (en) * 1999-03-15 2009-08-06 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20050018754A1 (en) * 1999-03-15 2005-01-27 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20060002453A1 (en) * 1999-03-15 2006-01-05 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US6987746B1 (en) * 1999-03-15 2006-01-17 Lg Information & Communications, Ltd. Pilot signals for synchronization and/or channel estimation
US7848393B2 (en) 1999-03-15 2010-12-07 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20100067517A1 (en) * 1999-03-15 2010-03-18 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US7317749B2 (en) 1999-03-15 2008-01-08 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US7643540B2 (en) 1999-03-15 2010-01-05 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US7616681B2 (en) 1999-03-15 2009-11-10 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20080298438A1 (en) * 1999-03-15 2008-12-04 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US6791960B1 (en) 1999-03-15 2004-09-14 Lg Information And Communications, Ltd. Pilot signals for synchronization and/or channel estimation
US7602841B2 (en) 1999-03-15 2009-10-13 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US20090196271A1 (en) * 1999-03-15 2009-08-06 Lg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US7496132B2 (en) 1999-03-15 2009-02-24 Kg Electronics Inc. Pilot signals for synchronization and/or channel estimation
US8116385B2 (en) * 2003-01-12 2012-02-14 Andreas Christian Wolf Method for the transmission of a data word
US20060256850A1 (en) * 2003-01-12 2006-11-16 Wolf Andreas C Method for the transmission of a data word
US20080123763A1 (en) * 2004-07-01 2008-05-29 Zarbana Digital Fund Llc Systems and methods for rapid signal detection and identification
US7773701B2 (en) * 2004-07-01 2010-08-10 Moher Michael L Systems and methods for rapid signal detection and identification
US7555034B2 (en) 2004-12-09 2009-06-30 Electronics And Telecommunications Research Institute Apparatus and method for detecting timing error based on cyclic correlation
US20060126765A1 (en) * 2004-12-09 2006-06-15 Eun-Jeong Shin Apparatus and method for detecting timing error based on cyclic correlation
US7830949B2 (en) * 2007-02-14 2010-11-09 Wilinx Corporation Cross correlation circuits and methods
US20080192867A1 (en) * 2007-02-14 2008-08-14 Wilinx Inc. Cross correlation circuits and methods
US9645249B2 (en) * 2011-06-28 2017-05-09 Nextnav, Llc Systems and methods for pseudo-random coding
US9801153B2 (en) 2011-06-28 2017-10-24 Nextnav, Llc Coding in a positioning system
US9973234B2 (en) 2011-06-28 2018-05-15 Nextnav, Llc Systems and methods for pseudo-random coding

Also Published As

Publication number Publication date Type
EP0624294A1 (en) 1994-11-17 application
WO1993015574A1 (en) 1993-08-05 application
DE4203301C1 (en) 1993-01-14 grant
EP0624294B1 (en) 1995-11-08 grant

Similar Documents

Publication Publication Date Title
US3414818A (en) Companding pulse code modulation system
US3523291A (en) Data transmission system
US3405235A (en) Systems for transmitting code pulses having low cumulative displarity
US6212239B1 (en) Chaotic dynamics based apparatus and method for tracking through dropouts in symbolic dynamics digital communication signals
US4242755A (en) Circuit arrangement for decoding digital signals
US3753113A (en) Multilevel code signal transmission system
US5408473A (en) Method and apparatus for transmission of communication signals over two parallel channels
US3504287A (en) Circuits for stuffing synch,fill and deviation words to ensure data link operation at designed bit rate
US4518947A (en) Apparatus for decoding redundant interleaved data
US4486739A (en) Byte oriented DC balanced (0,4) 8B/10B partitioned block transmission code
US3337864A (en) Duobinary conversion, reconversion and error detection
US3767855A (en) Pulse position modulation communication system
US5408498A (en) Serial-signal transmission apparatus
US4613980A (en) System for high accuracy remote decoding
US4896353A (en) Apparatus for fast decoding of a non-linear code
US6122376A (en) State synchronized cipher text scrambler
US5151699A (en) Data converting apparatus
US20080198904A1 (en) Multi-Channel Galvanic Isolator Utilizing a Single Transmission Channel
US3995264A (en) Apparatus for encoding and decoding binary data in a modified zero modulation data code
Xiao et al. A spectral characterization of correlation-immune combining functions
US4805174A (en) Error correcting coder/decoder
US4908804A (en) Combinatorial coded telemetry in MWD
US4675650A (en) Run-length limited code without DC level
US4787093A (en) Combinatorial coded telemetry
US4086587A (en) Apparatus and method for generating a high-accuracy 7-level correlative signal

Legal Events

Date Code Title Description
AS Assignment

Owner name: SIEMENS AKTIENGESELLSCHAFT, GERMANY

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:WOLF, ANDREAS;REEL/FRAME:007220/0899

Effective date: 19940622

AS Assignment

Owner name: TEKTRONIX INC., OREGON

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:SIEMENS AKTIENGESELLSCHAFT;REEL/FRAME:008848/0230

Effective date: 19971121

FPAY Fee payment

Year of fee payment: 4

FPAY Fee payment

Year of fee payment: 8

REMI Maintenance fee reminder mailed
REMI Maintenance fee reminder mailed
LAPS Lapse for failure to pay maintenance fees
FP Expired due to failure to pay maintenance fee

Effective date: 20080402