US4956644A - Channelized binary-level radiometer - Google Patents
Channelized binary-level radiometer Download PDFInfo
- Publication number
- US4956644A US4956644A US07/417,124 US41712489A US4956644A US 4956644 A US4956644 A US 4956644A US 41712489 A US41712489 A US 41712489A US 4956644 A US4956644 A US 4956644A
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
- H04B1/715—Interference-related aspects
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/713—Spread spectrum techniques using frequency hopping
- H04B1/715—Interference-related aspects
- H04B2001/7152—Interference-related aspects with means for suppressing interference
Definitions
- This disclosure relates to the field of receptivity to modulated or unmodulated frequency hopped signals in regard to detecting the presence of an information signal.
- frequency hopped nets have been developed to provide for secure and reliable digital communication systems. It has been noted that frequency hopped nets are able to maintain intelligible communication with as much as 20 percent of their channels jammed, and for this reason, it has been possible to operate frequency hopped (FH) net transmissions in very cluttered spectral regions.
- FH frequency hopped
- Fourth law detectors are detectors whose output signal-noise ratio is proportional to the 4th power of the input signal-noise ratio.
- FH detection schemes Due to this limitation, practical frequency hopping (FH) detection schemes have often used channelizers which break up the frequency spectrum into smaller-sized band widths and allow the operator to keep track of narrow band interference sources. These methods relay on the high, instantaneous signal-to-noise ratio in the occupied channel for the detection capability. It should be noted, however, that channelizers suffer from a lack of efficient, automatic detection algorithms. Thus, it was considered useful to develop a hybrid detector which would include both channelizing circuitry and automatic feature detection circuitry which would still retain the advantage of each of these two systems.
- Frequency hop radio transmissions create processing gain by utilizing a large number of independent hop frequency locations, for example, the Jaguar radio manufactured by Racal-Tactkom, Ltd. Berkshire, England, makes use of up to 2,000 different hop locations. It is generally seen that the input band width, W, of a frequency hop detector unit is much larger than the width of the binary phase shift keying envelop (BPSK).
- BPSK binary phase shift keying envelop
- the BPSK modulation can be collapsed and the noise decorrelated by a delay-and-complex conjugate multiply stage in which the delay is set to approximately 1/W.
- This method is utilized by the type of hop rate detector known as the MODAC hop rate detector, shown in FIG. 2B.
- the MODAC was developed by Pacific Sierra Research located at Los Angeles, Calif.
- PSKS phase-shift keying signal
- the PSK signal-to-noise ratio is significantly improved by low pass filtering near the hop rate, and a spectral line (at the hop rate) is generated by another delay-and-complete conjugate multiply stage in which the delay is set to approximately T h /2.
- the input band is divided into two "half bands", and the BPSK modulation is collapsed by "magnitude squaring".
- the outputs of the squaring devices are then subtracted to form a bipolar signal fed to a difference amplifier.
- the difference amplifier is AC-coupled (eliminating the DC) to the second stage of the detector because of a direct current (DC), a term generated by the magnitude squaring of the noise involved with the information signal.
- DC direct current
- the input signal hops randomly between the two half bands, and thus the first stage output signal is a random, "direct sequence” (DS) wave form with transitions occurring at the hop rate.
- DS direct sequence
- LPF low-pass filtering
- the AC radiometer collapses the direct sequence (DS) signal by squaring, and then utilizes an integrator or low-pass filter for detection.
- the AC hop rate detector (of FIG. 2) generates a spectral line at the hop rate with use of a delay-and-mix circuit.
- the AC hop rate detector and the AC radiometer are identical.
- the AC hop rate detector delay-and-mixer (FIG. 2A) generates a square wave with one-half the input signal amplitude, and thus, one-fourth the signal power.
- the power in the fundamental of the square wave is further reduced by a factor of 4/ ⁇ 2 .
- the simplified AC radiometer (FIG. 3) generates a DC level when frequency hopped (FH) signals are "present", thus reducing the signal present/signal absent decision to a comparison with a set threshold.
- the "hop rate” can be determined with both the AC hop rate detector (FIG. 2A) and the MODAC hop rate detector (FIG. 2B). Each of these detectors generates a spectral line at the hop rate, which can be detected and characterized by ordinary spectral analysis techniques.
- Another class of detectors which has been shown to be useful against frequency hopped signals are those which utilized "channeling" techniques. At any given point in time, the hybrid FH/DS signal is present in one channel only, thus providing a much higher instantaneous signal-to-noise ratio which can be exploited by various methods.
- Radiometers have been utilized extensively for the purpose of detecting various spread-spectrum signal types, but generally suffer in the presence of narrow-band interference sources. Further channelizers have been utilized where narrow-band interference signal operations is a problem, as it normally is with frequency hopped nets. However, the channelizers suffer from a lack of efficient detection algorithms. Thus, in cluttered frequency bands, in which frequency hopped communication networks operate, it is essentially desireable to have a detector which has considerable immunity to narrow-band (NB) signal interference.
- NB narrow-band
- FH frequency hopped
- the received frequency hopped input signal is divided into L adjacent frequency bands by a channelizer or filter bank.
- Each channel has its own magnitude squaring circuit which generates a power estimate.
- Each power estimate is compared to a preset threshold level by individual channelized threshold detectors which produce a "1" voltage level if the threshold is exceeded, and produce an output "0" otherwise.
- This summation and subtraction is generally accomplished by a differential amplifier and the resulting signal, which is AC-coupled to a radiometer, consists of the noise component and a direct sequence (DS) signal component.
- the DS signal component is present only if a frequency hopped signal (information signal) is present in the input signal, and thus, signal presence is determined by comparison with a threshold.
- one preferred embodiment consists of 16 channels of which eight channels form the upper half band of frequencies and eight channels form a set of lower band of frequencies.
- the channelization is accomplished by using 16 evenly spaced line oscillators (LO's) followed by band pass filters (BPF) all operating at the same intermediate frequency (IF).
- BPF band pass filters
- a threshold comparator performs the one-bit quantization for each channel.
- the upper half set of channels are summed in a first summing circuit while the lower half of the set of channels are summed in a second summing circuit whereby both summing circuits feed into a differential amplifier.
- the signal output from the differential amplifier is AC-coupled to a low-pass filter, then to a power-squaring unit and a second low-pass filter, providing an output which is then compared to a threshold to determine signal presence.
- FIG. 1 is a block diagram of a preferred embodiment of the channelized binary-level radiometer
- FIG. 2A is a block diagram of circuitry for a AC hop rate detector used in reception of frequency hopping transmissions
- FIG. 2B is a block diagram of a MODAC hop rate detector used in reception of frequency hopping transmissions
- FIG. 3 is a simplified block diagram of an AC radiometer using only two channels for accomplishing signal detection of frequency hop signals.
- the incoming signals are received on input line 10 and fed to a series of band pass filters 12.
- the channelization is accomplished by using, for example, 16 evenly spaced local oscillators followed by band pass filters (BPF) all operating at the same intermediate frequency.
- BPF band pass filters
- the input signal 10 being a frequency hopped signal, will, of course, have many variations of different frequency bands.
- a first group of band pass filters is designated B u to indicate representation of an upper band group of channels while a second group of band pass filters is indicated as B d which represent a second or lower group of channels for passing various bands of frequency signals.
- the band pass filters are designated as 12 a , 12 b through 12 i which in the preferred embodiment would represent the first group of eight channels. Then the band pass filters 12 j through 12 n represent the channels involving the second or lower group (B d ) which cover a lower range of frequencies.
- the symbol "L” is used to indicate that the input signal is divided into L adjacent frequency bands by the channelizer filter banks. Subsequently for each channel, there is a set of magnitude squaring circuits 14 which generate a power estimate for each individual channel. Each of these magnitude squaring circuits are designated 14 a through 14 i for the upper set of bands B u and designated as 14 j through 14 n for the lower set of bands B d .
- a "threshold detector” designated 15 a to 15 n involving a preset threshold voltage which will produce a “1" voltage level if the threshold is exceeded, and a "0" level if the threshold is not exceeded.
- each of the first group of threshold detectors 15 are fed to a first summation circuit 16 h1 .
- the outputs of the second group of threshold circuits 15 j through 15 n are fed to a second summation circuit 16 h2 .
- a differential amplifier 18 receives the outputs from the summation circuit 16 h1 and from 16 h2 in order to "add” those from 16 h1 and “subtract” those from 16 h2 .
- the resulting signal is AC-coupled, via capacitor 18 c , to a low pass filter 20.
- This signal consists of a direct sequence (DS) signal component and a noise component.
- the direct sequence (DS) signal will be present only if a frequency hopped (FH) signal is "present” in the input signal, and thus, the "signal presence” will be determined by comparison with a preset threshold level which will overcome and eliminate the noise factor.
- FH frequency hopped
- FIG. 1 The preferred embodiment of FIG. 1 is made to consist of 16 channels of which eight are in the upper group B u and eight are in the lower group B d .
- the low pass filter 20 of FIG. 1 receives the direct sequence and noise signal and is operated with a band pass of approximately 1/T h where T h is the hop dwell time and B represents the pass band frequencies.
- the output of the low pass filter 20 is fed to a magnitude squaring circuit 32 and then feeds it to a low pass filter 34 which has an output signal 40.
- the output signal 40 varies according to the threshold level V x placed in the low pass filter 34 such that if the incoming signal to the low pass filter 34 is above the threshold voltage V x , then the output 40 will signify a voltage indicative of "presence" of a frequency hopped signal while, on the other hand, if the input signal to low pass filter 34 is below the threshold voltage V x , then no voltage output is visible on output line 40 which thus indicates that there is no (absence of) frequency hopped signal at that time.
- the above configuration is designated to work for reception of and detection of the "presence of" frequency hop signals which operate at a "constant" hop rate which is the normally used type of frequency hopped transmission.
- An example of this would be a transmission where the frequency changed at a hop rate of 250 times per second.
- the present configuration combines the reliable quality and strengths of the channelizer features with that of power squaring and filtering techniques to provide a single, hybrid detector-type for signal presence detection.
- threshold detectors With the use of threshold detectors, there has not only been an improvement in performance, but considerably more immunity to narrow band interference sources.
- a channelized binary-level radiometer for detection of "signal presence" for either modulated or unmodulated frequency hopping signals which provide considerable immunity to narrow band interference. These are extremely useful in the cluttered frequency bands in which frequency hopping communication networks operate.
- the final output of the described channelized radiometer is a DC-level voltage signal which can be compared to a preset threshold which will signify whether a signal is present or a signal is absent.
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Abstract
Description
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US07/417,124 US4956644A (en) | 1989-10-04 | 1989-10-04 | Channelized binary-level radiometer |
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US07/417,124 US4956644A (en) | 1989-10-04 | 1989-10-04 | Channelized binary-level radiometer |
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Cited By (14)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5111210A (en) * | 1990-06-22 | 1992-05-05 | Survival Safety Engineering, Inc. | Collision avoidance radar detector system |
US5307379A (en) * | 1992-04-27 | 1994-04-26 | Motorola, Inc. | Automatic noise characterization for optimally enabling a receiver |
US5550546A (en) * | 1993-11-19 | 1996-08-27 | Trw Inc. | Advanced parameter encoder with dual integrated pulse present detection and channel/sector arbitration |
US5569708A (en) * | 1986-03-24 | 1996-10-29 | The Regents Of The University Of California | Self-doped polymers |
US6049562A (en) * | 1995-12-29 | 2000-04-11 | Nokia Telecommunications Oy | Multi-branch frequency-hopping receiver |
US6313620B1 (en) * | 1995-09-14 | 2001-11-06 | Northrop Grumman Corporation | Detector system for identifying the frequency of a received signal useful in a channelized receiver |
US6320896B1 (en) * | 1998-07-14 | 2001-11-20 | Intermec Ip Corp. | RF receiver having frequency-hopping/direct-sequence spread spectrum signal discrimination |
US20020093820A1 (en) * | 1999-08-04 | 2002-07-18 | Pederson John C. | Led reflector |
WO2002089350A1 (en) * | 2001-05-02 | 2002-11-07 | Ensure Technologies, Inc. | Synchronization of wireless communication between devices |
US20050069061A1 (en) * | 2003-09-26 | 2005-03-31 | Lockheed Martin Corporation | Cross-correlation signal detector |
GB2426421A (en) * | 2005-05-19 | 2006-11-22 | Itt Mfg Enterprises Inc | Detection of a frequency coded sequence in the presence of sinusoidal interference |
US7327303B1 (en) * | 2007-03-27 | 2008-02-05 | Information Systems Laboratories, Inc. | Hybrid radar receiver |
US20100019947A1 (en) * | 2008-07-23 | 2010-01-28 | Johannes Kruys | Adaptive sampling of radio frequency channels for radar detection |
US20180109286A1 (en) * | 2015-04-09 | 2018-04-19 | Nokia Solutions And Networks Oy | Frequency hopping method for machine type communication |
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Patent Citations (8)
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Cited By (21)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5569708A (en) * | 1986-03-24 | 1996-10-29 | The Regents Of The University Of California | Self-doped polymers |
US5111210A (en) * | 1990-06-22 | 1992-05-05 | Survival Safety Engineering, Inc. | Collision avoidance radar detector system |
US5307379A (en) * | 1992-04-27 | 1994-04-26 | Motorola, Inc. | Automatic noise characterization for optimally enabling a receiver |
US5550546A (en) * | 1993-11-19 | 1996-08-27 | Trw Inc. | Advanced parameter encoder with dual integrated pulse present detection and channel/sector arbitration |
US6313620B1 (en) * | 1995-09-14 | 2001-11-06 | Northrop Grumman Corporation | Detector system for identifying the frequency of a received signal useful in a channelized receiver |
US6049562A (en) * | 1995-12-29 | 2000-04-11 | Nokia Telecommunications Oy | Multi-branch frequency-hopping receiver |
US6320896B1 (en) * | 1998-07-14 | 2001-11-20 | Intermec Ip Corp. | RF receiver having frequency-hopping/direct-sequence spread spectrum signal discrimination |
US20020093820A1 (en) * | 1999-08-04 | 2002-07-18 | Pederson John C. | Led reflector |
WO2002089350A1 (en) * | 2001-05-02 | 2002-11-07 | Ensure Technologies, Inc. | Synchronization of wireless communication between devices |
US6745042B1 (en) | 2001-05-02 | 2004-06-01 | Ensure Technologies, Inc. | Synchronization of wireless communication between devices |
US20050069061A1 (en) * | 2003-09-26 | 2005-03-31 | Lockheed Martin Corporation | Cross-correlation signal detector |
US7336739B2 (en) | 2003-09-26 | 2008-02-26 | Lockheed Martin Corporation | Cross-correlation signal detector |
GB2426421A (en) * | 2005-05-19 | 2006-11-22 | Itt Mfg Enterprises Inc | Detection of a frequency coded sequence in the presence of sinusoidal interference |
US20060262831A1 (en) * | 2005-05-19 | 2006-11-23 | Kline David R | Method and apparatus for detection of a frequency coded sequence in the presense of sinusoidal interference |
GB2426421B (en) * | 2005-05-19 | 2009-10-14 | Itt Mfg Enterprises Inc | Method and apparatus for detection of a frequency coded sequence in the prescence of sinusoidal interference |
US7672356B2 (en) | 2005-05-19 | 2010-03-02 | Itt Manufacturing Enterprises, Inc. | Method and apparatus for detection of a frequency coded sequence in the presence of sinusoidal interference |
US7327303B1 (en) * | 2007-03-27 | 2008-02-05 | Information Systems Laboratories, Inc. | Hybrid radar receiver |
US20100019947A1 (en) * | 2008-07-23 | 2010-01-28 | Johannes Kruys | Adaptive sampling of radio frequency channels for radar detection |
US7764218B2 (en) * | 2008-07-23 | 2010-07-27 | Cisco Technology, Inc. | Adaptive sampling of radio frequency channels for radar detection |
US20180109286A1 (en) * | 2015-04-09 | 2018-04-19 | Nokia Solutions And Networks Oy | Frequency hopping method for machine type communication |
US11139855B2 (en) | 2015-04-09 | 2021-10-05 | Nokia Technologies Oy | Frequency hopping method for machine type communication |
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