US3812395A - Dual mode twt for low power cw and high power pulsed operation - Google Patents

Dual mode twt for low power cw and high power pulsed operation Download PDF

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Publication number
US3812395A
US3812395A US00333834A US33383473A US3812395A US 3812395 A US3812395 A US 3812395A US 00333834 A US00333834 A US 00333834A US 33383473 A US33383473 A US 33383473A US 3812395 A US3812395 A US 3812395A
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circuit
slow wave
wave circuit
output
switching signal
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US00333834A
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A Scott
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Varian Medical Systems Inc
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Varian Associates Inc
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Priority to US00333834A priority Critical patent/US3812395A/en
Priority to FR7403982A priority patent/FR2218644B1/fr
Priority to DE19742407807 priority patent/DE2407807A1/de
Priority to JP49019871A priority patent/JPS5025168A/ja
Priority to GB775774A priority patent/GB1430925A/en
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01J—ELECTRIC DISCHARGE TUBES OR DISCHARGE LAMPS
    • H01J25/00—Transit-time tubes, e.g. klystrons, travelling-wave tubes, magnetrons
    • H01J25/34—Travelling-wave tubes; Tubes in which a travelling wave is simulated at spaced gaps
    • H01J25/36—Tubes in which an electron stream interacts with a wave travelling along a delay line or equivalent sequence of impedance elements, and without magnet system producing an H-field crossing the E-field
    • H01J25/38—Tubes in which an electron stream interacts with a wave travelling along a delay line or equivalent sequence of impedance elements, and without magnet system producing an H-field crossing the E-field the forward travelling wave being utilised

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  • ABSTRACT A' traveling wave tube is capable of operating over relatively wide bandwidths and with relatively high efficiency at one or the other of two different power output levels which are separated by as much as 10 db.
  • the tube is switchable from one mode of operation to the other in a relatively short period of time, as of a few nanoseconds, by means of a control grid. In switching from the low power C.W.
  • the beam current is increased by a value of several times, as of five; the effective length of the outputsection of the slow wave circuit is automatically decreased; and the phase velocity on the output section of the slow wave circuit is decreased to maintain synchronism with the slow space charge wave of the beam.
  • the invention relates in general to traveling wave tubes and more particularly to an improved traveling wave tube capable of CW. and pulsed mode operation at power levels differing for the two modes by as much as db while maintaining relatively high RF conversion efficiency and bandwidth for both modes.
  • atraveling wave tube of this type should have a pulse power output of 10 kw peak power and provide an output of l kw of CW. power.
  • the tube In either mode of operation the tube should have equally high efficiency, i.e. above 25 percent, andshould maintain this high efficiency and dual mode power output capability over an octave or at least waveguide bandwidth, i.e. 40 percent.
  • An alternative range of power levels might be I kw peak power and 100 watts of average power.
  • the microwave circuit wave phase velocity. This is difficult to obtain in two modes of operation where the beam power is 10 db different since .the circuit wave should be in synchronism with the slow space charge wave even though the slow space charge wave velocity varies greatly with beam current.
  • the gain of the output section of the high power traveling wave tube is always chosen as a compromise between having enough gain for good efficiency and as little gain as possible to eliminate possibilities of oscillation.
  • the beam power changes by as much as 10 db from one mode of operation to the other, it is difficult to prevent oscillation in the highpower mode while preserving good efficiency in the low power mode.
  • a simple approach for obtaining dual mode opera tion in a traveling wave tube is to keep the beam voltage constant and change the beam current over a 10 to 1 range by the use of a high mu grid. This approach is not successful because the space charge in the electron beam determines the synchronism that must be maintained between the electron beam velocity and the circuit wave velocity. Another way of stating this same fact is that the circuit velocity must be synchronous with the slow space charge wave velocity, and of course the slow space charge wave velocity is determined both by the initial electron velocity and by the amount of current in the electron beam.
  • the only possibility for maintaining synchronism in dual mode operations is to change both the current in the beam and the electron beam voltage at the same time.
  • the change in electron beam voltage involves changing the high voltage on the electron beam, but this cannot be accomplished in the required nanosecond switching time.
  • the gain of the output section of the traveling wave tube must be at least 25. db. In most high power traveling wave tubes, the gain is maintained close to this minimum value to reduce the length of the output section as much as possible so that oscillations do not occur. If the output section length is selected to have 25 db gain in the low power CW mode of operation, then the increased gain that occurs with the 10 times higher beam current in the pulse mode will cause oscillation. Alternatively, if the output section length is chosen to have 25 db gain in the high current pulse mode so that oscillations do not occur, the output section will not have enough gain for even reasonable efficiency at the low current level of the CW mode.
  • the principal object of the present invention is the provision of an improved dual mode traveling wave tube for CW. and pulsed mode operation.
  • means are provided, such as' varactor diodes, PIN diodes, etc., connected in circuit with the output portion of the slow wave circuit for changing the phase velocity of the wave energy traveling on' the slow wave circuit such as to maintain synchronism between the slow space charge wave of the beam and the circuit wave as the beam current is switched from one mode of operation to the other, whereby efficient dual mode operation is achieved.
  • means are provided, such as PIN diodes, varactor diodes, etc., coupled in circuit with the output portion of the slow wave circuit, such means being switchable in synchronism with changes in the beam current for changing the effective length of the output slow wave circuit portion such that the gain in the output circuit portion stays within reasonable limits so as to maintain efficiency and gain for both modes of operation.
  • varactor diodes are electrically coupled to the output section of the slow wave circuit.
  • a bias potential is applied to such varactor diodes for changing the capacitive loading of the output section of slow wave circuit to maintain synchronism between the wave energy on the slow wave circuit and the slow space charge wave of the beam for substantially different conditions of beam power.
  • Attenuator means are connectable to the upstream end of the output section of the slow wave circuit via the intermediary of PIN diodes, such diodes being switched into a conductive state concurrently with an increase in beam power to reduce the effective interaction length of the output section of the slow wave circuit to compensate for the increased gain of the output slow wave circuit with increased beam power.
  • diode means responsive to a switching signal, are coupled to the-output section of the slow wave circuit in such a manner as to shift the phase velocity of the circuit wave over a portion of the output circuit by an amount as to place that portion of the circuit out of synchronism with the slow space charge wave of the electron beam to compensate for increased gain of the output section with increased beam current.
  • FIG. I is a schematic longitudinal sectional view, partly in block diagram form, of a traveling wave tube amplifier incorporating features of the present invention
  • FIG. 2 is a schematic view of a portion of the structure of FIG. 1 delineated by line 22,
  • the tube 11 includes an evacuated envelope 12 containing an electron gun assembly 13 at one end thereof for forming and projecting a beam of electrons 14 over an elongated beam path to a beam collector structure 15 disposed at the other end of the envelope 12.
  • a slow wave circuit 16 is disposed along the beam path 14 intermediate the electron gun l3 and collector 15 for cumulative electromagnetic wave interaction with the beam of electrons to produce an amplified output signal extracted from the slow wave circuit via output connector 17.
  • the slow wave circuit 16 is divided into an upstream input section 18 and a downstream output section 19. i I
  • Wave energy to be amplified is fed onto the input slow wave circuit section 18 at the upstream end via an input connector or coupler 21.
  • the phase velocity of the signal wave energy on the slow wave circuit 18 is chosen to be synchronous with'the velocity of the slow space charge wave of the beam to produce amplification of the input microwave signal.
  • the downstream end of the input slow wave circuit section 18 is terminated by an attenuator 22 which serves to absorb the amplified wave energy on the input section 18.
  • the cumulative electromagnetic interaction between the circuit wave and the slow space charge wave produces a bunching of the electron beam in the input section 18 which is carried by the beam into the second or output section 19 of the slow wave circuit 16.
  • the bunched electron beam excites a circuit wave on the output circuit 19 which cumulatively interacts with the beam to produce further velocity modulation and cumulative interaction to produce a greatly amplified output signal on the circuit.
  • the amplified signal is extracted from the output section 19 via the output coupler l7 and fed to a suitable load, not shown.
  • the electron beam 14' is focused through the slow wave circuit 16 by a magnetic beam focus structure 24 coaxially disposed of the beam and the slow wave circuit 16 itself which focuses the beam in a nonintercepting manner.
  • the beam focus structure 24 comprises a periodic permanent magnet focus structure of conventional design wherein the internal pole faces and spacers define the inside wall of the vacuum envelope 12.
  • the beam focus structure 24 may comprise a solenoid producing an axial magnetic field.
  • the electron gun assembly 13 includes a centrally apertured anode 2S and a thermionic cathode 26 having a spherically concave cathode emitting surface 27 coaxially aligned with the central aperture in the anode 25.
  • the electrostatic fields of the gun form and project a convergent flow of electrons through the central aperture in the anode 25.
  • the cathode 26 is heated to thermionic emission temperature by a filamentary heater 28 energized with current from a supply 29 and disposed in heat exchanging relation with the cathode 26.
  • An anode supply 31 supplies anode potential and beam current to the thermionic cathode emitter 26.
  • a high mu non-intercepting control grid 32 overlays the spherically concave emitting surface 27 of the cathode 26 for controlling the beam current produced by the electron gun l3.
  • control grid 32 is supplied with a predetermined fixed positive potential relative to that of the cathode 26 by supply 33 to enable a given power CW mode of operation at a given beam current.
  • the collector electrode 15 is insulated from the envelope 12 via a cylindrical insulator 34 and is supplied with a negative potential by supply 35 to supply depressed collector operation to improve the overall efficiency of the tube.
  • a second, pulsed mode of operation is initiated by a switch 36 which switches the tube from the CW mode to a pulsed mode wherein a pulser 37 supplies pulses of positive potential to the control grid 32 forpulsing the beam current through the interaction circuit 16.
  • a plurality of varactor diodes 38 are connected in shunt between the slow wave circuit 19 and the outer conductive shell or barrel of the tube.
  • the varactor diodes are biased with a potential derived from the pulser 37 via lead 39 for capacitively loading the output portion of the slow wave circuit 19.
  • Diodes 38 reduce the phase velocity of the circuit wave for the signal wave energy to the velocity of the slow space charge beam wave to maintain synchronism and rf conversion efficiency for the tube -11.
  • a second set of diodes 41 such as PIN diodes, are connected to the microwave ground or envelope 12 via attenuators 42 such that when the bias potential is applied from the output of the pulser 37 via lead 43, the diodes 41 are biased into a conducting state for connecting the upstream portion of the output slow wave circuit section 19 to ground via the attenuators 42, thereby effectively terminating or reducing the effective interaction length of the output slow wave circuit portion 19.
  • the gain of the output section 19 is proportional to its length, pulsing the diodes 41 into a conductive state serves to effectively shorten the interaction length of the output section 19 to reduce the overall effective gain for the output section 19 to a suitable value, as of 25 db.
  • the upstream end of the output section 19 is normally connected to attenuator 44 to in hibit undesired backward wave oscillations.
  • a resistor 45 in lead 39 serves to adjust the ratio of the bias voltages applied to the varactors 38 versus the bias potential applied to the PIN diodes 41.
  • DC blocking capacitors 46 are connected in series with each of the diodes 38 and 41 for blocking the DC bias potentials applied via lines 39 and 43 to the diodes 38 and 41,
  • Load resistors 47 and 48 are connected between each of the bias supply lines 39 and 43 and ground to develop the respective bias potentials thereacross.
  • FIG. 2 there is shown an alternative output slow wave circuit portion 19 incorporating an alternative embodiment of the present invention.
  • the structure of FIG. 2 is similar to that of FIG. 1 with the exception that the PIN diodes which serve to shorten the overall length of the output slow wave circuit portion 19 are replaced by varactor diodes 38.
  • the dc bias potential applied to the varactors 38 has two values produced by a voltage divider resistor 49 connected intermediate the length of dc bias supply lead 39 such that the bias potential applied across varactor diodes 38' is substantially greater than the bias potential applied across varactor diodes 38.
  • the phase velocity for wave energy on the slow wave circuit 19 is substantially different over the first part of the circuit controlled by varactors 38' than over the second portion of the circuit controlled by varactors 38.
  • the pulsed control signal applied to lead 39 serves to shift the phase of the signal circuit wave over the upstream portion of the output circuit portion 19 sufficiently so as not to be synchronous with the slow space charge wave of the beam, thereby effectively shortening the overall interaction length of the output section of slow wave circuit 19.
  • the bias applied to the latter portion of the output circuit 19, as loaded by bias varactor diodes 38 serves to reduce the phase velocity of the signal wave energy on the circuit, as previously described with regard to the structure of FIG. 1, to be synchronous with the slow space charge wave of the beam under the conditions of the increased beam current occasioned by the pulsed mode of operation.
  • the output section of slow wave circuit 19 is formed by a tape helix 51 coaxially supported within the cylindrical bore of the envelope 12 by three ceramic rods 52 extending lengthwise of the helix 51.
  • the rods 52 are brazed at the inner and outer side edges to the helix 51 and barrel or bore of the tube 12, respectively.
  • One of the ceramic support rods 52 has formed thereon, as by printed circuit and integrated circuit techniques, the diodes 41 and 38, respectively.
  • the dc bias potential to be applied to the diodes is supplied via a printed circuit lead 39 printed onto the opposite side of the ceramic support rod 52 from the diodes.
  • a dc connection is made through the rod 52 to the center of a spiral inductive RF choke 54.
  • Printed circuit blocking capacitors 46 serve as a microwave or radio frequency connection between the tubular envelope 12 and the helix 5] through the diodes 41 and 38, respectively.
  • FIG. 5 shows an arrangement of PIN diodes 41 connected for shorting (control signalapplied on lead 43) the upstream end of the output slow wave circuit portion 19 to ground through the attenuators 42.
  • the diodes 41 and attenuators 42 are disposed externally of the vacuum envelope 12; the connection from the diodes 41 and attenuators 42 is made to the slow wave circuit 19 through wave permeable gas tight windows 55 formed in the envelope 12.
  • the attenuators may be eliminated and the PIN diodes merely biased with a bias current intermediate those values of current representing full conduction and zero conduction of the diode.
  • the internal resistance of the diode then forms the attenuator 42.
  • FIG. 6 there is shown an altemative embodiment to the structure of FIG. 1 for changing the capacitive loading on the output section of slow wave circuit 19 for varying the phase velocity along the circuit 19.
  • a metallic loading member 39 which also serves as the lead for applying the phase control voltage to the output circuit is capacitively coupled to the slow wave circuit 19 and to the envelope 12.
  • a plurality of PIN diodes 56 are disposed in parallel with the capacitive coupling of the loading shell 39 to the tube envelope 12. The PIN diodes form a switchable connection for shorting out the capacitance between the tube shell 12 and the loading shell 39'.
  • a portion of the loading shell 39' near the upstream end of the output circuit 19 can also be dimensioned such that when the diodes 56 are rendered conductive, the capacitive loading to that upstream portion of the output circuit 19 is increased sufficiently to cause the circuit wave on the output circuit 19 to have a velocity out of synchronism with the slow space charge wave of the beam, thereby efiectively, shortening the output slow wave circuit portion 19 to reduce the gain to prevent undesired oscillation.
  • the diode means for changing the phase velocity and the effective length of the output slow wave circuit portion 19 has been connected in shunt with the output circuit 19, this is not a requirement.
  • the diodes may be connected in series with the slow wave circuit as, for example, connected in between adjacent turns of the helix or between adjacent rings of a ring and bar circuit in parallel with the bars. Attenuators and blocking capacitors would be connected in. series with the diodes for reducing the effective interaction length of the output circuit portion, whereas merely capacitors could be connected in series with the diodes for changing the effective velocity of the output circuit 19. While a helix has been shown as the slow wave circuit in the structure of FIG. 3 this is not a requirement.
  • Suitable alternative slow wave circuits would include, double meander line equivalents of the ring and bar circuit, and a vane loaded double meander line version of the ring and bar circuit as exemplified by US. Pat. No. 3,654,509, issued'Apr. 4, i972.
  • the PIN and varactor diodes for changing the phase velocity and effective length 'of the output slow wave section 19 have been shown extending the full length of the outputsection 19. This is not a requirement. ln high power tubes, i.e., those with peak powers above 100 watts, the diodes, if
  • the diodes for these highpower tubes would not be used in the last few electronic wavelengths of output circuits where the RF field could exceed their I ratings.
  • slow wave circuit means diposed along the beam path so as to enable cumulative electromagnetic interaction between the stream of electrons and a flow of microwave signal power injected on said slow wave circuit means;
  • said slow wave circuit means including an output portion displaced in the direction of said microwave signal power flow from another portion of said slow wave circuit means;
  • said means for changing the phase velocity of the microwave signal wave energy on said output circuit portion includes diode means connected in circuit with said output circuit portion, and means for applying said switching sigmeans is varied to change the phase velocity of the signal wave energy on said output portion of said slow wave circuit means.
  • said means for changing the phase velocity of the microwave signal energy flow on said output circuit portion includes capacitive loading means disposed in signal wave energy exchanging relation with said output portion of said slow wave circuit for capacitively loading said output portion of said slow wave circuit, and meansresponsive to said switching signal for varying the capacitive loading and thus the phase velocity of signal wave energy on said output circuit portion of said slow wave circuit.
  • said means responsive to said switching signal for varying the capacitive loading comprises, diode means connected in circuit with said capacitive loading means and said output portion of said slow wave circuit for varying the effective capacitive loading of said circuit in response to bias potential applied from said switching signal across said diode means.
  • the apparatus of claim 5 including an evacuated envelope containing said electron gun and slow wave circuit, said capacitive loading means comprising an electrically conductive structure capacitively coupled to said output portion of said slow wave circuit and also being capacitively coupled to said envelope, and wherein said means responsive to said switching signal includes diode means connected in shunt with the ca pacitance of said capacitive loading member and said capacitively coupled envelope for shunting out said last mentioned capacitance in response to said switching signal for varying the capactive loading on said output portion of said slow wave circuit means.
  • the apparatus of claim 2 including evacuated envelope means containing therewithin said electron gun means and said slow wave circuit means, electrically insulative support means interposed between said output portion of said slow wave circuit means and said envelope means for supporting said slow wave circuit within said envelope, and wherein said diode means is for changing the effective cumulative beam-field interaction length of said output portion of said slow wave circuit.
  • said second means responsive to a switching signal comprises diode means connected in circuit with said output circuit portion of said slow wave circuit, and means for applying said switching signal as a bias potential across said diode means.
  • slow wave circuit means disposed along the beam path so as to enable cumulative electromagnetic interaction between the stream of electrons and a flow of microwave signal power injected on said slow wave circuit means;
  • said slow wave circuit means including an output portion displaced in the direction of said microwave signal energyflow from another portion of said slow wave circuit means; means for changing the beam current from a first value to a second value at least a few times greater than the first value and for concurrently providing a switching signal;
  • said means responsive to a switching signal comprises diode means connected in circuit with said output circuit portion of said slow wave circuit, and means for applying said switching signal as a bias potential across said diode means.
  • said diode means comprises varactor diode means responsive to the switching signal for changing the effective length of said output circuit by changing the phase velocity for signal wave energy on said circuit by a sufficient amount to cause the signal wave energy on a portion of said output portion of said slow wave circuit to be out of synchronism with the slow space charge wave of the electron beam.
  • the apparatus of claim 12 including attenuator means connected in circuit with said diode means and said output portion of said slow wave circuit such that said diode means is responsive to said switching signal to switch said attenuator means into wave energy exchanging relation with said output portion of said slow wave circuit for changing the effective length of and for terminating a portion of said slow wave circuit in a wave reflectionless manner.
  • the apparatus of claim 14 including evacuated envelope means containing therewithin said electron gun means and said slow wave circuit means, and said diode means and said attenuator means being disposed externally of said envelope means.
  • said diode means comprises PIN diode means.

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US00333834A 1973-02-20 1973-02-20 Dual mode twt for low power cw and high power pulsed operation Expired - Lifetime US3812395A (en)

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Application Number Priority Date Filing Date Title
US00333834A US3812395A (en) 1973-02-20 1973-02-20 Dual mode twt for low power cw and high power pulsed operation
FR7403982A FR2218644B1 (enrdf_load_stackoverflow) 1973-02-20 1974-02-06
DE19742407807 DE2407807A1 (de) 1973-02-20 1974-02-19 Wanderfeldroehre fuer dauerstrich- und impulsbetrieb
JP49019871A JPS5025168A (enrdf_load_stackoverflow) 1973-02-20 1974-02-19
GB775774A GB1430925A (en) 1973-02-20 1974-02-20 Dual mode travelling wave tube for cw and pulsed mode of operation

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US00333834A US3812395A (en) 1973-02-20 1973-02-20 Dual mode twt for low power cw and high power pulsed operation

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JP (1) JPS5025168A (enrdf_load_stackoverflow)
DE (1) DE2407807A1 (enrdf_load_stackoverflow)
FR (1) FR2218644B1 (enrdf_load_stackoverflow)
GB (1) GB1430925A (enrdf_load_stackoverflow)

Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE2931746A1 (de) * 1979-08-04 1981-02-19 Licentia Gmbh Lauffeldroehre
US4471267A (en) * 1982-06-14 1984-09-11 Hughes Aircraft Company Grid structure for certain plural mode electron guns
US4553064A (en) * 1983-08-30 1985-11-12 Hughes Aircraft Company Dual-mode electron gun with improved shadow grid arrangement
US4757269A (en) * 1986-12-18 1988-07-12 The United States Of America As Represented By The Secretary Of The Navy Multi-gigawatt high-efficiency RF amplifier
US5561353A (en) * 1994-09-30 1996-10-01 Northrop Grumman Corporation Cathode pulse modulation of RF transmitter tubes
US6360084B1 (en) 1999-11-03 2002-03-19 The Boeing Company Dual-band RF power tube with shared collector and associated method
US20040032295A1 (en) * 2002-08-14 2004-02-19 Lockheed Martin Corporation Power regulator for intermittent use of traveling wave tube amplifiers in communications satellites
CN110993468A (zh) * 2019-12-30 2020-04-10 中国电子科技集团公司第十二研究所 一种双模折叠波导振荡器及其设计方法

Families Citing this family (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS6346708Y2 (enrdf_load_stackoverflow) * 1981-06-12 1988-12-02
JPS6337504Y2 (enrdf_load_stackoverflow) * 1981-06-12 1988-10-04
JPS5829191U (ja) * 1981-08-20 1983-02-25 セイコ−精機株式会社 気体圧縮機
JPS5829190U (ja) * 1981-08-20 1983-02-25 セイコ−精機株式会社 気体圧縮機
JPS5856183U (ja) * 1981-10-13 1983-04-16 セイコ−精機株式会社 気体圧縮機
US4765056A (en) * 1986-04-03 1988-08-23 Raytheon Company Method of manufacture of helical waveguide structure for traveling wave tubes
RU2404477C1 (ru) * 2009-11-18 2010-11-20 Российская Федерация, от имени которой выступает Государственная корпорация по атомной энергии "Росатом"-Госкорпорация "Росатом" Клистрон

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3573540A (en) * 1969-07-01 1971-04-06 Raytheon Co Microwave traveling wave device with electronically switched interaction characteristics

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE2931746A1 (de) * 1979-08-04 1981-02-19 Licentia Gmbh Lauffeldroehre
US4471267A (en) * 1982-06-14 1984-09-11 Hughes Aircraft Company Grid structure for certain plural mode electron guns
US4553064A (en) * 1983-08-30 1985-11-12 Hughes Aircraft Company Dual-mode electron gun with improved shadow grid arrangement
US4757269A (en) * 1986-12-18 1988-07-12 The United States Of America As Represented By The Secretary Of The Navy Multi-gigawatt high-efficiency RF amplifier
US5561353A (en) * 1994-09-30 1996-10-01 Northrop Grumman Corporation Cathode pulse modulation of RF transmitter tubes
US6360084B1 (en) 1999-11-03 2002-03-19 The Boeing Company Dual-band RF power tube with shared collector and associated method
US20040032295A1 (en) * 2002-08-14 2004-02-19 Lockheed Martin Corporation Power regulator for intermittent use of traveling wave tube amplifiers in communications satellites
US6909235B2 (en) * 2002-08-14 2005-06-21 Lockheed Martin Corporation Power regulator for intermittent use of traveling wave tube amplifiers in communications satellites
CN110993468A (zh) * 2019-12-30 2020-04-10 中国电子科技集团公司第十二研究所 一种双模折叠波导振荡器及其设计方法
CN110993468B (zh) * 2019-12-30 2022-08-30 中国电子科技集团公司第十二研究所 一种双模折叠波导振荡器及其设计方法

Also Published As

Publication number Publication date
JPS5025168A (enrdf_load_stackoverflow) 1975-03-17
FR2218644A1 (enrdf_load_stackoverflow) 1974-09-13
GB1430925A (en) 1976-04-07
FR2218644B1 (enrdf_load_stackoverflow) 1978-09-08
DE2407807A1 (de) 1974-08-22

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