US3737816A - Rectangular cavity resonator and microwave filters built from such resonators - Google Patents

Rectangular cavity resonator and microwave filters built from such resonators Download PDF

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Publication number
US3737816A
US3737816A US00169417A US3737816DA US3737816A US 3737816 A US3737816 A US 3737816A US 00169417 A US00169417 A US 00169417A US 3737816D A US3737816D A US 3737816DA US 3737816 A US3737816 A US 3737816A
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rectangular cavity
inner conductor
resonators
resonator
wall
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H Honicke
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STC PLC
Alcatel Lucent NV
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Standard Telephone and Cables PLC
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/06—Cavity resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/219—Evanescent mode filters

Definitions

  • the present invention relates to a rectangular cavity resonator and to microwave filters formed from such resonators in a ladder network.
  • German Patent 1,120,530 2la4-73 describes a method of manufacturing rectangular cavity resonators from flat sheet metal parts, of the sheets being provided with tongues fitting into corresponding recesses of the other sheets, so that the rectangular waveguide can be formed by plugging together the sheet metal parts, fixing the tongues and then be finished by brazing.
  • microwave filters for the TE mode may be composed of rectangular resonators with inductive diaphragms.
  • the resonant frequencies of the resonators must always lie above a definite fundamental frequency which, for the TE mode, depends on the waveguide width. It is also necessary to maintain the lengths of the resonators within less than 1 percent otherwise the resonant frequencies of the resonators coupled directly via inductive diaphragms would differ widely from each other.
  • microwave filters have become known which are operated considerably above the cutoff wavelength of the waveguide. These filters are not composed of individual coupled resonators but consist ofa single waveguide in which capacitive screws are arranged at a certain spaced relation. These spacings must be maintained with high accuracy.
  • the resonators and the microwave filters composed thereof use none of the above-mentioned conventional methods other than the method of manufacture disclosed in the above-cited German Patent. For their re alization, a different approach is adopted.
  • Another object of the present invention is to employ the manufacturing method of the above-cited German Patent to provide resonators which, independent of the respective resonant frequency required for a filter, have identical outer dimensions, and which, in order to form a ladder network must not have a straight line path for energy propagating through the filter. Rather the resonators must permit achieving a U-shaped or meander-shaped path for energy propagating through the filter by arranging the resonators side by side and in series even if the direction of energy propagation is reversed.
  • a rectangular resonator which not only permits an arbitrary joining together of a plurality of resonators thanks to identical outer dimensions but in which, in addition, the input and the output inductive diaphragms can be arranged in each of the four side walls.
  • a rectangular cavity resonator which is composed of individual sheet metal parts which, mechanically fixed against each other, are interconnected by brazing, is used for building up microwave filters in which the coupling of the individual resonators is effected by means of inductive diaphragms.
  • the invention is characterized in that width, length and height of the individual resonators can be freely chosen within limits such that the resonant frequency of the resonators, dependent thereon, still lies above the operating frequency and that a capacitive inner conductor is provided in each resonator, that the inner conductor is designed so that the inner conductor solely determines any desired resonant frequency of the resonator, and that the coupling factor can be chosen by suitably designing the inductive diaphragms.
  • a feature of the present invention is the provision of a rectangular cavity resonator comprising a rectangular cavity having its width, length and height freely chosen within limits so that the resonant frequency of the rectangular cavity is above a desired operating frequency; inductive coupling diaphragms disposed in selected side walls of the rectangular cavity and having a given design to provide a desired coupling factor for coupling energy into and out of the rectangular cavity; a capacitive inner conductor disposed in one wall of the rectangular cavity and extending into the rectangular cavity toward a wall opposite the one wall, the inner conductor being designed so that only the inner conductor can provide the desired operating frequency for the rectangular cavity.
  • FIG. 1 illustrates the rectangular cavity resonator in accordance with the principles of the present invention
  • FIG. 2 illustrates the resonator of FIG. 1 with another embodiment of the inner conductor thereof;
  • FIG. 3 is a diagram showing the tuning possibilities for a resonator for 2.1 GHZ and 4 GHz;
  • FIG. 4 is a diagram showing the deviations from a linear dependence between the frequency and the depth of insertion of the tuning plunger
  • FIGS. 5a and 5b illustrate the influence of the inductive diaphragm on the resonator of the present invention
  • FIG. 6 illustrates influence of FIG. 5 in a diagram
  • FIG. 7 shows a few of the possibilities for the position of the coupling diaphragms
  • FIG. 8 shows a microwave filter with constant envelope delay for impedance transformation composed of the resonators according to the invention
  • FIG. 9 shows a microwave filter built up by means of the resonators of this invention having a U-shaped path for the energy traversing the filter;
  • FIG. 10 shows a (meander-shaped) microwave filter built up by means of the resonators of this invention having a meander-shaped path for the energy transversing the filter;
  • FIG. 11 is a cross-section through such filters.
  • FIG. 12 is a top view of the filter of FIG. 11.
  • FIG. 1 shows a rectangular cavity resonator 4 capacitively loaded by an inner conductor 3.
  • the wavelength of this resonator may be greater than the cut-off wavelength lt 2a.
  • the lengths c of such resonators formed into a filter by means of inductive diaphragm 2 may be chosen largely independent of the resonant frequencies and the loaded Qs of the individual resonators under other aspects such as necessary resonator quality, space saving, etc. To realize the resonance condition, it is sufficient to properly dimension the inner conductor 3.
  • a capacitively loaded resonator may be regarded and calculated as a coaxial resonator.
  • the resonance conditions for such coaxial resonators can be determined from the equation wCZ ctg 21r(l/ t), 1
  • the inner conductor 3 is provided, at its lower end with a collar 7, as shown in FIG. 2, which forms a relatively great capacitance with respect to the opposite bottom plate 10 while a sufficiently high characteristic impedance is obtained by means of a reduction 8 of the shank of the inner conductor 3.
  • the diaphragms 2 have coupling apertures 9 whose mode of action will be described later.
  • the relation between the diameter D3 of the bore 6 of the inner conductor 3 and the diameter D4 of the tuning plunger 5 must be properly chosen.
  • the diameter ratio D3/D4 can be used to influenced both the increment and the slope (linearity) of the frequency variation during tuning.
  • the tuning plunger 5 is to be made of a low-loss dielectric material, such as quartz glass.
  • FIG. 4 shows the deviations A t of the depth of insertion of the tuning plunger 5 from a completely linear shape for the case of the shape for D3/D4 2 of a tuning plunger 5 with silver-coated cap, shown in FIG. 3, t itself being the depth of insertion of the tuning plunger 5.
  • the normalized susceptance 31,. of the k-th diaphragm of a filter is obtained from the loaded Qs of the (k-l )th circuit Q, and the k-th circuit Q according to the relation
  • the loaded Qs Q,.., and Q of the filter are calculated from the circuit parameters according to the data the filter must meet. They determine the overall width of the filter. The following equation holds:
  • equation (3) resonant frequency. If equation (3) is introduced into equation (2), then 7T Ir l k Furthermore, according to the equivalent circuit (FIG. 5a) of the inductive diaphragm of FIG. 5a the following equation holds:
  • the inductance L in equation (6) must have a frequency response which counteracts any extension of the bandwidth as the frequency increases. This can be achieved by means of a diaphragm as shown in FIG. 5b, which has a coupling aperture whose height h approximately corresponds to the stroke of the tuning plunger 5, the distance plunger 5 moves to tune the resonator through its frequency range. As the tuning plunger 5 approaches the bottom plate during tuning to lower frequencies, the magnetic field lines forming in the region of the coupling apertures 9 increase in density and cause a tighter coupling of the resonators. Thus, the equivalent circuit of FIG. 5b has a coupling inductance whose value changes with 1/).
  • the height h and the width d of the coupling apertures 9, the length of the inner conductor 3 and the spacings of the inner conductor 3 from the diaphragms must be chosen so that, in the tuning range, the coupling admittance y according to equation (4) decreases linearly in firstorder approximation as the frequency decreases.
  • the coupling admittances between the individual resonators and the distances of the inner conductors 3 from the diaphragms 2 differ from each other.
  • the resonator lengths, i.e. the spacings between the diaphragms 2 slightly differ from each other, too.
  • curve a clearly shows the strong dependence of the bandwidth B on the frequency adjustment of a four-section filter with resonators according to FIG. 2 having a slot diaphragm according to FIG. 5a. If the filter is provided with diaphragms 2 and coupling apertures as shown in FIG. 5b and the other measures to compensate for the coupling admittance are also taken, the curve I; is obtained which shows only little change in bandwidth.
  • a diameter D1 of the collar 7 of the inner conductor 3 of 20 mm was chosen for a resonant frequency of 2.3 GHz.
  • the length I of the inner conductor was 17 mm.
  • the diameter of the collar of the inner conductor is D1 15 mm.
  • the length of the inner conductor is 8 mm, and the smaller diameter D2 of the reduction 8 is 13 mm.
  • length of the inner conductor and resonator length c could also be reduced by means of the diameter ratio D1/D2.
  • the length c of the resonator 4 without inner conductor 3 would have to be about )tg/Z, i.e. about 57 mm, for the abovementioned frequency of 4.2 GHz.
  • a considerable shortening of the resonator length 0 is also achieved for those resonators whose resonant frequencies are above the cut-off frequencies.
  • FIG. 7 illustrates a further advantage which the resonator according to the invention has for the design of multi-section microwave filters. Since the electric field lines extend parallel to the axis of the inner conductor while the magnetic field lines extend around the middle conductor, coupling-out can be effected at each of the three other side walls of the resonator.
  • One inductive coupling-in or coupling-out aperture 9 may be associated with a plurality of inductive coupling-out or coupling-in apertures.
  • FIGS. 9 and 10 show a microwave filter with bandpass behavior, which consists of a ladder network of 6 resonators A F. While in the case of the filter shown in FIG. 9 theresonators are disposed in an arrangement to provide a U-shaped energy path, the arrangement of the resonators of FIG. 10 provides a meander-shaped energy path.
  • FIG. 11 shows a longitudinal section through a filter as shown in FIGS. 8 and 9 but without the additional diaphragms k and k of FIG. 8 while FIG. 12 is a top view of a filter as shown in FIGS. 8 and 9.
  • microwave filters e.g. a filter according to FIGS. 9, 11 and 12 for the range 3.8 4.2 GHZ, exactly corresponded, in their electrical behavior, to a microwave filter consisting of resonators arranged in a straight line.
  • Length, width and height can be freely chosen within certain limits, In so doing, parameters such as the unloaded Q of the resonator, space saving, etc., can be taken into account.
  • the lengths c of all resonators of a filter can be the same.
  • the resonant frequency is determined only by the inner conductor.
  • the special design of the inner conductors a wide and practically linear tuning range is obtained.
  • the resonators of a filter may be disposed to provide a U- or meander-shaped configuration of the energy path transmitted therethrough, so that compact designs are obtained which are adapted to the space available.
  • a rectangular cavity resonator comprising:
  • a rectangular cavity having its width, length and height freely chosen within limits so that the resonant frequency of said rectangular cavity is above a desired operating frequency
  • inductive coupling diaphragms disposed in selected walls of said rectangular cavity and having a given configuration to provide a desired coupling factor for coupling energy into and out of said rectangular cavity;
  • a capacitive inner conductor disposed to extend through a first wall of said rectangular cavity into said rectangular cavity toward a second wall thereof opposite said first wall;
  • said inner conductor including a first portion directly connected to said first wall having a first given diameter
  • a cylindrical tuning plunger disposed within said coaxial bore concentric with said longitudinal axis of said inner conductor having fourth given diameter less than said third given diameter
  • said tuning plunger including being composed of a low-loss insulating material and capable of adjustment relative to said second wall by a screw thread,
  • said first, second and third given diameters of said inner conductor, said fourth diameter of said tuning plunger and the length of said tuning plunger extending from said second portion being selected to cooperate in providing said desired operating resonant frequency for said rectangular cavity.
  • a resonator according to claim 1 wherein said conductive material is silver.
  • a resonator according to claim 1 wherein said tuning plunger travels a given distance to tune said rectangular cavity through the tuning range thereof, and
  • the height of said coupling aperture is approximately equal to said given distance.
  • a resonator according to claim I wherein a plurality of said resonators are disposed in an arrangement to provide a microwave filter having a meander-shaped path for energy traveling therethrough.
  • a resonator according to claim 1 wherein a plurality of said resonators are disposed in an arrangement to provide a microwave filter having U- shaped path for energy traveling therethrough.

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US00169417A 1970-09-15 1971-08-05 Rectangular cavity resonator and microwave filters built from such resonators Expired - Lifetime US3737816A (en)

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DE2045560A DE2045560C3 (de) 1970-09-15 1970-09-15 Mikrowellenfilter aus quaderförmigen Hohlraumresonatoren

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AU (1) AU466409B2 (de)
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CH (1) CH532845A (de)
DE (1) DE2045560C3 (de)
ES (1) ES395068A1 (de)

Cited By (28)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3882434A (en) * 1973-08-01 1975-05-06 Microwave Dev Lab Phase equalized filter
US4034319A (en) * 1976-05-10 1977-07-05 Trw Inc. Coupled bar microwave bandpass filter
US4216448A (en) * 1977-01-21 1980-08-05 Nippon Electric Co., Ltd. Microwave distributed-constant band-pass filter comprising projections adjacent on capacitively coupled resonator rods to open ends thereof
US4246555A (en) * 1978-07-19 1981-01-20 Communications Satellite Corporation Odd order elliptic function narrow band-pass microwave filter
FR2477783A1 (fr) * 1980-03-04 1981-09-11 Thomson Csf Dispositif d'accord a capacite variable et filtre hyperfrequences accordable comportant au moins un tel dispositif
US4360793A (en) * 1981-04-02 1982-11-23 Rhodes John D Extracted pole filter
US4396896A (en) * 1977-12-30 1983-08-02 Communications Satellite Corporation Multiple coupled cavity waveguide bandpass filters
US4535308A (en) * 1983-05-16 1985-08-13 Northern Telecom Limited Microwave cavity tuner
US4706051A (en) * 1983-07-08 1987-11-10 U.S. Philips Corporation Method of manufacturing a waveguide filter and waveguide filter manufactured by means of the method
US4794354A (en) * 1987-09-25 1988-12-27 Honeywell Incorporated Apparatus and method for modifying microwave
US4990869A (en) * 1988-11-04 1991-02-05 U.S. Philips Corporation UHF bandpass filter
FR2665577A1 (fr) * 1990-07-31 1992-02-07 Alcatel Telspace Filtre hyperfrequence de puissance, notamment filtre de sortie pour emetteur de radiocommunications.
US5153541A (en) * 1991-05-20 1992-10-06 At&T Bell Laboratories Folded interdigital notch filter
US5243309A (en) * 1992-06-04 1993-09-07 Ghz Technologies Inc. Temperature stable folded waveguide filter of reduced length
US5406233A (en) * 1991-02-08 1995-04-11 Massachusetts Institute Of Technology Tunable stripline devices
US5410284A (en) * 1992-12-09 1995-04-25 Allen Telecom Group, Inc. Folded multiple bandpass filter with various couplings
US5608363A (en) * 1994-04-01 1997-03-04 Com Dev Ltd. Folded single mode dielectric resonator filter with cross couplings between non-sequential adjacent resonators and cross diagonal couplings between non-sequential contiguous resonators
US5777534A (en) * 1996-11-27 1998-07-07 L-3 Communications Narda Microwave West Inductor ring for providing tuning and coupling in a microwave dielectric resonator filter
US5781085A (en) * 1996-11-27 1998-07-14 L-3 Communications Narda Microwave West Polarity reversal network
US5841330A (en) * 1995-03-23 1998-11-24 Bartley Machines & Manufacturing Series coupled filters where the first filter is a dielectric resonator filter with cross-coupling
US5919562A (en) * 1998-10-13 1999-07-06 Gm Nameplate, Inc. Repositionable mouse pad
US6275124B1 (en) * 1998-07-24 2001-08-14 Lucent Technologies Inc. Delay line filter having a single cross-coupled pair of elements
US20030117241A1 (en) * 2001-12-21 2003-06-26 Radio Frequency Systems, Inc. Adjustable capacitive coupling structure
US20040021533A1 (en) * 2000-05-23 2004-02-05 Yasunao Okazaki Dielectric resonator filter
JP2008098727A (ja) * 2006-10-06 2008-04-24 Mitsubishi Electric Corp 帯域通過フィルタ
US20150280299A1 (en) * 2014-03-27 2015-10-01 Electronics And Telecommunications Research Institute Waveguide band pass filter using short-circuit stub for rejection performance improvement
US20150295294A1 (en) * 2014-04-10 2015-10-15 Alexandre Rogozine RF Duplexer Filter Module with Waveguide Filter Assembly
RU197717U1 (ru) * 2020-01-29 2020-05-25 Акционерное общество «Российская корпорация ракетно-космического приборостроения и информационных систем» (АО «Российские космические системы») СВЧ-фильтр

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107615572B (zh) * 2014-12-30 2019-11-26 深圳市大富科技股份有限公司 腔体滤波器及射频拉远设备、信号收发装置和塔顶放大器

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2594037A (en) * 1946-08-28 1952-04-22 Rca Corp Ultrahigh-frequency filter
US2749523A (en) * 1951-12-01 1956-06-05 Itt Band pass filters
US3137828A (en) * 1961-08-01 1964-06-16 Scope Inc Wave guide filter having resonant cavities made of joined parts
US3353122A (en) * 1962-08-24 1967-11-14 Marconi Co Ltd Waveguide filters having adjustable tuning means in narrow wall of waveguide

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2594037A (en) * 1946-08-28 1952-04-22 Rca Corp Ultrahigh-frequency filter
US2749523A (en) * 1951-12-01 1956-06-05 Itt Band pass filters
US3137828A (en) * 1961-08-01 1964-06-16 Scope Inc Wave guide filter having resonant cavities made of joined parts
US3353122A (en) * 1962-08-24 1967-11-14 Marconi Co Ltd Waveguide filters having adjustable tuning means in narrow wall of waveguide

Cited By (39)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3882434A (en) * 1973-08-01 1975-05-06 Microwave Dev Lab Phase equalized filter
US4034319A (en) * 1976-05-10 1977-07-05 Trw Inc. Coupled bar microwave bandpass filter
US4216448A (en) * 1977-01-21 1980-08-05 Nippon Electric Co., Ltd. Microwave distributed-constant band-pass filter comprising projections adjacent on capacitively coupled resonator rods to open ends thereof
US4396896A (en) * 1977-12-30 1983-08-02 Communications Satellite Corporation Multiple coupled cavity waveguide bandpass filters
US4246555A (en) * 1978-07-19 1981-01-20 Communications Satellite Corporation Odd order elliptic function narrow band-pass microwave filter
EP0035922B1 (de) * 1980-03-04 1984-06-20 Thomson-Csf Abstimmungsvorrichtung mit veränderbarer Kapazität und abstimmbares Mikrowellenfilter mit wenigstens einer solchen Vorrichtung
US4380747A (en) * 1980-03-04 1983-04-19 Thomson-Csf Tunable ultra-high frequency filter with variable capacitance tuning devices
FR2477783A1 (fr) * 1980-03-04 1981-09-11 Thomson Csf Dispositif d'accord a capacite variable et filtre hyperfrequences accordable comportant au moins un tel dispositif
US4360793A (en) * 1981-04-02 1982-11-23 Rhodes John D Extracted pole filter
US4535308A (en) * 1983-05-16 1985-08-13 Northern Telecom Limited Microwave cavity tuner
US4706051A (en) * 1983-07-08 1987-11-10 U.S. Philips Corporation Method of manufacturing a waveguide filter and waveguide filter manufactured by means of the method
US4794354A (en) * 1987-09-25 1988-12-27 Honeywell Incorporated Apparatus and method for modifying microwave
US4990869A (en) * 1988-11-04 1991-02-05 U.S. Philips Corporation UHF bandpass filter
FR2665577A1 (fr) * 1990-07-31 1992-02-07 Alcatel Telspace Filtre hyperfrequence de puissance, notamment filtre de sortie pour emetteur de radiocommunications.
US5406233A (en) * 1991-02-08 1995-04-11 Massachusetts Institute Of Technology Tunable stripline devices
US5153541A (en) * 1991-05-20 1992-10-06 At&T Bell Laboratories Folded interdigital notch filter
US5243309A (en) * 1992-06-04 1993-09-07 Ghz Technologies Inc. Temperature stable folded waveguide filter of reduced length
US5410284A (en) * 1992-12-09 1995-04-25 Allen Telecom Group, Inc. Folded multiple bandpass filter with various couplings
US5608363A (en) * 1994-04-01 1997-03-04 Com Dev Ltd. Folded single mode dielectric resonator filter with cross couplings between non-sequential adjacent resonators and cross diagonal couplings between non-sequential contiguous resonators
US5841330A (en) * 1995-03-23 1998-11-24 Bartley Machines & Manufacturing Series coupled filters where the first filter is a dielectric resonator filter with cross-coupling
US6037541A (en) * 1995-03-23 2000-03-14 Bartley R.F. Systems, Inc. Apparatus and method for forming a housing assembly
US6094113A (en) * 1995-03-23 2000-07-25 Bartley Machines & Manufacturing Dielectric resonator filter having cross-coupled resonators
US6239673B1 (en) 1995-03-23 2001-05-29 Bartley Machines & Manufacturing Dielectric resonator filter having reduced spurious modes
US5777534A (en) * 1996-11-27 1998-07-07 L-3 Communications Narda Microwave West Inductor ring for providing tuning and coupling in a microwave dielectric resonator filter
US5781085A (en) * 1996-11-27 1998-07-14 L-3 Communications Narda Microwave West Polarity reversal network
US6275124B1 (en) * 1998-07-24 2001-08-14 Lucent Technologies Inc. Delay line filter having a single cross-coupled pair of elements
US5919562A (en) * 1998-10-13 1999-07-06 Gm Nameplate, Inc. Repositionable mouse pad
US20040029540A1 (en) * 2000-05-23 2004-02-12 Yasunao Okazaki Dielectric resonator filter
US20040021533A1 (en) * 2000-05-23 2004-02-05 Yasunao Okazaki Dielectric resonator filter
US6700461B2 (en) * 2000-05-23 2004-03-02 Matsushita Electric Industrial Co., Ltd. Dielectric resonator filter
US6771146B2 (en) 2000-05-23 2004-08-03 Matsushita Electric Industrial Co., Ltd. Dielectric resonator filter
US6861928B2 (en) 2000-05-23 2005-03-01 Matsushita Electric Industrial Co., Ltd. Dielectric resonator filter
US20030117241A1 (en) * 2001-12-21 2003-06-26 Radio Frequency Systems, Inc. Adjustable capacitive coupling structure
US6836198B2 (en) 2001-12-21 2004-12-28 Radio Frequency Systems, Inc. Adjustable capacitive coupling structure
JP2008098727A (ja) * 2006-10-06 2008-04-24 Mitsubishi Electric Corp 帯域通過フィルタ
US20150280299A1 (en) * 2014-03-27 2015-10-01 Electronics And Telecommunications Research Institute Waveguide band pass filter using short-circuit stub for rejection performance improvement
US20150295294A1 (en) * 2014-04-10 2015-10-15 Alexandre Rogozine RF Duplexer Filter Module with Waveguide Filter Assembly
US9466864B2 (en) * 2014-04-10 2016-10-11 Cts Corporation RF duplexer filter module with waveguide filter assembly
RU197717U1 (ru) * 2020-01-29 2020-05-25 Акционерное общество «Российская корпорация ракетно-космического приборостроения и информационных систем» (АО «Российские космические системы») СВЧ-фильтр

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BE772602A (nl) 1972-03-15
DE2045560C3 (de) 1978-03-09
CH532845A (de) 1973-01-15
AU466409B2 (en) 1975-10-30
ES395068A1 (es) 1975-11-16
AU3307371A (en) 1973-03-08
DE2045560B2 (de) 1977-07-14
DE2045560A1 (de) 1972-03-16

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AS Assignment

Owner name: ALCATEL N.V., DE LAIRESSESTRAAT 153, 1075 HK AMSTE

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNOR:INTERNATIONAL STANDARD ELECTRIC CORPORATION, A CORP OF DE;REEL/FRAME:004718/0023

Effective date: 19870311