US3689827A - Voltage and current regulated power supply circuit for gaseous discharge lamp - Google Patents

Voltage and current regulated power supply circuit for gaseous discharge lamp Download PDF

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Publication number
US3689827A
US3689827A US102610A US3689827DA US3689827A US 3689827 A US3689827 A US 3689827A US 102610 A US102610 A US 102610A US 3689827D A US3689827D A US 3689827DA US 3689827 A US3689827 A US 3689827A
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output
circuit means
circuit
voltage
power supply
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US102610A
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Halsey P Quinn
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Cooper Industries LLC
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Wagner Electric Corp
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Assigned to STUDEBAKER-WORTHINGTON, INC. reassignment STUDEBAKER-WORTHINGTON, INC. ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: WAGNER ELECTRIC CORPORATION
Assigned to EDISON INTERNATONAL, INC. reassignment EDISON INTERNATONAL, INC. ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: STUDEBAKER-WORTHINGTON, INC., A CORP. OF DE
Assigned to COOPER INDUSTRIES, INC., 1001 FANNIN, HOUSTON, TEXAS 77002, A CORP. OF reassignment COOPER INDUSTRIES, INC., 1001 FANNIN, HOUSTON, TEXAS 77002, A CORP. OF ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: EDISON INTERNATIONAL, INC., A CORP. OF DE.
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • ABSTRACT A voltage and current regulated circuit operative to supply sinusoidal high-frequency (28 kilohertz) electrical power which meets both the starting and running requirements of a gaseous discharge lamp without mechanical switching means or saturable 22 T, 44, 45, 62; 321/16, 18, 19 reactors.
  • the present invention relates to a power supply circuit, operative to generate and regulate both sinusoidal high-frequency voltage and current outputs for a variable-impedance load having widely-variable voltage and current requirements, e.g., a gaseous discharge lamp.
  • a load presents a unique problem because it initially requires a very high, regulated starting voltage and then, after the gaseous discharge has been initiated by the vflow of current through the lamp, a constant lamp current at a low voltage is required.
  • the present invention is embodied in a single supply circuit which does not utilize saturable reactors and which has two modes of operation, one for starting and one for running the lamp.
  • the output voltage is regulated when the supply circuit is in the starting mode, and the output current is regulated when the supply circuit is in the running mode.
  • a resonant circuit builds up a controlled high voltage only during the starting mode.
  • current regulation is effected by supplying high-frequency current pulses of constant amplitude and variable width to the input of a power circuit.
  • the width of the pulses is controlled by a variable bias voltage derived .from the output of the supply circuit combined with a series of saw-tooth pulses in a summation circuit.
  • a significant feature of this invention is the generation of a saw-tooth wave in synchronization with an oscillator by charging a capacitor through a first current path during one time interval and discharging that capacitor through the oscillator during a second time interval corresponding to the interpulse null of the oscillator.
  • the circuit shown therein is operable with a standard alternating current power source (117 volts RMS, 60 hertz) connected between input terminals 002 and 004.
  • a switch 006 connected to the high input terminal 002 enables control of the application of power to transformer 100,
  • variable-width pulse generator 500 which energizes the filaments of lamp 200, and to the AC/DC conversion circuit 300, the output of which is fed to high frequency oscillator 400 via switch 008 and resistance 010, to variable-width pulse generator 500, and to power circuit 600.
  • the high-frequency sinusoidal output voltage and current are monitored by voltage and current sensing circuits 800 and 900, respectively, the outputs of which are fed to bias circuit 1000.
  • the output of the bias circuit 1000 is fed to the variable-width pulse generator 500 to cause variations in the width of the high-frequency, constant-amplitude pulses which comprise the input to power circuit 600.
  • the AC/DC conversion circuit 300 includes a diode bridge full-wave rectifier circuit comprising diodes 5 302, 304, 306 and 308, a pair of choke coils 310 and 312 which are preferably inductively coupled by a common core 314 to act as a low-pass filter, and a capacitor'3l6 to eliminate substantially all of the AC ripple in the DC output.
  • An output voltage of approximately bolts DC is generated across capacitor 316 and is applied through switch 008 and resistance 010 to high-frequency oscillator 400, which is illustrated in detail in FIG. 3 and described in subsequent paragraphs.
  • variable-width pulse generator 500 The DC power output of AC/DC conversion circuit 300 is applied to the variable-width pulse generator 500 through the current-limiting resistance 516, which is efiectively in series with zener diode 524 between the output terminals of the AC/DC conversion circuit 300.
  • a constant DC voltage of approximately 5 volts DC is applied to the variable-width pulse generator 500, which comprises a charging circuit formed by resistance 502 and'capacitance 520, their junction being connected via resistance 504 to the base of transistor 526.
  • a discharge circuit for capacitance 520 is formed by diode 522 and resistance 506 connected in series between the aforementioned junction and the output terminal of high-frequency oscillator 400.
  • saw-tooth pulses along with the variable negative DC bias derived from the bias circuit 1000 and applied to the base of transistor 526, are amplified by the two-stage DC amplifier formed by transistor 526, resistance 508, transistor 528 and resistance 512.
  • the combined and amplified saw-tooth pulses and variable DC bias comprise one input to the NAND gate 532,
  • the positive high-frequency rectangular output pulses of oscillator 400 comprise the second input to the NAND gate 532. Only when both of these positive input signals are above the threshold voltage of NAND gate 532 is a negative output signal generated. Since the period of time during which the first input signal is above that threshold varies according to the variable DC component of the first input signal, the output pulses of NAND gate 532 will vary accordingly.
  • the variable-width, constant-amplitude, negative pulses which capacitance 518 to the base of normally conductive amplifier transistor 530, which is resultantly pulsed non-conductive to provide variable-width, positive input voltage pulses to the low terminal of winding 614 in power circuit 600.
  • the primary winding 614 of transformer 610 is connected in series with resistance 604 between the positive terminal of AC/DC conversion circuit 300 and the collector of transistor 530.
  • resistance 604 between the positive terminal of AC/DC conversion circuit 300 and the collector of transistor 530.
  • the resonant circuit 700 comprises first capacitance 702 connected across the output terminals of the autotransformer 616, a second capacitance 704 of approximately one-third the magnitude of first capacitance 702, and an inductance 706 connected between the low terminals of capacitances 702 and 704, whose high terminals are both connected to the positive output terminal of AC/DC conversion circuit 300, and to the lamp filament 204 by a center-tap connection to secondary winding 104 of transformer 100. Also, the low side of capacitance 704 is connected through the primary winding 916 of transformer 914 and through a center-tap connection of secondary winding 106 of transformer 100 to filament 202 of lamp 200.
  • the high-frequency power pulses appearing across the output terminals of autotransformer 616 are injected into the series resonant circuit 700 and cause that circuit to oscillate at the second harmonic of the frequency of the power pulses when the impedance of lamp 200 is high, i.e., when the lamp has not been started. Conse-quently, the voltage across the smaller capacitance 704 becomes very high and effects start-up of the lamp 200.
  • the voltage thus developed across the relatively high impedance of capacitance 704 has the frequency of the second harmonic of the high frequency power pulses injected into resonant circuit 700, i.e.,
  • the voltage applied to the load across the center-tap connections from the resonant circuit 700 to the secondary windings 104 and 106 of transformer. is monitored by the voltage sensing circuit 800, which is connected to the center-tap connection to the secondary winding 106. From this point, a capacitance 804 is connected to the junction of a pair of series-connected diodes 808 and 810, which are paralleled by a capacitance 806 and by a resistance 802, the output signal being derived from the latter by an adjustable tap connected through isolating diode 812 to bias circuit 1000. Diode 812 blocks the output current signal from current sensing circuit 900.
  • the current sensing circuit 900 is of similar construction, but includes a transformer 914 having fixed and variable resistances 902 and 904, respectively, connected in series across its secondary winding 918, withthe primary winding 916 being connected in series with inductance 706 of resonant circuit 700 and the center tap connection to the secondary winding 106 of transformer 100.
  • a capacitance 906 is connected from a junction of secondary winding 918 and resistance 902 to the junction of two series-connected diodes 910 and 912, which are paralleled by a capacitance 908.
  • the output of this circuit is derived from the junction of capacitance 908 and the anode of diode 912, and is applied to bias circuit 1000 along the same conductor as the output of current sensing circuit 800.
  • Bias circuit 1000 comprises resistances 1002 and 1004 connected in series between the base of transistor 526 and the outputs of voltage and current sensing circuits 800 and 900, and a resistance 1006 connected from the high side of voltage-regulating zener diode 524 to the junction of resistances 1002 and 1004.
  • These three interrelated circuits 800, 900 and 1000 form a feed-back loop from the 'output of the supply circuit to the first stage of the two-stage DC amplifier of the variable-width pulse generator 500.
  • the high-frequency alternating voltage impressed across the lamp filaments 202 and 204 is passed through capacitance 804, rectified by the diodes 808 and 810, and filtered by capacitance .806.
  • the voltage across capacitance 806 is impressed across resistance 802, from which a negative signal is picked off through a tap and applied through isolating diode 812 to the bias circuit. This signal is added through resistance 1004 to the steady positive bias voltage generated across resistances 1006 and 1002 of the bias circuit 1000.
  • the negative DC voltage applied by voltage sensing circuit 800 will alter the bias at the base of transistor 526 by making it less positive. Consequently,
  • the DC component of the signal applied as the first input to the NAND gate 532 will be lowered so as to cause a decrease in the width of the output pulses of the pulse generator 500.
  • the opposite variation is made upon the bias voltage at the base of transistor 528, with the opposite effect of increased pulse width.
  • the current sensing circuit 900 performs a similar function by generating a voltage across the two seriesconnected resistances 902 and 904 across the secondary winding 918 of transformer 914, applying this voltage through capacitance 906 to rectifying diodes 910 and 912 which cause capacitance 908 to become negatively charged with respect to ground. Variations in the level of negative charge will cause variations in the net bias voltage at the base of transistor 526 and consequently in the width of the output pulses of pulse generator 500 in the same manner as described above.
  • FIG. 2(a) illustrates the saw-tooth pulses generated at the base of transistor 526, with the dotted line representing the net negative voltage fed to bias circuit 1000 by the voltage and current sensing circuits 800 and 900, respectively.
  • FIG. 2(c) illustrates the width of the output pulses of the two-stage DC amplifier appearing at the collector of transistor 528 as narrowed as a result of the increasingly negative DC bias.
  • FIG. 2(d) illustrates the voltage at the base of the first-stage transistor 526 when the negative voltage produced by the voltage and current sensing circuits is relatively low, resulting in wider pulses appearing at the collector of transistor 528 as shown in FIG.
  • FIG. 2(f) illustrates the wave form of the bias voltage appearing at the base of transistor 530 during circuit operation. Absent any output from NAND circuit 532, the base is slightly positive.
  • this negative pulse is applied via capacitance 518 to the base of transistor 530 to render same negative, thereby cutting off the flow of current from the positive terminal of AC/DC conversion circuit 300 through resistance 604, through the primary winding 614 of transformer 610 and the parallel-connected resistance 602, and through the collector-emitter junction of transistor 530.
  • a pulse is generated across secondary winding 612 of transformer 610 corresponding in duration to the period of nonconductivity of transistor 530.
  • Power transistor 608 becomes conductive for a like period of time and causes the generation of a current pulse of equal duration in the input winding segment 618 of autotransformer 616.
  • the collector of transistor 530 which is normally at virtually ground potential when this transistor is conductive, becomes positive for periods corresponding directly to the duration of the negative pulses applied by NAND circuit 532 to the base of transistor 530.
  • the oscillator circuit shown in FIG. 3 is preferred because of its efiiciency.
  • This oscillator circuit comprises essentially a first-stage transistor switch having its output connected to the input of a second-stage transistor switch, with a resonant series circuit interconnecting the input of the first-stage switch and the output of the second-stage switch.
  • the output of the first-stage switch is connected to the input of that switch via a feedback loop comprising resistance 419 to make the oscillator circuit more linear and to enable oscillation.
  • VS 447 1002 10K ohms 308- 1004 10K ohms 426 (IC) 1006 10K ohms 428 -(IC) 522 lN9l4 Transistors 524 lN522l 808 lN5059 430 (IC) 810 1N5059 432-(IC) 812- lN9l4 434-(IC) 910- 1N9l4 436-(IC) 912- 1N9l4 43s (IC) 440 (IC) Transformers 442 (IC) 4 Primary winding 102 526 2N5 l 83 I 1 M5 turns Secondary windings 528 2N5l83 104 and 106 47 turns 530 DTS411 610 Primary winding 614 5 turns Secondary winding 610 608 MJE34O I50 turns 616 Winding segment 618 84 turns Winding segment 620 NAND Gate l4 turns 914 Primary winding 616 s turns Secondary winding 918 532 integrated with ISO turns oscill
  • third circuit means which, when coupled to the variable-impedance load is operative in response to the output of said second circuit means to generate high frequency, high voltage output power when the load impedance is high, and to generate high frequency, low voltage output power when the load impedance is low;
  • fourth circuit means operative to provide a variable bias signal to said second circuit means to vary the width of the output pulses of said second circuit means in response to variations in the output voltage and current from their predetermined normal levels.
  • said first circuit means comprises:
  • a diode bridge circuit having first and second input and output terminals
  • first and second inductances each having first and second terminals, said first terminal of said first inductance being connected to said first output terminal of said diode bridge circuit, and said first terminal of said second inductance being connected to said second output terminal of said diode bridge circuit;
  • high frequency oscillator means operative to generate high-frequency rectangular pulses
  • saw-tooth pulse generating means synchronized with said high-frequency oscillator means
  • first amplification circuit means connected to said saw-tooth pulse generating circuit and operative to amplify the output of said saw-tooth pulse generating means and said variable bias signal;
  • threshold circuit means having a first input terminal connected to the output of said first amplification circuit means and a second input terminal connected to the output of said high-frequency oscillator means, and operative to generate output pulses of constant amplitude and of variable width corresponding to the period of time during which both of said input pulses exceed its threshold;
  • second amplification circuit means operative to generate output pulses of predetermined polarity, constant amplitude, and variable width corresponding to the width of the output pulses of said threshold circuit means.
  • said high-frequency oscillator means comprises:
  • a first-stage transistor switch including a feedback 2.
  • a second-stage transistor switch
  • a capacitance and a charging resistance connected 3. a power transistor having its base and emitter connected across said secondary winding of said transformer, and having its collector connected through said second and first terminals of said autotransformer to said first circuit means; and
  • resonant circuit means connected between said first and thrid terminals of said autotransformer and operative to generate a high voltage by resonating at a first high frequency in response to input power pulses from said autotransformer when said load impedance is high, and by resonating at a second high frequency in response to input power pulses from said autotransformer when said load impedance is low.
  • said fourth circuit means comprises:
  • voltage sensing circuit means operative to generate an output voltage deviating from a predetermined norm in response to variations in the output voltage of said power supply circuit from a predetermined value
  • current sensing circuit means operative to generate an output current deviating from a predetermined norm in response to variations in the output current of said power supply circuit from a predetermined value
  • bias circuit means coupled to said voltage-and current-sensing circuit means and operative in response to the output voltage and current received therefrom to provide said variable bias signal to said second circuit means.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
US102610A 1970-12-30 1970-12-30 Voltage and current regulated power supply circuit for gaseous discharge lamp Expired - Lifetime US3689827A (en)

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US10261070A 1970-12-30 1970-12-30

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US (1) US3689827A (it)
CA (1) CA938343A (it)
DE (1) DE2160121A1 (it)
FR (1) FR2121178A5 (it)
GB (1) GB1326810A (it)
IT (1) IT944920B (it)

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3967159A (en) * 1975-02-03 1976-06-29 Morton B. Leskin Power supply for a laser or gas discharge lamp
US3969652A (en) * 1974-01-04 1976-07-13 General Electric Company Electronic ballast for gaseous discharge lamps
US4189663A (en) * 1976-06-15 1980-02-19 Forest Electric Company Direct current ballasting and starting circuitry for gaseous discharge lamps
US4511195A (en) * 1983-06-30 1985-04-16 Beckman Instruments, Inc. Device for starting and operating gas discharge tubes
US4528482A (en) * 1983-07-20 1985-07-09 Merlo Joseph C Control of energy to fluorescent lighting
US4999547A (en) * 1986-09-25 1991-03-12 Innovative Controls, Incorporated Ballast for high pressure sodium lamps having constant line and lamp wattage
US5034663A (en) * 1989-04-21 1991-07-23 Progressive Dynamics, Inc. Power source for metal halide lamps and the like
US5142203A (en) * 1989-06-02 1992-08-25 Koito Manufacturing Co., Ltd. Lighting circuit for high-pressure discharge lamp for vehicles
US5212428A (en) * 1990-10-01 1993-05-18 Koito Manufacturing Co., Ltd. Lighting circuit for vehicular discharge lamp

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE2419946C2 (de) * 1974-04-25 1983-04-21 Philips Patentverwaltung Gmbh, 2000 Hamburg Schaltungsanordnung zum Stellen einer Leistung
GB2137780B (en) * 1983-02-10 1986-09-17 Newton Derby Ltd Current regulated power supply circuit
GB2279187A (en) * 1993-06-19 1994-12-21 Thorn Lighting Ltd Fluorescent lamp starting and operating circuit

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3295048A (en) * 1961-05-22 1966-12-27 Electronic Energy Conversion C Capacitor means for controlling the conduction of unidirectional switching devices in a power supply
US3421069A (en) * 1966-08-04 1969-01-07 Brunswick Corp Regulated power supply including a blocking oscillator and trigger means to turn off the oscillator
US3467887A (en) * 1967-08-28 1969-09-16 Microdot Inc Lighting system
US3471747A (en) * 1967-02-02 1969-10-07 Gen Motors Corp Starting circuit and solid state running circuit for high pressure arc lamp

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3295048A (en) * 1961-05-22 1966-12-27 Electronic Energy Conversion C Capacitor means for controlling the conduction of unidirectional switching devices in a power supply
US3421069A (en) * 1966-08-04 1969-01-07 Brunswick Corp Regulated power supply including a blocking oscillator and trigger means to turn off the oscillator
US3471747A (en) * 1967-02-02 1969-10-07 Gen Motors Corp Starting circuit and solid state running circuit for high pressure arc lamp
US3467887A (en) * 1967-08-28 1969-09-16 Microdot Inc Lighting system

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3969652A (en) * 1974-01-04 1976-07-13 General Electric Company Electronic ballast for gaseous discharge lamps
US3967159A (en) * 1975-02-03 1976-06-29 Morton B. Leskin Power supply for a laser or gas discharge lamp
US4189663A (en) * 1976-06-15 1980-02-19 Forest Electric Company Direct current ballasting and starting circuitry for gaseous discharge lamps
US4511195A (en) * 1983-06-30 1985-04-16 Beckman Instruments, Inc. Device for starting and operating gas discharge tubes
US4528482A (en) * 1983-07-20 1985-07-09 Merlo Joseph C Control of energy to fluorescent lighting
US4999547A (en) * 1986-09-25 1991-03-12 Innovative Controls, Incorporated Ballast for high pressure sodium lamps having constant line and lamp wattage
US5034663A (en) * 1989-04-21 1991-07-23 Progressive Dynamics, Inc. Power source for metal halide lamps and the like
US5142203A (en) * 1989-06-02 1992-08-25 Koito Manufacturing Co., Ltd. Lighting circuit for high-pressure discharge lamp for vehicles
US5212428A (en) * 1990-10-01 1993-05-18 Koito Manufacturing Co., Ltd. Lighting circuit for vehicular discharge lamp

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Publication number Publication date
GB1326810A (en) 1973-08-15
DE2160121A1 (de) 1972-07-06
IT944920B (it) 1973-04-20
CA938343A (en) 1973-12-11
FR2121178A5 (it) 1972-08-18

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Owner name: STUDEBAKER-WORTHINGTON, INC., ILLINOIS

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:WAGNER ELECTRIC CORPORATION;REEL/FRAME:003984/0757

Effective date: 19801229

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Owner name: COOPER INDUSTRIES, INC., 1001 FANNIN, HOUSTON, TEX

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNOR:EDISON INTERNATIONAL, INC., A CORP. OF DE.;REEL/FRAME:004475/0382

Effective date: 19851031