US3660787A - Low frequency paper transient filters - Google Patents

Low frequency paper transient filters Download PDF

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US3660787A
US3660787A US64955A US3660787DA US3660787A US 3660787 A US3660787 A US 3660787A US 64955 A US64955 A US 64955A US 3660787D A US3660787D A US 3660787DA US 3660787 A US3660787 A US 3660787A
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transients
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
    • H02H9/005—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection avoiding undesired transient conditions
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output

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  • Oscilloscope recordings show conclusively that transients in electrical power systems consist of voltage spikes and dips varying in both magnitude and duration. They are usually characterized by a very fast rise time of between and 100 p. sec., and ordinarily are in the form of an oscillatory voltage superimposed on the basic 60-Hertz sine wave. The frequency of these disturbances customarily varies from a few kilocycles down to about 300 Hertz. Those from external sources are a primary cause of computer operational problems, while those generated internally can result in the malfunctioning of synchronous communications equipment.
  • Power filters which are employed to suppress such transients must satisfy a number of requirements. Not only must they attenuate the disturbances to a level harmless to the load without at the same time appreciably reducing the 60- Hertz line voltage, but they must also produce a minimal rise or drop in the output voltage as the load varies from light to full. In addition, they should not overheat under full-load operation, and should be economical, simple, compact and rugged with a high reliability factor and long operating life.
  • the present concept is directed to the provision of a basically two-element inductance-capacitance filter capable of protecting electronic equipment against commonly-occurring harmful power transients. With the addition of a capacitor across the filter input, load-originated disturbances are effectively precluded from being fed back onto the input power lines.
  • One object of the invention is to provide means for suppressing low-frequency transients in power lines.
  • Another object of the invention is to provide a two-element inductance-capacitance filter capable of protecting electronic equipment against externally-produced transients as well as those generated within the load itself.
  • An additional object of the invention is to provide a filter of the type described that is capable of yielding effective no-load to full-load voltage regulation.
  • a further object of the invention is to provide a filter of the type described which is not only simple and rugged but which possesses high reliability and a long operating life.
  • FIG. I is a circuit diagram of a filter network designed in accordance with a preferred embodiment of the present invention.
  • FIG. 2 is a set of voltage attenuation curves for the circuit of FIG. 1;
  • FIGS. 3(a), 3(b), 4(a), 4(b), 5(a) and 5(b) are waveforms of voltages appearing at the input and output terminals, respectively, of the filter network of FIG. 1;
  • FIG. 6 is a chart illustrating the effect of load variations on the attenuation characteristics of the filter network of FIG. 1;
  • FIG. 7 is a modification of the circuit of FIG. 1 to achieve voltage regulation during changes in load impedance.
  • FIG. 1 of the drawings A preferred form of filter network, together with its terminal impedances, is illustrated in FIG. 1 of the drawings.
  • the impedances Rs and RL represent the internal source impedance and the load impedance, respectively.
  • This L filter is capable of suppressing transients propagating towards the load designated as forward filtering action.
  • the capacitance C is added to the filter network to suppress transients that may originate on the load side and propagate back onto the critical bus, designated as reverse filtering action. By this network arrangement, forward and reverse filtering action is achieved.
  • Equation l The forward voltage attenuation characteristics of the filter network of FIG. 1 are given by Equation l:
  • Equation 1 may be reduced to Equation 2 and X, vanishes:
  • X 1- is essential only for reverse filter action: capacitor C. can be eliminated if reverse filter action is not needed.
  • FIG. 2 shows a set of voltage attenuation curves obtained by solving Equation l for a IO-ampere, l20-volt filter. Each curve represents a possible design value for L and C
  • R,- is assumed to be constant and is given the realistic value of 0.01 ohm.
  • R, is taken to be 10.4 ohms and the inductor resistance R is taken as 0.01 w/mh.
  • the cutoff frequency is decreased by increasing the values of either L or
  • the choice of values for L and C and thus the cutoff frequency is greatly limited by the requirement of nonappreciable voltage loss of gain at 60 Hertz.
  • the attenuation performance of this filter in the frequency range of interest is typically 40 db per decade slope.
  • FIG. 3(a) of the drawings shows an oscilloscope recording of the transients produced by a utility company switching on l-kva power factor correction capacitors.
  • FIG. 3(b) illustrates the manner in which the filter network of FIG. 1 effectively suppresses such transients.
  • FIGS. 4(a) and 4(b) illustrate the effective suppression by the circuit of FIG. 1 of low-frequency transients which cause considerable distortion of the input waveform.
  • FIGS. 5(a) and 5(b) present a similar comparison of filter input and output waves when the former contains a high-voltage pulse associated with a low-frequency oscillation.
  • the two-element L-filter of FIG. 1 acts to maintain the output voltage relatively constant as long as R, does not vary. However, if the load does undergo variations for any reason, the attenuation characteristics of the filter of FIG. 1 will be as shown in FIG. 6 of the drawings for representative conditions.
  • the inductor L is effectively divided into two portions 11-0 and a-b by connecting the capacitor C to a tap at point a.
  • portion a-c lies within the L-C network.
  • the portion a-c should consist of approximately 60 turns and the portion a-b of approximately 20 turns.
  • V The voltage V,,,, developed across that portion a-b of inductor L lying outside the L-C network varies in both magnitude and direction as the load changes. For example, when the load R increases, V also increases. This voltage V is injected into the filter output to compensate for the voltage drop V,,,, on capacitor C Consequently, the load voltage (which is the vectorial summation of V and V remains constant within about 1 percent.
  • the attenuation performance for a lO-ampere, l20-volt filter is shown in FIG. 2.
  • Each attenuation curve Y and Z represents a possible design value forL and C
  • the design attenuation curve must be selected to satisfy the filter requirements described previously. The selection criteria may be summarized as follows:
  • the attenuation curve should not have any voltage gain at any frequency. This guarantees the suppression of all transient harmonics as well as avoiding the amplification of any harmonics that may exist in the power supplied.
  • the cutoff frequency should be lower than the fundamental component frequency of the incoming transients.
  • Attenuation curves Y and Z satisfy all design criteria. They establish an inductance L of about 10 mh and a capacitance C, between 25 and 50 uf.
  • the cut-off frequency of the filter is 220 Hertz, which is far below the lowest transient normally present.
  • the circuit of FIG. 7 was devised, incorporating a split inductor one part of which is employed to inject a voltage into the basic L-C filter output.
  • the magnitude and direction of this injected voltage depends on the load current, on the mutual inductance between the two portions of the inductor, and on the ratio therebetween.
  • the circuit of FIG. 7 acts not only as a low cut-off frequency filter but also as a voltage regulator.
  • the inductor should be as linear as' possible. 2. It should not saturate at full load. 3. It should carry the full load on a continuous basis without appreciable heating.
  • Inductor linearity is usually obtained so that the inductance value is relatively independent of the property of the core material.
  • Equation 5 if 1 is chosen much larger than l.-/ .t the inductance L is determined primarily by the air gap, and the effect of the nonlinor iron core permeability "A becomes negligible.
  • E IwL I the full load current to 21rf radian frequency
  • the heating problem can be eliminated by minimizing the copper losses. This is achieved by selecting the proper wire size to obtain a low-resistance coil.
  • lO-mh lO-ampere inductor a l2-AWG wire should be chosen.
  • the resistance for this wire is 0.00162 w/ft. It was determined from conventional inductor design procedures that a 78-turn coil should be wound on a 1.5-inch stack of standard El seiectron laminations. The resistance of this coil is calculated as 0.1 ohm.
  • the air gap of the inductor is calculated as 0.030 inch to obtain 10 mh and assure linearity.
  • Equation 6 With 10 amperes flowing at 60 Hertz, the voltage across the lO-mh inductor is 37.7 volts. Substituting into Equation 6, the full load flux density is 14,500 gauss, which is below the saturation value of 16,000 gauss.
  • a filter network connected between said power line source and said load, said network including a series inductor L and a shunt capacitor C a further shunt capacitor C 1 interposed between said filter network and said power line source;
  • inductor L has a value of approximately 10 millihenries and capacitor C has a value of between and microfarads. yielding a filter cutoff frequency of approximately 220 Hertz.

Abstract

Transients in electrical power systems are capable of causing operational malfunctions in, and possible damage to, delicate equipment such as computers and data processing apparatus. The present disclosure is directed to the design of an inductancecapacitance filter which effectively suppresses externallyproduced transients as well as those generated within the load itself.

Description

United States Patent 51 May 2, 1972 Mahmoud et al.
LOW FREQUENCY PAPER TRANSIENT FILTERS Aly A. Mahmoud, Oxnard, Calif.
Assignec: The United States of America as represented by the Secretary of the Navy Filed: Aug. 19, 1970 Appl. N0.: 64,955
Inventors:
US. Cl. ..333/76, 333/12, 333/70 R Int. Cl ..H03h 7/04, H04b 15/00 Field of Search ..333/76 7O, 12
References Cited PROPAGATION DIRECTION OF TRANSI TS F FILTERING ACTION EN ROM I POWERSOURCE(FOI)RWARD FOREIGN PATENTS OR APPLICATIONS 890,818 3/1962 Great Britain "333/76 Primary E.\'aminerEli Lieberman Assistant Examiner-Marvin Nussbaum Attorney-Richard S. Sciascia, Q. Baxter Warner and Howard J. Murray, Jr.
[ 5 7] ABSTRACT 5 Claims, 10 Drawing Figures POWER FILTER L- C NETWORK I PROPAGATION DIRECTION OF TRANSIENTS CAUSED BY THE LOAD (REVERSE FILTERING ACTION) PATENTEUIIIY 2 I972 3.660, 787
SHEET 10F 4 PROPAGATION DIRECTION OF TRANSIENTS FROM POWER SOURCEIFORWARD FILTERING ACTION) I I I I I l I I I l R L I I I I I I I LOAD I I A I RI I I C2 I I I I I I I L !QK J I PROPAGATION DIRECTION OF TRANSIENTS CAUSED POWER FILTER av THE LOAD (REVERSE FILTERING ACTION) F I g.
I I I I I I I- I I l I I I b RS I I I INJECTED I I I VOLTAGE POWER I J I I VIIII [:ILOAD SOURCE I I I I RL I C| I I I I I C2 I I I I d I l I I IL-C NETWORK: --1
POWER FILTER Fig.7
ALI A. MAHMOUD INVENTOR PATENTEDMAY 2 m2 SHEET 2 BF 4 BBZOTZDZELH wo .50 Qm mOm FREQUENCY(HERTZ) Fig. 2
PATENTEDIMY 2 I972 SHEET 3 BF 4 IOSV/DIV SMSEC/DIV FILTER INPUT Fig. 3a
SMSEC/DIV FILTER OUTPUT FREQUENCY (HERTZ) Fig. 6
PATENTEUMAY 21972 SHEET t UP 4 +I SMSEC/DIV FILTER INPUT i LSMSEC/DIV FILTER OUTPUT ssv/mv *I 2 MSEC/DIV FILTER INPUT 85V/ DIV 1 --I I+2MSEC/DIV FILTER OUTPUT Fig. 40
Fig. 4b
Fig. 50
Fig.5b
LOW FREQUENCY PAPER TRANSIENT FILTERS STATEMENT OF GOVERNMENT INTEREST The invention described herein may be manufactured and used by or for the Government of the United States of America for governmental purposes without the payment of any royalties thereon or therefor.
BACKGROUND OF THE INVENTION Oscilloscope recordings show conclusively that transients in electrical power systems consist of voltage spikes and dips varying in both magnitude and duration. They are usually characterized by a very fast rise time of between and 100 p. sec., and ordinarily are in the form of an oscillatory voltage superimposed on the basic 60-Hertz sine wave. The frequency of these disturbances customarily varies from a few kilocycles down to about 300 Hertz. Those from external sources are a primary cause of computer operational problems, while those generated internally can result in the malfunctioning of synchronous communications equipment.
Power filters which are employed to suppress such transients must satisfy a number of requirements. Not only must they attenuate the disturbances to a level harmless to the load without at the same time appreciably reducing the 60- Hertz line voltage, but they must also produce a minimal rise or drop in the output voltage as the load varies from light to full. In addition, they should not overheat under full-load operation, and should be economical, simple, compact and rugged with a high reliability factor and long operating life.
SUMMARY OF THE INVENTION The present concept is directed to the provision of a basically two-element inductance-capacitance filter capable of protecting electronic equipment against commonly-occurring harmful power transients. With the addition of a capacitor across the filter input, load-originated disturbances are effectively precluded from being fed back onto the input power lines.
STATEMENT OF THE OBJECTS OF THE INVENTION One object of the invention, therefore, is to provide means for suppressing low-frequency transients in power lines.
Another object of the invention is to provide a two-element inductance-capacitance filter capable of protecting electronic equipment against externally-produced transients as well as those generated within the load itself.
An additional object of the invention is to provide a filter of the type described that is capable of yielding effective no-load to full-load voltage regulation.
A further object of the invention is to provide a filter of the type described which is not only simple and rugged but which possesses high reliability and a long operating life.
Other objects, advantages and novel features of the invention will become apparent from the following detailed descrip tion of the invention when considered in conjunction with the accompanying drawings wherein:
BRIEF DESCRIPTION OF THE DRAWINGS FIG. I is a circuit diagram of a filter network designed in accordance with a preferred embodiment of the present invention;
FIG. 2 is a set of voltage attenuation curves for the circuit of FIG. 1;
FIGS. 3(a), 3(b), 4(a), 4(b), 5(a) and 5(b) are waveforms of voltages appearing at the input and output terminals, respectively, of the filter network of FIG. 1;
FIG. 6 is a chart illustrating the effect of load variations on the attenuation characteristics of the filter network of FIG. 1; and
FIG. 7 is a modification of the circuit of FIG. 1 to achieve voltage regulation during changes in load impedance.
DESCRIPTION OF THE PREFERRED EMBODIMENT In designing an inductance-capacitance filter in accordance with the principles of the present invention, it is necessary, in order to obtain maximum transient attenuation, to select a cut-off frequency substantially below the lowest frequency component of the transients to be suppressed. However, the requirement for non-amplification and non-attenuation of the 60 Hertz line voltage places a limit on the selection of the lowest possible cut-off frequency. Also, to prevent overheating, proper choice of wire size for the inductor is essential, and, moreover, a capacitor with low dielectric loss is called for. The economy, simplicity, compactness and ruggedness requirements dictate a passive component design having a minimum number of elements.
The inability of resistance-capacitance filters to provide a low cut-off frequency rules out their use for the purposes herein set forth. However, the two-element L-filter network disclosed possesses the necessary simplicity, economy and compactness to satisfy the demands imposed by the widelydifi'erent types of installations where delicate equipment is operated.
A preferred form of filter network, together with its terminal impedances, is illustrated in FIG. 1 of the drawings. The impedances Rs and RL represent the internal source impedance and the load impedance, respectively. This L filter is capable of suppressing transients propagating towards the load designated as forward filtering action. The capacitance C is added to the filter network to suppress transients that may originate on the load side and propagate back onto the critical bus, designated as reverse filtering action. By this network arrangement, forward and reverse filtering action is achieved.
The forward voltage attenuation characteristics of the filter network of FIG. 1 are given by Equation l:
01 logmgi =20 log where 0t forward voltage attenuation E input voltage E load voltage Xi, l/jmC I capacitive reactance X l/jm C capacitive reactance X L =jwL inductor reactance R inductor resistance With R and R as known parameters, and by varying L and C in Equation I, a set of voltage attenuation curves is obtained. From this set the best attenuation curve that satisfies the filter requirements is selected. The proper values of inductance L and capacitance C are then determined.
Since the internal power source impedance R is usually much less than unity, Equation 1 may be reduced to Equation 2 and X,, vanishes:
X 1-, is essential only for reverse filter action: capacitor C. can be eliminated if reverse filter action is not needed.
The reverse voltage attenuation, a is given by FIG. 2 shows a set of voltage attenuation curves obtained by solving Equation l for a IO-ampere, l20-volt filter. Each curve represents a possible design value for L and C In solving Equation 1, R,- is assumed to be constant and is given the realistic value of 0.01 ohm. R, is taken to be 10.4 ohms and the inductor resistance R is taken as 0.01 w/mh.
It can be seen from the voltage attenuation curves of FIG. 2 that the cutoff frequency is decreased by increasing the values of either L or In addition the choice of values for L and C and thus the cutoff frequency, is greatly limited by the requirement of nonappreciable voltage loss of gain at 60 Hertz. The attenuation performance of this filter in the frequency range of interest is typically 40 db per decade slope.
FIG. 3(a) of the drawings shows an oscilloscope recording of the transients produced by a utility company switching on l-kva power factor correction capacitors. FIG. 3(b) illustrates the manner in which the filter network of FIG. 1 effectively suppresses such transients.
FIGS. 4(a) and 4(b) illustrate the effective suppression by the circuit of FIG. 1 of low-frequency transients which cause considerable distortion of the input waveform. FIGS. 5(a) and 5(b) present a similar comparison of filter input and output waves when the former contains a high-voltage pulse associated with a low-frequency oscillation.
The two-element L-filter of FIG. 1 acts to maintain the output voltage relatively constant as long as R, does not vary. However, if the load does undergo variations for any reason, the attenuation characteristics of the filter of FIG. 1 will be as shown in FIG. 6 of the drawings for representative conditions.
However, since the load voltage is a function of the load current passing through the inductor L, it is possible to achieve a constant load voltage E, by use of the circuit illustrated in FIG. 7 of the drawings.
In such Figure, the inductor L is effectively divided into two portions 11-0 and a-b by connecting the capacitor C to a tap at point a. Thus only portion a-c lies within the L-C network. For an inductor of 80 turns, the portion a-c should consist of approximately 60 turns and the portion a-b of approximately 20 turns.
The voltage V,,,, developed across that portion a-b of inductor L lying outside the L-C network varies in both magnitude and direction as the load changes. For example, when the load R increases, V also increases. This voltage V is injected into the filter output to compensate for the voltage drop V,,,, on capacitor C Consequently, the load voltage (which is the vectorial summation of V and V remains constant within about 1 percent.
The attenuation performance for a lO-ampere, l20-volt filter is shown in FIG. 2. Each attenuation curve Y and Z represents a possible design value forL and C The design attenuation curve must be selected to satisfy the filter requirements described previously. The selection criteria may be summarized as follows:
I. The attenuation curve should not have any voltage gain at any frequency. This guarantees the suppression of all transient harmonics as well as avoiding the amplification of any harmonics that may exist in the power supplied.
2. There should not be any appreciable voltage loss or gain at 60 Hertz.
3. The cutoff frequency should be lower than the fundamental component frequency of the incoming transients.
Attenuation curves Y and Z satisfy all design criteria. They establish an inductance L of about 10 mh and a capacitance C, between 25 and 50 uf. The cut-off frequency of the filter is 220 Hertz, which is far below the lowest transient normally present.
In order to lower the cut-off frequency of the filter and thus suppress harmful transients in this region, it was found necessary to employ a specially-designed inductor together with a high-value capacitor. In contrast to the usual powdered iron inductors utilized in filters of this type, it was discovered that one with a laminated iron core would yield a larger value of inductance. However, the presence of both high capacitance and high inductance caused the no-load to full-load regulation to be less than completely satisfactory.
To overcome this condition, the circuit of FIG. 7 was devised, incorporating a split inductor one part of which is employed to inject a voltage into the basic L-C filter output. The magnitude and direction of this injected voltage depends on the load current, on the mutual inductance between the two portions of the inductor, and on the ratio therebetween. When such factors are properly related, the circuit of FIG. 7 acts not only as a low cut-off frequency filter but also as a voltage regulator.
In choosing an inductor, the following factors must be considered:
l. The inductor should be as linear as' possible. 2. It should not saturate at full load. 3. It should carry the full load on a continuous basis without appreciable heating.
Inductor linearity is usually obtained so that the inductance value is relatively independent of the property of the core material. In the basic inductance design formula, Equation 5, if 1 is chosen much larger than l.-/ .t the inductance L is determined primarily by the air gap, and the effect of the nonlinor iron core permeability "A becomes negligible.
where E IwL I the full load current to 21rf radian frequency B full load flux density in gauss The heating problem can be eliminated by minimizing the copper losses. This is achieved by selecting the proper wire size to obtain a low-resistance coil. For the lO-mh, lO-ampere inductor a l2-AWG wire should be chosen. The resistance for this wire is 0.00162 w/ft. It was determined from conventional inductor design procedures that a 78-turn coil should be wound on a 1.5-inch stack of standard El seiectron laminations. The resistance of this coil is calculated as 0.1 ohm. The air gap of the inductor is calculated as 0.030 inch to obtain 10 mh and assure linearity. With 10 amperes flowing at 60 Hertz, the voltage across the lO-mh inductor is 37.7 volts. Substituting into Equation 6, the full load flux density is 14,500 gauss, which is below the saturation value of 16,000 gauss.
Obviously many modifications and variations of the present invention are possible in the light of the above teachings. It is therefore to be understood that within the scope of the appended claims the invention may be practiced otherwise than as specifically described.
I claim:
1. Apparatus for suppressing power line transients in the frequency range extending from several kilocycles to approximately 400 Hertz, said apparatus being efiective to attenuate transients propagating toward a load as well as those originating on the load side and propagating back toward the power line source, said apparatus comprising:
a filter network connected between said power line source and said load, said network including a series inductor L and a shunt capacitor C a further shunt capacitor C 1 interposed between said filter network and said power line source;
the forward voltage attenuation characteristic a, of said apparatus being given as :0 u V Ct ,1 EL
: 0 log as indicated by the voltage attenuation curve plotted for the particular values of inductance and capacitance so selected.
2. Apparatus according to claim 1 in which said inductor is of the high-permeability laminated iron core type.
3. Apparatus according to claim 1 in which inductor L has a value of approximately 10 millihenries and capacitor C has a value of between and microfarads. yielding a filter cutoff frequency of approximately 220 Hertz.
4. Apparatus according to claim 1 in which the shunt capacitor C is connected to a point on inductor L intermediate the ends thereof, the voltage developed on that por tion of the inductor between such point and the end nearest the load being in efi'ect injected into the output of the filter network to compensate for changes in the voltage developed on capacitor C in response to variations in said load.
5. Apparatus according to claim 4 in which the two portions of said inductor lying on opposite sides of said capacitor con- RLXC XC 01::20 log C Y where R, internal transient source impedance the respective values of inductor L and capacitor C being selected to yield optimum suppression of power line transients nection point have a ratio of approximately 3:1, the smallest portion lying on the load side of such point.

Claims (5)

1. Apparatus for suppressing power line transients in the frequency range extending from several kilocycles to approximately 400 Hertz, said apparatus being effective to attenuate transients propagating toward a load as well as those originating on the load side and propagating back toward the power line source, said apparatus comprising: a filter network connected between said power line source and said load, said network including a series inductor L and a shunt capacitor C2; a further shunt capacitor C1 interposed between said filter network and said power line source; the forward voltage attenuation characteristic Alpha 1 of said apparatus being given as
2. Apparatus according to claim 1 in which said inductor is of the high-permeability laminated iron core type.
3. Apparatus according to claim 1 in which inductor L has a value of approximately 10 millihenries and capacitor C2 has a value of between 25 and 50 microfarads, yielding a filter cut-off frequency of approximately 220 Hertz.
4. Apparatus according to claim 1 in which the shunt capacitor C2 is connected to a point on inductor L intermediate the ends thereof, the voltage developed on that portion of the inductor between such point and the end nearest the load being in effect injected into the output of the filter network to compensate for changes in the voltage developed on capacitor C2 in response to variations in said load.
5. Apparatus according to claim 4 in which the two portions of said inductor lying on opposite sides of said capacitor connection point have a ratio of approximately 3:1, the smallest portion lying on the load side of such point.
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Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4384331A (en) * 1979-04-23 1983-05-17 Nissan Motor Company, Limited Noise suppressor for vehicle digital system
US4752751A (en) * 1983-12-16 1988-06-21 Honeywell Inc. Reference circuit for alternator outputs
US5093641A (en) * 1989-06-20 1992-03-03 Telefonaktiebolaget L M Ericsson Rectifier smoothing filter
US5148360A (en) * 1992-01-29 1992-09-15 Gte Products Corporation Fourth order damped lowpass filter for obtaining high power factor and low total harmonic distortion
US5149931A (en) * 1989-04-11 1992-09-22 Mitsubishi Denki K.K. Power source for electric discharge machining
US5917302A (en) * 1997-08-25 1999-06-29 Kwangju Electronics Co., Ltd. Harmonic current attenuating device of a motor
EP0945969A1 (en) * 1996-12-10 1999-09-29 Matsushita Refrigeration Company Power unit
US6239992B1 (en) 1999-06-09 2001-05-29 Matsushita Refrigeration Company Electric power unit with early auxiliary capacitor charging

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB890818A (en) * 1959-11-20 1962-03-07 Belling & Lee Ltd Improvements in electrical interference suppression devices

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB890818A (en) * 1959-11-20 1962-03-07 Belling & Lee Ltd Improvements in electrical interference suppression devices

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4384331A (en) * 1979-04-23 1983-05-17 Nissan Motor Company, Limited Noise suppressor for vehicle digital system
US4752751A (en) * 1983-12-16 1988-06-21 Honeywell Inc. Reference circuit for alternator outputs
US5149931A (en) * 1989-04-11 1992-09-22 Mitsubishi Denki K.K. Power source for electric discharge machining
US5093641A (en) * 1989-06-20 1992-03-03 Telefonaktiebolaget L M Ericsson Rectifier smoothing filter
US5148360A (en) * 1992-01-29 1992-09-15 Gte Products Corporation Fourth order damped lowpass filter for obtaining high power factor and low total harmonic distortion
EP0945969A1 (en) * 1996-12-10 1999-09-29 Matsushita Refrigeration Company Power unit
US6157554A (en) * 1996-12-10 2000-12-05 Matsushita Refrigeration Company Power unit
EP0945969A4 (en) * 1996-12-10 2001-02-28 Matsushita Refrigeration Power unit
US5917302A (en) * 1997-08-25 1999-06-29 Kwangju Electronics Co., Ltd. Harmonic current attenuating device of a motor
US6239992B1 (en) 1999-06-09 2001-05-29 Matsushita Refrigeration Company Electric power unit with early auxiliary capacitor charging

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