US3641424A - Regenerative voltage regulators - Google Patents

Regenerative voltage regulators Download PDF

Info

Publication number
US3641424A
US3641424A US91336A US3641424DA US3641424A US 3641424 A US3641424 A US 3641424A US 91336 A US91336 A US 91336A US 3641424D A US3641424D A US 3641424DA US 3641424 A US3641424 A US 3641424A
Authority
US
United States
Prior art keywords
transistor
voltage
coupled
collector
terminal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
US91336A
Other languages
English (en)
Inventor
James H Kuykendall
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Optron Inc
Original Assignee
TRW Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by TRW Inc filed Critical TRW Inc
Application granted granted Critical
Publication of US3641424A publication Critical patent/US3641424A/en
Assigned to HOUSEHOLD COMMERCIAL FINANCIAL SERVICES, INC., 2700 SANDERS ROAD PROSPECT HEIGHTS, ILLINOIS 60070 reassignment HOUSEHOLD COMMERCIAL FINANCIAL SERVICES, INC., 2700 SANDERS ROAD PROSPECT HEIGHTS, ILLINOIS 60070 SECURITY INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: OPTRON, INC.,
Assigned to OPTRON INC., reassignment OPTRON INC., ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: TRW INC.,
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators

Definitions

  • the regulator cir- ST ATES PATENTS cuit having a positive common uses a feedback voltage from a top on the output filter choke winding to force a series T transistor into saturation
  • Field of the Invention This invention relates to the field of electronic voltage regulators and amplifiers.
  • the nonswitching regulator is characterized by a series transistor connected between an unregulated power supply and the regulated output, and a control circuit for controlling the base current in the series transistor to thereby control the voltage drop across the transistor in the required manner to achieve the regulated output. Since the series transistor delivers the output current with a substantial voltage drop across the transistor, there is a large power dissipation in the transistor. By way of example, if a 75-volt regulated output is desired, the minimum input voltage to the regulator must be somewhat higher than 75 volts. This is because since normally no voltage is available which is higher than the unregulated supply voltage (e.g., the regulator input), and as a result, the base current required to put the series transistor into full saturation cannot be supplied.
  • the unregulated supply voltage e.g., the regulator input
  • the minimum supply voltage must exceed the regulated voltage by a matter of a few volts.
  • the power dissipation capability of the series transistor must be even higher. For instance, if the voltage output of the unregulated supply ranges from 80 to I volts (approximately plus or minus percent) and the regulated output is at 75 volts, it is apparent that the power dissipation capability of the series transistor must be at least one-third the output power capability of the regulator.
  • the power dissipation in the series transistor as compared to the output power of the regulator must be even a higher percentage. For instance, if the output voltage is to be regulated at 50 volts, the power dissipation in the series transistor will equal the output power of the regulator, at least when the unregulated power supply is putting out 100 volts. This also illustrates the fact that the voltage output of the unregulated power supply must be matched reasonably well to the voltage output desired from the regulator, since extremely high power dissipation in the series transistor will result if the regulated voltage is to be only a fraction of the unregulated voltage.
  • the switching voltage regulator also uses a series transistor and generally uses an L-C filter on the output.
  • the series transistor is switched on and off at a relatively high frequency, the relative ontime being varied to maintain the output voltage across the capacitor at the desired voltage. If the series transistor is always switched between the off condition and saturation, it is apparent that the power dissipation in the series transistor will be quite low, since the off state is characterized by a substantial voltage across, but negligable current through, the transistor, and the saturation state is characterized by substantial current through, but very low voltage across, the transistor. This, of course, remains true even if the regulated output voltage is to be a relatively small fraction of the unregulated supply voltage.
  • the major source of power dissipation is power dissipation in the series transistor when driven into saturation. If this transistor is driven into true saturation, a base voltage exceeding the unregulated supply voltage must be used. This means that if the full advantage of this type of regulator is to be achieved, a voltage must be created which exceeds the unregulated supply voltage, and this voltage used to supply base current to the series transistor when switched to the saturation condition.
  • Such voltages are commonly generated in the prior art regulators by rectifying and filtering an AC voltage referenced to the high side of the unregulated supply, and using this voltage to force the series transistor into saturation during the on portion of the duty cycle.
  • Such circuits require a source of AC power referenced to one side of the unregulated supply, a rectifier and a filter for creating a DC voltage exceeding the voltage of the unregulated supply. In general this requires additional capacitors, inductors and other circuitry for this purpose.
  • the major source of power dissipation is the resistor and transistor switch supplying the base current to the series transistor.
  • This base current must be supplied at a potential of only a few volts. Consequently, since the gain of power-switching transistor is characteristically rather low and such current is normally supplied from the positive common, a large power dissipation occurs in the dropping resistor in series with the base of the series transistor.
  • the present invention is a regenerative power switch for use in semiconductor circuits such as in voltage regulators controlled by high-frequency pulses and having very low power dissipation.
  • the circuits of the present invention utilize an L-C output filter and are characterized by the use of a feedback voltage from a secondary winding on the filter inductor to drive a series transistor into saturation during the conducting portion of the duty cycle.
  • the series transistor is initially turned on by high-frequency pulse, the feedback voltage exceeds the unregulated supply voltage and drives the series transistor deep into saturation, thereby minimizing the voltage drop across the transistor.
  • a second transistor is in series with the feedback voltage, and the series transistor is turned off by turning off the second transistor and further biasing the series transistor to the off condition.
  • the only inductor required in the circuits of the present invention such as in regulators, is the output filter inductor and thus the basic regulator circuit may be readily packaged in hybrid form in a package of minimum size.
  • FIG. 1 is one embodiment of the regulator of the present invention having negative common.
  • FIG. 2 is a second embodiment of the present invention regulator having a positive common.
  • FIG. 3a is the waveform of the filter output voltage V32 at point 32 of FIG. 1 throughout a typical cycle operation of the regulator of FIG. 1.
  • FIG. 3b is a typical waveform of the control voltage V30 applied to point 30 of FIG. 1 throughout the same time period as the waveform of FIG. 3a.
  • FIG. 30 is the waveform of the voltage V54 on line 54 of FIG. 1 throughout the same time period as the waveform of FIG. 3a.
  • FIG. 3d is a waveform of the current I26 through the inductor 26 of FIG. 1 throughout the same time period as the waveform of FIG. 3a.
  • FIG. 36 is a waveform of the current I50 through transistor 50 of FIG. 1 throughout the same time period as the waveform of FIG. 3a.
  • FIG. 3f is a waveform of the current I66 through diode 66 of FIG. 1 throughout the same time period as the waveform of FIG. 3a.
  • FIG. 3g is a waveform of the feedback voltage V60 on line 60 of FIG. 1 over the same time period as the waveform of FIG. 3a.
  • FIG. 1 one embodiment of the present invention regulator, may be seen.
  • This embodiment is intended for use with an unregulated supply having a negative common.
  • the regulator circuit enclosed within the box of FIG. 1 connects to an unregulated voltage supply at points 22 and 24, and delivers power to the output filter comprised of choke 26 and output capacitor 28 in a manner controlled by a highfrequency pulse signal applied to point 30.
  • the pulse applied to point 30 for purposes of control of the voltage regulator may be of constant frequency but of varying pulse widths, that is, a pulse width modulated signal, or may be a varying frequency signal such as that created by a Schmitt trigger.
  • Such a signal could be generated by comparing the output voltage at point 32 with a reference voltage, such as a zener diode reference voltage, and the error signal used to drive a Schmitt trigger.
  • a reference voltage such as a zener diode reference voltage
  • the error signal used to drive a Schmitt trigger.
  • a Schmitt trigger is used to generate the feedback signal, though it is to be understood that other feedback signals such as a constant frequency, varying pulse width signal may also be used.
  • the Schmitt trigger initiates a negative pulse at point 30.
  • This negative pulse turns off transistor 34.
  • the turning off of transistor 34 turns on transistor 36 by supplying base current through resistor 38 so that current is supplied to the collector of transistor 40 through transistor 36, resistor 44 and diode 46. Since transistor 40 is turned on, current to the base of the series transistor 50 is supplied through transistor 40 and resistor 52. This partially turns on transistor 50 and suddenly raises the voltage in line 54. Since the voltage across capacitor 28 may not be changed quickly, the increase in voltage on line 54 results in an equivalent increase in voltage across the inductor 26.
  • a secondary coil 56 is also wound on the same core as inductor 26, one end of which is connected to lead 54 and the other end of which is connected to diode 58.
  • the winding sense of the secondary coil 56, as compared to the inductor 26, is such that the increase in the voltage across the inductor 26 due to the partial turnon of transistor 50 results in a positive induced voltage on line 60, which is imposed on the base of transistor 50 through diode S8, transistor 40 and resistor 52, thereby driving transistor 50 quickly and completely into saturation.
  • transistor 40 is initially turned on by current supplied through transistor 36, resistor 44, diode 46, and resistor 48, transistor 40 is maintained in the on condition by the high collector voltage on transistor 40 as a result of the feedback from the secondary coil 56 and the current supplied to the base of transistor 40 through resistor 48.
  • the Schmitt trigger changes the polarity of the voltage supplied to point 30 to a positive voltage. This turns on transistor 34, resulting in a substantial drop in the voltage in line 62, thereby turning off transistor 50 through diode 64 and resistor 42, and turning off transistor 40 by depleting the base current to this transistor which was previously supplied by resistor 48.
  • transistor 51 is a base-emitter return, that is, a leakage current return which enhances the stability of operation of transistor 50).
  • the magnetic field in inductor 26 will fall to zero, and at that time, the voltage across the inductor 26 will go to zero and the voltage across diode 66 will equal the voltage across capacitor 28. In this condition the voltage induced in the secondary coil 56 will be zero and, therefore, the voltage in line 60 will be equal to the voltage across the output capacitor 28. Since transistor 34 will still be on, diode 58 will be forward biased, and the collector of transistor 40 will be at a voltage just slightly below the output voltage across capacitor 28.
  • the voltage at the base of transistor 40 will be substantially lower than that on the col lector of transistor 40 because of the voltage drop in resistor 48 due to the current flowing through resistor 48, resistor 42 and transistor 34.
  • the base of transistor 50 will be at a voltage substantially equal to the voltage on the base of transistor 40 because it is connected to the base of transistor 40 through diode 64. Since this voltage on the base of transistor 50 is substantially less than the voltage in line 54, which is the voltage in the emitter of transistor 50, transistor 50 will remain in the off condition.
  • the Schmitt trigger When the output voltage across capacitor 28 drops to the control level, the Schmitt trigger will change the pulse applied to point 30 to a negative pulse and the regenerative sequence previously described is reinitiated. It is, therefore, apparent that the series transistor 50 is always rapidly switched into saturation as a result of the feedback of the induced voltage in the secondary coil 56, and is rapidly switched out of saturation by the drop in the base voltage on transistor 50 as a result of turning on of transistor 34. Consequently, the power dissipation in transistor 50 is minimized since the voltage drop across transistor 50 is minimized when the transistor 50 is conducting.
  • FIGS. 3a through 3g present typical waveforms for various voltages and currents within the circuit throughout a typical operating cycle.
  • a voltage at a particular point or for a particular line of the circuit of FIG. 1 is represented by a V followed by the numeral representing that point in FIG. 1.
  • a current in a given line is denoted by an I followed by the appropriate numeral.
  • Schmitt trigger has a fixed unique trigger level and is entirely free of hysteresis.
  • most Schmitt triggers have a significant hysteresis and it will become apparent in the explanation to follow how hysteresis of the Schmitt trigger affects the operation of the circuit.
  • the voltage V32 of line 32 is shown as it varies with time throughout one cycle of operation of the circuit, that is, throughout the time Tl to time T5. Between time T1 and T3 the voltage V32 is below the voltage labeled VC, which represents the control voltage for the Schmitt trigger, and between T3 and T5 is above the control voltage.
  • VC the voltage labeled VC
  • the voltage V54 of line 54 in this time interval is substantially equal to the supply voltage V24 of the unregulated supply as shown in FIG. 30.
  • the current 126 through inductor 26 (FIG. 3d) is slightly less than the load current II, that is, the current through the load attached to the output terminals of the regulator.
  • the voltage across inductor 26, (V54-V32) is substantially constant, since the voltage V32 varies only within a narrow control margin, (the periodic variation in voltage V32 as shown in FIG. 3a is grossly out of scale for purposes of this explanation). Therefore, the rate of increase of the current 126 in FIG. 3d is substantially linear, in the period T1 to T3. In the time period between T1 and T2, the current 126 is less than the load current 11 and, consequently, the output voltage V32 drops to a minimum value at time T2 because of the discharge of capacitor 28 through the load therein.
  • the winding sense of the secondary coil 56 is chosen so that the voltage V60 in line 60 is positive with respect to the voltage in line 54 when there is a positive rate of increase in the current through inductor 26. Therefore, when the voltage V30 at point 30 first goes negative and transistor 50 is thereby partially turned on, the voltage V54 in line 54 increases, causing a positive rate of increase of current 126 in inductor 26 and a voltage in line 60 exceeding that in line 54. Since transistor 40 is ON at this time, this further turning on transistor 50, further increasing the voltage in line 54 and the rate of increase of current I26 in inductor 26, and thereby causing an increased feedback voltage at line 60.
  • the transistor 50 when the voltage V30 first goes negative at time T1, the transistor 50 is rapidly switched into saturation as a result of the regenerative feedback caused by the secondary coil 56 on inductor 26.
  • This also causes the voltage on line 54 to very quickly increase to a value substantially equal to the input voltage to the regulator and, therefore, the voltage V60 in line 60 to be substantially above the supply voltage VS to the regulator as shown in FIG. 3g.
  • the voltage V60 remains substantially above the supply voltage VS throughout the time period T1 to T3, since the current I26 is steadily increasing during this time period, thereby causing a positive feedback from the secondary coil 56.
  • the voltage V60 is used as previously described to supply the base current to transistor 50 to force it into saturation and to maintain the transistor 50in saturation throughout the time period T1 to T3.
  • the output voltage V32 again achieves the Schmitt trigger control voltage VC as shown in FIG. 3a and the voltage V30 switches to a positive value, causing transistor 50 to be switched off.
  • the current 150 immediately goes to zero, but since the current in inductor 26 may not change instantaneously, the voltage across the inductor 26 will reverse polarity so as to instantaneously maintain the same current in the inductor.
  • the current flow through inductor 26 will be temporarily maintained by current supplied through diode 66.
  • FIG. 2 an embodiment of the present invention voltage regulator having a positive common may be seen.
  • This embodiment is similar to the embodiment of FIG. I in that the output filter inductor 70 is a three-terminal device, two of which are used as the inductor terminals and a third of which is a feedback voltage suitable for use in driving a series transistor into saturation
  • Line 72 connects to the positive side of the unregulated supply and is common to both the input and output of the regulator.
  • Line 74 connects to the negative side of the supply so that the main current flow is through line 72, through a load connected to the terminals 76 and 78, and back through inductor 70, series transistor 80, and line 74.
  • the high-frequency pulse control signal is applied at point 82 by a suitable control device such as a Schmitt trigger responding to variations in the output voltage between terminal 76 and 78.
  • a suitable control device such as a Schmitt trigger responding to variations in the output voltage between terminal 76 and 78.
  • transistor 86 When the voltage at point 82 switches to its lower value, characteristically a value approaching the voltage on line 74, transistor 86 is turned off and transistor 84 is turned on, thereby lowering the voltage at point 88 to a value just above the voltage on line 74. This depletes the base current in transistor 90 through resistor 94, and through resistor 92 and transistor 84.
  • Capacitor 96 is connected across resistor 92 and is used to speed up the turn on and turn off of transistor 90 and thus of transistor 80.
  • transistor 90 When transistor 90 is turned off, transistor is also turned off since resistor 102, in cooperation with diode 98 and resistor 94, hold the base of transistor 80 at a voltage very close to the voltage
  • the voltage on line 100 suddenly increases to a value slightly above that of line 72, so that current continues to flow through inductor 70 (and through diode 104 to charge capacitor 106) at a steadily decreasing rate in much the same manner as was heretofore described in detail in regard to FIG. 1 and FIGS. 3a through 33.
  • the voltage on line 108 is substantially higher than the voltage at point 78 and is sufficient to supply base current to transistor 80 through transistor when transistor 90 is again turned on.
  • transistor 84 When the voltage at point 82 is switched to its upper value, typically approximately equal to the voltage on line 72, transistor 84 is turned off and transistor 86 is turned on, thereby increasing the voltage on line 88 to a value just below that on line 72.
  • This turns on transistor 90 by supplying current to the base of transistor 90 through the voltage divider comprised of resistor 92 and resistor 94.
  • transistor 80 When transistor 90 is turned on, transistor 80 is also on because of current supplied through line 108, resistor 110, and transistor 90 to the base 112 of transistor 80.
  • transistor 80 When transistor 80 is on, the voltage in line 100 is substantially equal to the voltage in line 74.
  • the coil in inductor 70 acts as a voltage divider, with the voltage in line 108 being at a desired value between the voltage in line 74 and the voltage at point 78.
  • the voltage in lead 108 when transistor is on may be selected to be only slightly above the voltage drop from the collector to the emitter in transistor 90 plus the voltage drop from the base to the emitter of transistor 80, when both transistors are on.
  • resistor 110 has a very low value of resistance and the power dissipation therein is held to a minimum.
  • the high efficiency of the circuits of the present invention is achieved even when the regulated output voltage is substantially below the unregulated input voltage.
  • the control voltage VC and thus the regulator output voltage V32, neglecting output ripple
  • the output current I26 is the sum of the current I50 from the unregulated supply through transistor 50 and the current [66 through diode 66 after transistor 50 is switched off. As may be seen in FIGS.
  • Regulators have been fabricated with the circuits of the present invention and operated with efficiencies as high as 90 to 95 percent. As a result of these high efficiencies, voltage regulators with a power output capability as high as 200 watts have been built, using the circuits of the present invention, and packaged in a standard T-03 package. Furthermore, such circuits are ideal for fabrication as hybrid circuits because of the absence of inductors in the circuit and the low power dissipation characteristic of the circuit.
  • a voltage regulator having a positive input terminal, a positive output terminal, a control terminal, and a negative common input-output terminal, comprised of an inductor, having first and second end connections and an intermediate connection, a capacitor, first and second transistor switches, at least one diode and a coupling means;
  • said capacitor being coupled between said positive output terminal and said common input-output terminal;
  • said first end connection of said inductor winding being coupled to said positive output terminal
  • said first transistor switch being coupled between said first input terminal and said intermediate connection and being responsive to its base current
  • said second transistor switch being coupled between said second end connection of said inductor and said base of said first transistor switch and being responsive to its base current
  • said coupling means coupling said base of said second transistor switch and the lead of said second transistor switch coupled to said inductor to said control terminal, and being responsive to a pulse control signal applied thereto, to initially supply current through said second transistor switch to said base of said first transistor switch;
  • said intermediate connection and said negative common input-output terminal being coupled through said diode, said diode being conductive when the voltage of said negative common input-output terminal exceeds the voltage on said intermediate connection.
  • said first transistor switch is an NPN-transistor having an emitter, a base, and a collector;
  • said emitter being coupled to said intermediate connection
  • said collector being coupled to said first input terminal.
  • a circuit for a voltage regulator said circuit having a positive input terminal, a positive output terminal, a common negative input-output terminal, a control terminal and a feedback terminal, for use .with an output filter of a capacitor and an inductor having a first lead coupled to said capacitor, a second lead coupled to said feedback terminal and a third lead coupled to said positive output terminal, the combination comprised of first and second NPN-transistors, each having an emitter, a base and a collector, a first diode a resistor and a coupling means, said emitter of said first transistor being coupled to said positive output terminal, said collector of said first transistor being coupled to said positive input terminal, said emitter of said second transistor being coupled to said base of said first transistor, said collector of said second transistor being coupled to said feedback terminal through said first diode and to said base of said second transistor through said resistor, said first diode being conductive when the voltage on said feedback terminal exceeds the voltage on said collector of said second transistor, and said coupling means being coupled to said control terminal, to
  • said coupling means is coupled to said collector of said second transistor through a second diode
  • said second diode being conductive when the voltage on said last-named collector is less than the voltage directed thereto from said coupling means.
  • a voltage regulator having a positive input terminal, a positive output terminal, a control terminal and a negative common input-output terminal comprised of an inductor having first and second end connections and an intermediate connection, a capacitor, first and second NPN- transistors, each having an emitter, a base and a collector, first and second diodes and a coupling means, said capacitor being coupled between said positive output terminal and said common input-output terminal, said first end connection of said inductor being coupled to said positive output terminal, said emitter of said first transistor being coupled to said intermediate connection, said collector of said first transistor being coupled to said positive input terminal, said emitter of said second transistor being coupled to said base of said first transistor, said collector of said second transistor being coupled to said second end connection through a first diode and to said base of said second transistor through a resistor, said first diode being conductive when the voltage on said second end connection exceeds the voltage on said collector of said second transistor switch, said intermediate connection and said negative common input-output terminal being coupled through said second

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
US91336A 1970-11-20 1970-11-20 Regenerative voltage regulators Expired - Lifetime US3641424A (en)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
US9133670A 1970-11-20 1970-11-20

Publications (1)

Publication Number Publication Date
US3641424A true US3641424A (en) 1972-02-08

Family

ID=22227243

Family Applications (1)

Application Number Title Priority Date Filing Date
US91336A Expired - Lifetime US3641424A (en) 1970-11-20 1970-11-20 Regenerative voltage regulators

Country Status (2)

Country Link
US (1) US3641424A (Direct)
JP (1) JPS4710722A (Direct)

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3790879A (en) * 1971-11-12 1974-02-05 S Milovancevic Switching voltage regulator
US3982174A (en) * 1975-06-02 1976-09-21 Western Electric Company, Inc. Switching voltage regulator with low RFI noise
US4008429A (en) * 1973-08-23 1977-02-15 Intel Corporation Voltage translator for solid state watch
US4028612A (en) * 1975-09-10 1977-06-07 Honeywell Information Systems Italia Dynamic current limiter for switching voltage regulators
US4034281A (en) * 1974-07-25 1977-07-05 Sanken Electric Company Limited Direct current power supply with a transistor chopper
FR2442552A1 (fr) * 1978-11-27 1980-06-20 Accumulateurs Fixes Circuit d'aide a la commutation de transistors de puissance
US4713740A (en) * 1984-07-27 1987-12-15 Sms Advanced Power, Inc. Switch-mode power supply
US6331767B1 (en) * 1998-02-24 2001-12-18 Lucas Industries, Plc Power supplies of ECUs
US6628013B2 (en) * 2000-09-28 2003-09-30 Intel Corporation Redundant power subsystem
US20040070376A1 (en) * 2002-10-11 2004-04-15 Rohm Co., Ltd. Switching power supply unit
US20040075486A1 (en) * 2002-10-21 2004-04-22 Canon Kabushiki Kaisha Gate driving circuit
US20040080304A1 (en) * 2002-10-23 2004-04-29 Canon Kabushiki Kaisha Power source apparatus

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3365650A (en) * 1965-10-21 1968-01-23 Vapor Corp Static inverter having a regulated output
US3417321A (en) * 1968-12-17 Nasa Increasing efficiency of switching-type regulator circuits
US3461377A (en) * 1966-11-29 1969-08-12 Electronic Communications Blocking oscillator d.c. voltage regulator
US3462643A (en) * 1967-03-31 1969-08-19 Rca Corp Switching type voltage and current regulator and which can include voltage doubling means for a load

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR1479475A (fr) * 1966-03-22 1967-05-05 Thomson Houston Comp Francaise Perfectionnements aux dispositifs de commutation

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3417321A (en) * 1968-12-17 Nasa Increasing efficiency of switching-type regulator circuits
US3365650A (en) * 1965-10-21 1968-01-23 Vapor Corp Static inverter having a regulated output
US3461377A (en) * 1966-11-29 1969-08-12 Electronic Communications Blocking oscillator d.c. voltage regulator
US3462643A (en) * 1967-03-31 1969-08-19 Rca Corp Switching type voltage and current regulator and which can include voltage doubling means for a load

Cited By (15)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3790879A (en) * 1971-11-12 1974-02-05 S Milovancevic Switching voltage regulator
US4008429A (en) * 1973-08-23 1977-02-15 Intel Corporation Voltage translator for solid state watch
US4034281A (en) * 1974-07-25 1977-07-05 Sanken Electric Company Limited Direct current power supply with a transistor chopper
US3982174A (en) * 1975-06-02 1976-09-21 Western Electric Company, Inc. Switching voltage regulator with low RFI noise
US4028612A (en) * 1975-09-10 1977-06-07 Honeywell Information Systems Italia Dynamic current limiter for switching voltage regulators
FR2442552A1 (fr) * 1978-11-27 1980-06-20 Accumulateurs Fixes Circuit d'aide a la commutation de transistors de puissance
US4713740A (en) * 1984-07-27 1987-12-15 Sms Advanced Power, Inc. Switch-mode power supply
US6331767B1 (en) * 1998-02-24 2001-12-18 Lucas Industries, Plc Power supplies of ECUs
US6628013B2 (en) * 2000-09-28 2003-09-30 Intel Corporation Redundant power subsystem
US20040070376A1 (en) * 2002-10-11 2004-04-15 Rohm Co., Ltd. Switching power supply unit
US6919713B2 (en) * 2002-10-11 2005-07-19 Rohm Co., Ltd. Switching power supply unit
US20040075486A1 (en) * 2002-10-21 2004-04-22 Canon Kabushiki Kaisha Gate driving circuit
US6967520B2 (en) * 2002-10-21 2005-11-22 Canon Kabushiki Kaisha Gate drive circuit, which makes the gate-charge flow back to the load and the main power source
US20040080304A1 (en) * 2002-10-23 2004-04-29 Canon Kabushiki Kaisha Power source apparatus
US6967415B2 (en) 2002-10-23 2005-11-22 Canon Kabushiki Kaisha Power source apparatus

Also Published As

Publication number Publication date
JPS4710722A (Direct) 1972-05-29

Similar Documents

Publication Publication Date Title
US4030015A (en) Pulse width modulated voltage regulator-converter/power converter having push-push regulator-converter means
US4395675A (en) Transformerless noninverting buck boost switching regulator
US3569818A (en) Multiple output dc voltage regulator
US5398182A (en) Power supply
EP0059633B1 (en) Switching power supply
US3641424A (en) Regenerative voltage regulators
US4004187A (en) Push-pull inverter ballast for arc discharge lamps
US4420804A (en) Switching regulator with base charge removal circuit
US3381202A (en) Dc voltage magneitude modifying arrangement
US4574228A (en) Current controlled motor drive circuit
US6040686A (en) Low noise step-down switching regulator circuits with programmable slew rate limiter and methods of use
US5014176A (en) Switching converter with spike limiting circuit
US4737898A (en) Single-ended self-oscillating, DC-DC converter with regulation and inhibit control
US3461377A (en) Blocking oscillator d.c. voltage regulator
US4514679A (en) Secondary switch controller circuit for power supply
US3111632A (en) Transistor oscillator
US4792746A (en) Non-dissipative series voltage switching regulator having improved switching speed
US5036450A (en) Spike limiting circuit
US5239453A (en) DC to DC converter employing a free-running single stage blocking oscillator
US3898549A (en) Variable duty cycle balanced DC/DC power converter
US4744020A (en) Switching mode power supply
US4028612A (en) Dynamic current limiter for switching voltage regulators
US3959711A (en) Pulse width modulated power supplies
US3949278A (en) Document transfer device drive
US3135909A (en) Regulated voltage converter circuit

Legal Events

Date Code Title Description
AS Assignment

Owner name: HOUSEHOLD COMMERCIAL FINANCIAL SERVICES, INC., 270

Free format text: SECURITY INTEREST;ASSIGNOR:OPTRON, INC.,;REEL/FRAME:004915/0628

Owner name: OPTRON INC.,

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNOR:TRW INC.,;REEL/FRAME:004915/0632

Effective date: 19880714