US2392476A - Wide band phase shifter - Google Patents

Wide band phase shifter Download PDF

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Publication number
US2392476A
US2392476A US432680A US43268042A US2392476A US 2392476 A US2392476 A US 2392476A US 432680 A US432680 A US 432680A US 43268042 A US43268042 A US 43268042A US 2392476 A US2392476 A US 2392476A
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Prior art keywords
frequency
networks
network
phase
circuit
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Expired - Lifetime
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US432680A
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English (en)
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Hodgson Kenneth George
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International Standard Electric Corp
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International Standard Electric Corp
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/21—Networks for phase shifting providing two or more phase shifted output signals, e.g. n-phase output
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S84/00—Music
    • Y10S84/09—Filtering

Definitions

  • KeR "c -ea nmmn and KsR :f 1(p' then e 2 tenwhere in and Ir: are the resonant and antiproximate very closely to the desired characteristics.
  • Figures 1, 2 and 3 show three types of all-pass lattice networks.
  • the impedance arms are inverse i. e.
  • Kr and the ratio of resonance frequencies for any given case depends upon the phase angle difierence and frequency range required, and on the amount by which the phase angle diiierence may be permitted to depart from the desired value; however, K1 will generally be iound to be between 3 and 8 and the greater the permissible tolerance the greater is the frequency range which can be covered.
  • Figure 5 shows a family of curves in which the phase difierence between a pair of Figure 2 networks each having the same value of K1 and designed by adlusting the ratio 114 f oi the resonance frequencies of the two networks to give a mean phase difierence or 90, isplotted against a logarithmic frequency scale.
  • the network of Figure 3 for instance has a phase angle of 180 at its lower resonanc frequency and 360 at its upper resonance frequency; these two points may be located at any desired .points in the frequency range by the choice of values for the constants In and p, while choice of the third parameter K2 enable the value of 6 to be fixed at one other point in the frequency range.
  • a network similar to Figure 2 may be used in one branch of the circuit with a network similar to Figure 3 in the other branch.
  • the resonance frequencies of the latter will be located at or near the frequencies at which the Figure 2 network gives angles of 90 and 270 respectively.
  • the value of K: may then be chosen so that the Figure 3 network gives a phase angle of 270 at the resonance frequency (fr) of the- Figure 2 network. Under these conditions:
  • e network of Figure 1 gives 90 phase angle at the frequency jr/Ko and is symmetrical with respect to ice j about this point.
  • a favourable ary ranget consists of a pair or networks one of which has nelements per impedance arm and the other has n+1 elements per impedance arm.
  • the networks considered up to this point have all been of the constant resistance type and present their characteristic propagation constants, i. e., zero loss and an approximately logarithmic relation between phase angle and-frequency, when terminated in their characteristic impedance; two i such networks having their inputs connected in parallel, and each terminated in their characteristic impedance will give output voltages or currents of exactly equal amplitude and diflering in phase by an approximately constant angle over the frequency range for which they are designed, the maximum angular deviation from the design value depending on the range to be covered. It has been found, however, that the performance can be improved by theinclusion oi resistances in the networks and/or by modii the terminating impedance.
  • a further advantage of the use of such resistance elements is that the unavoidable resistance of inductance coils may be absorbed in the said resistances thereby enabling coils of comparativelv low Q value to be empioyed.
  • the power ratio ofthe transmitted and suppressed sidewnds is given by:
  • ere a is the amplitude ratio of the two input voltagm and 60 is the angular deviation from of the ph difierence between the input voltthe amplitude ratio a which, with no andby a bridged i network of identical charactas lar deviation. gives the same suppression as an angular deviation 60 with no amplitude deviation, is given by:
  • Figum 10 shows a pair of networks similar to Figure 9 having their inputs connected in parallel to a generator G and their outputs terminated in load impedances RL, R1 ⁇ respectively.
  • Figure 12 shows a known type of frequency translating device which is adapted to suppress one side-band; this circuit has not hitherto found much application for lack of convenient means to obtain over a suilicient frequency range a 90 phase shift with constant amplitude ratio between two circuits.
  • Modulators i, i are supplied with the same carrier frequency from generator 2 but with a phase difference of 90". If this carrier frequency is constant, the required conditions can readily be attained by the use of an inductance and capacitance 3, 3 in the carrier supply circuit. If the carrier frequency is variable the inductance and capacitance should be replaced by a pair of networks in accordance with the invention.
  • the modulating frequency from generator 4, which is frequently variable over a wide range. is applied to the translating device through phase networks 5, 5 whose output terminals are connected to the input terminals of modulators I, I respectively, and whose input terminals are connected in parallel or over a hybrid coil or differential transformer.
  • Networks 5, 8 which may be of the type shown in Figure 2 or Figure 3 are designed in accordance with the invention, so that currents or voltages in their output circuits differ in phase b 90 and have a constant amplitude ratio;
  • the output circuits of modulators I, l are connected in parallel or over a hybrid coil to line 6.
  • Each modulator generates an upper and a lower sldeband in its output circuit, but the phase relations are such thatfor one sideband the I components from the two modulators are in phase and for the other sideband the component are 180 out of phase. Either sideband may be suppressed by suitable poling of the input, output 1 advantages.
  • the modulating frequency from generator 4 passes through phase networks 5, 5 designed for 90 phase difference, to the input circuits of modulator l, 6
  • the carrier frequency from generator 2 is connected in the same phase to modulators I, i and a second pair of phase networks I, 1 similar to 5, 5 but designed to have a phase difference of 90 over the frequency range covered by the upper and lower sidebands are connected in the output circuits of modulators i, I
  • the translating device of Figure id is similar to that of Figure 13 except that the input network 5, l are omitted and the carriers supplied to modulators I, i have a phase difference of 90.
  • the circuit of Figure 12 with one poling will suppress in its output the upper sideband of any input frequency, and with the other poling will suppress the lower sideband of any input frequency
  • the circuits of Figures 13 and 14 possess the property of discriminating between input frequencies, which lie respectively above and below the carrier frequency.
  • the circuit of Figure 13 with one poling will suppress the upper sideband of input frequencies, which lie below the carrier frequency, and both sidebands of input frequencies which lie above the carrier frequency; with the other poling it will suppress the lower sideband of input frequencies which lie below the carrier frequency and. neither sideband of input frequencies which lie above the carrier frequency.
  • the circuit of Figure 14 has properties inverse to those of Figure 13 and with one poling will suppress the upper sideband of frequencies which lie above the carrier frequency and both sidebands 0 frequency translating devices used in receiving is known as second channel interference," and at the same time to eliminate in the output the upper sideband, due to the desired input ire quency.
  • the output of translating device 28 is arranged so that one sideband (say p-ql is suppressed and is connected to line 23.
  • circuit line '23 At the receiving end of the circuit line '23 is connected to the input of afrequency translating device 26 of the type of Figure 14, which is supplied with a carrier frequency 11 from generator 25, and whose output is connected to a load 26.
  • the single sideband input of fre-' quency p+q will give rise to a lower sideband of frequency qi in the load as, the upper sided 2p+q being suppressed.
  • a irequency Pq in line 28 e. g., from an adjacent channel, will not give rise to any output in load 25, since both sidebands q and 232-1; are suppressed.
  • Figures'ls and 17 show alternative arrangements of the output circuits or frequency translating devices, in accordance with Figures 13 or 14.
  • the output terminals of networks l, l are connected to conjugate pairs of terminals on a hybrid coil 8. Across the other conjugate pairs of terminals are connected loads s, il The upper sideband will then appear in one load and the lower sideband in the other.
  • the circuit of Figure 17 is only suitable for use where the ratio of the highest and lowest frequencies in the sideband range is small.
  • a variable oscillator controlling the sweep frequency is connected to the vertical plates of an oscillograph through a phase network, and to the horizontal plates through a second phase network, said networks being designed in accordance with the principles of the invention, so that the currents or voltages in their outputs diiier in phase by 90 over the frequency range of the variable oscillator.
  • a transmission circuit capable of producin phase shifts of currents or voltages, which are substantially constant over a relatively vwide range I of frequencies, including a circuit having a pin aaaasre plitudes of said currents or voltages in said branches are substantially constant over the said range of frequencies;
  • a circuit'according to claim 1 in which said networks are of lattice form and at least one network has n impedance elements in each arm while at least one other network has n+1 impedance elements in each arm, and in which each resonance frequency of one of said a. element networks is located approximately at the geometric mean of a pair of adjacent resonance frequencies of one of said n+1 element networks.
  • a circuit according to claim 1 in which said networks are all-pass constant resistance and a shunt arm comprisinga negative induot ance and a capacitance in series.
  • each network comprises a bridged 1' network he," 1: a series arm comprising a capacitance and a re sistance in series, two equal T arms each comprising an inductance and a'resistance in series and a shunt arm comprising a negative inductance and a capacitance inseries, and in which said resistance in said series arm is approataly twice said resistance in each of said T 13.

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  • Amplitude Modulation (AREA)
US432680A 1941-01-31 1942-02-27 Wide band phase shifter Expired - Lifetime US2392476A (en)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
GB257867X 1941-01-31

Publications (1)

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US2392476A true US2392476A (en) 1946-01-08

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Application Number Title Priority Date Filing Date
US432680A Expired - Lifetime US2392476A (en) 1941-01-31 1942-02-27 Wide band phase shifter

Country Status (4)

Country Link
US (1) US2392476A (enrdf_load_stackoverflow)
BE (1) BE477467A (enrdf_load_stackoverflow)
CH (1) CH257867A (enrdf_load_stackoverflow)
GB (1) GB547601A (enrdf_load_stackoverflow)

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2511137A (en) * 1944-12-16 1950-06-13 Rca Corp Frequency control
US2529117A (en) * 1945-08-30 1950-11-07 Philco Corp Electrical phase shift system
US2668238A (en) * 1946-08-20 1954-02-02 Frederick W Frink Wide-band phase shifting means
US2676308A (en) * 1947-12-05 1954-04-20 Hartford Nat Bank & Trust Co Device for deriving phase-shifted voltages from an input voltage of varying frequency
US2923871A (en) * 1954-03-08 1960-02-02 Nathaniel L Cohen Two-phase variable frequency power supply for motor
US3060389A (en) * 1959-03-19 1962-10-23 Leonard R Kahn Audio signal peak energy equalization
US3083606A (en) * 1959-03-02 1963-04-02 Don L Bonham Electrical music system
US3195073A (en) * 1961-07-26 1965-07-13 Texas Instruments Inc Single-sideband suppressed carrier signal generator
US3263019A (en) * 1964-03-18 1966-07-26 Hurvitz Hyman Randomization of phases and frequencies of musical spectra
US3805163A (en) * 1959-05-01 1974-04-16 Hughes Aircraft Co Image rejection receiver
US4885562A (en) * 1987-07-20 1989-12-05 Electronique Serge Dassault Microwave delay circuit having a bridge-T circuit
US8487716B1 (en) 2012-09-19 2013-07-16 Werlatone, Inc. Single-ended phase-shift network
US8542080B2 (en) 2011-04-08 2013-09-24 Werlatone, Inc. All-pass network
CN119448977A (zh) * 2025-01-10 2025-02-14 四川益丰电子科技有限公司 一种超宽带小移相位的数字移相电路及其仿真方法

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2135844B (en) * 1983-02-21 1986-08-28 Nippon Telegraph & Telephone Oscillator with variable frequency and phase

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2511137A (en) * 1944-12-16 1950-06-13 Rca Corp Frequency control
US2529117A (en) * 1945-08-30 1950-11-07 Philco Corp Electrical phase shift system
US2668238A (en) * 1946-08-20 1954-02-02 Frederick W Frink Wide-band phase shifting means
US2676308A (en) * 1947-12-05 1954-04-20 Hartford Nat Bank & Trust Co Device for deriving phase-shifted voltages from an input voltage of varying frequency
US2923871A (en) * 1954-03-08 1960-02-02 Nathaniel L Cohen Two-phase variable frequency power supply for motor
US3083606A (en) * 1959-03-02 1963-04-02 Don L Bonham Electrical music system
US3060389A (en) * 1959-03-19 1962-10-23 Leonard R Kahn Audio signal peak energy equalization
US3805163A (en) * 1959-05-01 1974-04-16 Hughes Aircraft Co Image rejection receiver
US3195073A (en) * 1961-07-26 1965-07-13 Texas Instruments Inc Single-sideband suppressed carrier signal generator
US3263019A (en) * 1964-03-18 1966-07-26 Hurvitz Hyman Randomization of phases and frequencies of musical spectra
US4885562A (en) * 1987-07-20 1989-12-05 Electronique Serge Dassault Microwave delay circuit having a bridge-T circuit
US8542080B2 (en) 2011-04-08 2013-09-24 Werlatone, Inc. All-pass network
US8487716B1 (en) 2012-09-19 2013-07-16 Werlatone, Inc. Single-ended phase-shift network
CN119448977A (zh) * 2025-01-10 2025-02-14 四川益丰电子科技有限公司 一种超宽带小移相位的数字移相电路及其仿真方法

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Publication number Publication date
CH257867A (de) 1948-10-31
BE477467A (enrdf_load_stackoverflow)
GB547601A (en) 1942-09-03

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