US2163403A - Stabilized oscillator - Google Patents

Stabilized oscillator Download PDF

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Publication number
US2163403A
US2163403A US151564A US15156437A US2163403A US 2163403 A US2163403 A US 2163403A US 151564 A US151564 A US 151564A US 15156437 A US15156437 A US 15156437A US 2163403 A US2163403 A US 2163403A
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Prior art keywords
bridge
frequency
feedback
resistance
oscillation
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Expired - Lifetime
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US151564A
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English (en)
Inventor
Larned A Meacham
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AT&T Corp
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Bell Telephone Laboratories Inc
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Application filed by Bell Telephone Laboratories Inc filed Critical Bell Telephone Laboratories Inc
Priority to US151564A priority Critical patent/US2163403A/en
Priority to GB18056/38A priority patent/GB510379A/en
Priority to BE428862D priority patent/BE428862A/xx
Priority to DEW3444D priority patent/DE905151C/de
Priority to FR840149D priority patent/FR840149A/fr
Priority to NL88642A priority patent/NL62472C/xx
Priority to US246791A priority patent/US2258128A/en
Application granted granted Critical
Publication of US2163403A publication Critical patent/US2163403A/en
Priority to GB30329/39A priority patent/GB533736A/en
Priority to FR51068D priority patent/FR51068E/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
    • H03B5/14—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance frequency-determining element connected via bridge circuit to closed ring around which signal is transmitted
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
    • H03B5/14—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance frequency-determining element connected via bridge circuit to closed ring around which signal is transmitted
    • H03B5/16—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance frequency-determining element connected via bridge circuit to closed ring around which signal is transmitted active element in amplifier being vacuum tube
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B3/00—Line transmission systems
    • H04B3/02—Details
    • H04B3/04—Control of transmission; Equalising
    • H04B3/06—Control of transmission; Equalising by the transmitted signal
    • H04B3/08—Control of transmission; Equalising by the transmitted signal in negative-feedback path of line amplifier

Definitions

  • FIGS i Bo -cA 8H A 1., L R n R, 0 c 0 c INVENTOR LA. MEACHAM ATTORNEY Patented June 20, 1939 UNITED. STATES PATENT OFFICE STABILIZED OSCILLATOR Larned A. Meacham, Verona. N. 1., asslgnor to Bell Telephone Laboratories, Incorporated, New York, N. Y., a corporation of New York Application July 2, 1937, Serial No. 151,584
  • erated in a vacuum tube oscillator circuit is dependent, in the general case, on the resistances of the grid and plate space paths of the vacuum tube, and that one of the principal causes of frequency of the tube excitation voltages particular instability in the presence of variation is the non-linear of these resistances.
  • oscillator cir'- frequency determining combination In oscillator cir'- frequency determining combination.
  • the amplitude of the oscillations is regulated and maintained substantially constant by automatic control of the magnitude of the feedback.
  • the arrangements provided in accordance with the invention for the automatic control of the amplitude make it possible to operate the vacuum tube with its grid negatively biased to such an extent that no grid current is drawn, thereby elimmating the grid space path as a source of wave form distortion. These arrangements also permit the oscillations to be limited to a relatively small amplitude, within which the plate resistance of the tube is substantially linear and is not productive of distortion.
  • the feedback circuit comprises a Wheatstones bridge one branch of pedance, resistance which includes a frequency selective imthe other branches being constituted by s.
  • the feedback circuit comprises a Wheatstones bridge one branch of pedance, resistance which includes a frequency selective imthe other branches being constituted by s.
  • all four (Cl. zso-soi branches are resistive thereby giving the feedback the necessary phase angle of 180 degrees independently of the tube resistances and, consequently, improving the frequency stability.
  • the magnitude of the feedback is determined by the degree of the resistance unbalance of the bridge.
  • the circuit is operated with a very small amount of resistance unbalance and the frequency selective arm is made such that its reactance is strongly variable with frequency. As will be shown later this has the effect of rendering the frequency more stable in the presence of variations of the impedances in other parts of the circuit.
  • one of the resistive bridge arms is constituted by a variable resistance, the value of which, and therefore the degree of the bridge unbalance, is varied in response to variations of the strength of the current traversing it.
  • a this variable resistance is a linear element 50 that it does not cause any wave form distortion. It may, for example, consist of a lamp filament, metallic or carbon, in which case the resistance value is dependent on the operating temperature.
  • Fig. 1 shows an embodiment of the invention
  • Fig. 2 is a diagram useful in explaining the invention
  • Figs. 3, 4 and 5 show modified forms ofa portion of the system of Fig. 1;
  • Fig. 6 shows another embodiment of the invention
  • Fig. 7 shows a network equivalent to a portion of the system of Fig. 6;
  • Figs. 8 and 9 show other types of network that may be utilized in accordance with the invention.
  • the oscillation generator shown in Fig. 1 comprises a vacuum tube l, preferably of the screengrid, high amplification type, and a feedback path between the output and input circuits of the tube including an output transformer l, a frequency selective Wheatstone bridge network 2, and an input transformer 3.
  • Energizing circuits for the vacuum tube are provided as shown, the negative biasing potential for the control grid being obtained from a resistor ii in the cathode lead which is, traversed by the plate current.
  • the grid bias is proferably sufflciently large to prevent the flow of grid current in normal operation.
  • a load impedance II which may be the input circuit of an amplifier. is connected to the secondary winding of output transformer 4 through a pad consisting of resistors l3 and II.
  • transformers I and 4 should introduce a very small phase shift and that the phase of the feedback should be controlled substantially exclusively by the selective bridge network 2.
  • the transformers may be of close coupled high emciency type in which the phase shift is inherently small.
  • the trans- may be of close coupled high emciency type in which the phase shift is inherently small.
  • formers may be tuned by condensers such as shownat it, it, ll,and I ,whichmaybeadiusted to make the transformer phase shifts substantially zero at any desired frequency.
  • a third arm comprises a variable resistance device 1. such as the filament of a lamp.
  • the fourth arm includes a piezoelectric crystal I, a small variable inductance 9 and a variable condenser ll.
  • Frequency selective combination I. i, ll exhibits a series resonance at a frequency somewhere near the series resonance of the crystal. Since the addition of a series inductance gives rise to a second resonance at a higher frequency, the value of inductance 9 should be very small so that the second resonance is far removed from that of the crystal. The transformers in the feedback path then operate to prevent possible oscillation at this frequency. Further.
  • One pair of diagonally opposite corners, B and D, are connected to the output terminals of transformer l and the other pair, A and C. are connected to the terminals of input transformer 3.
  • the requisite phase of the feedback for the production of oscillations may be obtained by poling the connections of one or other of the transformers or by interchanging the connections of the bridge corners.
  • the operation of the system is as follows: Assuming that the transformers produce no phase shift, the phase of the feedback becomes 180 degrees at the resonance frequency of the selective impedance I, 9, II. at which frequency the bridge circuit is purely resistive. Because of the purely resistive character of the bridge and of the absence of phase shift in the transformus. the feedback phase is independent of the non-linear resistances of the tube and oscillations occurring at this frequency are stable. Furthermore. un-
  • the initial unbalance of the bridge Assuming the initial unbalance of the bridge to be such as to provide suilicient feedback. oscillations will start and will grow in amplitude until a condition of equilibrium is reached. Ordinarily this condition of equilibrium is reached only after the grid path of the vacuum tube becomes conductive and depends on the value of the grid path resistance. In the circuit of the invention. however, the steady oscillation amplitude is controlled and maintained by the automatic regulating action of the feedback network itself, the grid path of the tube remaining nonconductive. For this purpose the variable resistance device is so in the circuit and has such characteristics that, as the oscillation amplitude increases, the bridge tends to become more nearly balanced, thereby diminishing the feedback. For example, if the device I consist of a metallic filament lamp.
  • Adjustment of the operating amplitude to a desired value may be effected by changing the value of one or other of the fixed resistors I and 6-. Adjustment of the oscillator output may be effected by variation of resistors II and II.
  • variable resistor having a negative temperature coefficient for example, a carbon filament lamp
  • the cold resistance of thelamp should be greater than the resistance needed for balance of the bridge.
  • temperature controlled linear resistances such as lamp filaments. has the advantage that control of the amplitude is eifected without the production of wave form distortion.
  • the control of the amplitude by means external t8 the tube also permits the tube to be operated without the overloading and consequent wave form distortion which ordinarily occur when the tube resistances control the amplitude.
  • the over-all feedback phase of degrees is obtained at some frequency different from that of the resonance of the frequency selective bridge arm.
  • the phase shift in the Ill bridge itself must be slightly different from 180' degrees at the oscillation frequency. the departure being Just enough to compensate the phase shift in the other parts of the feedback path.
  • the effect of this upon the frequency stability is made negligibly small by the operation of the bridge in a nearly balanced condition and is further reduced by the use of elements in the frequency selective branch of the bridge having reactances that vary strongly with frequency at ttTe resonance of the branch.
  • a piezoelectric quartz crystal is well suited for this purpose.
  • the voltage across the frequency selective arm DA is represented by the vector DA, this being the resultant of two quadrature components, namely, DB in phase with the current and representing the resistance drop, and FA representing the fall of potential in the reactance.
  • the voltage across the branch AB is represented by the vector AB which is in phase with the resistance component DF.
  • the locus of the end of the vector DA for variation of the reactance of the frequency selective branch is the circle 20, the center of which lies on the line of vector DB.
  • the point A at which the circle intersects the vector DB represents the potential of the bridge corner A at the resonance frequency.
  • the voltage between the bridge corners A and C, that is. the output voltage of the bridge. is represented by the vector CA, its value at the resonance frequency being represented by CA.
  • the phase angle between the input and output voltages of the bridge is dependent on the resistance unbalance of the bridge.
  • the degree of resistance unbalance is small the phase angle is very strongly variable with the reactance of the frequency selective branch at frequencies close to resonance.
  • a relatively large phase shift produced by elements external to the bridge can therefore be compensated by the phase shift in the bridge itself resulting from an extremely small departure of the frequency from the resonance value.
  • the operation of the bridge in a nearly balanced condition therefore, increases the stability of the oscillation frequency. Under the condition described above, that is, with the bridge proportions such that the point C in the vector diagram, Fig.
  • the variation of the reactance of the frequency selective branch between the values zero and infinity results in the movement of the end of the vector DA around the circle from the point A to the point B and in the progressive variation of the angle through 180 degrees.
  • a particular value of the phase shift can thus be produced by only one value of the reactance and at only one frequency. The compensation of an external phase shift is therefore effected at a single frequency only and only one frequency of oscillation is possible.
  • the requirement ensuring a single oscillation frequency is met by making the resistance of the lamp 1 less than enough to balance the bridge.
  • the lamp filament must then have a positive temperature coefficient.
  • the resistances of the bridge arms should be so related that a complete phase reversal of the output voltage occurs as the reactance of the reactance elements changes from zero to an infinite value. The necessary resistance relationship can be determined readily by means of this criterion in any particular case.
  • Fig. 2 shows also that, as the frequency departs from the resonance frequency of the selective bridge arm, the total unbalance of the bridge and, therefore, the amount of the feedback, increases very rapidly and acquires such phase as toproduce a strong degenerative action.
  • the system operates as a degenerative feedback amplifier and any harmonies that may be generated are subject to strong attenuation.
  • the oscillation frequency is that of the series resonance of the selective bridge arm.
  • the piezoelectric crystal which constitutes the selective impedance has also an anti-resonance at an adjacent frequency, but at this frequency the phase of the output voltage. of the bridge is opposite to that required for oscillation.
  • the oscillation frequency may be determined by the anti-resonance of a selective impedance. Examples of bridge circuits of this type being shown inFigs. 3 and 4.
  • the frequency selective arm in the circuit of Fig. 3 comprises the parallel combination of a capacity C, an inductance L and a resistance R.
  • the resistance may represent the energy dissipation in the inductance or it may include an actual resistance element.
  • the impedance of the anti-resonant circuit becomes purely resistive, with the resistance large as compared with R so that the impedance of the arm as a 6 able element is included in a branch adiacent the Ill selective impedance. Its value in this position should be less than that required for bridge balance and its temperature coefficient should be positive.
  • Fig. 5 shows a bridge circuit of similar type to that of Fig. 1 in which the crystal resonator is replaced by a simple series resonant circuit including resistance.
  • the feedback control element is inserted in a branch adjacent the selective impedance.
  • the variable element should have, in this position, a resistance greater than needed for bridge balance and should have a negative temperature coefllcient.
  • the variable element may be included in the same arm as the selective impedance if desired. In that caseyif the selective impedance is of the series resonant type, the variable element should have a positive temperature coefficient and should have a negative coeillcient if the impedance is parallel resonant.
  • shunt branch including an inductance La and a resistance Ra
  • a bridging branch comprising an inductance L1 and a resistance R1 in parallel.
  • the inductance and resistance elements are proportioned so that L1 is equal to Ila and R1 is slightly greater than 4R1.
  • the oscillation frequency is determined by the resonance of Li with the two capacities in series.
  • Resistances R1 and R: are preferably actual resistors, their values being proportioned with proper allowance for the effective resistances of the inductances. 1 Either resistor may be made automatically vari- 'able in response to current changes to provide the feedback control in accordance with the invention. If the bridging resistance R1 be used for this purpose its temperature coefilcient must be negative and if the shunt resistance R: be
  • the shunt resistance R2 is indicated as the variable feedback control element.
  • the (bridged-T network shown in Fig. 6 is equivalent, with respect to its transmission characteristics to the symmetrical Wheatstones bridge shown in Fig. 'i.
  • the input and output terminals of the two networks are correspondingly designatedand the element values' in Fig. I are indicated in relation to the corresponding elementsin Fig. 8. From the relationship imposed on inductances L1 and La in Fig. 6, it follows that branches AB and CD of the equivalent bridge are resonant at the same frequency at whichthe branches AD and BC become antiresonant. At this frequency the bridge arms all become purely resistive and the output voltage is dependent only 'upon the amount of the resistance unbalance.
  • the output voltage will be either in phasewith or in opposition to the impressed voltage according to the sense of the resistance unbalance and, since the bridge arms are purely resistive, the phase relationship of the voltages is independent of the connected terminal impedances.
  • the bridge circuit of Fig. 7 provides stability of the oscillation frequency.
  • the circuits described above are all characterized by the property that their image impedahces are purely resistive at the frequency for which the phase shift components of their image transfer constants take the value r or 180 degrees. Because of this relationship, the over-all insertion phase shifts, when the networks are inserted between resistive source and load impedances, take the value of 180 degrees at frequencies determined solely by the image transfer constant characteristics and independently of the magnitudes of the terminal resistances. When such networks are used as feedback networks in vacuum tube oscillator circuits, the requisite phase shift for the production of oscillations is obtained at a frequency which,is independent of the space path resistances of the vacuum tube and is therefore stable.
  • the automatic control of the oscillation amplitude which is a feature of the invention, may be applied also to circuits which do not conform exactly to the above-mentioned relationship.
  • Feedback networks of this type are illustrated in Figs. 8 and 9.
  • the network shown in Fig. 8 is a bridged-T network similar to that of Fig. 6, but having the bridging inductance Ll omitted,
  • the bridging resistance R1 constitutes the variable feedback control element.
  • R1 should be somewhat greater than R: and for control purposes should have a negative temperature coeilicient.
  • the oscillation frequency lies very close to the value determined by the product 2140. Stability of the oscillation frequency is obtained by making the difference between Bi and IR: very small, that is, by making the attenuation in the network very great at the oscillation frequency, and is enhanced by making the capacity 0 small and the inductance La large.
  • the bridging impedance is a capacity C1
  • the shunt branch consists of a variable resistance R: which constitutes the feedback control.
  • the operating conditions are readily found from inspection of the equivalent Wheatstones bridge, or lattice, obtained by wellknown methods.
  • the oscillation frequency is approximately that determined by the product 2101.
  • the resistance R: should be slightly less than the value and for control purposes should have a positive temperature coeillcient.
  • the inductance L should be small and the capacity 01 large.
  • An oscillation generator comprising an aln-. pliiler, input and output circuits therefor. and a Wheatstone bridge network coupling said input greases and output circuits, the bridge arms including a resonator and a resistance, the latter being variable with temperature.
  • An oscillator comprising an amplifier and a feedback circuit therefor, the latter including a bridge network containing a series resonant element in one arm and a thermally'variable resistor in the opposite arm, said resistor having a positive temperature coefllcient of resistance variation.
  • An oscillation generating system comprising an amplifier, input and output circuits therefor, and a W'heatstone bridge network connecting said input and output circuits, one arm of the bridge containing a resonant element and another arm containing a lamp the resistance of which is a function of its temperature.
  • An oscillator comprising an amplifier and a feedback circuit therefor, the latter including a Wheatstone bridge containing a series resonant element in one bridge arm and a resistor having a negative temperature coefilcient of resistance change in an adjacent bridge arm.
  • An oscillator comprising an amplifier and a feedback circuit therefor, the latter including a Wheatstone bridge network having a parallel resonant tuning element in one bridge arm and a resistance with a negative temperature ooemcient in the opposite bridge arm.
  • An oscillation generator comprising an amplifier having an input circuit and an output circuit, and a bridge network having two opposite arms comprising fixed resistances and having a resistor whose resistance varies as in accordance with its current and a tuned circuit respectively in the remaining arms, the input and output circuits of the amplifier being connected across the respective diagonals of the bridge, whereby both the amplitude and the frequency of oscillations are stabilized.
  • a feedback circuit including a Wheatstone bridge with a series resonant tuning element in one bridge arm and a resistance with a'positive temperature coemcient of resistance change in the opposite bridge arm.
  • afeedback circuit including a bridge having a series resonant element in one bridge arm and a negative temperature coefiicient resistor in an adjacent bridge arm.
  • an oscillation generator comprising an amplifier and a feedback path coupling the output and the input terminals of the amplifier, a frequency ⁇ determining network included in said feedback gith, said network having a frequency selective nsmission characteristic providing a minimum feedback in regenerative phase substantially at the oscillation frequency and strong degenerative feedback at frequencies removed therefrom, and means forming part-of said network for controlling the amount of the said minimum feedback in response to variations of the oscillation amplitude whereby the oscillation amplitude is maintained substantially constant, said means comprising a circuit element having an impedance variable in magnitude with the strength of the amt travelling it.
  • an oscillation generator comprising an amplifier and a feedback path coupling the output and the input terminals of the amplifier, a frequency determining network included in said feedback path, said network having a frequency selective transmission characteristic providing a minimum feedback in regenerative phase substantially at the oscillation frequency and strong degenerative feedback at frequencies removed therefrom, and means forming part of said network for selectively controlling the amount of the said minimum feedback in respouse to variations of the oscillation amplitude whereby the oscillation amplitude is maintained substantially constant, said means comprising a circuit element having an impedance variable in magnitude with the strength of the current traversing it.
  • an oscillation generator comprising an amplifier and a feedback path coupling the output and the input terminals of the amplifier
  • a frequency determining network included in said feedback path, said network having a frequency selective transmission characteristic providing a minimum feedback in regenerative phase substantially at the oscillation frequency and strong degenerative feedback at frequencies removed therefrom, and a resistance element included in said network the resistance of which, in relation to other resistances in said network, determines the amount of the said minimum feedback and is variable with the current strength therein in such sense as to diminish the feedback in response to an increase in the oscillation amplitude; whereby the oscillation amplitudeis maintained substantially constant.
  • An oscillation generator comprising .an amplifier, a feedback path coupling the output and the input terminals of the amplifier, and a frequency determining network included in said feedback path, said network having a maximum attenuation substantially at the oscillation frequency and relatively low attenuation at other frequencies, and a resistance element included in said network the resistance of which determines the amount of the attenuation of said network at the oscillation frequency and is variable in response to variations of the oscillation amplitude in such sense as to maintain the amplitude substantially constant.
  • An oscillation generator comprising an amplifier, a feedback path coupling the output and the input terminals of the amplifier, and a frequency determining network included in said feedback path comprising a Wheatstone bridge circuit proportioned to have a small unbalance productive of regenerative feedback at the oscillation frequency, a resonant impedance included in an arm of said bridge circuit, the ream nance of said impedance substantially determining the oscillation frequency, and an impedance element the impedance of which is variable in response to variations of the osdliation amplitude included in another arm of said bridge circuit, said variable impedance operating to diminish the unbalance of the bridge circuit as the oscillation amplitude increases, whereby substantial constancy of amplitude is maintained.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Amplifiers (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
  • Microwave Amplifiers (AREA)
  • Inductance-Capacitance Distribution Constants And Capacitance-Resistance Oscillators (AREA)
US151564A 1937-07-02 1937-07-02 Stabilized oscillator Expired - Lifetime US2163403A (en)

Priority Applications (9)

Application Number Priority Date Filing Date Title
US151564A US2163403A (en) 1937-07-02 1937-07-02 Stabilized oscillator
GB18056/38A GB510379A (en) 1937-07-02 1938-06-17 Stabilised vacuum tube oscillators
BE428862D BE428862A (en, 2012) 1937-07-02 1938-06-28
DEW3444D DE905151C (de) 1937-07-02 1938-06-30 Schwingungserzeuger
FR840149D FR840149A (fr) 1937-07-02 1938-07-01 Oscillateurs stabilisés
NL88642A NL62472C (en, 2012) 1937-07-02 1938-07-02
US246791A US2258128A (en) 1937-07-02 1938-12-20 Wave translating system
GB30329/39A GB533736A (en) 1937-07-02 1939-11-18 Stabilised vacuum tube oscillators
FR51068D FR51068E (fr) 1937-07-02 1939-12-18 Oscillateurs stabilisés

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US151564A US2163403A (en) 1937-07-02 1937-07-02 Stabilized oscillator
US246791A US2258128A (en) 1937-07-02 1938-12-20 Wave translating system

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US2163403A true US2163403A (en) 1939-06-20

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US151564A Expired - Lifetime US2163403A (en) 1937-07-02 1937-07-02 Stabilized oscillator
US246791A Expired - Lifetime US2258128A (en) 1937-07-02 1938-12-20 Wave translating system

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US246791A Expired - Lifetime US2258128A (en) 1937-07-02 1938-12-20 Wave translating system

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US (2) US2163403A (en, 2012)
BE (1) BE428862A (en, 2012)
DE (1) DE905151C (en, 2012)
FR (2) FR840149A (en, 2012)
GB (2) GB510379A (en, 2012)
NL (1) NL62472C (en, 2012)

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US2435487A (en) * 1943-02-01 1948-02-03 Zenith Radio Corp Electromechanical vibrator
US2451858A (en) * 1945-01-26 1948-10-19 Gen Electric Controlled frequency oscillator
US2495177A (en) * 1946-01-18 1950-01-17 Jefferson Standard Broadcastin High stability oscillator generator
US2556296A (en) * 1949-04-26 1951-06-12 Bell Telephone Labor Inc High-frequency transistor oscillator
US2583837A (en) * 1944-10-13 1952-01-29 Automatic Elect Lab Thermionic valve oscillator
US2586167A (en) * 1945-07-03 1952-02-19 Us Navy Oscillator
US2587294A (en) * 1942-12-16 1952-02-26 Telecommunications Sa Device for stabilizing oscillations
US2602139A (en) * 1948-08-10 1952-07-01 Gen Precision Lab Inc Bridge oscillator
US2611874A (en) * 1945-01-01 1952-09-23 Int Standard Electric Corp Electric wave filter
US2625650A (en) * 1948-10-16 1953-01-13 Sperry Corp Superregenerative apparatus
US2674692A (en) * 1950-09-13 1954-04-06 Bell Telephone Labor Inc Frequency changing repeater employing feedback amplifiers
US2680197A (en) * 1951-05-15 1954-06-01 Mackay Radio & Telegraph Co Crystal controlled oscillator
US2681996A (en) * 1950-09-12 1954-06-22 Bell Telephone Labor Inc Transistor oscillator
US2692337A (en) * 1948-12-29 1954-10-19 Bell Telephone Labor Inc Oscillation generator
US2727993A (en) * 1953-04-07 1955-12-20 Lenkurt Electric Co Inc Stabilized oscillator
US2764355A (en) * 1953-06-10 1956-09-25 George A F Machlet Electronic measuring and control apparatus
US2776372A (en) * 1953-07-31 1957-01-01 Hartford Nat Bank & Trust Co Stabilized transistor oscillator
US2798953A (en) * 1954-12-28 1957-07-09 Charles B Fisher Oscillation generators
US2799826A (en) * 1952-03-05 1957-07-16 Sperry Rand Corp Wattmeter self-balancing bridge apparatus
US2806200A (en) * 1952-12-17 1957-09-10 Bell Telephone Labor Inc Ambient temperature compensation of thermistors
US2811578A (en) * 1954-04-05 1957-10-29 Bell Telephone Labor Inc Television band width reducing system
US2895108A (en) * 1955-12-22 1959-07-14 Rca Corp Electronic circuit
US2913677A (en) * 1956-10-31 1959-11-17 Hermes Electronics Co Frequency modulating system for crystal oscillators
US2925561A (en) * 1955-07-01 1960-02-16 Motorola Inc Crystal oscillator system
US2928039A (en) * 1956-10-05 1960-03-08 Welex Inc Constant electromagnetic field well logging system
US3005148A (en) * 1957-06-13 1961-10-17 Bofors Ab Voltage derivation network
US3042880A (en) * 1958-09-17 1962-07-03 Avco Mfg Corp Bridge-stabilized oscillator
US3082382A (en) * 1958-10-10 1963-03-19 Packard Bell Electronics Corp Transmitter system including amplitude controlled oscillator means
US3114886A (en) * 1960-11-01 1963-12-17 Sperry Rand Corp Pulse regulating system
US3196350A (en) * 1962-01-15 1965-07-20 Donald F Dimon Narrow bandwidth high q communication system
US3308400A (en) * 1962-06-13 1967-03-07 Hewlett Packard Co Frequency adjustment circuit

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DE1075169B (de) * 1960-02-11 Standard Elektrik Lorenz Aktiengesellschaft, Stuttgart-Zuffenhausen Belastungsunabhängiger Oszillator:
US2735937A (en) * 1956-02-21 Low-frequency oscillator
US2418842A (en) * 1943-03-04 1947-04-15 Bell Telephone Labor Inc Scanning oscillator
US2447248A (en) * 1944-12-23 1948-08-17 Curtiss Wright Corp Stabilized oscillator
BE477845A (en, 2012) * 1945-02-23
US2641705A (en) * 1946-12-04 1953-06-09 Bell Telephone Labor Inc Stabilized oscillator
US2754418A (en) * 1949-04-28 1956-07-10 Bendix Aviat Corp Control circuit for a servo system
US2724807A (en) * 1950-02-16 1955-11-22 Harold B Rex Frequency-selective systems
US2734172A (en) * 1952-02-04 1956-02-07 appert
US2749441A (en) * 1952-08-28 1956-06-05 Dunford A Kelly Phase shift oscillator
US2790898A (en) * 1953-05-04 1957-04-30 Bady Isidore Weak signal detector using synchronously switched rectifier bridge
DE1003285B (de) * 1954-10-05 1957-02-28 Telefunken Gmbh Rueckgekoppelter Generator, der aus einem RC-Verstaerker und einem Rueckkopplungsglied besteht
NL99049C (en, 2012) * 1955-02-17
US3109149A (en) * 1958-09-18 1963-10-29 Fielden Electronics Ltd Bridge oscillating arrangement utilizing output to vary balance
US12199828B2 (en) * 2021-09-27 2025-01-14 International Business Machines Corporation Network topology monitoring

Cited By (32)

* Cited by examiner, † Cited by third party
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US2587294A (en) * 1942-12-16 1952-02-26 Telecommunications Sa Device for stabilizing oscillations
US2435487A (en) * 1943-02-01 1948-02-03 Zenith Radio Corp Electromechanical vibrator
US2423505A (en) * 1943-08-09 1947-07-08 Rca Corp Bridge stabilized oscillator
US2583837A (en) * 1944-10-13 1952-01-29 Automatic Elect Lab Thermionic valve oscillator
US2611874A (en) * 1945-01-01 1952-09-23 Int Standard Electric Corp Electric wave filter
US2451858A (en) * 1945-01-26 1948-10-19 Gen Electric Controlled frequency oscillator
US2586167A (en) * 1945-07-03 1952-02-19 Us Navy Oscillator
US2495177A (en) * 1946-01-18 1950-01-17 Jefferson Standard Broadcastin High stability oscillator generator
US2602139A (en) * 1948-08-10 1952-07-01 Gen Precision Lab Inc Bridge oscillator
US2625650A (en) * 1948-10-16 1953-01-13 Sperry Corp Superregenerative apparatus
US2692337A (en) * 1948-12-29 1954-10-19 Bell Telephone Labor Inc Oscillation generator
US2556296A (en) * 1949-04-26 1951-06-12 Bell Telephone Labor Inc High-frequency transistor oscillator
US2681996A (en) * 1950-09-12 1954-06-22 Bell Telephone Labor Inc Transistor oscillator
US2674692A (en) * 1950-09-13 1954-04-06 Bell Telephone Labor Inc Frequency changing repeater employing feedback amplifiers
US2680197A (en) * 1951-05-15 1954-06-01 Mackay Radio & Telegraph Co Crystal controlled oscillator
US2799826A (en) * 1952-03-05 1957-07-16 Sperry Rand Corp Wattmeter self-balancing bridge apparatus
US2806200A (en) * 1952-12-17 1957-09-10 Bell Telephone Labor Inc Ambient temperature compensation of thermistors
US2727993A (en) * 1953-04-07 1955-12-20 Lenkurt Electric Co Inc Stabilized oscillator
US2764355A (en) * 1953-06-10 1956-09-25 George A F Machlet Electronic measuring and control apparatus
US2776372A (en) * 1953-07-31 1957-01-01 Hartford Nat Bank & Trust Co Stabilized transistor oscillator
US2811578A (en) * 1954-04-05 1957-10-29 Bell Telephone Labor Inc Television band width reducing system
US2798953A (en) * 1954-12-28 1957-07-09 Charles B Fisher Oscillation generators
US2925561A (en) * 1955-07-01 1960-02-16 Motorola Inc Crystal oscillator system
US2895108A (en) * 1955-12-22 1959-07-14 Rca Corp Electronic circuit
US2928039A (en) * 1956-10-05 1960-03-08 Welex Inc Constant electromagnetic field well logging system
US2913677A (en) * 1956-10-31 1959-11-17 Hermes Electronics Co Frequency modulating system for crystal oscillators
US3005148A (en) * 1957-06-13 1961-10-17 Bofors Ab Voltage derivation network
US3042880A (en) * 1958-09-17 1962-07-03 Avco Mfg Corp Bridge-stabilized oscillator
US3082382A (en) * 1958-10-10 1963-03-19 Packard Bell Electronics Corp Transmitter system including amplitude controlled oscillator means
US3114886A (en) * 1960-11-01 1963-12-17 Sperry Rand Corp Pulse regulating system
US3196350A (en) * 1962-01-15 1965-07-20 Donald F Dimon Narrow bandwidth high q communication system
US3308400A (en) * 1962-06-13 1967-03-07 Hewlett Packard Co Frequency adjustment circuit

Also Published As

Publication number Publication date
FR51068E (fr) 1941-08-06
US2258128A (en) 1941-10-07
FR840149A (fr) 1939-04-19
BE428862A (en, 2012) 1938-07-30
NL62472C (en, 2012) 1949-02-15
DE905151C (de) 1954-02-25
GB510379A (en) 1939-08-01
GB533736A (en) 1941-02-19

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