US20220190709A2

US20220190709A2 - Self-commutated inverter and operation of same

Info

Publication number: US20220190709A2
Application number: US17/312,313
Authority: US
Inventors: Harald WIESSMANN
Original assignee: Siemens AG
Current assignee: Siemens AG
Priority date: 2018-12-10
Filing date: 2019-11-25
Publication date: 2022-06-16
Also published as: US20220029525A1; US11837947B2; EP3667882A1; EP3871326A1; CN113424421A; WO2020120116A1

Abstract

The invention relates to a method for operating a self-commutated inverter (1), which is supplied from a direct voltage circuit (3) and comprises electronic switches (S1, S2, S3) for producing a three-phase output voltage and a three-phase output filter (5) which is connected downstream of the electronic switches (S1, S2, S3) and is coupled to the direct voltage circuit (3). The electronic switches (S1, S2, S3) are controlled in an open-loop manner by space-vector modulation, in which a zero-phase-sequence system voltage is controlled in a closed-loop manner by filter-input voltages of the output filter (5) on the basis of a target-voltage space vector (uα, β_s) of the space-vector modulation and filter input currents (i1_in, 12_in, i3_in) of the output filter (5) such that oscillations in a zero-phase-sequence system of the filter input currents (i1_in, i2_in, i3_in) are suppressed.

Description

The invention relates to a self-commutated inverter which is supplied from a direct voltage circuit and has electronic switches for producing a three-phase output voltage and a three-phase output filter which is connected downstream of the electronic switches and is coupled to the direct voltage circuit.
Self-commutated inverters, in particular rapidly switching inverters, frequently have an output filter, in order to delimit high voltage gradients which occur during switching and/or to enable shielded lines to be omitted. One special variant of an output filter couples interferences back to a direct voltage circuit which supplies the inverter.
Output filters of inverters frequently have a pronounced resonance frequency. In order to obtain the highest possible damping in the region of a switching frequency of the inverter and its multiples, the components of an output filter are typically selected so that the resonance frequency of the output filter is located in the region between a maximum fundamental oscillation output frequency and the switching frequency. Filter output currents of the output filter can be used for closed-loop current control. The use of the filter output currents can advantageously influence the behavior of the closed-loop current control in relation to a use of the filter input currents of the output filter.
By linking the output filter to the direct voltage circuit, parts of the filter input currents of the output filter can also flow directly into the direct voltage circuit. These so-called common mode currents are not detected by a closed-loop current control on the output side and can therefore also not be adjusted. A conventional dq closed-loop current control with a current measurement downstream of the inverter would also not detect these currents. If the currents are considered after a dq0 transformation, in addition to the actual d- and q-components in this constellation a significant zero-phase-sequence system component also exists. The resonance frequency of the output filter is also visible in the common mode circuit and results in oscillations of the filter input currents, which load the filter components of the output filter and the electronic switches of the inverter.
An output filter coupled to the direct voltage circuit therefore requires measures for damping these oscillations. One approach is to introduce damping resistors in order to reduce the amplitude peaks in the region of the resonance frequency. These damping resistors nevertheless require additional installation space and produce losses which have to be discharged.
In addition, active electronic circuits can also be used in order to dampen oscillations. This alternative is very complicated, however. One further solution for circumventing this problem is the change in the filter topology. If the connection to the direct voltage circuit is separated, for instance, common mode currents can in principle no longer flow, but the filter effect for common mode interferences is also lost, however. By using additional components, for instance a common mode inductor or additional capacitors, the filter transmission function can be embodied differently for common mode and what are known as differential mode signals and as a result resonance oscillations in the common mode system can likewise be reduced. However, this solution also requires additional components and additional installation space.
US 2016/0156291 A1 discloses a bidirectional high frequency drive, which is designed to connect a supply network and an electric machine. The high frequency drive comprises inductors, which are configured in each case for connection with respective phase outputs of the electric machine, circuit breakers, which are connected to the inductors, and a controller, which is connected to the circuit breakers and generates control signals on the basis of an operating state and a predetermined operating state of the electric machine.
CN 105 553 309 A discloses a three-level inverter of the T type and a method for controlling its center point voltage in an open-loop manner. With the inverter, a connection point of an upper bus capacitance and a lower bus capacitance is short-circuited on a direct current side of the inverter with a neutral line of an alternating current side. The method for controlling the center point voltage in an open-loop manner is based on a dq axes decoupling controller.
EP 3 058 646 A1 discloses a method for controlling a power converter, which is connected to an electrical load or an electrical energy source by way of a filter, in an open loop manner. With the method, output signals are determined, which comprise currents and/or voltages measured in the filter. At least one of the output signals is filtered algorithmically by applying a signal filter to the output signal, in order to amplify the output signal in the case of a resonance frequency of the filter.
The object underlying the invention is to suppress oscillations of filter input currents in a self-commutated inverter with an output filter, which is coupled to a direct voltage circuit supplying the inverter, without using additional components.
The object is achieved according to the invention by a method having the features of claim 1 and a self-commutated inverter having the features of claim 10.
Advantageous embodiments of the invention are the subject matter of the dependent claims.
With the inventive method for operating a self-commutated inverter, which is supplied from a direct voltage circuit and has electronic switches for generating a three-phase output voltage and a three-phase output filter which is connected downstream of the electronic switches and is coupled to the direct voltage circuit, the electronic switches are controlled in an open-loop manner by space-vector modulation, in which a zero-phase-sequence system voltage is controlled in a closed-loop manner by filter-input voltages of the output filter as a function of a target-voltage space vector of the space-vector modulation and filter input currents of the output filter such that oscillations in a zero-phase sequence system of the filter input currents are suppressed.
The invention therefore provides to suppress in a targeted manner oscillations in a zero-phase-sequence system of the filter input currents of the output filter by modifying a space-vector modulation, with which the electronic switches are activated. With the use of a conventional space vector modulation, a zero-phase-sequence system in the phases of the inverter voltage changes as a function of the degree of modulation and the angular position of the voltage. The changes to the zero-phase-sequence system result in common-mode excitations of the output filter and oscillations of the filter input currents. By means of a targeted influencing of the zero-phase-sequence system voltage of the filter input voltages of the output filter by modifying the space-vector modulation, oscillations can therefore be suppressed in a zero-phase-sequence system of the filter input currents. By means of the inventive method, oscillations of the filter input currents and therefore loads of the output filter and the electronic switches of the inverter are reduced, without further passive components, for instance damping resistors, additional inductors or capacitors or active electronic circuits being used.
One embodiment of the invention provides that the zero-phase-sequence system voltage of the filter input voltages is controlled in a closed loop manner by a zero-phase-sequence system shift, which defines a duration ratio of durations, in which one of the zero-phase-sequence voltage space vectors is applied in each case during a clock period of the space vector modulation. This embodiment of the invention takes advantage of the fact that there are a number of zero-phase-sequence voltage space vectors and the zero-phase-sequence system voltage of the filter input voltages can be influenced by the duration ratio of the durations, in which one of the zero-phase-sequence system voltage space vectors is applied during a clock period of the space vector modulation in each case.
A further shaping of the afore-cited embodiment of the invention provides that the zero-phase-sequence shift has two shift portions, wherein a first shift portion is determined as a function of the target voltage space vector of the space vector modulation and the second shift portion is formed as a function of the filter input currents of the output filter. For instance, the zero-phase-sequence system shift is formed by adding the two shift portions. The first shift portion defines for instance a duration ratio with which the target voltage space vector can be realized without a zero-phase-sequence system. A zero-phase-sequence system voltage of the filter input voltages is effected by the second shift portion, which dampens oscillations in the zero-phase-sequence system of the filter input currents. The second shift portion is determined for instance by means of a P controller as a function of a total current which is formed from the filter input currents of the output filter. For instance, the filter input currents of the output filter are measured and the total current is formed by adding the measured filter input currents.
The afore-cited embodiments of the invention enable excitations of common mode oscillations to be avoided as much as possible by the first shift portion of the zero-phase-sequence system shift and oscillations in the filter input currents to be dampened by the second shift portion. Avoiding excitations of common mode oscillations by means of a zero-phase-sequence system-free realization of the target voltage space vector is especially possible with relatively small degrees of modulation, in other words with small ratios of the target voltage in relation to the direct voltage of the direct voltage circuit. A zero-phase-sequence system-adjusted space vector modulation of this type is however not effective with higher degrees of modulation and cannot dampen slowly decaying oscillations in the zero-phase-sequence system of the filter input currents. The second shift portion of the zero-phase-sequence system shift, which depends on the filter input currents and dampens oscillations in the zero-phase-sequence system of the filter input currents by means of a zero-phase sequence system which counteracts the oscillations, is used to dampen these oscillations.
A further embodiment of the invention provides that the target voltage space vector of the space vector modulation is formed as a function of filter output currents of the output filter. The invention provides that the space vector modulation controls the filter output currents in a closed-loop manner and in the process simultaneously suppresses oscillations in a zero-phase-sequence system of the filter input currents.
An inventive self-commutated inverter is supplied from a direct voltage circuit and comprises electronic switches for producing a three-phase output voltage, a three-phase output filter which is connected downstream of the electronic switches and is coupled to the direct voltage circuit, and a control unit. The control unit is designed to activate the electronic switches with a space vector modulation, in which a zero-phase-sequence system voltage is controlled in a closed-loop manner by filter input voltages of the output filter as a function of a target voltage space vector of the space vector modulation and filter input currents of the output filter so that oscillations in a zero-phase-sequence system of the filter input currents are suppressed. The inverter can be embodied in a two-level or multi-level topology. The advantages of an inventive inverter correspond to the advantages of the inventive method already cited above.
Embodiments of the inventive inverter correspond to embodiments of the inventive method.
In particular, one embodiment of the inventive inverter provides that the control unit is designed to control the zero-phase-sequence system voltage of the filter input voltages in a closed-loop manner by means of a zero-phase-sequence system shift, which defines a duration ratio of durations, in which one of the zero-phase-sequence voltage space vectors is applied in each case during a clock period of the space vector modulation. For instance, the control unit has a space vector modulator, which is designed to determine a first shift portion of the zero-phase-sequence system shift as a function of the target voltage space vector of the space vector modulation. Furthermore, the control unit has a P-controller, for instance, which is designed to form a second shift portion of the zero-phase-sequence system shift as a function of a total current, which is formed from the filter input currents of the output filter.
One further embodiment of the inventive inverter provides that the control unit is embodied to form a target voltage space vector of the space vector modulation as a function of filter output currents of the output filter.
A further embodiment of the inventive inverter provides a first measuring apparatus for measuring the filter input currents and/or a second measuring apparatus for measuring filter output currents of the output filter.

The above-described characteristics, features and advantages of this invention, as well as the manner in which these are realized will become more clearly and easily intelligible in connection with the following description of exemplary embodiments which are explained in more detail with reference to the drawings, in which:

FIG. 1 shows a circuit diagram of a self-commutated inverter,

FIG. 2 shows a block diagram of a self-commutated inverter.

Parts which correspond to one another are provided with the same reference characters in the figures.
FIG. 1 shows a circuit diagram of a self-commutated inverter 1. The inverter 1 is supplied from a direct voltage circuit 3. The inverter 1 has electronic switches S1, S2, S3 for generating a three-phase output voltage, a three-phase output filter 5 and a control unit 7 for closed-loop current control. The inverter 1 and the direct voltage circuit 3 can be components of a converter, which also has a rectifier, which is connected to the inverter 1 by way of the direct voltage circuit 3.
Each electronic switch S1, S2, S3 switches a phase of the output voltage of the inverter 1 and has a first switching state, in which it sets the phase onto a first direct voltage potential Z+ of the direct voltage circuit 3, and a second switching state, in which the phase is set onto a second direct voltage potential Z− of the direct voltage circuit 3. The potential difference between the direct voltage potentials Z+, Z− is a direct voltage U_zof the direct voltage circuit 3. The electronic switches S1, S2, S3 are only shown schematically in FIG. 1 and formed in each case for instance as a half-bridge with two semiconductor switches 9. Each semiconductor switch 9 is embodied for instance as an IGBT (bipolar transistor with insulated gate electrode) or as a MOSFET (metal oxide semiconductor field effect transistor).
The output filter 5 is arranged downstream of the electronic switches S1, S2, S3 and has a filter inductor 11 and two filter capacitors 13, 15 for each phase of the output voltage. The filter inductor 11 of a phase is connected to the electronic switch S1, S2, S3 of this phase. The output filter 5 is connected to the direct voltage circuit 3 by way of the filter capacitors 13, 15. A first filter capacitor 13 of each phase is connected with the first direct voltage potential Z+ of the direct voltage circuit 3 and the second filter capacitor 15 of each phase is connected to the second direct voltage potential Z− of the direct voltage circuit 3.
A filter input current i1_in, i2_in, i1_in of this phase flows between the electronic switch S1, S2, S3 of one phase and the output filter 5. Filter output currents i1_out, i2_out, i3_out which form an output current of the inverter 1 for one phase in each case, flow behind the output filter 5, in other words on the output side. Common mode currents of the output filter 5 can flow by way of the filter capacitors 13, 15.
The control unit 7 controls the electronic switches S1, S2, S3 with activation signals C1, C2, C3. The activation signals C1, C2, C3 are formed by the control unit 7 with a space vector modulation, in which, in a manner described in more detail below, a zero-phase-sequence system voltage of filter input voltages of the output filter 5 is controlled in a closed-loop manner as a function of a target voltage space vector μ_{α,β_s}of the space vector modulation and the filter input currents i2_in, i3_in so that oscillations in a zero-phase-sequence system of the filter input currents i1_in, i2_in, i3_in are suppressed, wherein the target voltage space vector μ_{α,β_s}is formed as a function of the filter output currents i1_out, i2_out, i3_out. The filter input currents i2_in, i3_in are detected by means of a first measuring apparatus 17. The filter output currents i1_out, i2_out, i3_out are detected by means of a second measuring apparatus 19.
FIG. 2 shows a block diagram of the inverter 1 shown in FIG. 1, wherein the output of the inverter 1 is connected to a three-phase electric motor 21, so that the filter output currents i1_out, i2_out, i3_out of the inverter 1 are the motor currents of the electric motor 21. The electric motor 21 is embodied as a rotating electric machine with a rotor and a stator and has an angular position sensor, which detects a rotor angle φ, which specifies a position of the rotor in relation to the stator. Alternatively, the electric motor 21 can also be embodied as a linear motor with a stator and a rotor which can be moved linearly in relation to the stator, and have a position sensor, which specifies a rotor position of the rotor in relation to the stator. The rotor position then appears at the position of the rotor angle φ.
The control unit 7 is designed to carry out the inventive method described below. To this end, the control unit 7 has an adder 23, a P controller 25, a PI controller 27, a space vector modulator 29 and two transformers 31, 33.
The actual values of the filter output currents i1_out, i2_out, i3_out detected by the second measuring apparatus 19 and the actual value of the rotor angle φ are supplied to a first transformer 31. The first transformer 31 determines an actual current space vector i_{d,q_out}of the filter output currents i1_out, i2_out, i3_out in a dq coordinate system rotating with the rotor from these actual values by means of a dq transformation.
A differential current space vector i_{d,q_delta}is formed from the actual current space vector i_{d,q_out}and a target current space vector i_{d,q_s}, by the actual current space vector i_{d,q_out}being subtracted from the target current space vector i_{d,q_s}. The differential current space vector i_{d,q_delta}is the control deviation of the closed-loop current control of the filter output currents i1_out, i2_out, i3_out.
A dq target voltage space vector u_{d,q_s}is formed by the PI controller 27 from the differential space vector i_{d,q_delta}, and describes a target voltage of the inverter 1, in a dq coordinate system, which counteracts the control deviation.
A target voltage space vector u_{α,β_s}for the space vector modulation is formed by the second transformer 33 from the dq target voltage space vector u_{d,q_s}, by the dq target voltage space vector u_{d,q_s}being transformed into a stator-fixed αβ coordinate system by using the rotor angle φ.
The space vector modulator 29 generates the activation signals C1, C2, C3, with which the electronic switches S1, S2, S3 are activated, from the target voltage space vector u_{α,β_s}and a zero-phase-sequence system shift μ. The zero-phase-sequence system shift p defines a duration ratio of durations, in which one of the zero-phase-sequence voltage space vectors is applied during a clock period of the space vector modulation in each case. In the case of two zero-phase-sequence voltage space vectors, the zero-phase-sequence system shift μ therefore defines the quotients of a first duration, for instance, in which a first zero-phase-sequence voltage space vector is applied during a clock period, and a second duration, in which the second zero-phase-sequence voltage space vector is applied during the clock period.
The zero-phase-sequence system shift p is additionally formed according to μ=μ₁+μ₂from two shift portions μ₁, μ₂. A first shift portion μ₁is formed by the space vector modulator 29 as a function of the target voltage space vector μ_{α,β_s}, defines a duration ratio, with which the target voltage space vector μ_{α,β_s}can be realized free of a zero-phase-sequence system.
The second shift part μ₂is formed by the adder 23 and the P controller 25 as a function of the filter input currents i1_in, i2_in, i3_in so that it effects a zero-phase-sequence system voltage of the filter input voltages, dampens the oscillations in the zero-phase-sequence system of the filter input currents i3_in. To this end, the actual values of the filter input currents i1_in, i2_in, i3 detected by the first measuring apparatus 17 are added by the adder 23 to form a total current i0_in. The second shift portion μ₂is determined from the total current i0_in by the P controller 25.
Instead of measuring the filter input currents i1_in, i2_in, i3_in and the filter output currents i1_out, i2_out, i3_out with measuring apparatuses 17 and 19, provision can also be made to measure only the filter input currents i1_in, i2_in, i3_in and to calculate the filter output currents i1_out, i2_out, i3_out. Alternatively, provision can be made to measure only the filter output currents i1_out, i2_out, i3_out and to calculate the filter input currents i1_in, i2_in, i3_in.
Although the invention has been illustrated and described in detail based on preferred exemplary embodiments, the invention is not restricted by the examples given and other variations can be derived therefrom by a person skilled in the art without departing from the protective scope of the invention.

Claims

1. A method for operating a self-commutated inverter (1), which is supplied from a direct voltage circuit (3) and electronic switches (S1, S2, S3) for generating a three-phase output voltage and a three-phase output filter (5) arranged downstream of the electronic switches (S1, S2, S3) and coupled to the direct voltage circuit (3), so that common mode portions of filter input currents (i1_in, i2_in, i3_in) of the output filter (5) can flow into the direct voltage circuit (3), wherein

the electronic switches (S1, S2, S3) are controlled in an open-loop manner by space vector modulation, in which

filter output currents (i1_out, i2_out, i3_out) of the output filter (5) are controlled in a closed-loop manner and a zero-phase-sequence system voltage of filter input voltages of the output filter (5) is controlled in a closed loop manner as a function of a target voltage space vector (u_{α,β_s}) of the space vector modulation and the filter input currents (i1_in, i2_in, i3_in) of the output filter (5) so that oscillations in a zero-phase-sequence system of the filter input currents (i1_in, i2_in, i3_in) are suppressed.

2. The method as claimed in claim 1, wherein the zero-phase-sequence system voltage of the filter input voltages is controlled in a closed-loop manner by a zero-phase-sequence system shift (μ), which defines a duration ratio of durations, in which one of the zero-phase-sequence voltage space vectors is applied in each case during a clock period of the space vector modulation.

3. The method as claimed in claim 2, wherein the zero-phase-sequence system shift (μ) has two shift portions (μ₁, μ₂), wherein a first shift portion (μ₁) is determined as a function of the target voltage space vector (μ_{α,β_s}) of the space vector modulation and the second shift portion (μ₂) is formed as a function of the filter input currents (i1_in, i2_in, i3_in) of the output filter (5).

4. The method as claimed in claim 3, wherein the zero-phase-sequence system shift (μ) is formed by adding the two shift portions (μ₁, μ₂).

5. The method as claimed in claim 3 or 4, wherein the first shift portion (μ₁) defines a duration ratio, with which the target voltage space vector (u_{α,β_s}) can be realized free of a zero-phase-sequence system.

6. The method as claimed in one of claims 3 to 5, wherein a zero-phase-sequence system voltage of the filter input voltages is effected by the second shift portion (μ₂) and dampens oscillations in the zero-phase-sequence system of the filter input currents (i1_in, i2_in, i3_in).

7. The method as claimed in one of claims 3 to 6, wherein the second shift portion is formed by means of a P controller (25) as a function of a total current (i0_in), which is formed from the filter input currents (i1_in, i2_in, i3_in) of the output filter (5).

8. The method as claimed in claim 7, wherein the filter input currents (i1_in, i2_in, i3_in) of the output filter (5) are measured and the total current (i0_in) is formed by adding the measured filter input currents (i1_in, i2_in, i3_in).

9. The method as claimed in one of the preceding claims, wherein the target voltage space vector (μ_{α,β_s}) of the space vector modulation is formed as a function of filter output currents (i1_out, i2_out, i3_out) of the output filter (5).

10. A self-commutated inverter (1), which is supplied from a direct voltage circuit (3), the inverter (1) comprising

electronic switches (S1, S2, S3) for generating a three-phase output voltage,

a three-phase output filter (5) arranged downstream of the electronic switches (S1, S2, S3) and coupled to the direct voltage circuit (3), so that common mode portions of filter input currents (i1_in, i2_in, i3_in) of the output filter (5) can flow into the direct voltage circuit (3), and

a control unit (7) which is designed to activate the electronic switches (S1, S2, S3) with a space vector modulation, with which filter output currents (i1_out, i2_out, i3_out) of the output filter (5) are controlled in a closed-loop manner and a zero-phase-sequence system voltage of filter input voltages of the output filter (5) is controlled in a closed-loop manner as a function of a target voltage space vector (μ_{α,β_s}) of the space vector modulation and the filter input currents (i1_in, i2_in, i3_in) of the output filter (5) so that oscillations in a zero-phase-sequence system of the filter input currents (i1_in, i2_in, i3_in) are suppressed.

11. An inverter (1) as claimed in claim 10, wherein the control unit (7) is designed to control in a closed-loop manner the zero-phase-sequence system voltage of the filter input voltages by means of a zero-phase-sequence system shift (μ), which defines a duration ratio of durations, in which one of the zero-phase-sequence voltage space vectors is applied in each case during a clock period of the space vector modulation.

12. The inverter (1) as claimed in claim 11, wherein the control unit (7) has a space vector modulator (29), which is designed to determine a first shift portion (μ_i) of the zero-phase-sequence system shift (μ) as a function of the target voltage space vector (μ_{α,β_s}) of the space vector modulation.

13. The inverter (1) as claimed in claim 11 or 12, wherein the control unit (7) has a P controller (25), which is designed to form a second shift portion (μ₂) of the zero-phase-sequence system shift (μ) as a function of a total current (i0_in), which is formed from the filter input currents (i1_in, i2_in, i3_in) of the output filter (5).

14. The inverter (1) as claimed in one of claims 10 to 13, wherein the control unit (7) is embodied to form the target voltage space vector (μ_{α,β_s}) of the space vector modulation as a function of the filter output currents (i1_out, i2_out, i3_out) of the output filter (5).

15. The inverter (1) as claimed in one of claims 10 to 14 with a first measuring apparatus (17) for measuring the filter input currents (i1_in, i2_in, i3_in) and/or a second measuring apparatus (19) for measuring the filter output currents (i1_out, i2_out, i3_out) of the output filter (5).