US20200177087A1 - Adjustable power supply device for supplying power to a power switch control device - Google Patents
Adjustable power supply device for supplying power to a power switch control device Download PDFInfo
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- US20200177087A1 US20200177087A1 US16/783,705 US202016783705A US2020177087A1 US 20200177087 A1 US20200177087 A1 US 20200177087A1 US 202016783705 A US202016783705 A US 202016783705A US 2020177087 A1 US2020177087 A1 US 2020177087A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33538—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
- H02M3/33546—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current
- H02M3/33553—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/0081—Power supply means, e.g. to the switch driver
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- This application relates to an adjustable power supply circuit for power switch gate drivers, and in particular to an adjustable power supply circuit capable of being used with multiple variants of power switch gate driver circuits.
- Power electronics devices such as DC to DC converters and switched mode power supplies, make use of high power transistors to provide a stable output voltage of a predetermined value from a given input power supply.
- the transistors are switched on and off to regulate the output voltage.
- Power electronics devices have important applications in switching high currents in uninterruptible power supplies, motor drives, solar inverters, and electric vehicles, and must therefore meet stringent constraints and requirements imposed upon the output voltage they produce. For example, it may not be acceptable for the output voltage to deviate from a nominal value by more than a predetermined tolerance.
- Power electronics devices can provide gate drive potential differences to power switch devices.
- power switch devices such as high power transistors, each require a 25 Volt (V) gate drive potential difference.
- Isolated Gate Bipolar Transistors require a connection to rails held at +15 V and ⁇ 10 V; Silicon Carbide transistors require a connection to rails held at +20 V and ⁇ 5 V; and Metal Oxide Field Effect Transistors require a connection to rails held at +15 V and ⁇ 5 V.
- a preferred embodiment of the present invention provides an adjustable power supply device for supplying power to a power switch control device configured to provide control signals to a power switch device, the adjustable power supply device including: a pair of input terminals; switching circuitry connected to the pair of input terminals; converter circuitry, the converter circuitry including a pair of intermediate terminals and first, second, and third output terminals that output power to the power switch control device; a transformer including a primary side winding coupled to the pair of input terminals and a secondary side winding coupled to the pair of intermediate terminals, wherein a potential difference generated between the pair of intermediate terminals is divided by a dividing circuit into a first output voltage difference applied across the first and the second output terminals and a second output voltage difference applied across the second and the third output terminals; the converter circuitry including a first adjustment circuit that adjusts the first output voltage difference and second output voltage difference, the first adjustment circuit including at least one external terminal that is coupled to a first resistance element; and the switching circuitry including a second adjustment circuit that adjusts the potential difference generated between the
- the switching circuitry may further include a switch controller coupled to a switch and coupled to the primary side winding to control a current flowing through the primary side winding.
- one of the at least one external terminals of the second adjustment circuit may be coupled to the switch controller.
- one of the at least one external terminals of the second adjustment circuit may be coupled to a voltage feedback pin of the switch controller.
- the voltage feedback pin of the switch controller may be coupled to a primary side feedback winding.
- the second adjustment circuit may include a switching circuit voltage divider including at least a first resistor connected between the voltage feedback pin and the primary side feedback winding, and a second resistor connected between the voltage feedback pin and ground wherein the voltage feedback pin of the switch controller is connected to the switching circuit voltage divider.
- the second adjustment circuit may include a pair of external terminals that is coupled to a pair of corresponding external connections configured to receive the first resistance element therebetween, one of the pair of external terminals is coupled to ground, and the first resistance element, when connected between the pair of corresponding external connections, is coupled via the pair of external terminals of the second adjustment circuit in parallel with a resistor in the switching circuit voltage divider.
- the second adjustment circuit may adjust the potential difference generated between the pair of intermediate terminals by adjusting the duty cycle of the switch controller.
- the dividing circuit may include a further resistive element.
- one of the at least one external terminals of the first adjustment circuit may be coupled to the low voltage side of the secondary side winding via one of the pair of intermediate terminals.
- the first adjustment circuit may include a converter circuitry voltage divider including at least a first resistor and a second resistor connected in parallel between the pair of intermediate terminals.
- the at least one external terminal of the first adjustment circuit includes a pair of external terminals, and the pair of external terminals of the first adjustment circuit is coupled to a the first adjustment circuit may include a pair of external terminals that is coupled to a pair of external connections configured to receive the second resistance element mounted therebetween.
- the dividing circuit includes a further resistance element, and one of the pair of external terminals may be coupled to a divider circuit and to the high voltage side of the secondary side winding via the other of the pair of intermediate terminals and the converter circuitry voltage divider, such that the first resistance element is coupled to the further resistance element of the dividing circuit.
- the further resistance element may be a transistor.
- the other of the pair of external terminals of the first adjustment circuit may be coupled to the base/gate terminal of the transistor.
- the transistor may be connected in parallel between the pair of intermediate terminals such that the source/emitter terminal of the transistor is coupled to the high voltage side of the secondary side winding.
- the further resistance element may include an adjustable voltage drop.
- a node of the first adjustment circuit may be connected to the further resistance element such that a change in voltage at the node adjusts the voltage dropped across the further resistance element.
- the first adjustment circuit may adjust the first output voltage difference and the second output voltage difference by adjusting the voltage dropped across the further resistance element.
- a preferred embodiment of the present inventions provides a device including: a header on which the switching circuitry, converter circuitry, and transformer are mounted; wherein the pair of input terminals and the at least one external terminals of the first and the second adjustment circuits are connections on the external surface of the header that connect with a third party circuit board.
- the reference voltage may be the source voltage of the power switch device.
- the reference voltage may be zero volts.
- FIG. 1 shows a known DC to DC converter which provides fixed voltages to a gate driver.
- FIG. 2 shows a simplified diagram of a Pulse Width Modulation controller that supplies gate control signals to a transistor.
- FIG. 3 shows a preferred embodiment of an adjustable power supply that provides adjustable voltages to a gate driver.
- FIG. 4 shows an alternative preferred embodiment of an adjustable power supply that provides adjustable voltages to a gate driver.
- FIG. 5 shows a power supply unit including a header, planar transformer, and printed circuit board mounted in position.
- flyback converter For the purposes of illustration, a flyback converter is shown in the accompanying figures, however other DC to DC converter configurations, such as a forward converter, for example, would also be acceptable.
- FIG. 1 shows a DC to DC converter 100 in a flyback converter configuration.
- the converter accepts an input voltage Vin relative to a ground voltage and is configured to provide three fixed voltages, for example +20 V, 0 V and ⁇ 5 V, at output terminals 131 , 132 and 133 .
- the DC to DC converter 100 shown in FIG. 1 includes a transformer TX 1 , primary-side circuitry connected to a pair of input terminals including an input voltage (Vin) terminal and a ground input terminal, and secondary-side circuitry connected to three output terminals 131 , 132 and 133 .
- the primary-side circuitry shown in FIG. 1 includes switching circuitry 101 to periodically control whether a Metal Oxide Field Effect Transistor (MOSFET) Q 5 is in a conducting or a non-conducting state.
- the secondary-side circuitry includes converter circuitry 102 and ensures the potential difference supplied across intermediate terminals 121 and 122 is correctly shared across output terminals 131 , 132 and 133 .
- Transformer TX 1 includes transformer primary windings, P 1 and P 2 , and a transformer secondary winding, S 1 , which are wound around a transformer core.
- the transformer core is made of ferrite, however in alternative arrangements it is possible to use other materials for the core, or the core may be absent in which case the windings are air-cored.
- Input voltage terminal Vin is connected to the high voltage side of primary winding P 1 and the drain of a Metal Oxide Field Effect Transistor (MOSFET) Q 5 located in switching circuitry 101 is connected to the low voltage side of primary winding P 1 .
- the feedback primary winding P 2 is connected to feedback circuitry 103 located on the primary side of transformer TX 1 and secondary winding S 1 is connected to the converter circuitry 102 .
- a capacitor C 6 is connected between input terminals Vin and ground and acts as a short bypass path that provides high peak currents to transistor Q 5 .
- Transistor Q 5 includes a drain, source and gate. As indicated above, the drain of transistor Q 5 is connected to the low voltage side of primary transformer winding P 1 . The source of transistor Q 5 is connected to ground via a transistor source resistor R 1 . The gate of transistor Q 5 is connected to a Pulse Width Modulation (PWM) switch controller U 3 such that transistor Q 5 receives gate control signals from PWM switch controller U 3 .
- PWM Pulse Width Modulation
- Feedback primary winding P 2 is connected to feedback circuitry 103 located within the switching circuitry 101 and includes a diode D 1 , a capacitor C 1 and a voltage divider circuit R 2 , R 3 .
- Primary winding P 2 is connected to the feedback circuitry 103 at nodes 111 and 112 .
- a further node 113 is located at the midpoint of voltage divider circuit R 2 , R 3 and is connected to PWM switch controller U 3 such that the voltage at node 113 is provided to an input pin of PWM switch controller U 3 .
- Capacitor C 1 is connected between nodes 111 and 112 and acts as a smoothing capacitor as further described below.
- Node 112 is connected to ground and diode D 1 is connected between node 111 and the low voltage side of feedback primary winding P 2 such that, when transistor Q 5 is turned on, diode D 1 is reverse-biased.
- Voltage divider resistors R 2 and R 3 are connected in series between node 111 and ground at node 114 .
- Node 113 of the feedback voltage divider is connected to PWM switch controller U 3 at the Vfb (voltage feedback) pin.
- the PWM switch controller U 3 depicted in FIG. 1 includes 8 pins: a positive voltage pin, Vp; a ground voltage pin, Gnd; a feedback voltage pin Vfb; a reference voltage pin, Ref; a comparison voltage pin, Comp; a current sense voltage pin, Sense; an oscillator input pin, Osc; and an output voltage pin, Vout.
- the PWM switch controller U 3 shown in FIG. 1 may be provided as a portion of an integrated circuit (IC) incorporated within the circuitry shown in FIG. 1 .
- a supply voltage may be provided to the PWM switch controller U 3 via input pins Vp and Gnd.
- the Gnd input pin is connected to ground via node 115 .
- a voltage at node 113 in feedback circuitry 103 is provided to the Vfb pin.
- Gate control signals produced by U 3 are provided to transistor Q 5 via the Vout pin.
- the secondary-side circuitry 102 includes: a diode D 2 and a capacitor C 2 ; intermediate terminals 121 and 122 ; a capacitive voltage divider C 3 , C 4 ; a resistor and Zener diode voltage divider R 4 , D 3 ; and output terminals 131 , 132 and 133 .
- Diode D 2 is connected between intermediate terminal 121 and the low voltage side of transformer secondary winding S 2 such that when transistor Q 5 is in a conductive mode, diode D 2 is reverse-biased.
- Capacitor C 2 is provided between intermediate terminals 121 and 122 to smooth the voltage applied across intermediate terminals 121 and 122 .
- diode D 2 and capacitor C 2 operate as a half-wave rectifier circuit with a smoothing capacitor that provides a DC voltage across intermediate terminals 121 and 122 .
- the capacitive voltage divider includes capacitors C 3 and C 4 connected in series across intermediate terminals 121 and 122 . As shown in FIG. 1 , capacitor C 3 is connected to terminal 121 via node 123 and is connected to capacitor C 4 via node 124 . Similarly, capacitor C 4 is connected to terminal 122 via node 125 and to capacitor C 3 via node 124 .
- the secondary-side voltage divider depicted in FIG. 1 includes resistor R 4 and Zener diode D 3 connected in series across intermediate terminals 121 and 122 via nodes 126 and 128 .
- resistor R 4 is connected to terminal 121 via nodes 126 and 123 and is connected to Zener diode D 3 via node 127 .
- Zener diode D 3 is connected to terminal 122 via nodes 128 and 125 and to resistor R 4 via node 127 .
- the resistor and Zener diode voltage divider and the capacitive voltage divider are connected between nodes 124 and 127 which results in fixing these nodes at the same potential.
- Output terminal 131 is connected to the resistor and Zener diode voltage divider circuit via node 126 and is connected to the capacitive voltage divider circuit via nodes 126 and 123 .
- Output terminal 132 is connected to the resistor and Zener diode voltage divider circuit via node 127 and is connected to the capacitive voltage divider circuit via nodes 127 and 124 .
- Output terminal 132 is also connected to the source of power switch device Q 1 via node 129 and is held at a reference voltage, Vsource. In some preferred embodiments, output terminal 132 is held at 0 V so that output terminal 132 acts as a gate drive 0 V reference.
- Output terminal 133 is connected to the resistor and Zener diode voltage divider circuit via node 128 and is connected to the capacitive voltage divider circuit via nodes 128 and 125 .
- the voltages produced at output terminals 131 , 132 and 133 may be provided to a power switch device, such as transistor Q 1 , via a power switch control device, for example gate driver integrated circuit (IC) U 1 .
- a power switch control device for example gate driver integrated circuit (IC) U 1 .
- gate driver IC U 1 includes: a fixed supply voltage input pin (VCC); a ground input pin (COM) pin; a control input pin (IN) pin that receives a clock signal from clock signal generator U 2 ; an absolute supply voltage input pin (VB) connected to output terminal 131 that receives a first, high, fixed voltage; an offset supply voltage input pin (VS) connected to output terminal 133 that receives a second, low, fixed voltage; and an output voltage pin (HO) that sends gate drive signals to Q 1 .
- the IN, VS and VB pins may be connected to logic circuitry to provide gate drive control signals at output pin HO.
- a gate driver IC U 1 is powered by the potential difference provided by terminals 131 and 133 .
- the gate drive waveform provided to the gate of the power switch device Q 1 will vary between a first and second fixed voltage provided by terminals 131 and 133 .
- the gate of the power switch device Q 1 may be provided with a signal alternating between +20 V and ⁇ 5 V. The signal alternates between the first and second fixed voltages in response to a clock signal produced by U 2 .
- the gate driver IC U 1 is provided with a first and second fixed voltage signal from the power supply.
- the first fixed voltage signal may be provided to the VB pin from terminal 131 , which in a specific preferred embodiment may be held at a voltage level of +20 V, for example, and the second fixed voltage signal may be provided to the VS pin from terminal 133 , which in a specific preferred embodiment may be held at a voltage level of ⁇ 5 V, for example.
- the gate driver IC U 1 shown in FIG. 1 may be provided as a portion of an integrated circuit (IC) incorporated within the circuitry shown in FIG. 1 . Additionally, it will be appreciated by those skilled in the art that power switch device Q 1 may be included in other configurations than shown in FIG. 1 . For example, power switch device Q 1 may be connected directly to ground, connected in series with a load, or connected in series with another transistor in a half-bridge configuration.
- IC integrated circuit
- transistor Q 5 when transistor Q 5 is in a conducting state, the input voltage Vin applied across the primary windings of transformer TX 1 causes current to flow in the windings and energy is thereby stored in the resulting magnetic field produced by the transformer TX 1 .
- Switching Q 5 to a non-conductive state induces a voltage across the feedback and secondary transformer windings. Energy stored within the magnetic field is converted to electrical energy which may be used to supply, for example, transistors in switched-mode power supplies or power switch devices.
- transistor Q 5 When transistor Q 5 is turned on, an applied voltage Vin drives a current through the transformer primary winding P 1 , energizing the winding.
- the primary winding P 1 When the primary winding P 1 is energized, the increasing magnetic flux passing through the core of transformer TX 1 induces a voltage across feedback primary winding P 2 and secondary winding S 1 .
- the voltage induced in the secondary and feedback windings is proportional to the number of turns on the secondary and feedback windings and the changing magnetic flux through the windings.
- the polarity of the transformer windings is such that when primary winding P 1 is energized, diodes D 1 and D 2 are reverse biased resulting in no current flowing through feedback winding P 2 and secondary winding S 1 . Energy is therefore stored in the magnetic field within the transformer until transistor Q 5 is switched off.
- Feedback circuitry 103 enables the PWM switch controller U 3 to decide whether to increase or decrease the duty cycle of the gate drive pulses. This maintains a constant output voltage across intermediate terminals 121 and 122 .
- diode D 1 in the feedback winding becomes forward biased when transistor Q 5 is switched off due to a decreasing magnetic flux. Energy stored in the transformer is converted to electrical energy and transferred through the feedback circuit. Smoothing capacitor C 1 ensures that the current and voltage are delivered through the feedback circuit at a constant level instead of as a pulse.
- diodes D 1 and C 1 operate as a half-wave rectifier circuit with a smoothing capacitor that provides a DC voltage to node 111 .
- Resistors R 2 and R 3 act as a voltage divider to provide an appropriate voltage level to switch transistor Vfb pin via node 113 .
- the voltage induced across capacitor C 1 is directly proportional to the voltage induced across capacitor C 2 and also the intermediate terminals 121 and 122 .
- the use of capacitor C 1 and voltage divider R 2 , R 3 therefore provides feedback that is proportional to the output at the secondary side of the transformer without a separate isolated feedback path.
- Adjusting the voltage level at node 113 will change the duty cycle of PWM switch controller IC U 3 , as described below with reference to FIG. 2 .
- the components which also appear in FIG. 1 have been allocated the same numerals.
- FIG. 2 depicts a PWM switch controller U 3 that provides gate control signals to the gate of transistor Q 5 .
- PWM switch controller IC U 3 includes an error amplifier 141 , a comparator 142 , a Set-Reset (SR) latch 143 and a pulse oscillator 144 .
- SR Set-Reset
- Node 113 of feedback circuitry 103 is connected to the negative input of error amplifier 141 via the Vfb pin (not shown) such that the voltage at node 113 is provided to error amplifier 141 as a feedback voltage.
- the positive input of error amplifier 141 is connected to a reference voltage Vref and the difference between Vfb and Vref is output as an error signal Verror.
- error amplifier 141 is connected to the negative input of comparator 142 and the positive input of comparator 142 is connected to node 116 which is located between the source of Q 5 and resistor R 1 such that node 116 supplies a voltage Vsense to comparator 142 .
- the output of the comparator 142 is provided to the reset input R of SR latch 143 .
- the set input S of SR latch 143 is connected to pulse oscillator 144 which provides a signal of a set frequency.
- the Q output of SR latch 143 is connected to the gate of transistor Q 5 via output pin Vout (not shown).
- Vsense depends upon the current flowing through transistor Q 5 . Due to inductive effects in the primary transformer winding P 1 , when transistor Q 5 is switched on the current flowing in the primary winding, and hence the current flowing through transistor Q 5 , increases linearly. Therefore a linearly increasing voltage, Vsense, is established across R 1 . When Vsense equals Verror, the output of comparator 142 is high (1). This resets the RS latch and terminates the gate drive pulse. The Q output of RS latch produces the next gate drive signal when the internal oscillator provides a high signal (1) to the set input S of the RS latch.
- a predetermined and substantially constant voltage is provided between the intermediate terminals 121 and 122 .
- the intermediate terminals 121 and 122 of converter circuitry 102 are alternatively held at a potential by the charge stored in capacitor C 2 or by the opposing voltage set up in the secondary winding.
- Capacitor C 2 acts to reduce the variations in the voltage applied across the intermediate terminals 121 and 122 which result from this cycling, providing an output voltage that may be treated as a constant DC output.
- capacitors C 3 and C 4 are high-frequency capacitors that additionally provide high peak currents to minimize switching losses when power switch device Q 1 switches on or off. As the gate of power switch device Q 1 includes an associated capacitance, the average current flowing into the gate can be very low. Additional capacitors C 3 and C 4 therefore provide the additional functionality of providing high peak currents during switching.
- nodes 124 and 127 are held at the same potential.
- nodes 123 and 126 are held at a first fixed potential and nodes 125 and 128 are held at a second fixed potential.
- nodes 124 and 127 are held at a reference voltage, for example at 0 V.
- a fixed negative voltage is produced at nodes 125 and 128 and a fixed positive voltage is produced at nodes 123 and 126 .
- the fixed voltage levels produced by the voltage divider configuration may be associated with the voltage levels required by the terminals of a power switch device.
- the secondary winding produces a potential difference of 25 V and Zener diode BZX79-5V1 is used, which includes a reverse breakdown voltage of 5.1 V.
- terminal 132 is held at 0 V
- terminal 133 will be held at approximately ⁇ 5 V
- terminal 131 will be held at approximately +20 V.
- the voltages produced in this specific example would be suitable in powering a Silicon Carbide transistor.
- FIG. 3 shows a DC to DC flyback converter 200 in accordance with a preferred embodiment of the present invention.
- a PNP transistor Q 2 replaces the Zener diode D 3 of FIG. 1 .
- a resistive voltage divider R 5 , R 6 is included to adjust the fixed voltages produced at output terminals 131 and 133 .
- resistive voltage divider R 5 , R 6 acts as a first adjustable circuit as further described below.
- Preferred embodiments in accordance with the present invention provide an adjustable power supply to a power switch gate driver, as further described below.
- the first adjustable circuit shown in FIG. 3 includes resistor R 5 and external resistor R 6 connected in series across intermediate terminals 121 and 122 . As shown in FIG. 3 , resistor R 5 is connected to intermediate terminal 121 via nodes 221 and 123 and is connected to external resistor R 6 via nodes 222 and 224 . External resistor R 6 is connected to the converter circuit via nodes 223 and 224 and to resistor R 5 via node 222 .
- the base terminal of PNP transistor Q 2 is connected to terminal 121 via node 222 , resistor R 5 and node 221 , and connected to terminal 122 via nodes 222 and 224 , external resistor R 6 and node 223 .
- the emitter terminal of PNP transistor Q 2 is also connected to terminal 121 via node 127 , resistor R 4 and node 126 .
- the emitter terminal is also connected to the source of power switch device Q 1 via node 132 .
- the collector terminal of PNP transistor Q 2 is connected to terminal 122 via node 128 .
- node 127 is held at a reference voltage, for example 0 V, and nodes 126 and 128 are held at a constant voltage due to the near-constant emitter-collector voltage drop across the PNP transistor.
- node 128 is held at ⁇ 5 V, for example, by establishing an emitter voltage of approximately 5 V.
- the emitter voltage is the sum of the forward biased emitter-base voltage of the transistor, which is approximately 0.6 V, and the voltage at node 222 . Therefore, an emitter voltage of 5 V may be set by producing a voltage of approximately 4.4 Vat node 222 with respect to node 128 .
- node 128 may be held at ⁇ 5 V by setting voltage divider resistors R 5 and R 6 to produce a voltage of approximately 4.4 V at node 222 with respect to node 128 . Once the voltage at node 222 is set, the emitter voltage, and hence the voltage at node 128 , will remain at an approximately constant level even when the voltage across C 4 rises.
- resistor R 4 and transistor Q 2 act as a dividing circuit that divides a potential difference generated across intermediate terminals 121 and 122 into a first output voltage difference applied across output terminals 131 and 132 and a second output voltage difference applied across output terminals 132 and 133 .
- the amount of voltage dropped by transistor Q 2 is dependent upon the voltage at node 222 , which is adjusted by a first adjustment circuit that includes external resistor R 6 .
- the voltage at node 222 is equal to:
- V 222 V C ⁇ ⁇ 2 ⁇ R 6 R 5 + R 6
- V C2 is the potential difference across capacitor C 2 or, in other words, the potential difference generated across intermediate terminals 121 and 122 .
- Adjusting the resistance of resistor R 6 affects the ratio with which the voltage applied between intermediate terminals 121 and 122 is divided between resistors R 5 and R 6 , and hence the voltage at node 222 .
- Increasing the resistance of resistor R 6 results in an increased voltage at node 222 .
- a larger voltage at node 222 will result in a larger emitter-collector potential difference and hence a larger emitter-collector voltage drop, which adjusts the voltage difference between output terminals 132 and 133 so that a larger negative voltage is produced at output terminal 133 .
- increasing the resistance value of resistor R 6 may result in the voltage produced at output terminal 133 increasing from ⁇ 5 V to ⁇ 10 V.
- the supply voltage provided to a power switch device may be adjusted by modify the duty cycle of transistor Q 5 using a second adjustment circuit including external resistor R 7 , as further described below.
- the voltage generated between intermediate terminals 121 and 122 depends upon the duty cycle of transistor Q 5 , which is regulated by a feedback voltage Vfb at node 113 . If, for example, Vfb is reduced so that there is a greater difference between a reference voltage Vref and Vfb, a difference signal Verror will also increase. This results in Vsense being able to linearly increase to a higher level before the RS latch 143 terminates the gate drive signal. Therefore, the duty cycle of PWM switch controller U 3 is lengthened, enabling more energy to be stored and transferred to intermediate terminals 121 and 122 , and hence to output terminals 131 and 133 .
- the power supply may be adjusted to supply a power switch device with a variety of supply voltages. For example, a 15 V, 20 V or 25 V supply may be provided to a power switch device.
- External resistors R 6 and R 7 are provided externally to the switching circuitry 101 and converter circuitry 102 . External resistor R 6 and R 7 may be connected to the power supply via external connections or nodes external to the switching or converter circuitry, which enables the resistance of resistors R 6 and R 7 to be easily adjusted without having to access the power supply circuitry. As shown in FIG. 3 , resistor R 6 may be connected to the converter circuitry via nodes 223 and 224 and resistor R 7 may be connected to the switching circuitry via nodes 225 and 226 . Nodes 223 , 224 , 225 and 226 may be provided external to the adjustable power supply. This enables resistors R 6 and R 7 to be adjusted without requiring access to the power supply circuitry.
- Adjusting the resistance of resistor R 7 affects the feedback voltage at node 113 , which in turn adjusts the magnitude of the potential difference appearing across intermediate terminals 121 and 122 , thereby allowing the output voltage to be supplied to the power switch gate driver to be adjusted.
- Resistor R 7 defines a portion of the feedback resistive voltage divider along with feedback circuit resistors R 2 and R 3 . Increasing the resistance of resistor R 7 increases the voltage level at node 113 . As described above, if the voltage at node 113 increases such that the difference between Vfb and a reference voltage Vref is reduced, the duty cycle of PWM switch controller U 3 is adjusted to reduce the voltage applied across intermediate terminals 121 and 122 .
- the voltage supplied to intermediate terminals 121 and 122 may be simply adjusted by varying the input voltage.
- adjusting the resistance of external resistors R 6 and R 7 enables the converter to provide an adjustable output voltage potential difference to a load and also enables the converter to provide a wide range of positive and negative voltages at output terminals 131 and 133 .
- the preferred embodiments of the present invention are therefore able to advantageously provide the voltage requirements for many switch variants using only a single power supply. Products embodying the preferred embodiments of the present invention therefore reduce the qualification time, reducing qualifications costs and being able to accommodate future developments.
- FIG. 4 shows a DC to DC flyback converter 300 in accordance with an alternative preferred embodiment of the present invention where the Zener diode D 3 of FIG. 1 is replaced by a reference integrated circuit U 4 .
- the above advantages associated with the preferred embodiment shown in FIG. 3 are also present for the alternative preferred embodiment shown in FIG. 4 .
- capacitor C 3 , capacitor C 4 , resistor R 4 and reference integrated circuit U 4 are connected to define a capacitive voltage divider and a resistive voltage divider.
- node 127 is held at a reference voltage of 0 V and connected to the source terminal of power switch device Q 1 via node 129 .
- Compensation capacitor C 5 is connected to the integrated circuit cathode pin via node 311 and the Vref pin via node 312 . The compensation capacitor is included to stabilize the integrated circuit U 4 .
- the potential difference generated across intermediate terminals 121 and 122 is divided into a first output voltage difference applied across output terminals 131 and 132 and a second output voltage difference applied across output terminals 132 and 133 in accordance with the resistances of resistors R 4 , R 6 and R 8 .
- Resistor R 8 is an internal resistor connected to the integrated circuit cathode pin via nodes 313 and 127 and the integrated circuit Vref pin via nodes 314 and 312 .
- Resistor R 6 is an external resistor connected to the integrated circuit anode pin via node 223 , output terminal 133 and node 128 and connected to the Vref pin via nodes 224 , 314 and 312 .
- Resistors R 4 , R 8 and R 6 define an adjustment circuit whereby the voltage at node 314 is held at a reference voltage provided by the integrated circuit at the Vref pin.
- the integrated circuit may be a shunt regulator.
- shunt regulator TL431 may be used to hold output terminal 133 at ⁇ 5 V. Since shunt regulator TL431 maintains a voltage drop of approximately 2.5 V between nodes 313 and 314 , the value of external resistor R 6 may be selected to determine the fixed voltages at output terminals 131 and 133 . For example, if the resistance of R 6 matches that of R 8 , the voltage drop across R 6 will equal that of the voltage drop across R 8 .
- node 314 As node 314 is held at approximately ⁇ 2.5 V by U 4 the voltage at node 223 , and hence at node 133 , will be held at ⁇ 5 V. The remaining voltage will be distributed across R 4 . For example, if a potential difference of 25 V is applied between intermediate terminals 121 and 122 , holding output terminal 133 at ⁇ 5 V will ensure output terminal 131 is held at +20 V.
- Resistor R 6 may be adjusted externally to the power supply with the advantages described above in relation to FIG. 3 , namely providing adjustable output voltages to power switch device Q 1 .
- adjusting external resistor R 7 adjusts the duty cycle of the PWM switch controller U 3 such that the potential difference between intermediate terminals 121 and 122 may be adjusted.
- the power supply output may range from 20 V to 30 V.
- FIG. 5 illustrates an example of a power supply unit 10 which may include the power supply circuitry described above.
- the power supply unit 10 includes a header 20 , a planar transformer 30 and a main Printed Circuit Board (PCB) 40 .
- the header 20 includes a plurality of side walls 21 and electrical connectors 22 , passing from the top of the header 20 to the bottom side and providing both mechanical and electrical connections by which the planar transformer 30 and the main PCB 40 are connected to the header 20 and to each other.
- the main PCB 40 may be mounted onto a third party PCB or motherboard (not shown).
- Planar transformer 30 includes a substrate 31 and a surrounding magnetic core 32 .
- the magnetic core may be made of a ferrite material for example, and may be secured in place in the header 20 by clips 33 .
- the substrate 31 is typically a single piece of resin-like material that passes through the magnetic core 32 from an input side to an output side.
- Substrate 31 contains transformer windings P 1 , P 2 and S 1 located in its interior surrounded by the magnetic core 32 .
- the transformer windings arrangement includes a winding axis that is perpendicular or substantially perpendicular within manufacturing tolerances to the top and bottom surface of the substrate to thereby define the windings of the planar transformer.
- the coil arrangement includes primary coil windings P 1 , P 2 connected to the input or primary side connectors 22 of the header 20 by traces (not shown), and secondary coil windings S 1 connected to the output or secondary side connectors 22 of the header 20 by traces (not shown).
- the connectors 22 may pass through the substrate 31 at plated via holes 34 .
- the plated via holes 34 and the connectors 22 thread through the substrate 31 from one side of the substrate 31 to the other.
- Main PCB 40 includes switching circuitry 101 that controls the transformer and converter circuitry 102 that converts a generated potential difference into three fixed voltages.
- the components described above in relation to the switching circuitry 101 and converter circuitry 102 may be mounted above and/or below the main PCB 40 .
- Main PCB 40 also includes surface mount feet (not shown) that connects to PCB lands on the third party PCB.
- the external connectors 223 , 224 , 225 and 226 are main PCB 40 surface mount feet which are connected to first and second external resistors located on the third party PCB.
- the external connectors 223 , 224 , 225 and 226 and external resistors R 6 , R 7 are therefore external to the header 20 , switching circuitry 101 and converter circuitry 102 .
- Providing connectors 223 , 224 , 225 and 226 external to the header 20 , switching circuitry 101 , and converter circuitry 102 enables external resistors R 6 and R 7 to be adjusted without requiring access to the switching or converter circuitry mounted on the main PCB 40 within the header 20 .
- a consumer may therefore adjust the voltages provided to a power switch gate driver in a simple manner without requiring access to the circuitry located within the power supply unit.
- the preferred embodiments described above are not limited to power supplies for IGBT, SIC, MOS, and GaN power switches and may readily be used in other power switching technologies. Additionally, the above described technique of adjusting the division of voltage across two outputs can be applied to any power supply topology including, but not limited to, flyback, forward converter, Half bridge, Full bridge, Push Pull, Buck, Boost, Sepic, Cuk or Zeta circuit configurations.
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Abstract
Description
- This application claims priority to United Kingdom Patent Application No. 1712666.5 filed on Aug. 7, 2017 and is a Continuation Application of PCT Application No. PCT/GB2018/052252 filed on Aug. 7, 2018. The entire contents of each application are hereby incorporated by reference.
- This application relates to an adjustable power supply circuit for power switch gate drivers, and in particular to an adjustable power supply circuit capable of being used with multiple variants of power switch gate driver circuits.
- Power electronics devices, such as DC to DC converters and switched mode power supplies, make use of high power transistors to provide a stable output voltage of a predetermined value from a given input power supply. The transistors are switched on and off to regulate the output voltage. Power electronics devices have important applications in switching high currents in uninterruptible power supplies, motor drives, solar inverters, and electric vehicles, and must therefore meet stringent constraints and requirements imposed upon the output voltage they produce. For example, it may not be acceptable for the output voltage to deviate from a nominal value by more than a predetermined tolerance.
- Power electronics devices can provide gate drive potential differences to power switch devices. Typically, power switch devices, such as high power transistors, each require a 25 Volt (V) gate drive potential difference. In the commonly recognized industry standard, Isolated Gate Bipolar Transistors require a connection to rails held at +15 V and −10 V; Silicon Carbide transistors require a connection to rails held at +20 V and −5 V; and Metal Oxide Field Effect Transistors require a connection to rails held at +15 V and −5 V.
- However, other power switch devices, especially emerging technologies, such as Silicon Carbide (SiC) and Gallium Nitride (GaN), have various different power requirements. This is exaggerated further by the fact that the voltages required at the switch are not necessarily the voltages that are required from the gate drive power supply. This is due to system differences like voltage drops in the driver IC and the need to overcome inductance in the source or emitter connection of the switch. This results in the power supply needing to deliver a slightly higher positive and negative voltage to overcome these voltage drops.
- There is therefore a need for a single adjustable power supply that can be used with power electronics applications that require a variety of input voltages.
- A preferred embodiment of the present invention provides an adjustable power supply device for supplying power to a power switch control device configured to provide control signals to a power switch device, the adjustable power supply device including: a pair of input terminals; switching circuitry connected to the pair of input terminals; converter circuitry, the converter circuitry including a pair of intermediate terminals and first, second, and third output terminals that output power to the power switch control device; a transformer including a primary side winding coupled to the pair of input terminals and a secondary side winding coupled to the pair of intermediate terminals, wherein a potential difference generated between the pair of intermediate terminals is divided by a dividing circuit into a first output voltage difference applied across the first and the second output terminals and a second output voltage difference applied across the second and the third output terminals; the converter circuitry including a first adjustment circuit that adjusts the first output voltage difference and second output voltage difference, the first adjustment circuit including at least one external terminal that is coupled to a first resistance element; and the switching circuitry including a second adjustment circuit that adjusts the potential difference generated between the pair of intermediate terminals, the second adjustment circuit including at least one external terminal that is coupled to a second resistance element. The second output terminal is held at a reference voltage. The first output terminal provides the first output voltage difference to a first input of the power switch control device, and the third output terminal provides the second output voltage difference to a second input of the power switch control device.
- Optionally, the switching circuitry may further include a switch controller coupled to a switch and coupled to the primary side winding to control a current flowing through the primary side winding.
- Optionally, one of the at least one external terminals of the second adjustment circuit may be coupled to the switch controller.
- Optionally, one of the at least one external terminals of the second adjustment circuit may be coupled to a voltage feedback pin of the switch controller.
- Optionally, the voltage feedback pin of the switch controller may be coupled to a primary side feedback winding.
- Optionally, the second adjustment circuit may include a switching circuit voltage divider including at least a first resistor connected between the voltage feedback pin and the primary side feedback winding, and a second resistor connected between the voltage feedback pin and ground wherein the voltage feedback pin of the switch controller is connected to the switching circuit voltage divider.
- Optionally, the second adjustment circuit may include a pair of external terminals that is coupled to a pair of corresponding external connections configured to receive the first resistance element therebetween, one of the pair of external terminals is coupled to ground, and the first resistance element, when connected between the pair of corresponding external connections, is coupled via the pair of external terminals of the second adjustment circuit in parallel with a resistor in the switching circuit voltage divider.
- Optionally, the second adjustment circuit may adjust the potential difference generated between the pair of intermediate terminals by adjusting the duty cycle of the switch controller.
- Optionally, the dividing circuit may include a further resistive element.
- Optionally, one of the at least one external terminals of the first adjustment circuit may be coupled to the low voltage side of the secondary side winding via one of the pair of intermediate terminals.
- Optionally, the first adjustment circuit may include a converter circuitry voltage divider including at least a first resistor and a second resistor connected in parallel between the pair of intermediate terminals.
- Optionally, the at least one external terminal of the first adjustment circuit includes a pair of external terminals, and the pair of external terminals of the first adjustment circuit is coupled to a the first adjustment circuit may include a pair of external terminals that is coupled to a pair of external connections configured to receive the second resistance element mounted therebetween.
- Optionally, the dividing circuit includes a further resistance element, and one of the pair of external terminals may be coupled to a divider circuit and to the high voltage side of the secondary side winding via the other of the pair of intermediate terminals and the converter circuitry voltage divider, such that the first resistance element is coupled to the further resistance element of the dividing circuit.
- Optionally, the further resistance element may be a transistor.
- Optionally, the other of the pair of external terminals of the first adjustment circuit may be coupled to the base/gate terminal of the transistor.
- Optionally, the transistor may be connected in parallel between the pair of intermediate terminals such that the source/emitter terminal of the transistor is coupled to the high voltage side of the secondary side winding.
- Optionally, the further resistance element may include an adjustable voltage drop.
- Optionally, a node of the first adjustment circuit may be connected to the further resistance element such that a change in voltage at the node adjusts the voltage dropped across the further resistance element.
- Optionally, the first adjustment circuit may adjust the first output voltage difference and the second output voltage difference by adjusting the voltage dropped across the further resistance element.
- A preferred embodiment of the present inventions provides a device including: a header on which the switching circuitry, converter circuitry, and transformer are mounted; wherein the pair of input terminals and the at least one external terminals of the first and the second adjustment circuits are connections on the external surface of the header that connect with a third party circuit board.
- Optionally, the reference voltage may be the source voltage of the power switch device.
- Optionally, the reference voltage may be zero volts.
- The above and other features, elements, characteristics, steps, and advantages of the present invention will become more apparent from the following detailed description of preferred embodiments of the present invention with reference to the attached drawings.
-
FIG. 1 shows a known DC to DC converter which provides fixed voltages to a gate driver. -
FIG. 2 shows a simplified diagram of a Pulse Width Modulation controller that supplies gate control signals to a transistor. -
FIG. 3 shows a preferred embodiment of an adjustable power supply that provides adjustable voltages to a gate driver. -
FIG. 4 shows an alternative preferred embodiment of an adjustable power supply that provides adjustable voltages to a gate driver. -
FIG. 5 shows a power supply unit including a header, planar transformer, and printed circuit board mounted in position. - For the purposes of illustration, a flyback converter is shown in the accompanying figures, however other DC to DC converter configurations, such as a forward converter, for example, would also be acceptable.
-
FIG. 1 shows a DC toDC converter 100 in a flyback converter configuration. The converter accepts an input voltage Vin relative to a ground voltage and is configured to provide three fixed voltages, for example +20 V, 0 V and −5 V, atoutput terminals - The DC to
DC converter 100 shown inFIG. 1 includes a transformer TX1, primary-side circuitry connected to a pair of input terminals including an input voltage (Vin) terminal and a ground input terminal, and secondary-side circuitry connected to threeoutput terminals FIG. 1 includesswitching circuitry 101 to periodically control whether a Metal Oxide Field Effect Transistor (MOSFET) Q5 is in a conducting or a non-conducting state. The secondary-side circuitry includesconverter circuitry 102 and ensures the potential difference supplied acrossintermediate terminals output terminals - Transformer TX1 includes transformer primary windings, P1 and P2, and a transformer secondary winding, S1, which are wound around a transformer core. In one preferred embodiment, the transformer core is made of ferrite, however in alternative arrangements it is possible to use other materials for the core, or the core may be absent in which case the windings are air-cored.
- Input voltage terminal Vin is connected to the high voltage side of primary winding P1 and the drain of a Metal Oxide Field Effect Transistor (MOSFET) Q5 located in
switching circuitry 101 is connected to the low voltage side of primary winding P1. The feedback primary winding P2 is connected tofeedback circuitry 103 located on the primary side of transformer TX1 and secondary winding S1 is connected to theconverter circuitry 102. A capacitor C6 is connected between input terminals Vin and ground and acts as a short bypass path that provides high peak currents to transistor Q5. - Transistor Q5 includes a drain, source and gate. As indicated above, the drain of transistor Q5 is connected to the low voltage side of primary transformer winding P1. The source of transistor Q5 is connected to ground via a transistor source resistor R1. The gate of transistor Q5 is connected to a Pulse Width Modulation (PWM) switch controller U3 such that transistor Q5 receives gate control signals from PWM switch controller U3.
- Feedback primary winding P2 is connected to
feedback circuitry 103 located within the switchingcircuitry 101 and includes a diode D1, a capacitor C1 and a voltage divider circuit R2, R3. Primary winding P2 is connected to thefeedback circuitry 103 atnodes further node 113 is located at the midpoint of voltage divider circuit R2, R3 and is connected to PWM switch controller U3 such that the voltage atnode 113 is provided to an input pin of PWM switch controller U3. - Capacitor C1 is connected between
nodes Node 112 is connected to ground and diode D1 is connected betweennode 111 and the low voltage side of feedback primary winding P2 such that, when transistor Q5 is turned on, diode D1 is reverse-biased. Voltage divider resistors R2 and R3 are connected in series betweennode 111 and ground atnode 114.Node 113 of the feedback voltage divider is connected to PWM switch controller U3 at the Vfb (voltage feedback) pin. - The PWM switch controller U3 depicted in
FIG. 1 includes 8 pins: a positive voltage pin, Vp; a ground voltage pin, Gnd; a feedback voltage pin Vfb; a reference voltage pin, Ref; a comparison voltage pin, Comp; a current sense voltage pin, Sense; an oscillator input pin, Osc; and an output voltage pin, Vout. The PWM switch controller U3 shown inFIG. 1 may be provided as a portion of an integrated circuit (IC) incorporated within the circuitry shown inFIG. 1 . - Although not illustrated in
FIG. 1 , a supply voltage may be provided to the PWM switch controller U3 via input pins Vp and Gnd. The Gnd input pin is connected to ground vianode 115. A voltage atnode 113 infeedback circuitry 103 is provided to the Vfb pin. Gate control signals produced by U3 are provided to transistor Q5 via the Vout pin. Although the Ref, Osc, Comp and Sense pins are depicted as being disconnected inFIG. 1 , it will be appreciated that in some preferred embodiments other components and signals may be provided to these pins. - Turning to the secondary side of transformer TX1, the secondary-
side circuitry 102 includes: a diode D2 and a capacitor C2;intermediate terminals output terminals - Diode D2 is connected between
intermediate terminal 121 and the low voltage side of transformer secondary winding S2 such that when transistor Q5 is in a conductive mode, diode D2 is reverse-biased. Capacitor C2 is provided betweenintermediate terminals intermediate terminals intermediate terminals - The capacitive voltage divider includes capacitors C3 and C4 connected in series across
intermediate terminals FIG. 1 , capacitor C3 is connected toterminal 121 vianode 123 and is connected to capacitor C4 vianode 124. Similarly, capacitor C4 is connected toterminal 122 vianode 125 and to capacitor C3 vianode 124. - The secondary-side voltage divider depicted in
FIG. 1 includes resistor R4 and Zener diode D3 connected in series acrossintermediate terminals nodes FIG. 1 , resistor R4 is connected toterminal 121 vianodes node 127. Similarly, Zener diode D3 is connected toterminal 122 vianodes node 127. - The resistor and Zener diode voltage divider and the capacitive voltage divider are connected between
nodes -
Output terminal 131 is connected to the resistor and Zener diode voltage divider circuit vianode 126 and is connected to the capacitive voltage divider circuit vianodes Output terminal 132 is connected to the resistor and Zener diode voltage divider circuit vianode 127 and is connected to the capacitive voltage divider circuit vianodes Output terminal 132 is also connected to the source of power switch device Q1 vianode 129 and is held at a reference voltage, Vsource. In some preferred embodiments,output terminal 132 is held at 0 V so thatoutput terminal 132 acts as a gate drive 0 V reference.Output terminal 133 is connected to the resistor and Zener diode voltage divider circuit vianode 128 and is connected to the capacitive voltage divider circuit vianodes - The voltages produced at
output terminals - In
FIG. 1 , gate driver IC U1 includes: a fixed supply voltage input pin (VCC); a ground input pin (COM) pin; a control input pin (IN) pin that receives a clock signal from clock signal generator U2; an absolute supply voltage input pin (VB) connected tooutput terminal 131 that receives a first, high, fixed voltage; an offset supply voltage input pin (VS) connected tooutput terminal 133 that receives a second, low, fixed voltage; and an output voltage pin (HO) that sends gate drive signals to Q1. The IN, VS and VB pins may be connected to logic circuitry to provide gate drive control signals at output pin HO. - A gate driver IC U1 is powered by the potential difference provided by
terminals terminals - The gate driver IC U1 is provided with a first and second fixed voltage signal from the power supply. The first fixed voltage signal may be provided to the VB pin from
terminal 131, which in a specific preferred embodiment may be held at a voltage level of +20 V, for example, and the second fixed voltage signal may be provided to the VS pin fromterminal 133, which in a specific preferred embodiment may be held at a voltage level of −5 V, for example. - The gate driver IC U1 shown in
FIG. 1 may be provided as a portion of an integrated circuit (IC) incorporated within the circuitry shown inFIG. 1 . Additionally, it will be appreciated by those skilled in the art that power switch device Q1 may be included in other configurations than shown inFIG. 1 . For example, power switch device Q1 may be connected directly to ground, connected in series with a load, or connected in series with another transistor in a half-bridge configuration. - As will be appreciated by persons of ordinary skill in the art, when transistor Q5 is in a conducting state, the input voltage Vin applied across the primary windings of transformer TX1 causes current to flow in the windings and energy is thereby stored in the resulting magnetic field produced by the transformer TX1. Switching Q5 to a non-conductive state induces a voltage across the feedback and secondary transformer windings. Energy stored within the magnetic field is converted to electrical energy which may be used to supply, for example, transistors in switched-mode power supplies or power switch devices.
- When transistor Q5 is turned on, an applied voltage Vin drives a current through the transformer primary winding P1, energizing the winding. When the primary winding P1 is energized, the increasing magnetic flux passing through the core of transformer TX1 induces a voltage across feedback primary winding P2 and secondary winding S1. For an ideal transformer, the voltage induced in the secondary and feedback windings is proportional to the number of turns on the secondary and feedback windings and the changing magnetic flux through the windings. The polarity of the transformer windings is such that when primary winding P1 is energized, diodes D1 and D2 are reverse biased resulting in no current flowing through feedback winding P2 and secondary winding S1. Energy is therefore stored in the magnetic field within the transformer until transistor Q5 is switched off.
- When the switching
circuitry 101 disconnects the primary windings from the input voltage by turning transistor Q5 off, primary winding P1 is no longer energized and the magnetic field within the transformer collapses leading to a rapid decrease in magnetic flux. This rapid decrease in magnetic flux induces a voltage of opposing polarity in the secondary and feedback windings. Hence, when transistor Q5 is turned off diodes D1 and D2 become forward biased resulting in current flowing through windings P2 and S1. Energy stored within the magnetic field is converted to electrical energy and is delivered tointermediate terminals -
Feedback circuitry 103 enables the PWM switch controller U3 to decide whether to increase or decrease the duty cycle of the gate drive pulses. This maintains a constant output voltage acrossintermediate terminals - As previously described, diode D1 in the feedback winding becomes forward biased when transistor Q5 is switched off due to a decreasing magnetic flux. Energy stored in the transformer is converted to electrical energy and transferred through the feedback circuit. Smoothing capacitor C1 ensures that the current and voltage are delivered through the feedback circuit at a constant level instead of as a pulse. Thus, diodes D1 and C1 operate as a half-wave rectifier circuit with a smoothing capacitor that provides a DC voltage to
node 111. Resistors R2 and R3 act as a voltage divider to provide an appropriate voltage level to switch transistor Vfb pin vianode 113. - Since the feedback and secondary coils include a fixed difference between turn ratios, the voltage induced across capacitor C1 is directly proportional to the voltage induced across capacitor C2 and also the
intermediate terminals - Adjusting the voltage level at
node 113 will change the duty cycle of PWM switch controller IC U3, as described below with reference toFIG. 2 . The components which also appear inFIG. 1 have been allocated the same numerals. -
FIG. 2 depicts a PWM switch controller U3 that provides gate control signals to the gate of transistor Q5. In the example shown inFIG. 2 , PWM switch controller IC U3 includes anerror amplifier 141, acomparator 142, a Set-Reset (SR)latch 143 and a pulse oscillator 144. -
Node 113 offeedback circuitry 103 is connected to the negative input oferror amplifier 141 via the Vfb pin (not shown) such that the voltage atnode 113 is provided toerror amplifier 141 as a feedback voltage. The positive input oferror amplifier 141 is connected to a reference voltage Vref and the difference between Vfb and Vref is output as an error signal Verror. - The output of
error amplifier 141 is connected to the negative input ofcomparator 142 and the positive input ofcomparator 142 is connected tonode 116 which is located between the source of Q5 and resistor R1 such thatnode 116 supplies a voltage Vsense tocomparator 142. - The output of the
comparator 142 is provided to the reset input R ofSR latch 143. The set input S ofSR latch 143 is connected to pulse oscillator 144 which provides a signal of a set frequency. The Q output ofSR latch 143 is connected to the gate of transistor Q5 via output pin Vout (not shown). - The value of Vsense depends upon the current flowing through transistor Q5. Due to inductive effects in the primary transformer winding P1, when transistor Q5 is switched on the current flowing in the primary winding, and hence the current flowing through transistor Q5, increases linearly. Therefore a linearly increasing voltage, Vsense, is established across R1. When Vsense equals Verror, the output of
comparator 142 is high (1). This resets the RS latch and terminates the gate drive pulse. The Q output of RS latch produces the next gate drive signal when the internal oscillator provides a high signal (1) to the set input S of the RS latch. - When the switch duty cycles and circuit capacitances are correctly adjusted, a predetermined and substantially constant voltage is provided between the
intermediate terminals FIG. 1 , as the switchingcircuitry 101 energizes and de-energizes the windings of transformer TX1, theintermediate terminals converter circuitry 102 are alternatively held at a potential by the charge stored in capacitor C2 or by the opposing voltage set up in the secondary winding. Capacitor C2 acts to reduce the variations in the voltage applied across theintermediate terminals - Positioning a reverse-biased Zener diode D3 between
nodes - In the capacitive voltage divider, capacitors C3 and C4 are high-frequency capacitors that additionally provide high peak currents to minimize switching losses when power switch device Q1 switches on or off. As the gate of power switch device Q1 includes an associated capacitance, the average current flowing into the gate can be very low. Additional capacitors C3 and C4 therefore provide the additional functionality of providing high peak currents during switching.
- Connecting
node 127 of the resistive voltage divider tonode 124 of the capacitive voltage divider ensures thatnodes nodes nodes - In the preferred embodiment shown in
FIG. 1 ,nodes nodes nodes - In a specific example, the secondary winding produces a potential difference of 25 V and Zener diode BZX79-5V1 is used, which includes a reverse breakdown voltage of 5.1 V. As
terminal 132 is held at 0 V, terminal 133 will be held at approximately −5 V and terminal 131 will be held at approximately +20 V. The voltages produced in this specific example would be suitable in powering a Silicon Carbide transistor. - However, known DC to DC flyback converters as described above cannot be easily adjusted to provide voltage levels suitable for a variety of power switch devices with different power requirements.
-
FIG. 3 shows a DC toDC flyback converter 200 in accordance with a preferred embodiment of the present invention. InFIG. 3 , a PNP transistor Q2 replaces the Zener diode D3 ofFIG. 1 . A resistive voltage divider R5, R6 is included to adjust the fixed voltages produced atoutput terminals - The first adjustable circuit shown in
FIG. 3 includes resistor R5 and external resistor R6 connected in series acrossintermediate terminals FIG. 3 , resistor R5 is connected tointermediate terminal 121 vianodes nodes nodes node 222. - The base terminal of PNP transistor Q2 is connected to
terminal 121 vianode 222, resistor R5 andnode 221, and connected toterminal 122 vianodes node 223. The emitter terminal of PNP transistor Q2 is also connected toterminal 121 vianode 127, resistor R4 andnode 126. The emitter terminal is also connected to the source of power switch device Q1 vianode 132. The collector terminal of PNP transistor Q2 is connected toterminal 122 vianode 128. - In the circuit configuration shown in
FIG. 3 ,node 127 is held at a reference voltage, for example 0 V, andnodes node 128 is held at −5 V, for example, by establishing an emitter voltage of approximately 5 V. - The emitter voltage is the sum of the forward biased emitter-base voltage of the transistor, which is approximately 0.6 V, and the voltage at
node 222. Therefore, an emitter voltage of 5 V may be set by producing a voltage of approximately 4.4Vat node 222 with respect tonode 128. - As
node 127 is fixed at a reference voltage of 0 V,node 128 may be held at −5 V by setting voltage divider resistors R5 and R6 to produce a voltage of approximately 4.4 V atnode 222 with respect tonode 128. Once the voltage atnode 222 is set, the emitter voltage, and hence the voltage atnode 128, will remain at an approximately constant level even when the voltage across C4 rises. - In other words, resistor R4 and transistor Q2 act as a dividing circuit that divides a potential difference generated across
intermediate terminals output terminals output terminals node 222, which is adjusted by a first adjustment circuit that includes external resistor R6. - The voltage at
node 222 is equal to: -
- where VC2 is the potential difference across capacitor C2 or, in other words, the potential difference generated across
intermediate terminals - Therefore, in a specific preferred embodiment, a suitable resistor combination for a 25 V supply which produces 20 V and −5 V at
output terminals - Adjusting the resistance of resistor R6 affects the ratio with which the voltage applied between
intermediate terminals node 222. Increasing the resistance of resistor R6 results in an increased voltage atnode 222. A larger voltage atnode 222 will result in a larger emitter-collector potential difference and hence a larger emitter-collector voltage drop, which adjusts the voltage difference betweenoutput terminals output terminal 133. For example, increasing the resistance value of resistor R6 may result in the voltage produced atoutput terminal 133 increasing from −5 V to −10 V. - Since the potential difference generated between
intermediate terminals output terminals output terminals output terminals terminal 133 increases, the voltage produced atterminal 131 decreases. In the above example, a voltage increase from −5 V to −10 V atterminal 133 will produce a voltage decrease from +20 V to +15 V atterminal 131. - The supply voltage provided to a power switch device may be adjusted by modify the duty cycle of transistor Q5 using a second adjustment circuit including external resistor R7, as further described below.
- As described above with regard to
FIGS. 1 and 2 , the voltage generated betweenintermediate terminals node 113. If, for example, Vfb is reduced so that there is a greater difference between a reference voltage Vref and Vfb, a difference signal Verror will also increase. This results in Vsense being able to linearly increase to a higher level before theRS latch 143 terminates the gate drive signal. Therefore, the duty cycle of PWM switch controller U3 is lengthened, enabling more energy to be stored and transferred tointermediate terminals output terminals node 113 modifies the duty cycle of U3 which adjusts the output voltage difference betweenoutput terminals output terminals - External resistors R6 and R7 are provided externally to the switching
circuitry 101 andconverter circuitry 102. External resistor R6 and R7 may be connected to the power supply via external connections or nodes external to the switching or converter circuitry, which enables the resistance of resistors R6 and R7 to be easily adjusted without having to access the power supply circuitry. As shown inFIG. 3 , resistor R6 may be connected to the converter circuitry vianodes nodes Nodes - Adjusting the resistance of resistor R7 affects the feedback voltage at
node 113, which in turn adjusts the magnitude of the potential difference appearing acrossintermediate terminals node 113. As described above, if the voltage atnode 113 increases such that the difference between Vfb and a reference voltage Vref is reduced, the duty cycle of PWM switch controller U3 is adjusted to reduce the voltage applied acrossintermediate terminals - It should be noted that for some fixed output non-regulated power supply topologies, such as the Royer circuit, the voltage supplied to
intermediate terminals - Hence, adjusting the resistance of external resistors R6 and R7 enables the converter to provide an adjustable output voltage potential difference to a load and also enables the converter to provide a wide range of positive and negative voltages at
output terminals -
FIG. 4 shows a DC toDC flyback converter 300 in accordance with an alternative preferred embodiment of the present invention where the Zener diode D3 ofFIG. 1 is replaced by a reference integrated circuit U4. The above advantages associated with the preferred embodiment shown inFIG. 3 are also present for the alternative preferred embodiment shown inFIG. 4 . - In the preferred embodiment of
FIG. 4 , capacitor C3, capacitor C4, resistor R4 and reference integrated circuit U4 are connected to define a capacitive voltage divider and a resistive voltage divider. As before inFIG. 4 ,node 127 is held at a reference voltage of 0 V and connected to the source terminal of power switch device Q1 vianode 129. Compensation capacitor C5 is connected to the integrated circuit cathode pin vianode 311 and the Vref pin vianode 312. The compensation capacitor is included to stabilize the integrated circuit U4. - The potential difference generated across
intermediate terminals output terminals output terminals nodes nodes node 223,output terminal 133 andnode 128 and connected to the Vref pin vianodes - Resistors R4, R8 and R6 define an adjustment circuit whereby the voltage at
node 314 is held at a reference voltage provided by the integrated circuit at the Vref pin. In a specific preferred embodiment, the integrated circuit may be a shunt regulator. For example, shunt regulator TL431 may be used to holdoutput terminal 133 at −5 V. Since shunt regulator TL431 maintains a voltage drop of approximately 2.5 V betweennodes output terminals node 314 is held at approximately −2.5 V by U4 the voltage atnode 223, and hence atnode 133, will be held at −5 V. The remaining voltage will be distributed across R4. For example, if a potential difference of 25 V is applied betweenintermediate terminals output terminal 133 at −5 V will ensureoutput terminal 131 is held at +20 V. - As before, adjusting the value of external resistor R6 will affect how the potential difference between
intermediate terminals output terminals FIG. 3 , namely providing adjustable output voltages to power switch device Q1. - As also described above in relation to
FIG. 3 , adjusting external resistor R7 adjusts the duty cycle of the PWM switch controller U3 such that the potential difference betweenintermediate terminals -
FIG. 5 illustrates an example of apower supply unit 10 which may include the power supply circuitry described above. Thepower supply unit 10 includes aheader 20, aplanar transformer 30 and a main Printed Circuit Board (PCB) 40. As can be seen inFIG. 5 , theheader 20 includes a plurality ofside walls 21 andelectrical connectors 22, passing from the top of theheader 20 to the bottom side and providing both mechanical and electrical connections by which theplanar transformer 30 and themain PCB 40 are connected to theheader 20 and to each other. Themain PCB 40 may be mounted onto a third party PCB or motherboard (not shown). -
Planar transformer 30 includes asubstrate 31 and a surroundingmagnetic core 32. The magnetic core may be made of a ferrite material for example, and may be secured in place in theheader 20 byclips 33. Thesubstrate 31 is typically a single piece of resin-like material that passes through themagnetic core 32 from an input side to an output side. -
Substrate 31 contains transformer windings P1, P2 and S1 located in its interior surrounded by themagnetic core 32. In the example shown, the transformer windings arrangement includes a winding axis that is perpendicular or substantially perpendicular within manufacturing tolerances to the top and bottom surface of the substrate to thereby define the windings of the planar transformer. The coil arrangement includes primary coil windings P1, P2 connected to the input orprimary side connectors 22 of theheader 20 by traces (not shown), and secondary coil windings S1 connected to the output orsecondary side connectors 22 of theheader 20 by traces (not shown). Theconnectors 22 may pass through thesubstrate 31 at plated via holes 34. The plated viaholes 34 and theconnectors 22 thread through thesubstrate 31 from one side of thesubstrate 31 to the other. -
Main PCB 40 includes switchingcircuitry 101 that controls the transformer andconverter circuitry 102 that converts a generated potential difference into three fixed voltages. The components described above in relation to the switchingcircuitry 101 andconverter circuitry 102 may be mounted above and/or below themain PCB 40. -
Main PCB 40 also includes surface mount feet (not shown) that connects to PCB lands on the third party PCB. In a preferred embodiment, theexternal connectors main PCB 40 surface mount feet which are connected to first and second external resistors located on the third party PCB. - The
external connectors header 20, switchingcircuitry 101 andconverter circuitry 102. Providingconnectors header 20, switchingcircuitry 101, andconverter circuitry 102 enables external resistors R6 and R7 to be adjusted without requiring access to the switching or converter circuitry mounted on themain PCB 40 within theheader 20. A consumer may therefore adjust the voltages provided to a power switch gate driver in a simple manner without requiring access to the circuitry located within the power supply unit. - The preferred embodiments described above are not limited to power supplies for IGBT, SIC, MOS, and GaN power switches and may readily be used in other power switching technologies. Additionally, the above described technique of adjusting the division of voltage across two outputs can be applied to any power supply topology including, but not limited to, flyback, forward converter, Half bridge, Full bridge, Push Pull, Buck, Boost, Sepic, Cuk or Zeta circuit configurations.
- Various modifications to the preferred embodiments described above are possible and will occur to those skilled in the art without departing from the scope of the present invention which is defined by the following claims.
- It should be understood that the foregoing description is only illustrative of the present invention. Various alternatives and modifications can be devised by those skilled in the art without departing from the present invention. Accordingly, the present invention is intended to embrace all such alternatives, modifications, and variances that fall within the scope of the appended claims.
Claims (19)
Applications Claiming Priority (4)
Application Number | Priority Date | Filing Date | Title |
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GB1712666 | 2017-08-07 | ||
GB1712666.5A GB2565297B (en) | 2017-08-07 | 2017-08-07 | An adjustable power supply device for supplying power to a power switch control device |
GB1712666.5 | 2017-08-07 | ||
PCT/GB2018/052252 WO2019030516A1 (en) | 2017-08-07 | 2018-08-07 | An adjustable power supply device for supplying power to a power switch control device |
Related Parent Applications (1)
Application Number | Title | Priority Date | Filing Date |
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PCT/GB2018/052252 Continuation WO2019030516A1 (en) | 2017-08-07 | 2018-08-07 | An adjustable power supply device for supplying power to a power switch control device |
Publications (2)
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US20200177087A1 true US20200177087A1 (en) | 2020-06-04 |
US11502593B2 US11502593B2 (en) | 2022-11-15 |
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US16/783,705 Active US11502593B2 (en) | 2017-08-07 | 2020-02-06 | Adjustable power supply device for supplying power to a power switch control device |
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US (1) | US11502593B2 (en) |
CN (1) | CN110999053B (en) |
DE (1) | DE112018003431T5 (en) |
GB (1) | GB2565297B (en) |
WO (1) | WO2019030516A1 (en) |
Cited By (4)
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US20220037074A1 (en) * | 2018-12-21 | 2022-02-03 | Sumitomo Electric Industries, Ltd. | Power conversion device, multilayer board included in the same, and vehicle having power conversion device mounted therein |
US20220103058A1 (en) * | 2020-09-30 | 2022-03-31 | Solaredge Technologies Ltd. | Method and Apparatus for Power Conversion |
US20220149613A1 (en) * | 2019-02-05 | 2022-05-12 | Siemens Energy Global GmbH & Co. KG | Switching device for opening a current path |
US20230049832A1 (en) * | 2020-01-16 | 2023-02-16 | Signify Holding B.V. | A direct current, dc, voltage source arranged for providing a dc voltage based on an input voltage as well as a corresponding method |
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GB2586049B (en) * | 2019-07-31 | 2022-03-09 | Murata Manufacturing Co | Power supply output device |
GB2586050B (en) * | 2019-07-31 | 2021-11-10 | Murata Manufacturing Co | Power supply output device |
CN114079368A (en) * | 2020-08-20 | 2022-02-22 | Tdk株式会社 | Drive circuit and switching power supply device |
GB2602127B (en) * | 2020-12-18 | 2024-04-24 | Murata Manufacturing Co | Adjustable three output DC voltage supply with short circuit protection |
GB2602132A (en) * | 2020-12-18 | 2022-06-22 | Murata Manufacturing Co | Three output DC voltage supply with short circuit protection |
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Also Published As
Publication number | Publication date |
---|---|
GB2565297A (en) | 2019-02-13 |
US11502593B2 (en) | 2022-11-15 |
GB201712666D0 (en) | 2017-09-20 |
DE112018003431T5 (en) | 2020-04-02 |
GB2565297B (en) | 2020-09-02 |
CN110999053B (en) | 2023-11-14 |
CN110999053A (en) | 2020-04-10 |
WO2019030516A1 (en) | 2019-02-14 |
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