US20070061690A1 - Block puncturing for turbo code based incremental redundancy - Google Patents

Block puncturing for turbo code based incremental redundancy Download PDF

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Publication number
US20070061690A1
US20070061690A1 US11/428,656 US42865606A US2007061690A1 US 20070061690 A1 US20070061690 A1 US 20070061690A1 US 42865606 A US42865606 A US 42865606A US 2007061690 A1 US2007061690 A1 US 2007061690A1
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canceled
bits
row
block
parity
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Kenneth Stewart
Amitava Ghosh
Michael Buckley
Raja Bachu
Rapeepat Ratasuk
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Motorola Solutions Inc
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Motorola Inc
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0064—Concatenated codes
    • H04L1/0066—Parallel concatenated codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0067—Rate matching
    • H04L1/0068—Rate matching by puncturing
    • H04L1/0069—Puncturing patterns
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/12—Arrangements for detecting or preventing errors in the information received by using return channel
    • H04L1/16—Arrangements for detecting or preventing errors in the information received by using return channel in which the return channel carries supervisory signals, e.g. repetition request signals
    • H04L1/18—Automatic repetition systems, e.g. Van Duuren systems
    • H04L1/1812—Hybrid protocols; Hybrid automatic repeat request [HARQ]
    • H04L1/1819—Hybrid protocols; Hybrid automatic repeat request [HARQ] with retransmission of additional or different redundancy

Definitions

  • This invention relates generally to communication systems, and more particularly to coding in a turbo coded communication system.
  • Convolutional codes are often used in digital communication systems to protect transmitted information from error.
  • Such communication systems include the Direct Sequence Code Division Multiple Access (DS-CDMA) standard IS-95, the Global System for Mobile Communications (GSM), and next generation wideband communication systems.
  • DS-CDMA Direct Sequence Code Division Multiple Access
  • GSM Global System for Mobile Communications
  • a signal is convolutionally coded into an outgoing code vector that is transmitted.
  • a decoder such as a Viterbi decoder as is known in the art, uses a trellis structure to perform an optimum search for the transmitted signal bits based on maximum likelihood criterion.
  • turbo codes have been developed that outperform conventional coding techniques.
  • Turbo codes are generally composed of two or more convolutional codes and turbo interleavers.
  • turbo decoding is iterative and uses a soft output decoder to decode the individual convolutional codes.
  • the soft outputs of the decoders are used in the decoding procedure to iteratively approach the converged final results.
  • FIG. 1 shows a typical turbo encoder that is constructed with one interleaver and two constituent codes which are recursive systematic convolutional (RSC) codes, but can be block codes, also.
  • a turbo encoder is shown which is a parallel concatenation of two RSCs with an interleaver, ⁇ , between them.
  • the output, c k , of the turbo encoder is generated by multiplexing (concatenating) the information bits, b k , and parity bits, P 1k and p 2k , from the two encoders.
  • the parity bits are punctured as is known in the art to increase code rate.
  • Each RSC has a one parity bit output, but the number of parity bits of the RSC can be more than one.
  • the encoded data is transmitted to a receiver, which uses error detection. If an error is detected, the receiver can request that the transmitter, such as a base station for example, retransmit the data using an Automatic Repeat Request (ARQ).
  • ARQ Automatic Repeat Request
  • the radio can request the transmitter to resend that portion of bits from the block or a portion of a frame of data that failed so as to be properly decoded.
  • ARQ a Hybrid Automatic Repeat Request
  • HARQ Two known forms of HARQ are Chase combining and Incremental Redundancy (IR).
  • Chase combining is a simplified form of HARQ wherein the receiver simply requests a retransmission of the same codeword again.
  • IR is more complicated in that it provides for a retransmission of the code word using more parity bits. However, this involves a lowering of the code rate due to the added information, which can only be alleviated by further puncturing of bits.
  • Conventional means of defining a puncturing pattern such as a rate matching algorithm or alternatively a classical code puncturing matrix, as are known in the art, are unable to provide the necessary smooth and flexible transition between changing coding rates, as are envisioned for next generation communication products.
  • turbo coder that utilizes a unified puncturing scheme, which allows flexibility in choosing coding rates for the initial and subsequent transmissions. It would also be advantageous to provide this improvement using any of the combined ARQ techniques. It would also be of benefit to provide an improved turbo coder with a minimal increase of computational complexity or implementation effort.
  • FIG. 1 shows a simplified block diagram for a turbo encoder as is known in the prior art
  • FIG. 2 shows a simplified flow chart for a prior art coding structure
  • FIG. 3 shows a simplified flow chart for a coding structure, in accordance with the present invention
  • FIG. 4 shows a simplified block diagram for a turbo decoder, in accordance with the present invention
  • FIG. 5 shows a chart for block interleaver management, in accordance with the present invention
  • FIG. 6 shows simplified graphic representation for redundancy version, in accordance with the present invention.
  • FIG. 7 shows a chart for bit priority mapping, in accordance with the present invention.
  • FIG. 8 shows a matrix representation of a prior art puncture matrix
  • FIG. 9 shows a set of puncturing matrices, in accordance with the present invention.
  • FIG. 10 shows a first graphical representation of the improvement provided by the present invention
  • FIG. 11 shows a first graphical representation of the improvement provided by the present invention.
  • FIG. 12 shows a simplified flow chart of a method, in accordance with the present invention.
  • the present invention provides a turbo coder that supports incremental redundancy (IR) as a form of ARQ combining, using a single, unified puncturing scheme.
  • IR incremental redundancy
  • the present invention uses a puncturing scheme based on a block interleaver. Codeword bits are read in column-wise while the desired amount of unpunctured data is then read out row-wise after row and column rearrangement.
  • the block nature of the interleaver ensures a regular puncturing distributed throughout the encoder trellis ensuring good code performance.
  • the block puncturing approach of the present invention has the advantage of ease of implementation as well as retaining the flexibility in adapting to any desired coding rate without a significant increase in complexity.
  • the present invention provides for flexible and fine-grained support of predefined redundancy versions at each transmission with progressive reduction in effective coding rates and support for full and partial forms of both Chase combining and IR.
  • the present invention also provides for symbol priority mapping onto the most reliable Quadrature Amplitude Modulation (QAM) constellation points to further reduce decoding errors.
  • QAM Quadrature Amplitude Modulation
  • the High Speed Downlink Packet Access (HSDPA) feature of the Third Generation Partnership Project (3GPP) UTRA (UMTS Terrestrial Radio Access) or Wideband Code Division Multiple Access (WCDMA) system details a hybrid-ARQ scheme based on Incremental Redundancy (IR) methods applied to a rate-1/3 turbo-code.
  • the present invention defines the High Speed Downlink Shared Channel (HS-DSCH) coding and modulation scheme to permit the use of incremental redundancy block interleaving in user equipment (UE), such as a cellular radio communication device.
  • UE user equipment
  • the present invention describes a specific method and apparatus for applying IR to HSDPA.
  • IR methods are known in the art, and have been applied before to systems such as Enhanced Data for GSM Evaluation (EDGE).
  • EDGE Enhanced Data for GSM Evaluation
  • the HSDPA problem is novel, in that the number of Soft Metric Locations (or SMLs) available to the Hybrid Acknowledge Repeat Request (HARQ) process can change depending on factors such as the number of ARQ processes in existence.
  • the present invention allows for a change in the final coding rate according to the available coded symbol memory.
  • prior systems such as EDGE, utilized convolutional codes rather than turbo-codes, and supported a different number of redundancy versions.
  • the present invention provides a flexible IR scheme specifically applicable to HSDPA.
  • the IR scheme of the present invention supports: a) a flexible method of controlling the instantaneous and variable final code rate of the HARQ process (ranging from Chase combining to rate-1/3 expansion), b) general QAM modulation, including 16-QAM, c) a specific set of possible redundancy versions from which can be selected an optimal (or simply preferred) sequence of redundancy versions, based on the specific acknowledge/negative acknowledge (ACK/NACK) signal evolution applicable to HSDPA, and d) a novel implementation of block interleavers.
  • ACK/NACK acknowledge/negative acknowledge
  • IR Prior art implementations for IR, such as those of EDGE, do not meet the specific requirements of the current problem since they cannot change the final coding rate according to the available coded symbol memory.
  • the terminal memory requirements of the user equipment are derived based on Chase (soft) combining at the maximum data rate defined by the associated UE capability parameters.
  • the UE has memory limitations and can only accept particular code rates.
  • the present invention accounts for these memory limitations and allows the UE to vary coding rates accordingly.
  • FIG. 2 shows the existing reference channel coding model for High Speed Downlink Packet Access (HSDPA) in accordance with the 3GPP specification protocols of section 4.2, “Technical Specification Group Radio Access Network; Multiplexing and Channel Coding (FDD) (Release 1999)”, TS 25.212 v3.5.0 (2000-12), which is hereby incorporated by reference.
  • HSDPA High Speed Downlink Packet Access
  • FDD Multiplexing and Channel Coding
  • TS 25.212 v3.5.0 2000-12
  • each of the code blocks are individually subjected to channel coding 208 and rate matching 210 for the puncturing and incremental redundancy used.
  • the blocks are then subject to physical channel segmentation 212 , interleaving 214 , and physical channel mapping 216 , where physical channels 1 through K are output. [maybe give overview of what goes on in each of these blocks? what does the box shading on the last two blocks signify?]
  • FIG. 3 shows a channel coding model for HSDPA in accordance with the present invention.
  • the first four operations proceed according to the 3GPP protocols previously described.
  • channel coding 208 proceeds according to a channel coder operable at a rate-1/3 turbo encoding function.
  • the last three stages (physical channel segmentation 312 , (second) interleaver 314 , and physical channel mapping 316 ) also proceed similarly to the 3GPP protocols with the exception of operation on symbols instead of bits.
  • the improvement of the present invention occurs in the first interleaver 300 , redundancy version selection 302 , and optional the bit priority mapper 304 . [I see that rate matching 210 is not present. Where does rate selection occur in this diagram?]
  • FIG. 4 shows the operation of the first interleaver ( 300 in FIG. 3 ) in entering a codeword into puncturing matrices.
  • the unpunctured codeword bits are bit separated into respective “Systematic”, “Parity 1 ” and “Parity 2 ” streams denoted by X S,k , p 1,k , p 2,k where k ⁇ 1, . . . , N info ⁇ .
  • Each stream is read into separate N row ⁇ N col block matrix interleavers.
  • the parity bits are combined into one puncturing matrix, but separate parity block interleavers can be used for each parity stream.
  • x s ,k ⁇ 1,0 ⁇ and x P,k ⁇ p 1,k , p 2,k ⁇ where x P,k ⁇ 1,0 ⁇ , ⁇ 0,1 ⁇ , ⁇ 1,0 ⁇ , ⁇ 1,1 ⁇ .
  • the tail bits from the coder are buffered separately and are later appended onto the unpunctured instantaneous codeword transmitted in a specific transmission time interval (TTI).
  • TTI transmission time interval
  • the number of rows, N row , and number of columns, N col , in each interleaver can be variable and allocated dynamically.
  • the number of rows, N row is always fixed at thirty, while the number of columns, N col , is variable (dependent on the number of information bits N info ) and is determined in the same manner as the turbo code internal interleavers, such as is described in section 4.2.3.2.3.1 of “Technical Specification Group Radio Access Network; Multiplexing and Channel Coding (FDD) (Release 1999)”, TS 25.212 v3.5.0 (2000-12), which is hereby incorporated by reference.
  • FDD Technical Specification Group Radio Access Network; Multiplexing and Channel Coding
  • FIG. 5 shows the data stream of the interleavers of FIG. 4 .
  • a novel aspect of the present invention is having data read in a column-wise fashion into each interleaver.
  • These dummy bits are later removed when reading the codeword data row-wise from top-to-bottom from the block matrix, similar to the description in section 4.2.3.2.3.2 of TS 25.212, incorporated by reference.
  • both columns and rows are permuted prior to reading out the block matrix contents.
  • the desired number of codeword bits can then be read out in row-wise fashion.
  • the parity bit p 1,k is used as a codeword bit while the parity bit p 2,k is discarded.
  • the maximum number of rows that can be transmitted N p,max — row may be less than N row due to UE memory restrictions, while for the systematic interleaver N s,max — row is always equal to N row .
  • N SML denotes the total number of Soft Metric Locations (SML's) provisioned at the UE
  • N tail denotes the number of tail bits per code block
  • N ARQ — proc denotes the number of ARQ processes currently defined in the UE
  • N P , max_row min ⁇ ( ⁇ ⁇ ⁇ N ⁇ SML ⁇ 2 ⁇ ⁇ N ⁇ CB ⁇ ⁇ N ⁇ col ⁇ ⁇ N ⁇ ARQ_proc ⁇ - ⁇ ⁇ ⁇ N ⁇ row ⁇ 2 ⁇ ⁇ N ⁇ CB ⁇ - ⁇ ⁇ N ⁇ tail ⁇ 2 ⁇ ⁇ N ⁇ col ⁇ ⁇ N ⁇ CB ⁇ , N ⁇ row ) ( Eq . ⁇ 1 )
  • Eq. (1) all the independent variables in Eq. (1) are derivable at the UE following delivery of the signaled Hybrid Automatic Repeat Request (HARQ) information on the High Speed Downlink Secondary Control Channel (HS-DSCCH).
  • HARQ Hybrid Automatic Repeat Request
  • HS-DSCCH High Speed Downlink Secondary Control Channel
  • the above equation defines the memory available to a UE (given that the systematic matrix is substantially fixed), and accounts for the available SML's per ARQ process. Using the above information a transmitting base station can choose the transmit rate suitable to work with the available memory by selecting particular block rows to output to fit the chosen rate, as will be described below. [at what step in FIG. 3 does rate selection occur? Claim 16 ] Moreover, the block interleaver is not used in conventional block interleaving per se, but is used to select rows from the block that are not punctured, so as to provide a higher equivalent code rate. [correct?]
  • the present invention also incorporates a redundancy version selector 302 . Since a different number of codeword bits may be obtained from the systematic and parity block interleavers, the framework of the present invention allows for both Chase and incremental redundancy (IR) coding schemes. In order to support different redundancy versions, any row may be assigned as a starting point at which to commence the readout of codeword bits. Preferably, a static set of starting point combinations is pre-defined, as shown in FIG. 6 . Although, smaller or larger sets of redundancy versions can be used, the eight redundancy versions (RVi,i ⁇ 0, . . . ,7 ⁇ ) shown require three bits for signaling in the HS-DSCCH with the following rules used to define all the versions shown.
  • RVi,i ⁇ 0, . . . ,7 ⁇ the eight redundancy versions shown require three bits for signaling in the HS-DSCCH with the following rules used to define all the versions shown.
  • the X (e.g. RV 1 , RV 2 , RV 3 ) signifies no bits are used from that interleaver to form the instantaneous codeword.
  • Rule 3 The double arrowed line signifies all bits in 1 to N i,max — row in that block interleaver must be transmitted exactly once (e.g. RV 0 ).
  • the present invention includes a specific set of eight redundancy versions for selecting coded bits from the systematic and parity interleavers in accordance with the above rules, as shown in FIG. 6 and as described below.
  • Redundancy version zero the starting row is the top row of both the systematic and parity interleavers, and coded bits from the systematic interleaver is read from its starting row to completion before the remaining coded bits are read from the parity interleaver starting at its starting row.
  • Redundancy version one the starting row is the top row of the parity interleaver, the coded bits are read from the parity interleaver starting at its starting row.
  • Redundancy version two the starting row is N p,max — row /3 for the parity interleaver, and the coded bits are read from the parity interleaver starting at its starting row.
  • Redundancy version three the starting row is 2 ⁇ N p,max — row /3 for the parity interleaver, and the coded bits are read from the parity interleaver starting at its starting row.
  • Redundancy version four the respective starting rows are the top row of the parity interleaver and N S,max — row /2 for the systematic interleaver, and the coded bits are read equally from the systematic and parity interleaver starting at their respective starting rows.
  • Redundancy version five the respective starting rows are N p,max — row /4 for the parity interleaver and 3 ⁇ N S,max — row /4 for the systematic interleaver, and the coded bits are read equally from the systematic and parity interleaver starting at their respective starting rows.
  • Redundancy version six the respective starting rows are the top row of the systematic interleaver and N p,max — row /2 for the parity interleaver, and the coded bits are read equally from the systematic and parity interleaver starting at their respective starting rows.
  • Redundancy version seven the respective starting rows are 3 ⁇ N p,max — row /4 for the parity interleaver and N S,max — row /4 for the systematic interleaver, and the coded bits are read equally from the systematic and parity interleaver starting at their respective starting rows.
  • redundancy versions in the present invention are that their numbering does not suggest a particular order of transmission. For example, if on the first transmission RVO is signaled with enough codeword bits to result in a rate 3/5 code (exactly one third of the parity bits transmitted), the scheduler is permitted choose RV 2 for the second transmission. Similarly, if in the first transmission, a rate 1/4 code is desired, RV 4 might be selected for the second transmission. Moreover, systematic bits can be used in the first selected and unpunctured rows and parity bits in subsequent and punctured rows to reduce error. Using this approach, the chosen redundancy version can be used to support Chase, partial and full IR schemes in conjunction with any adaptive modulation and coding scheme (AMCS).
  • AMCS adaptive modulation and coding scheme
  • a preferred embodiment of the present invention incorporates a bit priority mapper (BPM), which further improves the performance of IR.
  • BPM bit priority mapper
  • Priority bit mapping is based on utilizing the differing bit reliability offered by higher order constellations (16-QAM or higher). It is well known that systematic portions of a turbo codeword are of greater importance to decoder performance than the parity portions. It naturally follows that system performance can be further improved by placing systematic bits in positions of high reliability if a higher order constellation is used.
  • the symbol mapping is dependent on the type of modulation and the number of systematic and parity bits used in transmission. As an example, if redundancy version 0 (RV0) is used with an effective code rate of 3/4 and 16-QAM modulation, each QAM symbol comprises of three systematic bits and one parity bit, while if the same version is used with a code rate of 1/2 and 16-QAM modulation, each QAM symbol then comprises of two systematic and 2 parity bits.
  • RV0 redundancy version 0
  • each QAM symbol then comprises of two systematic and 2 parity bits.
  • FIG. 7 shows an example of the proposed priority bit mapping for the case of 16-QAM modulation where a grouping of four bits is used to define one symbol.
  • the four bits are denoted i 1 , q 1 , i 2 , q 2 with bits i 1 and q i offering greater reliability than bits i 2 and q 2 due to the nature of the constellation, as is known in the art.
  • Systematic codeword bits 700 are read from left-to-right into the BPM array one code block at a time. Once all systematic codeword bits 700 have been read in, parity codeword bits 702 are read in again from left-to-right and one code block at a time.
  • the output of the BPM is a sequence of QAM symbols or bit vectors (a vector of four bits in the case of 16-QAM and a vector of two bits in the case of QPSK) given by the columns of the BPM array, read in sequence from left-to-right.
  • the puncturing matrix can then be chosen to select the rows of systematic bits to be unpunctured rows of the block for better accuracy. [correct? If not, why is having the systematic bits in the top row an advantage?]
  • the physical channel segmentation 312 proceeds according to the 3GPP protocol of section 4.2.10 of TS 25.212, incorporated by reference, but with a modification. Instead of applying the algorithm on bits as in section 4.2.10, it is applied on the QAM symbols/bit vectors output from the BPM described above.
  • second interleaving 314 is applied, again with a modification.
  • the interleaver instead of applying the interleaver on the bits comprising each physical channel, it is applied on the QAM symbols values or symbol indices of each of the physical channel which are output from the physical channel segmentation 312 .
  • the first curve 1000 represents the spectral efficiency of a signal using the traditional method of puncturing.
  • the second curve 1002 represents the spectral efficiency of a signal using block puncturing in accordance with the present invention.
  • the third curve 1004 represents the spectral efficiency of a signal using block puncturing and symbol mapping, in accordance with a preferred embodiment of the present invention. As can be seen there is no loss between traditional and block puncturing methods of the present invention, while the use of symbol mapping gives a significant advantage for 16QAM.
  • FIG. 11 shows the simulated error for a rate 3/4 QPSK coding for both Chase and full IR combining.
  • the traditional puncturing pattern is defined by the matrix of FIG. 8 for all transmissions.
  • the puncturing matrices for the respective first, second and third block transmissions are shown in FIG. 9 , respectively.
  • the simulation was conducted to determine frame error rate (FER) for a Quadrature Phase Shift Keying (QPSK) signal at a 3/4 rate with a spreading factor (SF) of 16 and Orthogonal Variable Spreading Factor (OVSF) of 1 over an AWGN channel.
  • the first curve 1100 shows the FER of the traditional IR scheme with one transmission (Chase combining).
  • the second curve 1102 shows the FER of the traditional IR scheme with two transmissions.
  • the third curve 1104 shows the FER of the traditional IR scheme with three transmissions.
  • the fourth curve 1106 shows the FER of the block puncturing IR scheme with one transmission
  • the fifth curve 1108 shows the FER of the block puncturing IR scheme with two transmissions
  • sixth curve 1110 shows the FER of the block puncturing IR scheme with three transmissions.
  • the block puncturing of the present invention so no loss of performance, for both Chase and IR schemes, in all cases except for in the three transmission, full incremental redundancy where there a slight loss in performance of the proposed block-puncturing scheme versus the more traditional yet very inflexible matrix based traditional puncturing approach. Considering the overall improvement provided by the present invention, this is quite acceptable. Moreover, symbol remapping may be used to alleviate deficiency.
  • FIG. 12 shows a flow chart representing a method of block puncturing for turbo code based incremental redundancy, in accordance with the present invention.
  • a first step of the method is coding 1200 , such as turbo coding, an input data stream into systematic bits and parity bits.
  • a next step is loading 1202 loading the systematic bits and parity bits into respective systematic and parity block interleavers in a column-wise manner, as described previously.
  • a next step is selecting 1204 a predetermined redundancy. This step follows the redundancy rules previously described, and preferably utilizes the specific redundancy version outlined above.
  • a next step is outputting 1206 data from the block interleavers in a row-wise manner in accordance with the selected redundancy.
  • a outputting step includes mapping the bits from the systematic and parity block into a symbol mapping array wherein the systematic bits are mapped into the upper rows of the array and the parity bits are mapped into the lower rows of the array. This is followed by a step of selecting the final code rate dependant upon the available symbol memory, as defined by Eq. 1.

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20060133533A1 (en) * 2004-12-22 2006-06-22 Qualcomm Incorporated Method and apparatus for using multiple modulation schemes for a single packet
US20080256410A1 (en) * 2005-09-23 2008-10-16 Electronics And Telecommunications Research Instit Mimo System Performing Hybrid Arq and Retransmission Method Thereof
US20080317152A1 (en) * 2005-07-05 2008-12-25 Shanghai Ultimate Power Communications Technology, Method and Apparatus for Multi-Carrier Hsdpa Traffic Transmission Channel Coding
US20090327831A1 (en) * 2008-06-30 2009-12-31 Fujitsu Limited Automatic Retransmission Controller And Retransmission Block Recombination Apparatus
EP2178239A2 (en) 2008-10-20 2010-04-21 Fujitsu Limited Retransmission data generating apparatus and receiver
US20110119568A1 (en) * 2009-11-18 2011-05-19 Samsung Electronics Co., Ltd. Method and apparatus for transmitting and receiving data in a communication system
US20110173517A1 (en) * 2008-10-01 2011-07-14 Kim Yong-Ho Symbol-level random network coded cooperation with hierarchical modulation in relay communication
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Families Citing this family (41)

* Cited by examiner, † Cited by third party
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US7372837B2 (en) * 2001-10-26 2008-05-13 Texas Instrument Incorporated Incremental redundancy using two stage rate matching for automatic repeat request to obtain high speed transmission
KR100584426B1 (ko) * 2001-12-21 2006-05-26 삼성전자주식회사 고속 패킷 이동통신시스템에서 심벌 매핑을 위한 인터리빙장치 및 방법
KR100754552B1 (ko) * 2001-12-28 2007-09-05 삼성전자주식회사 고속 순방향 패킷 접속 방식을 사용하는 통신 시스템에서고속 공통 제어 채널 송수신 장치 및 방법
US20030177047A1 (en) * 2002-02-04 2003-09-18 Buckley Michael E. Method and system for decision oriented systems engineering
US7236480B2 (en) * 2002-06-07 2007-06-26 Sandbridge Technologies, Inc. Method of first interleaving of a two interleaver transmitter
US7003703B2 (en) * 2002-06-21 2006-02-21 Sandbridge Technologies, Inc. Method of interleaving/deinterleaving in a communication system
US7245669B2 (en) * 2003-04-14 2007-07-17 Millimetrix Broadband Networks Ltd. Dual polarity coding system and method for a millimeter wave communication system
KR20050020526A (ko) * 2003-08-23 2005-03-04 삼성전자주식회사 이동통신시스템에서 비트 인터리빙장치 및 방법
JP4224370B2 (ja) * 2003-09-25 2009-02-12 パナソニック株式会社 入力制御装置及び入力制御方法
US7925953B2 (en) * 2003-10-07 2011-04-12 Nokia Corporation Redundancy strategy selection scheme
GB2407945B (en) * 2003-10-25 2006-04-19 Andrew John Rogers Cyclic redundancy check for error correcting codes with minimal code rate loss
KR100770902B1 (ko) * 2004-01-20 2007-10-26 삼성전자주식회사 고속 무선 데이터 시스템을 위한 가변 부호율의 오류 정정부호 생성 및 복호 장치 및 방법
US7366477B2 (en) * 2004-05-06 2008-04-29 Nokia Corporation Redundancy version implementation for an uplink enhanced dedicated channel
EP1779575A1 (en) 2004-08-17 2007-05-02 Nokia Corporation Methods and apparatus for balancing modulation in cellular communications over noisy channels
EP1794921B1 (en) 2004-09-15 2009-04-15 Nokia Siemens Networks Gmbh & Co. Kg Decoding method
FI20050264A0 (fi) * 2005-03-11 2005-03-11 Nokia Corp Tietojenkäsittelymenetelmä, verkkoelementti, lähetin, komponentti ja tietokoneohjelmatuote
US20070008944A1 (en) * 2005-07-06 2007-01-11 Qian Zhang Method and system for spreading and scrambling downlike physical channels
KR100875888B1 (ko) * 2006-03-24 2008-12-26 삼성전자주식회사 무선 통신시스템에서 복합 자동 재전송 요청을 수행하기위한 장치 및 방법
US8065588B2 (en) * 2007-01-17 2011-11-22 Broadcom Corporation Formulaic flexible collision-free memory accessing for parallel turbo decoding with quadratic polynomial permutation (QPP) interleave
US8379738B2 (en) * 2007-03-16 2013-02-19 Samsung Electronics Co., Ltd. Methods and apparatus to improve performance and enable fast decoding of transmissions with multiple code blocks
US8225165B2 (en) * 2007-10-12 2012-07-17 Industrial Technology Research Institute Methods and devices for encoding data in communication systems
WO2009057922A1 (en) * 2007-10-29 2009-05-07 Lg Electronics Inc. Method of data transmission using harq
US8386903B2 (en) * 2007-10-31 2013-02-26 Futurewei Technologies, Inc. Bit reverse interleaving methods for QAM modulation in a wireless communication system
CN102084683B (zh) * 2008-03-12 2016-09-28 松下电器（美国）知识产权公司 无线通信装置、无线通信系统以及无线通信方法
US8873671B2 (en) 2008-03-26 2014-10-28 Qualcomm Incorporated Method and system for LLR buffer reduction in a wireless communication modem
US8787241B2 (en) * 2008-07-07 2014-07-22 Interdigital Patent Holdings, Inc. Method and apparatus for use in cooperative relays using incremental redundancy and distributed spatial multiplexing
US8565326B2 (en) * 2008-07-08 2013-10-22 Industrial Technology Research Institute System and method for bit allocation and interleaving
US8965320B2 (en) * 2008-11-04 2015-02-24 Telefonaktiebolaget L M Ericsson (Publ) Method and arrangement for enabling improved receiver quality for noise limited uplink signals
RU2011147727A (ru) * 2009-04-24 2013-05-27 Панасоник Корпорэйшн Устройство беспроводной связи и способ беспроводной связи
KR101740335B1 (ko) * 2011-01-03 2017-05-26 삼성전자주식회사 다중 안테나 통신 시스템에서 저밀도 패리티 검사 부호 기반의 채널 부호화 및 복호화 장치 및 방법
KR102046343B1 (ko) * 2013-04-18 2019-11-19 삼성전자주식회사 디지털 영상 방송 시스템에서의 송신 장치 및 방법
JP2016174195A (ja) * 2013-08-05 2016-09-29 シャープ株式会社 基地局装置、端末装置、および集積回路
US10367621B2 (en) * 2014-10-27 2019-07-30 Qualcomm Incorporated Fountain HARQ for reliable low latency communication
TWI589125B (zh) * 2016-08-26 2017-06-21 國立交通大學 渦輪編碼的數位資料之去穿刺方法與裝置及渦輪解碼器系統
US10324168B2 (en) 2016-09-12 2019-06-18 The Boeing Company Systems and methods for spatial filtering using data with widely different error magnitudes
US10429491B2 (en) 2016-09-12 2019-10-01 The Boeing Company Systems and methods for pulse descriptor word generation using blind source separation
US10324167B2 (en) 2016-09-12 2019-06-18 The Boeing Company Systems and methods for adding functional grid elements to stochastic sparse tree grids for spatial filtering
US9954561B2 (en) 2016-09-12 2018-04-24 The Boeing Company Systems and methods for parallelizing and pipelining a tunable blind source separation filter
CN109039546B (zh) * 2016-12-28 2020-12-29 上海朗帛通信技术有限公司 一种用于信道编码的ue、基站中的方法和设备
CN115428370B (zh) * 2020-04-08 2025-05-02 苹果公司 用于改进的数据传输的冗余间隙指示
CN116566404B (zh) * 2023-07-11 2023-09-19 北京谷数科技股份有限公司 删余Turbo码交织映射关系的确定方法及装置

Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6192084B1 (en) * 1998-05-28 2001-02-20 Sony Corporation Soft output decoding apparatus and method for convolutional code
US6339834B1 (en) * 1998-05-28 2002-01-15 Her Majesty The Queen In Right Of Canada, As Represented By The Minister Of Industry Through The Communication Research Centre Interleaving with golden section increments
US6370669B1 (en) * 1998-01-23 2002-04-09 Hughes Electronics Corporation Sets of rate-compatible universal turbo codes nearly optimized over various rates and interleaver sizes
US6430722B1 (en) * 1998-01-23 2002-08-06 Hughes Electronics Corporation Forward error correction scheme for data channels using universal turbo codes
US6480503B1 (en) * 1998-12-28 2002-11-12 Texas Instruments Incorporated Turbo-coupled multi-code multiplex data transmission for CDMA
US6621871B2 (en) * 2001-03-30 2003-09-16 Nokia Corporation Incremental redundancy packet combiner and decoder
US6744744B1 (en) * 1999-04-13 2004-06-01 Nortel Networks Limited Rate matching and channel interleaving for a communications system

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6370669B1 (en) * 1998-01-23 2002-04-09 Hughes Electronics Corporation Sets of rate-compatible universal turbo codes nearly optimized over various rates and interleaver sizes
US6430722B1 (en) * 1998-01-23 2002-08-06 Hughes Electronics Corporation Forward error correction scheme for data channels using universal turbo codes
US6192084B1 (en) * 1998-05-28 2001-02-20 Sony Corporation Soft output decoding apparatus and method for convolutional code
US6339834B1 (en) * 1998-05-28 2002-01-15 Her Majesty The Queen In Right Of Canada, As Represented By The Minister Of Industry Through The Communication Research Centre Interleaving with golden section increments
US6480503B1 (en) * 1998-12-28 2002-11-12 Texas Instruments Incorporated Turbo-coupled multi-code multiplex data transmission for CDMA
US6744744B1 (en) * 1999-04-13 2004-06-01 Nortel Networks Limited Rate matching and channel interleaving for a communications system
US6621871B2 (en) * 2001-03-30 2003-09-16 Nokia Corporation Incremental redundancy packet combiner and decoder

Cited By (22)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20060133533A1 (en) * 2004-12-22 2006-06-22 Qualcomm Incorporated Method and apparatus for using multiple modulation schemes for a single packet
US10291349B2 (en) 2004-12-22 2019-05-14 Qualcomm Incorporated Method and apparatus for using multiple modulation schemes for a single packet
US9385843B2 (en) * 2004-12-22 2016-07-05 Qualcomm Incorporated Method and apparatus for using multiple modulation schemes for a single packet
US20080317152A1 (en) * 2005-07-05 2008-12-25 Shanghai Ultimate Power Communications Technology, Method and Apparatus for Multi-Carrier Hsdpa Traffic Transmission Channel Coding
US8081696B2 (en) * 2005-07-05 2011-12-20 Shanghai Ultimate Power Communications Technology Co., Ltd. Method and apparatus for multi-carrier HSDPA traffic transmission channel coding
US20080256410A1 (en) * 2005-09-23 2008-10-16 Electronics And Telecommunications Research Instit Mimo System Performing Hybrid Arq and Retransmission Method Thereof
US8347161B2 (en) * 2005-09-23 2013-01-01 Electronics And Telecommunications Research Institute MIMO system performing hybrid ARQ and retransmission method thereof
US8631296B2 (en) 2008-06-30 2014-01-14 Fujitsu Limited Automatic retransmission controller and retransmission block recombination apparatus
US20090327831A1 (en) * 2008-06-30 2009-12-31 Fujitsu Limited Automatic Retransmission Controller And Retransmission Block Recombination Apparatus
EP2141851A2 (en) 2008-06-30 2010-01-06 Fujitsu Ltd. Automatic retransmission controller and retransmission block recombination apparatus
US20110173517A1 (en) * 2008-10-01 2011-07-14 Kim Yong-Ho Symbol-level random network coded cooperation with hierarchical modulation in relay communication
US8516344B2 (en) * 2008-10-01 2013-08-20 Lg Electronics Inc. Symbol-level random network coded cooperation with hierarchical modulation in relay communication
EP2178239A2 (en) 2008-10-20 2010-04-21 Fujitsu Limited Retransmission data generating apparatus and receiver
US20100100787A1 (en) * 2008-10-20 2010-04-22 Fujitsu Limited Transmission data generating apparatus and receiver
US8707125B2 (en) * 2009-11-18 2014-04-22 Samsung Electronics Co., Ltd Method and apparatus for transmitting and receiving data in a communication system
US9154341B2 (en) 2009-11-18 2015-10-06 Samsung Electronics Co., Ltd. Method and apparatus for transmitting and receiving data in a communication system
US20110119568A1 (en) * 2009-11-18 2011-05-19 Samsung Electronics Co., Ltd. Method and apparatus for transmitting and receiving data in a communication system
US10038576B2 (en) 2009-11-18 2018-07-31 Samsung Electronics Co., Ltd. Method and apparatus for transmitting and receiving data in a communication system
US10425258B2 (en) 2009-11-18 2019-09-24 Samsung Electronics Co., Ltd Method and apparatus for transmitting and receiving data in a communication system
CN105637791A (zh) * 2014-05-27 2016-06-01 华为技术有限公司 一种循环映射方法和设备
EP3142282A4 (en) * 2014-05-27 2017-05-24 Huawei Technologies Co. Ltd. Cyclic mapping method and device
CN107409023A (zh) * 2015-03-17 2017-11-28 华为技术有限公司 一种合并层域中的数据和重传数据的方法和装置

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