US20050225374A1 - Self-oscillating full bridge driver IC - Google Patents
Self-oscillating full bridge driver IC Download PDFInfo
- Publication number
- US20050225374A1 US20050225374A1 US11/099,818 US9981805A US2005225374A1 US 20050225374 A1 US20050225374 A1 US 20050225374A1 US 9981805 A US9981805 A US 9981805A US 2005225374 A1 US2005225374 A1 US 2005225374A1
- Authority
- US
- United States
- Prior art keywords
- controlling
- drivers
- low
- circuit
- driver
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/217—Class D power amplifiers; Switching amplifiers
- H03F3/2173—Class D power amplifiers; Switching amplifiers of the bridge type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/06—Modifications for ensuring a fully conducting state
- H03K17/063—Modifications for ensuring a fully conducting state in field-effect transistor switches
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
- H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
Definitions
- the present invention relates to a self-oscillating full-bridge driver IC, and more particularly to a driver having a pre-charging circuit, which may include a bootstrap circuit for pre-charging a bootstrap capacitor before starting up or transferring signals from the oscillator.
- a self-oscillating full-bridge driver of background interest is the IR2153 integrated circuit.
- a functional block diagram of the IR2153 is shown in FIG. 1 .
- the IR2153 has several features of particular interest:
- UVLO Under voltage lockout
- This block marked as UV Detect on FIG. 1 , ensures that the gate drive outputs, HO and LO are both low should bias become too marginal for comfortable gate drive to the output transistors.
- the UVLO circuit also assures a repeatable start-up sequence and controls bias current needed for various elements of the IC.
- the UVLO circuit monitors the bias supply Vcc.
- the UVLO circuit is further provided with hysteresis to improve noise immunity.
- two threshold levels are defined; one sensitive to a rising edge and the other to a falling edge.
- these two thresholds are listed as VccUV+ and VccUV ⁇ .
- Hysteresis is a measure of the difference between these two thresholds and is separately listed on data sheets as VccUVH.
- VccUV+ is the threshold at which the chip is first enabled, when Vcc is rising. Once enabled, Vcc is allowed to drop slightly without adverse effects.
- the IR2153 also has micropower start-up, which means that the bias current needed when the IC is in a quiescent state (i.e. not oscillating and Vcc ⁇ VccUV) is reduced to a very low level.
- Micropower start-up is beneficial because off-line applications usually have a single resistor from a high voltage bus for start-up bias to keep component cost and complexity low. In some cases this resistor provides bias for all modes of operation(both start-up and running, where current demand is highest). However, an auxiliary low voltage source is more common for this purpose.
- “Bootstrapping” is beneficial because an auxiliary supply can be derived with much higher efficiency than from a simple dropping resistor connected to the line.
- the micropower feature allows the pull-up resistor to be increased in value compared to schemes in which a single dropping resistor provides all the bias. This is because the resistor needs only to overcome the quiescent bias current requirements for the IC and raise Vcc to UV+. When the IC starts oscillating, the additional bias requirement is met by an auxiliary supply.
- bootstrap is also used to describe the diode and Vbs capacitor arrangement used in the typical circuit configuration. This part of the circuit serves a different function than the resistor in a bootstrap “start up” scheme. Bootstrap diode/capacitor circuits are described in Design Tip DT-2, by Jonathan Adams, which is available at www.irf.com. incorporated by reference.
- the IR2153 further incorporates a fast shutdown mode providing a protective action against fault conditions that would otherwise destroy output switches.
- Fusing is the simplest option but is often ineffective at preventing damage to semiconductors and is not self-resetting, unless comparatively more expensive devices are used.
- the load is capacitively coupled or resonant in nature, for example as in most electronic ballast designs, ample protection may be afforded by merely halting the oscillator and preventing further switching cycles. However, adequate protection sometimes calls for both FET's to be rapidly turned off.
- Vcc below VccUV ⁇ so as to turn off both FETs. This requirement may to an extent conflict with the need to provide a healthy charge reservoir and solid decoupling.
- the shutdown network must be capable of rapidly pulling charge from the Vcc reservoir capacitor (and the decoupling capacitor, if present). Low holding current thyristors can be used to crowbar Vcc and latch the chip off until the supply is recycled. This approach is both simple and inexpensive but does not support automatic power-on reset.
- the IR2153 offers a convenient shutdown solution by adding a second function to the Ct pin.
- a third functional threshold is added to Ct and set at Vcc/6. Below this threshold a fast shutdown mode is invoked and both output buffers are set low with minimal delay. This allows a simple open-collector NPN transistor or similar to be used as part of an inexpensive protection scheme.
- IR 2153 can be if desired be driven directly as a slave device, for example to complete a fill bridge.
- the Ct input can be directly fed from a square wave source, provided Vct high>2 ⁇ 3 Vcc and Vct low ⁇ 1 ⁇ 3 Vcc.
- the Rt output of any self-oscillating control IC can generate a master clock to feed directly into the Ct input of another, effectively bypassing the internal oscillator of the slaved device. This can be a useful way to implement a full bridge using just one type of IC or hybrid.
- Dead time is the period during which both HO and LO outputs are intentionally low. This period is fixed inside the IC and serves several essential functions. The primary function of dead-time is to prevent cross conduction or shoot-through in half-bridge designs. If the load is resonant in nature, such as in electronic ballasts and resonant mode power supplies, dead-time also helps maintain zero voltage switching (ZVS). Sometimes called soft switching, this technique significantly reduces switching losses.
- circuit efficiency is generally highest when zero voltage switching (ZVS or soft switching) occurs.
- ZVS zero voltage switching
- ZVS Soft switching
- IR2153 output buffers also have a reduced di/dt output stage. This means that the peak rate of change of current (rate of current rise and fall for turn-on and turn-off) has been deliberately reduced. In effect the IR2153 output buffers are turned on and off at a controlled rate.
- Benefits of reduced di/dt output buffers include lower gate ringing (Vgs overshoot/undershoot) from a combination of di/dt and gate circuit parasitics.
- gate resistors can be eliminated altogether, however this depends on several factors such as layout and transistor type used. Rf interference may also be reduced.
- the invention provides improvements in the type of self-oscillating full-bridge driver described above, and more particularly provides a bootstrap circuit in a driver IC, which may include a circuit for pre-charging a bootstrap capacitor before starting up the oscillator.
- the invention relates to an integrated control circuit for controlling switching devices arranged in a full bridge for supplying power to a load, comprising: a pair of high-side drivers in the integrated circuit for controlling respective high-side switching devices in the full bridge, the high-side drivers each having a respective high side control terminal for supplying control signals to the corresponding high-side switching device; a pair of low-side drivers in the integrated circuit for controlling respective low-side switching devices in the full bridge; the low-side drivers each having a respective low-side control terminal for supplying control signals to the corresponding low-side switching device; and an oscillator and timing circuits in the integrated circuit supplying control signals for controlling the high- and low-side drivers.
- a control circuit and method for controlling switching devices for supplying power to a load may comprise a high-side driver for controlling a high-side switching device and a low-side driver for controlling a low-side switching device; said high-side driver having a high-side floating supply terminal and a high-side floating supply return terminal; and a precharging circuit connected to said high-side driver.
- the precharging circuit may include a bootstrap capacitor connected between the high-side floating supply and floating supply return terminals for contributing power to the high-side driver, and a bootstrap circuit connected to said high-side floating supply terminal for supplying current to charge the bootstrap capacitor.
- the invention further may include a method or apparatus in which a timing circuit delivers drive signals to said high-side driver to cause said high-side driver to drive said high-side switching device, and the timing circuit further controls the precharging circuit so that the high-side driver is powered, possibly by charging a bootstrap capacitor, before the high-side driver receives the drive signals.
- a bootstrap precharging circuit briefly switches on both of the low-side outputs LO 1 and LO 2 to allow bootstrap capacitors to fully charge, advantageously before the oscillator starts up. Precharging the bootstrap capacitors helps avoid missing high-side pulses at start up. This feature is incorporated for example in the IRS2453D Self-Oscillating Full-Bridge Driver IC manufactured by International Rectifier.
- the IRS2453D is based on the IR2153 self-oscillating half-bridge gate driver IC described above, and incorporates a high voltage full-bridge gate driver with a front end oscillator similar to the industry standard 555 CMOS timer. HVIC and latch immune CMOS technologies enable ruggedized monolithic construction.
- the output driver features a high pulse current buffer stage designed for minimum driver cross-conduction. Noise immunity is achieved with low di/dt peak of the gate drivers, and with an undervoltage lockout hysteresis greater than 1V.
- the IRS2453D also includes latched and non-latched shutdown pins.
- FIG. 1 is a functional block diagram of the prior art IR 2153 chip.
- FIG. 2 is a functional block diagram of the IR 2453 D chip incorporating an embodiment of the invention.
- FIG. 3 is a typical connection diagram.
- FIG. 4 is a diagram showing lead assignments.
- FIG. 5 is a table showing lead definitions.
- FIG. 6 is a diagram showing the timing of signals in the IR 2453 D.
- FIG. 7 is a diagram showing the timing of certain signals shown in FIG. 6 at start-up.
- FIGS. 8A and 8B show respectively a deadtime waveform and a rise and fall time waveform.
- UVLO Under-voltage Lock-Out Mode
- the under-voltage lockout mode is defined as the state the IC is in when VCC is below the turn-on threshold of the IC.
- the IRS2453D under-voltage lock-out is designed to maintain an ultra low supply current of less than 150 ⁇ A, and to guarantee the IC is fully functional before the high and low side output drivers are activated.
- the high-side and low-side driver outputs LO 1 , LO 2 , HO 1 , HO 2 are all low. With VCC above the VCCUV+ threshold, the IC turns on and the output begin to oscillate.
- VCC VCC ⁇ VRT+
- VCT ⁇ about 1 ⁇ 3 of VCC
- LO 1 and HO 2 turn on with a delay equivalent to the deadtime td.
- VCT+ approximately 2 ⁇ 3 of VCC
- LO 1 and HO 2 go low
- RT goes down to approximately ground (VRT ⁇ )
- the CT capacitor starts discharging and the deadtime circuit is activated.
- LO 2 and HO 1 go high.
- the deadtime LO 1 and HO 2 go low, RT goes to high again, and the deadtime is activated.
- LO 1 and HO 2 go high and the cycle starts over again.
- the internal bootstrap FETs (MBOOT 1 , MBOOT 2 ) and supply capacitors (CBOOT 1 and CBOOT 2 ) comprise the supply voltage (VB 1 , VB 2 ) for the high side driver circuitry.
- the internal boostrap FET only turns on when the corresponding LO is high. To guarantee that the high-side supply is charged up before the first pulse on HO 1 and HO 2 , LO 1 and LO 2 are both on when CT ramps between 1 ⁇ 6*VCC and 1 ⁇ 3*VCC.
- LO 1 and LO 2 are both high while CT is between 1 ⁇ 6 and 1 ⁇ 3 of VCC, allowing the internal bootstrap MOSFETs MBOOT 1 and MBOOT 2 connected to VB 1 and VB 2 to precharge the respective bootstrap capacitors CBOOT 1 and CBOOT 2 .
- CT does not charge up and oscillation stops. All outputs are held low and the bootstrap FETs are off. Oscillation will resume once CT is able to charge up again to VCT ⁇ .
- the SD pin When the SD pin is brought above 2V, the IC goes into fault mode and all outputs are low. VCC has to be recycled below VCCUV ⁇ to restart the IC.
- the SD pin can be used for over-current or over-voltage protection, for example, using appropriate external circuitry.
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Electronic Switches (AREA)
- Logic Circuits (AREA)
Abstract
Description
- The present application is based on and claims priority of U.S. Provisional Application Ser. No. 60/560,876 filed by the present inventors on Apr. 8, 2004, the disclosures of which are incorporated by reference.
- 1. Field of the Invention
- The present invention relates to a self-oscillating full-bridge driver IC, and more particularly to a driver having a pre-charging circuit, which may include a bootstrap circuit for pre-charging a bootstrap capacitor before starting up or transferring signals from the oscillator.
- 2. Related Art
- A self-oscillating full-bridge driver of background interest is the IR2153 integrated circuit. A functional block diagram of the IR2153 is shown in
FIG. 1 . The IR2153 has several features of particular interest: - Under voltage lockout (UVLO) is the name for a protection feature built into several control IC's manufactured by International Rectifier. This block, marked as UV Detect on
FIG. 1 , ensures that the gate drive outputs, HO and LO are both low should bias become too marginal for comfortable gate drive to the output transistors. The UVLO circuit also assures a repeatable start-up sequence and controls bias current needed for various elements of the IC. The UVLO circuit monitors the bias supply Vcc. - The UVLO circuit is further provided with hysteresis to improve noise immunity. Instead of switching on/off at one voltage level, two threshold levels are defined; one sensitive to a rising edge and the other to a falling edge. In product data sheets describing Vcc undervoltage lockout, these two thresholds are listed as VccUV+ and VccUV−. Hysteresis is a measure of the difference between these two thresholds and is separately listed on data sheets as VccUVH. VccUV+ is the threshold at which the chip is first enabled, when Vcc is rising. Once enabled, Vcc is allowed to drop slightly without adverse effects.
- The IR2153 also has micropower start-up, which means that the bias current needed when the IC is in a quiescent state (i.e. not oscillating and Vcc<VccUV) is reduced to a very low level. Micropower start-up is beneficial because off-line applications usually have a single resistor from a high voltage bus for start-up bias to keep component cost and complexity low. In some cases this resistor provides bias for all modes of operation(both start-up and running, where current demand is highest). However, an auxiliary low voltage source is more common for this purpose.
- “Bootstrapping” is beneficial because an auxiliary supply can be derived with much higher efficiency than from a simple dropping resistor connected to the line. In bootstrap start-up schemes, the micropower feature allows the pull-up resistor to be increased in value compared to schemes in which a single dropping resistor provides all the bias. This is because the resistor needs only to overcome the quiescent bias current requirements for the IC and raise Vcc to UV+. When the IC starts oscillating, the additional bias requirement is met by an auxiliary supply.
- The term “bootstrap” is also used to describe the diode and Vbs capacitor arrangement used in the typical circuit configuration. This part of the circuit serves a different function than the resistor in a bootstrap “start up” scheme. Bootstrap diode/capacitor circuits are described in Design Tip DT-2, by Jonathan Adams, which is available at www.irf.com. incorporated by reference.
- The IR2153 further incorporates a fast shutdown mode providing a protective action against fault conditions that would otherwise destroy output switches. Fusing is the simplest option but is often ineffective at preventing damage to semiconductors and is not self-resetting, unless comparatively more expensive devices are used. If the load is capacitively coupled or resonant in nature, for example as in most electronic ballast designs, ample protection may be afforded by merely halting the oscillator and preventing further switching cycles. However, adequate protection sometimes calls for both FET's to be rapidly turned off.
- One way to implement shutdown is to pull Vcc below VccUV− so as to turn off both FETs. This requirement may to an extent conflict with the need to provide a healthy charge reservoir and solid decoupling. The shutdown network must be capable of rapidly pulling charge from the Vcc reservoir capacitor (and the decoupling capacitor, if present). Low holding current thyristors can be used to crowbar Vcc and latch the chip off until the supply is recycled. This approach is both simple and inexpensive but does not support automatic power-on reset.
- The IR2153 offers a convenient shutdown solution by adding a second function to the Ct pin. A third functional threshold is added to Ct and set at Vcc/6. Below this threshold a fast shutdown mode is invoked and both output buffers are set low with minimal delay. This allows a simple open-collector NPN transistor or similar to be used as part of an inexpensive protection scheme.
- IR2153 can be if desired be driven directly as a slave device, for example to complete a fill bridge. The Ct input can be directly fed from a square wave source, provided Vct high>⅔ Vcc and Vct low<⅓ Vcc. The Rt output of any self-oscillating control IC can generate a master clock to feed directly into the Ct input of another, effectively bypassing the internal oscillator of the slaved device. This can be a useful way to implement a full bridge using just one type of IC or hybrid.
- IR2153 further has improved dead-time accuracy with zero average temperature coefficient. Dead time is the period during which both HO and LO outputs are intentionally low. This period is fixed inside the IC and serves several essential functions. The primary function of dead-time is to prevent cross conduction or shoot-through in half-bridge designs. If the load is resonant in nature, such as in electronic ballasts and resonant mode power supplies, dead-time also helps maintain zero voltage switching (ZVS). Sometimes called soft switching, this technique significantly reduces switching losses.
- Cross-conduction will occur in half bridge circuits if both high and low side transistors are either fully or partially on at the same time. The resulting short across the supply exacerbates EMI, increases dissipation and may destroy power switches, the control IC, or both if extreme. MOSFET turn on/off times are often inequal and vary in production, so dead-time offers a guard band to account for these differences. To prevent cross conduction, or shoot-through, the IR2153 is available with various dead time options. Moreover, switching times can be easily modified using small signal diodes across series resistors in the gate drive loop if necessary.
- When the load is inductive or resonant, circuit efficiency is generally highest when zero voltage switching (ZVS or soft switching) occurs. In ZVS, there is just enough time when both FETs are off (approximately equal to the dead-time) to allow load energy to swing the output to the opposite rail, where current will flow into the FET body drain diode. This desirable process is called self-commutation.
- Soft switching (ZVS) is more efficient than hard switching. MOSFETSs become hot when the load is removed.
- Self-commuation is almost completely lossless because output capacitance of the half bridge rings with the inductive component of the load when both half bridge transistors are off. When the next transistor turns on, the voltage across it is already at or close to zero, so its internal capacitance is already discharged. When its load is not resonant or inductive in nature, the output cannot self-commute to the opposite rail during off time, so the voltage across the next transistor to turn on is high. It must therefore discharge its own output capacitance in addition to providing load current. This explains why half bridge transistors often get hot when there is no load at all, or in ballasts when the lamp is removed and the oscillator is allowed to continue running.
- If ZVS is required but the dead-time is too short, there is insufficient time for the half-bridge output voltage to completely self-commutate to the opposite rail. This leaves a fraction of the bus voltage remaining across the output capacitance of both transistors which the next transistor to switch on must discharge. This is partial hard switching (or partial soft switching). Conversely, if the dead-time is too long, the output voltage will self-commutate to the opposite rail, but a short time later, the load current will reverse or ring, producing a voltage transient. Again, the results is partial hard switching and less than optimal switching efficiency. For ZVS, optimal dead time occurs when there is just enough time for self commutation to occur. IR2153 is available with several dead-time options to help meet this requirement. If further adjustments are necessary, small signal diodes can be used in the gate drive loop to independently change charge/discharge timing.
- IR2153 output buffers also have a reduced di/dt output stage. This means that the peak rate of change of current (rate of current rise and fall for turn-on and turn-off) has been deliberately reduced. In effect the IR2153 output buffers are turned on and off at a controlled rate.
- Benefits of reduced di/dt output buffers include lower gate ringing (Vgs overshoot/undershoot) from a combination of di/dt and gate circuit parasitics. In some cases gate resistors can be eliminated altogether, however this depends on several factors such as layout and transistor type used. Rf interference may also be reduced.
- The invention provides improvements in the type of self-oscillating full-bridge driver described above, and more particularly provides a bootstrap circuit in a driver IC, which may include a circuit for pre-charging a bootstrap capacitor before starting up the oscillator.
- According to a general aspect, the invention relates to an integrated control circuit for controlling switching devices arranged in a full bridge for supplying power to a load, comprising: a pair of high-side drivers in the integrated circuit for controlling respective high-side switching devices in the full bridge, the high-side drivers each having a respective high side control terminal for supplying control signals to the corresponding high-side switching device; a pair of low-side drivers in the integrated circuit for controlling respective low-side switching devices in the full bridge; the low-side drivers each having a respective low-side control terminal for supplying control signals to the corresponding low-side switching device; and an oscillator and timing circuits in the integrated circuit supplying control signals for controlling the high- and low-side drivers.
- According to another aspect of the invention, a control circuit and method for controlling switching devices for supplying power to a load may comprise a high-side driver for controlling a high-side switching device and a low-side driver for controlling a low-side switching device; said high-side driver having a high-side floating supply terminal and a high-side floating supply return terminal; and a precharging circuit connected to said high-side driver. The precharging circuit may include a bootstrap capacitor connected between the high-side floating supply and floating supply return terminals for contributing power to the high-side driver, and a bootstrap circuit connected to said high-side floating supply terminal for supplying current to charge the bootstrap capacitor.
- The invention further may include a method or apparatus in which a timing circuit delivers drive signals to said high-side driver to cause said high-side driver to drive said high-side switching device, and the timing circuit further controls the precharging circuit so that the high-side driver is powered, possibly by charging a bootstrap capacitor, before the high-side driver receives the drive signals.
- To carry out these functions, according to a disclosed embodiment of the invention, a bootstrap precharging circuit briefly switches on both of the low-side outputs LO1 and LO2 to allow bootstrap capacitors to fully charge, advantageously before the oscillator starts up. Precharging the bootstrap capacitors helps avoid missing high-side pulses at start up. This feature is incorporated for example in the IRS2453D Self-Oscillating Full-Bridge Driver IC manufactured by International Rectifier.
- The IRS2453D is based on the IR2153 self-oscillating half-bridge gate driver IC described above, and incorporates a high voltage full-bridge gate driver with a front end oscillator similar to the industry standard 555 CMOS timer. HVIC and latch immune CMOS technologies enable ruggedized monolithic construction. The output driver features a high pulse current buffer stage designed for minimum driver cross-conduction. Noise immunity is achieved with low di/dt peak of the gate drivers, and with an undervoltage lockout hysteresis greater than 1V. The IRS2453D also includes latched and non-latched shutdown pins.
- Other features of the product are:
-
- Integrated 600V Full-Bridge Gate Driver;
- CT, RT programmable oscillator;
- 15.6V Zener Clamp on VCC;
- Micropower Startup;
- Logic Level Latched Shutdown Pin;
- Non-latched shutdown on CT pin (⅙th VCC);
- Internal bootstrap FETs;
- Latch Immunity on All Inputs & Outputs;
- ESD Protection on All Pins;
- 14-lead SOIC or PDIP package;
- 1.2 μsec (typical) internal deadtime.
- These and other features will be described in the following detailed description of embodiments of the invention, with reference to the drawings.
-
FIG. 1 is a functional block diagram of the prior art IR2153 chip. -
FIG. 2 is a functional block diagram of the IR2453D chip incorporating an embodiment of the invention. -
FIG. 3 is a typical connection diagram. -
FIG. 4 is a diagram showing lead assignments. -
FIG. 5 is a table showing lead definitions. -
FIG. 6 is a diagram showing the timing of signals in the IR2453D. -
FIG. 7 is a diagram showing the timing of certain signals shown inFIG. 6 at start-up. -
FIGS. 8A and 8B show respectively a deadtime waveform and a rise and fall time waveform. - Under-voltage Lock-Out Mode (UVLO)
- The under-voltage lockout mode (UVLO) is defined as the state the IC is in when VCC is below the turn-on threshold of the IC. The IRS2453D under-voltage lock-out is designed to maintain an ultra low supply current of less than 150 μA, and to guarantee the IC is fully functional before the high and low side output drivers are activated. During under voltage lock-out mode, the high-side and low-side driver outputs LO1, LO2, HO1, HO2 are all low. With VCC above the VCCUV+ threshold, the IC turns on and the output begin to oscillate.
- Normal Timing/Normal operating mode (
FIG. 6 ) - Once VCC reaches the start-up threshold VCCUV+, the MOSFET M1 opens, VRT increases to approximately VCC (VCC−VRT+) and the external CT capacitor starts charging. Once the CT voltage reaches VCT− (about ⅓ of VCC), established by an internal resistor ladder (R, R, R/2, R/2), LO1 and HO2 turn on with a delay equivalent to the deadtime td. Once the CT voltage reaches VCT+ (approximately ⅔ of VCC), LO1 and HO2 go low, RT goes down to approximately ground (VRT−), the CT capacitor starts discharging and the deadtime circuit is activated. At the end of the deadtime, LO2 and HO1 go high. Once the CT voltage reaches VCT−, LO2 and HO1 go low, RT goes to high again, and the deadtime is activated. At the end of the deadtime, LO1 and HO2 go high and the cycle starts over again.
- The following equation provides the oscillator frequency:
- Start-up Timing/Bootstrap MOSFET (
FIG. 7 ) - The internal bootstrap FETs (MBOOT1, MBOOT2) and supply capacitors (CBOOT1 and CBOOT2) comprise the supply voltage (VB1, VB2) for the high side driver circuitry. The internal boostrap FET only turns on when the corresponding LO is high. To guarantee that the high-side supply is charged up before the first pulse on HO1 and HO2, LO1 and LO2 are both on when CT ramps between ⅙*VCC and ⅓*VCC.
- As shown in
FIG. 7 , at start-up, LO1 and LO2 are both high while CT is between ⅙ and ⅓ of VCC, allowing the internal bootstrap MOSFETs MBOOT1 and MBOOT2 connected to VB1 and VB2 to precharge the respective bootstrap capacitors CBOOT1 and CBOOT2. - Non-Latched Shutdown
- If CT is pulled down below VCTSD (approximately ⅙ of VCC) by an external circuit, CT does not charge up and oscillation stops. All outputs are held low and the bootstrap FETs are off. Oscillation will resume once CT is able to charge up again to VCT−.
- Latched Shutdown
- When the SD pin is brought above 2V, the IC goes into fault mode and all outputs are low. VCC has to be recycled below VCCUV− to restart the IC. The SD pin can be used for over-current or over-voltage protection, for example, using appropriate external circuitry.
- Although the present invention has been described in relation to particular embodiments thereof, many other variations and modifications and other uses will become apparent to those skilled in the art. Therefore, the present invention is not limited by the specific disclosure herein.
Claims (13)
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US11/099,818 US7190208B2 (en) | 2004-04-08 | 2005-04-06 | Self-oscillating full bridge driver IC |
DE102005015990A DE102005015990A1 (en) | 2004-04-08 | 2005-04-07 | Self-oscillating full-bridge driver IC |
JP2005111160A JP2005354666A (en) | 2004-04-08 | 2005-04-07 | Self-oscillation full-bridge driver integrated circuit |
JP2008166396A JP2009033736A (en) | 2004-04-08 | 2008-06-25 | Self-oscillating full bridge driver ic |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US56087604P | 2004-04-08 | 2004-04-08 | |
US11/099,818 US7190208B2 (en) | 2004-04-08 | 2005-04-06 | Self-oscillating full bridge driver IC |
Publications (2)
Publication Number | Publication Date |
---|---|
US20050225374A1 true US20050225374A1 (en) | 2005-10-13 |
US7190208B2 US7190208B2 (en) | 2007-03-13 |
Family
ID=35059988
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US11/099,818 Active 2025-04-11 US7190208B2 (en) | 2004-04-08 | 2005-04-06 | Self-oscillating full bridge driver IC |
Country Status (3)
Country | Link |
---|---|
US (1) | US7190208B2 (en) |
JP (2) | JP2005354666A (en) |
DE (1) | DE102005015990A1 (en) |
Cited By (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20070176855A1 (en) * | 2006-01-31 | 2007-08-02 | International Rectifier Corporation | Diagnostic/protective high voltage gate driver ic (hvic) for pdp |
EP1887838A1 (en) * | 2006-08-09 | 2008-02-13 | Cheng-Lung Ku | Lamp driving circuit with floating power supply driver |
EP2237406A1 (en) * | 2009-04-02 | 2010-10-06 | Vacon Oyj | Frequency converter start-up |
US8456867B1 (en) | 2011-12-01 | 2013-06-04 | Telefonaktiebolaget Lm Ericsson (Publ) | Start-up procedure for an isolated switched mode power supply |
US20170179841A1 (en) * | 2015-12-22 | 2017-06-22 | Thermatool Corp. | High Frequency Power Supply System with Closely Regulated Output for Heating a Workpiece |
WO2020143009A1 (en) * | 2019-01-11 | 2020-07-16 | 贵州航天林泉电机有限公司 | Bootstrap starting circuit for electric motor |
Families Citing this family (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5359918B2 (en) * | 2010-02-16 | 2013-12-04 | 三菱電機株式会社 | Semiconductor device |
US8923473B2 (en) * | 2010-09-02 | 2014-12-30 | Sharp Kabushiki Kaisha | Signal processing circuit, driver circuit, and display device |
KR101728550B1 (en) * | 2010-11-26 | 2017-04-19 | 엘지이노텍 주식회사 | Circuit for reducing electromagnetic interference noise |
KR101319789B1 (en) | 2010-12-23 | 2013-10-17 | 전남대학교산학협력단 | A switching device and a method for malfunction preventing of the same |
US9406457B2 (en) | 2011-05-19 | 2016-08-02 | Black & Decker Inc. | Electronic switching module for a power tool |
JP5754399B2 (en) * | 2012-03-13 | 2015-07-29 | 三菱電機株式会社 | Semiconductor device driving apparatus |
JP5903635B2 (en) * | 2012-11-28 | 2016-04-13 | パナソニックIpマネジメント株式会社 | Discharge lamp lighting device and headlamp using the same |
US10608501B2 (en) | 2017-05-24 | 2020-03-31 | Black & Decker Inc. | Variable-speed input unit having segmented pads for a power tool |
DE102017125726A1 (en) | 2017-11-03 | 2019-05-09 | Infineon Technologies Austria Ag | Electronic circuit with undervoltage cut-off function |
Citations (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4042838A (en) * | 1976-07-28 | 1977-08-16 | Rockwell International Corporation | MOS inverting power driver circuit |
US5625548A (en) * | 1994-08-10 | 1997-04-29 | American Superconductor Corporation | Control circuit for cryogenically-cooled power electronics employed in power conversion systems |
US5963066A (en) * | 1997-03-31 | 1999-10-05 | Mitsubishi Denki Kabushiki Kaisha | Semiconductor device which drives low-voltage driven switching device, using low-voltage direct current power source, a diode and a capacitor |
US6038142A (en) * | 1998-06-10 | 2000-03-14 | Lucent Technologies, Inc. | Full-bridge isolated Current Fed converter with active clamp |
US6900600B2 (en) * | 1998-12-11 | 2005-05-31 | Monolithic Power Systems, Inc. | Method for starting a discharge lamp using high energy initial pulse |
US6982886B2 (en) * | 2002-12-25 | 2006-01-03 | Rohm Co., Ltd | Dc-ac converter parallel operation system and controller ic therefor |
Family Cites Families (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0750627B2 (en) | 1988-05-16 | 1995-05-31 | 日本特殊陶業株式会社 | Method for manufacturing spark plug for internal combustion engine |
JPH0249388U (en) * | 1988-09-29 | 1990-04-05 | ||
US5545955A (en) | 1994-03-04 | 1996-08-13 | International Rectifier Corporation | MOS gate driver for ballast circuits |
KR100454278B1 (en) * | 2000-06-19 | 2004-10-26 | 인터내쇼널 렉티파이어 코포레이션 | Ballast control ic with minimal internal and external components |
-
2005
- 2005-04-06 US US11/099,818 patent/US7190208B2/en active Active
- 2005-04-07 DE DE102005015990A patent/DE102005015990A1/en not_active Withdrawn
- 2005-04-07 JP JP2005111160A patent/JP2005354666A/en active Pending
-
2008
- 2008-06-25 JP JP2008166396A patent/JP2009033736A/en active Pending
Patent Citations (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4042838A (en) * | 1976-07-28 | 1977-08-16 | Rockwell International Corporation | MOS inverting power driver circuit |
US5625548A (en) * | 1994-08-10 | 1997-04-29 | American Superconductor Corporation | Control circuit for cryogenically-cooled power electronics employed in power conversion systems |
US5963066A (en) * | 1997-03-31 | 1999-10-05 | Mitsubishi Denki Kabushiki Kaisha | Semiconductor device which drives low-voltage driven switching device, using low-voltage direct current power source, a diode and a capacitor |
US6038142A (en) * | 1998-06-10 | 2000-03-14 | Lucent Technologies, Inc. | Full-bridge isolated Current Fed converter with active clamp |
US6900600B2 (en) * | 1998-12-11 | 2005-05-31 | Monolithic Power Systems, Inc. | Method for starting a discharge lamp using high energy initial pulse |
US6982886B2 (en) * | 2002-12-25 | 2006-01-03 | Rohm Co., Ltd | Dc-ac converter parallel operation system and controller ic therefor |
Cited By (11)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20070176855A1 (en) * | 2006-01-31 | 2007-08-02 | International Rectifier Corporation | Diagnostic/protective high voltage gate driver ic (hvic) for pdp |
EP1887838A1 (en) * | 2006-08-09 | 2008-02-13 | Cheng-Lung Ku | Lamp driving circuit with floating power supply driver |
EP2237406A1 (en) * | 2009-04-02 | 2010-10-06 | Vacon Oyj | Frequency converter start-up |
US20100253256A1 (en) * | 2009-04-02 | 2010-10-07 | Vacon Oyj | Frequency converter start-up |
US8350506B2 (en) | 2009-04-02 | 2013-01-08 | Vacon Oyj | Frequency converter start-up |
US8456867B1 (en) | 2011-12-01 | 2013-06-04 | Telefonaktiebolaget Lm Ericsson (Publ) | Start-up procedure for an isolated switched mode power supply |
WO2013079111A1 (en) * | 2011-12-01 | 2013-06-06 | Telefonaktiebolaget L M Ericsson (Publ) | Start-up procedure for an isolated switched mode power supply |
CN103959626A (en) * | 2011-12-01 | 2014-07-30 | 瑞典爱立信有限公司 | Start-up procedure for an isolated switched mode power supply |
US20170179841A1 (en) * | 2015-12-22 | 2017-06-22 | Thermatool Corp. | High Frequency Power Supply System with Closely Regulated Output for Heating a Workpiece |
US10855194B2 (en) * | 2015-12-22 | 2020-12-01 | Thermatool Corp. | High frequency power supply system with closely regulated output for heating a workpiece |
WO2020143009A1 (en) * | 2019-01-11 | 2020-07-16 | 贵州航天林泉电机有限公司 | Bootstrap starting circuit for electric motor |
Also Published As
Publication number | Publication date |
---|---|
JP2005354666A (en) | 2005-12-22 |
DE102005015990A1 (en) | 2006-03-02 |
JP2009033736A (en) | 2009-02-12 |
US7190208B2 (en) | 2007-03-13 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US7190208B2 (en) | Self-oscillating full bridge driver IC | |
KR101202204B1 (en) | Power mosfet driver and method therefor | |
US6781422B1 (en) | Capacitive high-side switch driver for a power converter | |
US7551004B2 (en) | Inverter apparatus with improved gate drive for power MOSFET | |
US7602229B2 (en) | High frequency control of a semiconductor switch | |
JP4436329B2 (en) | Isolated gate driver circuit for power switching devices | |
US7307462B2 (en) | Self-oscillating driver with soft start circuit | |
US7692474B2 (en) | Control circuit for a high-side semiconductor switch for switching a supply voltage | |
US7859138B2 (en) | Drive circuit | |
US6674268B2 (en) | Swithing regulator utilizing seperate integrated circuits for driving each switch | |
US8724352B2 (en) | Power supply apparatus driving circuit, power supply apparatus driving integrated circuit, and power supply apparatus | |
WO2000025424A1 (en) | Level shifter | |
JP3937354B2 (en) | Bootstrap diode emulator with dynamic backgate bias and short-circuit protection | |
JPH09298871A (en) | Back regulator circuit | |
US5754065A (en) | Driving scheme for a bridge transistor | |
JP2004112987A (en) | Power converter | |
JP2005143282A (en) | Step-down pwm converter | |
US20240204777A1 (en) | Semiconductor device | |
Trivedi | Design of a driver IC-IR2110 for mosfet in half bridge drive | |
US12021517B2 (en) | Gate driver with feed forward control of gate current | |
US20240088888A1 (en) | Gate drive circuit for switching circuit, module including the same, and switching power supply |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
AS | Assignment |
Owner name: INTERNATIONAL RECTIFIER CORPORATION, CALIFORNIA Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:RIBARICH, THOMAS J.;GREEN, PETER;REEL/FRAME:016591/0976 Effective date: 20050408 |
|
STCF | Information on status: patent grant |
Free format text: PATENTED CASE |
|
FPAY | Fee payment |
Year of fee payment: 4 |
|
FPAY | Fee payment |
Year of fee payment: 8 |
|
AS | Assignment |
Owner name: INFINEON TECHNOLOGIES AMERICAS CORP., CALIFORNIA Free format text: CHANGE OF NAME;ASSIGNOR:INTERNATIONAL RECTIFIER CORPORATION;REEL/FRAME:046612/0968 Effective date: 20151001 |
|
MAFP | Maintenance fee payment |
Free format text: PAYMENT OF MAINTENANCE FEE, 12TH YEAR, LARGE ENTITY (ORIGINAL EVENT CODE: M1553); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY Year of fee payment: 12 |