US20050048933A1 - Adaptive transmit diversity with quadrant phase constraining feedback - Google Patents

Adaptive transmit diversity with quadrant phase constraining feedback Download PDF

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US20050048933A1
US20050048933A1 US10/720,596 US72059603A US2005048933A1 US 20050048933 A1 US20050048933 A1 US 20050048933A1 US 72059603 A US72059603 A US 72059603A US 2005048933 A1 US2005048933 A1 US 2005048933A1
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transmit antennas
feedback information
transmit
phase
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Jingxian Wu
Jinyun Zhang
Andreas Molisch
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Mitsubishi Electric Research Laboratories Inc
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Mitsubishi Electric Research Laboratories Inc
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Assigned to MITSUBISHI ELECTRIC RESEARCH LABORATORIES, INC. reassignment MITSUBISHI ELECTRIC RESEARCH LABORATORIES, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: WU, JINGXIAN
Priority to JP2004326528A priority patent/JP2005176325A/ja
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0621—Feedback content
    • H04B7/0626—Channel coefficients, e.g. channel state information [CSI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
    • H04B7/0658—Feedback reduction
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H04L1/0675—Space-time coding characterised by the signaling
    • H04L1/0693—Partial feedback, e.g. partial channel state information [CSI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0667—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal
    • H04B7/0669—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal using different channel coding between antennas

Definitions

  • This invention relates generally to transmit diversity gain in wireless communications networks, and more particularly to maximizing the diversity gain adaptively in transmitters.
  • HSDPA high speed downlink packet access
  • WCDMA wideband code-division multiple access
  • EDGE enhance data rate for GSM evolution
  • 3GPP TR25.848 v4.0.0 3GPP technical report: Physical layer aspects of ultra high speed downlink packet access,” March 2001, and ETSI.
  • GSM 05.05 “Radio transmission and reception,” ETSI EN 300 910 V8.5.1, November 2000.
  • Antenna diversity can increase the data rate. Antenna diversity effectively combats adverse effects of multipath fading in channels by providing multiple replicas of the transmitted signal at the receiver. Due to the limited size and cost of a typical end user device, e.g., a cellular telephone or handheld computer, downlink transmissions favor transmit diversity over receiver diversity.
  • Space-time trellis coding exploits the full potential of multiple antennas by striving to maximize both the diversity gains and coding gains of the system. Better performance is achieved at the cost of relatively higher encoding and decoding complexity.
  • System performance can be further improved when some channel information is available at the transmitter from feedback information from the receiver. Those systems are classified as having closed loop transmit diversity.
  • the feedback information can be utilized in transmit diversity systems to maximize the gain in the receiver, see Jongren et al., “Combining beamforming and orthogonal space-time block coding,” IEEE Trans. Info. Theory , vol.48, pp.611-627, March 2002, Zhou et al., “Optimal transmitter eigen-beamforming and space-time block coding based on channel mean feedback,” IEEE Trans. Signal Processing , vol. 50, pp.2599-2613, October 2002, Rohani et al., “A comparison of base station transmit diversity methods for third generation cellular standards,” Porc. IEEE Veh. Techno. Conf.
  • the space-time block coding can be combined with linear optimum beamforming.
  • Linear encoding matrices can be optimized based on the feedback information of the fading channels.
  • Transmit adaptive array (TxAA) is another close loop transmit diversity system with the transmitted symbols encoded only in the space domain. Increased performance can be achieved, provided the fading channel vector is known to the transmitter.
  • the concept of space encoded transmit diversity can be generalized as maximal ratio transmission (MRT).
  • All of the above closed loop systems require the feedback information to be M ⁇ N complex-valued matrices, where M and N are respectively the number of antennas at the transmitter and receiver.
  • the matrix elements are either the channel impulse response (CIR), or statistics of the CIR, e.g., mean or covariance. Because the feedback matrices contain 2MN real-valued scalars, considerable bandwidth is consumed by the feedback information in the reverse link from the receiver to the transmitter.
  • Adaptive space-time block coding uses a real-valued vector made up of power ratios of the fading channels as feedback information. There, the feedback information is used to adjust the power of each transmission antenna. That technique still consumes a large number of bits.
  • the invention provides an adaptive transmit diversity scheme with simple feedback for a wireless communication systems.
  • the number of feedback bits is 2 (M ⁇ 1) bits. This is still significantly less than the number of bits required by most conventional closed loop transmit diversity techniques.
  • the amount of feedback information can be further reduced.
  • the amount of feedback can be as few as one and two bits, respectively.
  • the computational complexity of the invented method is much lower compared with optimum quantized TxAA closed loop technique with the same amount of feedback.
  • the method outperforms some closed loop transmit diversity techniques that have more information transmitted in the feedback channel.
  • FIG. 1 is a block diagram of a system with diversity gain according to the invention
  • FIG. 2 is a diagram of four quadrants of a coordinate system for indicating quadrant phase constraining according to the invention
  • FIG. 3 is a diagram of a normalized coordinate system with the phase of the reference signal on the x-axis of the coordinate system according to the invention.
  • FIG. 4 is a block diagram of a system combining orthogonal space time block code and quadrant phase constraining according to the invention.
  • FIG. 1 shows a baseband representation of a diversity system 100 according to our invention.
  • Our system has M antennas 101 at a transmitter 10 , for example, a base station, and one antenna 102 at a receiver 20 , e.g., a cellular telephone.
  • the space encoding vector p k 111 is determined 120 at the transmitter according to feedback information 121 determined from space decoding 130 of the received signal 105 at the receiver.
  • the feedback information 121 relates to phase differences between pairs of received signals in a fading transmission channel 115 . It is desired to minimize the phase difference between signals, so that diversity gain is maximized at the receiver. Furthermore, it is desired to minimize the number of bits required to indicate the phase difference. It is also desired to reduce the amount of computation involved generating the feedback information at the receiver 20 .
  • the received signal is a sum of the propagation signals from all the transmit antennas subject to the channel impulse responses, plus additive white Gaussian noise (AWGN) 104 with variance N 0 /2 per dimension.
  • E s is the sum of the transmit energy of all the transmit antennas
  • M is the number of antennas
  • z k is the additive noise 104 .
  • This scheme is called transmit adaptive array (TxAA).
  • TxAA transmit adaptive array
  • the set contains 2 b(M ⁇ 1) possible vectors for systems with b bits quantization and M transmit antennas.
  • the receiver In order to find the optimum quantized feedback vector ⁇ circumflex over (p) ⁇ k , the receiver must exhaustively determine the values of p k h k h k H p k H for all the possible 2 b(M ⁇ 1) encoding vectors before the optimum encoding vector can be selected.
  • the adaptive transmit diversity method uses a quadrant phase constraining method to determine the feedback information.
  • both the amount of feedback and computation complexity can be greatly reduced.
  • the present adaptive transmit diversity method is described first for the simplest system with two transmit antennas and one receive antenna.
  • exactly one bit of feedback information is required to generate the space encoding vector 111 used by the space encoding 110 .
  • it takes 2(M ⁇ 1) bits of feedback information to determine 120 the space encoding vector 111 .
  • b k [1, ( ⁇ 1) b k ], (4) where b k ⁇ 0, 1 ⁇ is the quantized binary feedback information 121 sent out from the receiver.
  • the bit is zero if the product of the CIR of one channel with the complex conjugate of the CIR of the other channel is positive, and one otherwise, and thus, the space encoding vector p 111 is either [1,1] or [1, ⁇ 1], respectively.
  • r ⁇ ( k ) E s 2 ⁇ [ h 1 ⁇ ( k ) + h 2 ⁇ ( k ) ⁇ ( - 1 ) b k ] ⁇ s k + z k . ( 6 )
  • the conventional diversity gain g is the same as the diversity gain of the orthogonal space-time block coding (STBC), while the feedback diversity gain g b is the extra diversity gain contributed by the binary feedback information 121 .
  • the process described above is for systems with two transmit antennas. If there are more than two antennas (M>2) at the transmitter, then a modified transmit diversity method with 2(M ⁇ 1) bits feedback information is used.
  • each q m (k) contains two bits of information, and there are a total of 2(M ⁇ 1) bits of feedback information used to form the space encoding vector P k .
  • the decision variable y(k) is obtained by multiplying the received sample r(k) with (p k h k ) H .
  • v k (p k h k ) H ⁇ z k is the noise component with variance
  • the conventional diversity gain g c is fixed for a certain value of M, while the feedback diversity gain is maximized by appropriately selecting the feedback information based on q m (k).
  • Equation (19) are positive when the following condition is satisfied
  • phase ⁇ 1 of the signal in the first sub-channel n 1 (k) unchanged.
  • the reference phase can be selected arbitrarily from any of the M transmit antennas, or the CIR with the highest power.
  • the goal is to make the phases difference between all the signals less than ⁇ 2 , or constraining all the shifted phases to a quadrant phase sector, i.e., a sector of 90 degrees.
  • the phases ⁇ m of the signals in all other sub-channels need to be rotated counter-clockwise at the transmitter q m ⁇ ( k ) 2 ⁇ ⁇ so that the absolute phase difference is less than 90 degrees.
  • the absolute phase difference is less than 90 degrees.
  • One method to fulfill the quadrant phase constraining condition is to put all the phases in the same coordinate quadrant as the reference phase.
  • FIG. 2 we label four quadrants I-IV of the Cartesian coordinate system for real (Re) and imaginary (Im) numbers.
  • the quadrant number of any angle ⁇ [0, 2 ⁇ ) is ⁇ 2 ⁇ ⁇ ⁇ ⁇ , where ⁇ ⁇ denotes rounding up to the nearest integer.
  • q m ⁇ ( k ) ⁇ 2 ⁇ ⁇ 1 ⁇ ⁇ - ⁇ 2 ⁇ ⁇ m ⁇ ⁇ . ( 21 )
  • the example 200 in FIG. 2 has ⁇ 1 in quadrant II, and ⁇ m in quadrant IV.
  • all the phases are put in a 90 degree sector 300 centered around the reference phase as shown in FIG. 3 .
  • We normalize all the phases with respect to the reference phase as follows ⁇ tilde over ( ⁇ ) ⁇ m ⁇ m ⁇ 1 +2l ⁇ , where the integer l is chosen such that the normalized phase ⁇ tilde over ( ⁇ ) ⁇ m is in the range of [0, 2 ⁇ ).
  • the normalized phase ⁇ tilde over ( ⁇ ) ⁇ m is rotated counter-clockwise by the angle of q m ⁇ ⁇ 2 , so that the rotated angle ⁇ ⁇ m + q m ⁇ ⁇ 2 is in the quadrant phase sector from [ ⁇ /4, ⁇ /4] of the coordinate system as shown in FIG. 3 .
  • the rotated phases are confined to the same quadrant phase sector, and the non-negativity of each summed element of the diversity gain g b can be guaranteed.
  • This method achieves the non-negativity of the feedback diversity gained by constraining all the rotated phases of the CIRs of one group of transmit antennas in a quadrant phase sector of ⁇ /2. Hence, we call it quadrant phase constraining method.
  • the method described above only involves the encoding process in the space domain.
  • the quadrant phase constraining feedback scheme is combined with orthogonal space-time block coding (STBC).
  • STBC space-time block coding
  • the time domain is also utilized in the encoding process.
  • Input symbols 401 are generated and modulated by conventional means.
  • the symbols are fed into an orthogonal STBC encoder 410 .
  • the energy of the modulation symbol is E(
  • 2 ) E s .
  • the input data symbols s 1 and s 2 are demultiplexed into multiple data streams, one for each group of transmit antennas.
  • the M transmit antennas are divided into multiple groups of transmit antennas 421 - 422 . Each group corresponds to one of the data streams d 1 , d 2 produced by the STBC encoder 410 .
  • Adaptive linear space encoders 431 - 432 are applied to each data stream 411 for each group of transmit antennas.
  • the space encoders 431 - 432 map the multiple data streams 411 to the groups of transmit antennas according to channel feedback information 440 for each group.
  • the received signals 461 are corrupted by both time-varying mulitpath fading and AWGN 462 .
  • a receiver 450 includes a space-time decoder 451 , a channel estimation module 452 , and a feedback computation unit 453 for generating the feedback information 440 for each group of transmit antennas.
  • the signals Rx 461 received by the receiver 450 are the sum of the propogational signals from all the transmit antennas plus the noise 462 .
  • r [r 1 ,r 2 ] T
  • the matrix H is an 2 ⁇ 2 orthogonal matrix, i.e., H H H ⁇ (
  • 2 )I 2 ⁇ N 0 , and N 0 E(
  • 2 ) ⁇ 0 , (33) where ⁇ 0 E s N 0 is the SNR without diversity. It can be seen from Equation (15) that the SNR ⁇ is a function of the space encoding vectors p 1 , p 2 and the CIR vectors h 1 , h 2 .
  • the optimum values of p 1 and p 2 can be obtained by exhaustive search of all the elements of W.
  • the size of the set W increases exponentially with the number of transmit antennas, therefore this optimum space encoding vector design method is inappropriate for systems with large number of transmit antennas.
  • M 1 M + 1 2
  • ⁇ M 2 M - 1 2 when M is an odd number.
  • each group has two transmit antennas at most.
  • our sub-optimum design criterion can be satisfied with only one bit of feedback information.
  • b k ⁇ 0,1 ⁇ is the feedback information for the k th antenna group.
  • 2 ) , ( 44 ) g 3 , b 2 3
  • Equations (46-48) evaluate the method according to the invention on a theoretical basis, and these equations can be used as a guide for designing wireless communication systems.
  • the transmit diversity method according to the invention can be used for systems with an arbitrary number of transmit antennas. This is extremely useful for a high speed downlink data transmission of next generation wireless communication systems, where higher diversity orders are required to guarantee high data throughput in the downlink with multiple transmit antennas and one receive antenna.
  • the method according to the invention outperforms conventional orthogonal STBC by up to 2 dB.
  • the performance of the version with two bits of feedback information is approximately 0.4 dB better than the version with one bit of feedback information.
  • the prior art full rate STTD and ASTTD systems can be implemented for systems with at most two transmit antennas.
  • our transmit diversity method can be used for systems with an arbitrary number of transmit antennas.
  • the performance of the method improves substantially linearly with the increasing number of transmit antennas.
  • Our method is very computationally efficient compared to the prior art optimum quantized method.
  • Our method requires only 0.3% computation efforts of the prior art optimum quantized feedback TxAA for systems with 4 transmit antennas. This computation saving is significant at the receiver, which is usually a battery powered cellular phone.
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