US20010046145A1 - Inductor current synthesizer for switching power supplies - Google Patents
Inductor current synthesizer for switching power supplies Download PDFInfo
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- US20010046145A1 US20010046145A1 US09/814,237 US81423701A US2001046145A1 US 20010046145 A1 US20010046145 A1 US 20010046145A1 US 81423701 A US81423701 A US 81423701A US 2001046145 A1 US2001046145 A1 US 2001046145A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01L—SEMICONDUCTOR DEVICES NOT COVERED BY CLASS H10
- H01L2924/00—Indexing scheme for arrangements or methods for connecting or disconnecting semiconductor or solid-state bodies as covered by H01L24/00
- H01L2924/19—Details of hybrid assemblies other than the semiconductor or other solid state devices to be connected
- H01L2924/1901—Structure
- H01L2924/1904—Component type
- H01L2924/19043—Component type being a resistor
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to current mode control of switching power supplies, particularly low voltage power supplies.
- the present invention in lieu of directly sensing the inductor current with a resistor, derives the inductor current by sensing the voltage drop across the synchronous MOSFET of the half-bridge and reconstructs the current using a sample and hold technique.
- a ripple current synthesizer is employed to reconstruct inductor current outside the sample and hold window.
- the sampled product I Load ⁇ R DSon is used to update the ripple current synthesizer with dc information every switching cycle.
- the resulting voltage waveform is directly proportional to the inductor current.
- the power converter may operate at constant switching frequency if desired.
- the synchronous MOSFET may be turned off after a brief sample period if desired.
- the inductor current synthesizer of the present invention can be used not only in a synchronous buck converter power supply, but also with boost converter, flyback converter and forward converter topologies.
- FIG. 1 shows a circuit schematic of the inductor current synthesizer circuit of the present invention.
- FIG. 2 shows a set of timing and control waveforms that illustrate the operation of the circuit the schematic of which is provided in FIG. 1.
- FIG. 3 shows a digital embodiment of the inductor current synthesizer of the present invention.
- FIGS. 4 a , 4 b and 4 c show common power circuit topologies in which the inductor current synthesizer of the present invention can employed.
- the inductor current synthesizer circuit of the present invention is identified generally by reference numeral 2 and comprises two major circuit blocks, namely a switching power supply dc load information converter 4 , and an inductor ripple current estimator 6 .
- Switching power supply dc load information converter 4 comprises inverting amplifier 10 and sample and hold switches 12 and 14 .
- Inductor ripple current estimator 6 comprises transconductance amplifier 16 , current slope synthesizer C slope , and control switch 18 .
- the current synthesizer circuit of the present invention can also be used in boost converter, flyback converter and forward converter topologies.
- a high drive pulse at UG (upper gate driver) turns MOSFET Q 1 on and a high drive pulse at LG (lower gate driver) turns MOSFET Q 2 on.
- Drive pulses UG and LG are complementary as shown in FIG. 2, waveforms 2 and 3 .
- the operation of the inductor current synthesizer of the present invention is as follows:
- Sample Period 1 (SH 1 ), which is the settling time period for inverting amplifier 10 , allows the transfer of switch node negative voltage V SW information expressed in equation (1) to inverting amplifier 10 .
- V SW ⁇ ( I Load ) ⁇ ( R dsonQ2 ) (1)
- Sample period SH 1 is adequate to allow inverting amplifier output 10 to settle before Sample Period 2.
- Inverting amplifier 10 amplifies the sampled portion of V SW by a factor required by current mode control system loop, and is denoted by Idc shown as waveform 6 in FIG. 2.
- the output Idc of inverting amplifier 10 is described by equation (2), where ⁇ K 10 is the gain of inverting amplifier 10 .
- I dc ⁇ K 10 ⁇ V SW (2)
- Sample Period 2 is initiated through closure of switch 14 by the dc update signal SH 2 as shown in waveform 5 of FIG. 2.
- the closure of switch 14 provides cycle-by-cycle update of dc information to C slope .
- ILsynth shown in waveform 7 of FIG. 2, experiences a slight correction of ramp voltage, which is indicative of the ILsynth signal being calibrated to Idc level through closure of switch 14 .
- the correction to ILsynth may be either positive, negative, or rarely, zero.
- the DC update signal SH 2 is held high throughout the Q 2 on time period.
- Waveform 8 of FIG. 2 shows the inductor voltage V L1 which can be calculated according to equation (3):
- V L1Q2 V out +I L1 ⁇ R dson (3)
- transconductance amplifier 16 provides a charging current to charge Cslope which can be derived from equations (4) through (9):
- V L1Q1 V in ⁇ V out (4)
- the i Cslope capacitor charging current is related to the inductor voltage V L1Q1 by the transconductance G m16 of amplifier 16 , and is represented by equation (6):
- i Cslope C slope ⁇ ⁇ v Cslope ⁇ t on ( 7 )
- the switch node settling period is the period when turn-off and recovery of Q 1 take place and Q 2 is in the turn-on process. It provides adequate switch node settling time before Period 1 is initiated.
- the inductor current synthesizer represented in FIG. 3 is the digital embodiment of the inductor current synthesizer circuit of the present invention.
- the digital embodiment consists of two major building blocks.
- the switching power supply dc load and accumulated error information converter 30 which comprises n-bit analog to digital converter 32 , two to one line selector 34 , and current accumulator 36 ; and
- Inductor ripple current estimator 38 which comprises n-bit analog to digital converters 40 and 42 , two to one line selector 44 , adder 46 , and scaling stage 48 .
- Inputs from both stages are added at adder 50 , and scaled in scaler 52 , the output of which is the digitally synthesized inductor current.
- the power stage is similar to the one described with respect to the first embodiment of the invention. It consists of Q 1 and Q 2 power MOSFETs, inductor L 1 , output capacitor C 1 and load R load .
- a high output UG turns Q 1 on and a high output LG turns Q 2 on.
- UG and LG are complementary drive pulses.
- Vout Output voltage of the synchronous regulator, in volts
- Vin Input voltage of the synchronous regulator, in volts
- Vsw Switching node voltage of the synchronous regulator, in volts
- HF Frequency of the high frequency clock in MHz
- L 1 inductance of L 1 inductor, in henries
- K 1 scaling factor, unitless
- K 2 scaling factor, unitless
- n number of Analog to Digital converter bits
- Sample period SH 1 is the period when the output of A/D converter 32 is allowed to settle. This includes the period of quantization of the analog information and the binary coding of the quantized input.
- Vsw(t) is digitized into n-bits by analog to digital converter 32 .
- V sw ( t ) ⁇ ⁇ nbits ⁇ Vsw ( 0 ) ⁇ ⁇ ... ⁇ ⁇ Vsw ( n )
- SH 2 is a timed signal that enables the output of A/D converter 32 to be transferred to the output of selector 34 during the on time of Q 2 .
- the digitized current information is supplied to current accumulator 36 via selector 34 selector during SH 2 .
- V sw ( t ) ⁇ ⁇ nbits ⁇ Vsw ( 0 ) ⁇ ⁇ ... ⁇ ⁇ Vsw ( n )
- K 1 in equation (12) indicates that it is independent of the input and the output voltages and is modified due to errors caused by variations in inductance of the inductor, the high frequency clock, and number of A/D converter bits.
- the selected data at the output of selector 34 is loaded to the current accumulator 36 at each occurrence of the high frequency clock HF.
- the accumulated data is fed to adder 50 .
- V sw ( t ) Vin converted to n-bits: V sw ( t ) ⁇ ⁇ nbits ⁇ Vsw ( 0 ) ⁇ ⁇ ... ⁇ ⁇ Vsw ( n )
- the inductor current up-slope and down-slope information is fed to adder 50 after being scaled by scaler 48 .
- the selected data at the output of selector 34 is loaded to the current accumulator 36 at each occurrence of the high frequency clock HF.
- the accumulated data is fed to adder 50 .
- Scaling factor K 2 at scaler 52 provides correction for changes for synchronous MOSFET Q 2 Rdson process variations and Rdson temperature variations.
- A/D converter 32 is 10 bits.
- A/D converters 40 and 42 are 8 bits.
- Switching frequency f s 300 Khz
- Switching period T s 3.33 microseconds
- Inductor L 1 800 nH HF
- Clock 10 MHz
- Q2 on resistance R dson 6 milliohms
- Inductor ripple current 5 A
- n 10 bits for A/D converter 32 and 8 bits for A/D converters 40 and 42 Input of A/D converter 32 when Q 2 is conducting is:
- V SW R dson ⁇ I L1 (1)
Abstract
Description
- This application claims the benefit of U.S. Provisional Application Ser. No. 60/190,926, filed Mar. 21, 2000, and U.S. Provisional Application Ser. No. 60/209,478, filed Jun. 5, 2000.
- 1. Field of Invention
- The present invention relates to current mode control of switching power supplies, particularly low voltage power supplies.
- 2. Description of Related Art
- Current mode power supplies, such as the synchronous buck converter shown in FIG. 1, typically use a resistive element to sense current. This method has the drawback of causing additional circuit losses, and the sense resistor occupies space. Accordingly, it would be desirable to provide a current mode power supply which does not require a resistive element for sensing inductor current.
- The present invention, in lieu of directly sensing the inductor current with a resistor, derives the inductor current by sensing the voltage drop across the synchronous MOSFET of the half-bridge and reconstructs the current using a sample and hold technique. A ripple current synthesizer is employed to reconstruct inductor current outside the sample and hold window. The sampled product ILoad×RDSon is used to update the ripple current synthesizer with dc information every switching cycle. The resulting voltage waveform is directly proportional to the inductor current.
- The power converter may operate at constant switching frequency if desired. The synchronous MOSFET may be turned off after a brief sample period if desired. The inductor current synthesizer of the present invention can be used not only in a synchronous buck converter power supply, but also with boost converter, flyback converter and forward converter topologies.
- Other features and advantages of the present invention will become apparent from the following description of the invention, which refers to the accompanying drawings.
- FIG. 1 shows a circuit schematic of the inductor current synthesizer circuit of the present invention.
- FIG. 2 shows a set of timing and control waveforms that illustrate the operation of the circuit the schematic of which is provided in FIG. 1.
- FIG. 3 shows a digital embodiment of the inductor current synthesizer of the present invention.
- FIGS. 4a, 4 b and 4 c show common power circuit topologies in which the inductor current synthesizer of the present invention can employed.
- Referring to FIG. 1, the inductor current synthesizer circuit of the present invention is identified generally by
reference numeral 2 and comprises two major circuit blocks, namely a switching power supply dcload information converter 4, and an inductor ripplecurrent estimator 6. - Switching power supply dc
load information converter 4 comprises invertingamplifier 10 and sample andhold switches current estimator 6 comprisestransconductance amplifier 16, current slope synthesizer Cslope, andcontrol switch 18. - The synchronous buck power stage in FIG. 1, which consists of power MOSFETs Q1 and Q2,
MOSFET driver 24, inductor L1, output capacitor C1 and Rload, is used to illustrate the operation of the current synthesizer circuit of the present invention. As shown in FIGS. 4a-4 c, the current synthesizer circuit of the present invention can also be used in boost converter, flyback converter and forward converter topologies. - In a conventional buck converter as shown in FIG. 1, a high drive pulse at UG (upper gate driver) turns MOSFET Q1 on and a high drive pulse at LG (lower gate driver) turns MOSFET Q2 on. Drive pulses UG and LG are complementary as shown in FIG. 2,
waveforms - Referring to FIG. 2, the operation of the inductor current synthesizer of the present invention is as follows:
- Sample Period 1 (SH1), which is the settling time period for inverting
amplifier 10, allows the transfer of switch node negative voltage VSW information expressed in equation (1) to invertingamplifier 10. - V SW=−(I Load)×(R dsonQ2) (1)
- Sample period SH1 is adequate to allow inverting
amplifier output 10 to settle beforeSample Period 2. Invertingamplifier 10 amplifies the sampled portion of VSW by a factor required by current mode control system loop, and is denoted by Idc shown aswaveform 6 in FIG. 2. The output Idc of invertingamplifier 10 is described by equation (2), where −K10 is the gain of invertingamplifier 10. - I dc =−K 10 ×V SW (2)
- After an appropriate delay from the application of SH1,
Sample Period 2 is initiated through closure ofswitch 14 by the dc update signal SH2 as shown inwaveform 5 of FIG. 2. The closure ofswitch 14 provides cycle-by-cycle update of dc information to Cslope. - ILsynth, shown in
waveform 7 of FIG. 2, experiences a slight correction of ramp voltage, which is indicative of the ILsynth signal being calibrated to Idc level through closure ofswitch 14. In practice, the correction to ILsynth may be either positive, negative, or rarely, zero. The DC update signal SH2 is held high throughout the Q2 on time period. - Waveform8 of FIG. 2 shows the inductor voltage VL1 which can be calculated according to equation (3):
- V L1Q2 =V out +I L1 ×R dson (3)
- As UG goes high, Q2 is turned off and Q1 is turned on and VSW approaches the input voltage and the inductor voltage becomes VL1Q1 as expressed in equation (4) and as shown in waveform 8 of FIG. 2. The output of
transconductance amplifier 16 provides a charging current to charge Cslope which can be derived from equations (4) through (9): - V L1Q1 =V in −V out (4)
-
- The iCslope capacitor charging current is related to the inductor voltage VL1Q1 by the transconductance Gm16 of
amplifier 16, and is represented by equation (6): - i Cslope =G m16 ×V L1Q1 (6)
-
- The change of inductor current diL1 is related to change in capacitor voltage dvCslope by scaling factor K and is represented in equation (8):
- di L1 =K×dV Cslope (8)
-
- The switch node settling period is the period when turn-off and recovery of Q1 take place and Q2 is in the turn-on process. It provides adequate switch node settling time before
Period 1 is initiated. - The inductor current synthesizer represented in FIG. 3 is the digital embodiment of the inductor current synthesizer circuit of the present invention.
- Similar to the analog counterpart shown in FIG. 1, the digital embodiment consists of two major building blocks.
- 1. The switching power supply dc load and accumulated
error information converter 30, which comprises n-bit analog todigital converter 32, two to oneline selector 34, andcurrent accumulator 36; and - 2. Inductor ripple
current estimator 38, which comprises n-bit analog todigital converters adder 46, and scalingstage 48. - Inputs from both stages are added at
adder 50, and scaled inscaler 52, the output of which is the digitally synthesized inductor current. - The power stage is similar to the one described with respect to the first embodiment of the invention. It consists of Q1 and Q2 power MOSFETs, inductor L1, output capacitor C1 and load Rload.
- As in a conventional buck converter, a high output UG turns Q1 on and a high output LG turns Q2 on. UG and LG are complementary drive pulses.
- The states of the inductor current digital synthesizer are described in the following table:
Sample Sample Ripple Ripple Period SH1 Period SH2 Discharge Period Charge Period UG Low Low Low High LG High High High Low SH1 High High Low Low SH2 High, delayed High Low Low wrt to SH1 - The operation of the inductor current digital synthesizer is described in the following paragraphs:
- In the following paragraphs, the notations used in the formulae are defined as:
- Vout: Output voltage of the synchronous regulator, in volts
- Vin: Input voltage of the synchronous regulator, in volts
- Vsw: Switching node voltage of the synchronous regulator, in volts
- ΔCountdis: Incremental count during discharge period, unitless
- ΔCountch: Incremental count during charge period, unitless
- HF: Frequency of the high frequency clock in MHz
- FS: Full scale voltage range, in volts
- L1: inductance of L1 inductor, in henries
- K1: scaling factor, unitless
- K2: scaling factor, unitless
- n: number of Analog to Digital converter bits
- Sample period SH1 is the period when the output of A/
D converter 32 is allowed to settle. This includes the period of quantization of the analog information and the binary coding of the quantized input. -
- During this period, the output of analog to
digital converter 32 is used to recalibrate the synthesized inductor current information atcurrent accumulator 36. - SH2 is a timed signal that enables the output of A/
D converter 32 to be transferred to the output ofselector 34 during the on time of Q2. Thus, the digitized current information is supplied tocurrent accumulator 36 viaselector 34 selector during SH2. - When Q2 is turned on, Logic Low inputs of selector 44 are selected. Therefore, the output of
adder 46 is the complemented value of the output voltage. -
- and is complemented at inverter45 because during this period the inductor voltage is −Vout.
- The output of selector44 steers the logic low inputs to adder 46.
-
-
- The expression for K1 in equation (12) indicates that it is independent of the input and the output voltages and is modified due to errors caused by variations in inductance of the inductor, the high frequency clock, and number of A/D converter bits.
- During this period, the selected data at the output of
selector 34 is loaded to thecurrent accumulator 36 at each occurrence of the high frequency clock HF. The accumulated data is fed to adder 50. - When Q1 is turned on, the quantized input voltage Vin at the output of n-bit A/
D converter 40 is selected by two to one line selector 44. The output of selector 44 is provided to one of the inputs ofadder 46. The data at the output ofadder 46 is the digital representation of Vin−Vout. -
- The output of selector44 steers the digitized Vin inputs to adder 46. During this period, the inductor voltage will be Vin−Vout.
-
- Through a similar exercise, one can demonstrate that the expression obtained for K1 in ripple charge period is identical to the one obtained in the ripple discharge period, which is independent of Vin and Vout.
- The inductor current up-slope and down-slope information is fed to adder50 after being scaled by
scaler 48. - During this period, the selected data at the output of
selector 34 is loaded to thecurrent accumulator 36 at each occurrence of the high frequency clock HF. The accumulated data is fed to adder 50. - Scaling factor K2 at
scaler 52 provides correction for changes for synchronous MOSFET Q2 Rdson process variations and Rdson temperature variations. - Assume A/
D converter 32 is 10 bits. A/D converters Switching frequency fs: 300 Khz, Switching period Ts: 3.33 microseconds Inductor L1: 800 nH HF Clock: 10 MHz, Q2 on resistance Rdson: 6 milliohms Input voltage Vin: 20 Volts Output voltage Vout: 1.3 Volts IL1 = 20 A Inductor ripple current: 5 A - n: 10 bits for A/
D converter 32 and 8 bits for A/D converters D converter 32 when Q2 is conducting is: - V SW =R dson ×I L1 (1)
- V SW=0.006*20 A=120 mV
-
- At the ripple generator, 25.5 volts Full Scale for an 8 bit A/D. Number of counts to maintain 5 A peak to peak ripple:
- C ripple=5 A×6 count/A=30 counts (2)
-
- Number of counts required to generate 5 A ripple
- C clk=Count/A×Count ch
- C clk=6×2.34=14.04 counts
-
- Although the present invention has been described in relation to particular embodiments thereof, many other variations and modifications and other uses will become apparent to those skilled in the art. It is preferred, therefore, that the present invention be limited not by the specific disclosure herein, but only by the appended claims.
Claims (19)
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US09/814,237 US6381159B2 (en) | 2000-03-21 | 2001-03-21 | Inductor current synthesizer for switching power supplies |
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DE10255357B4 (en) * | 2002-11-27 | 2009-12-10 | Texas Instruments Deutschland Gmbh | Gleichspanungswandlerschaltung and method for DC voltage conversion |
ATE394728T1 (en) | 2003-12-15 | 2008-05-15 | Dialog Semiconductor Gmbh | CURRENT MEASUREMENT CIRCUIT FOR DC TO DC DOWN CONVERTER |
US7372238B1 (en) * | 2004-04-29 | 2008-05-13 | National Semiconductor Corporation | Apparatus and method for step-down switching voltage regulation |
GB0413494D0 (en) * | 2004-06-16 | 2004-07-21 | Elantec Semiconductor Inc | Non-Leb restricted DC-DC converter |
EP1632827B1 (en) * | 2004-08-27 | 2007-05-23 | Infineon Technologies AG | Control circuit for current mode buck converter |
US7239117B2 (en) | 2005-01-06 | 2007-07-03 | Solomon Systech Limited | Programmable inductor current control for DC-DC converters |
TW200739335A (en) * | 2006-04-07 | 2007-10-16 | Sunplus Technology Co Ltd | Circuit emulation system having function of burning record |
US7593200B2 (en) * | 2006-08-15 | 2009-09-22 | International Rectifier Corporation | Buck converter fault detection method |
US7746042B2 (en) * | 2006-10-05 | 2010-06-29 | Advanced Analogic Technologies, Inc. | Low-noise DC/DC converter with controlled diode conduction |
US7812579B2 (en) * | 2006-12-30 | 2010-10-12 | Advanced Analogic Technologies, Inc. | High-efficiency DC/DC voltage converter including capacitive switching pre-converter and up inductive switching post-regulator |
US8749158B2 (en) * | 2007-02-26 | 2014-06-10 | Koninklijke Philips N.V. | Driving a lighting device |
US8729881B2 (en) | 2007-09-25 | 2014-05-20 | Alpha & Omega Semiconductor Ltd | Voltage/current control apparatus and method |
US7557554B2 (en) * | 2007-09-25 | 2009-07-07 | Alpha & Omega Semiconductor, Ltd | Voltage/current control apparatus and method |
EP2399335A2 (en) * | 2009-02-19 | 2011-12-28 | Koninklijke Philips Electronics N.V. | Output current sensing method in discontinuous dc-to-dc voltage converter |
GB0912745D0 (en) | 2009-07-22 | 2009-08-26 | Wolfson Microelectronics Plc | Improvements relating to DC-DC converters |
US8487598B2 (en) * | 2010-08-30 | 2013-07-16 | Texas Instruments Incorporated | DC-DC converter with unity-gain feedback amplifier driving bias transistor |
CN102243505B (en) * | 2011-07-07 | 2013-08-14 | 矽力杰半导体技术(杭州)有限公司 | Low-offset and fast-response voltage-controlled current source, control method and power circuit applying voltage-controlled current source |
US8866464B2 (en) * | 2011-12-15 | 2014-10-21 | Texas Instruments Incorporated | Systems and methods for real time current sense for a switching converter |
US9966855B2 (en) | 2011-12-15 | 2018-05-08 | Texas Instruments Incorporated | Systems and methods for real-time inductor current simulation for a switching converter |
US9035624B1 (en) * | 2011-12-27 | 2015-05-19 | International Rectifier Corporation | Power supply circuitry and current measurement |
US9502980B2 (en) * | 2011-12-27 | 2016-11-22 | Infineon Technologies Americas Corp. | Circuit and method for producing an average output inductor current indicator |
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US10193442B2 (en) | 2016-02-09 | 2019-01-29 | Faraday Semi, LLC | Chip embedded power converters |
US10243464B2 (en) * | 2017-04-06 | 2019-03-26 | Texas Instruments Incorporated | Power regulator with prevention of inductor current reversal |
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US10504848B1 (en) | 2019-02-19 | 2019-12-10 | Faraday Semi, Inc. | Chip embedded integrated voltage regulator |
US11069624B2 (en) | 2019-04-17 | 2021-07-20 | Faraday Semi, Inc. | Electrical devices and methods of manufacture |
US11005363B1 (en) | 2020-04-08 | 2021-05-11 | Delta Electronics (Thailand) Public Company Limited | Resonant power converter and current synthesizing method therefor |
CN111416519B (en) * | 2020-05-07 | 2021-06-22 | 矽力杰半导体技术(杭州)有限公司 | Inductive current reconstruction circuit, reconstruction method and power converter applying inductive current reconstruction circuit and reconstruction method |
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Family Cites Families (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4974141A (en) * | 1988-05-18 | 1990-11-27 | Viteq Corporation | AC to DC power converter with input current waveform control for buck-boost regualtion of output |
US5457624A (en) * | 1994-06-13 | 1995-10-10 | Texas Instruments Incorporated | Efficient switched mode power converter circuit and method |
US5773966A (en) | 1995-11-06 | 1998-06-30 | General Electric Company | Dual-mode, high-efficiency dc-dc converter useful for portable battery-operated equipment |
US5847554A (en) | 1997-06-13 | 1998-12-08 | Linear Technology Corporation | Synchronous switching regulator which employs switch voltage-drop for current sensing |
US6160388A (en) * | 1997-12-30 | 2000-12-12 | Texas Instruments Incorporated | Sensing of current in a synchronous-buck power stage |
US6246220B1 (en) * | 1999-09-01 | 2001-06-12 | Intersil Corporation | Synchronous-rectified DC to DC converter with improved current sensing |
US6166528A (en) | 1999-11-02 | 2000-12-26 | Fairchild Semiconductor Corporation | Lossless current sensing in buck converters working with low duty cycles and high clock frequencies |
-
2001
- 2001-03-20 TW TW090106515A patent/TW512578B/en not_active IP Right Cessation
- 2001-03-21 US US09/814,237 patent/US6381159B2/en not_active Expired - Lifetime
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