TWM522514U - Power conversion system - Google Patents

Abstract

A power conversion system includes an isolating transformer, a resonant module, a switching module, and an output-controlling device. The isolating transformer includes a primary winding and a plurality of secondary windings, wherein the transformer has a least one coupling distance between the secondary windings and the primary winding. The resonant module is electrically connected to the primary winding and the switching module. The output-controlling device includes a controller and a plurality of output-controlling modules, wherein each one of the secondary windings is electrically connected to one of the output-controlling device. The controller makes at least one output-controlling device generate an operation power meeting the power required for an electric power.

Description

Electric energy conversion system

This creation relates to a power conversion system, and more particularly to a power conversion system that can vary the output power depending on the operating state of the electronic device.

The conventional rectifier circuit using a diode or a Schottky diode has a large forward voltage of the diode and the Schottky diode, so that the loss of the rectifier circuit becomes the main loss of the power converter. The metal oxide semiconductor field effect transistor has a low on-resistance, a short switching time, and a high input impedance, and is a preferred rectifying element for a low-voltage and high-current power converter. According to the control characteristics of the metal oxide semiconductor field effect transistor, Synchronous rectification technology is produced.

A conventional power converter having a plurality of sets of outputs includes a plurality of sets of synchronous rectifying units. When the electronic device is activated, the plurality of sets of synchronous rectifying units are simultaneously activated and output power to the electronic device. When the electronic device is turned off, the plurality of sets of synchronous rectification units are simultaneously turned off, and the output of the power is stopped to the electronic device. Although the control method of the synchronous rectification unit described above has the characteristics of simple control, regardless of whether the electronic device is operated in a light load or non-light load state, the power output from the power converter is constant, which makes the power converter light in the electronic device. The loss during load operation is increased.

The present invention provides a power conversion system that can change output power depending on an operating state of an electronic device.

According to the present invention, an electric energy conversion system is provided for providing a plurality of required electric power of an electronic device under different operating states. The power conversion system includes an isolation transformer, a resonance module, a switching module, and an output control device. The isolation transformer includes a primary winding and a plurality of secondary windings, each having a coupling distance from the secondary winding. The resonant module is electrically connected to the primary winding, and the switching module is electrically connected to the resonant module. The output control device comprises a controller and a plurality of output control modules, the controller is electrically connected to the output control module, and each of the output control modules is electrically connected to one of the secondary windings. The controller drives the at least one output control module synchronous rectification unit of the dynamic output control device to perform synchronous rectification according to the operating state of the electronic device, and outputs one of the required powers corresponding to one of the required powers.

The power conversion method of the present invention controls the synchronous rectification unit to perform synchronous rectification or the output switch is turned on or off through the controller to change the leakage inductance of the isolation transformer, and the power conversion system outputs the operation power corresponding to the different demand power.

10‧‧‧Full Bridge Switching Module

20‧‧‧Resonance Module

30‧‧‧Isolation transformer

310‧‧‧Primary winding

320a, 320b, 320c, 320d‧‧‧ secondary winding

330‧‧‧ Winding frame

340‧‧‧ magnetic core

40‧‧‧Output control module

400a~400d‧‧‧output control module

410a‧‧‧First Synchronous Rectifier

410b‧‧‧Second synchronous rectifier unit

410c‧‧‧3rd synchronous rectification unit

410d‧‧‧fourth synchronous rectification unit

420‧‧‧ Controller

C‧‧‧ capacitor

Cb‧‧‧ Isolated DC Capacitors

Co‧‧‧ output capacitor

Ip‧‧‧ primary side current

L1, L2, L3, L4, L5, L6, L7, L8‧‧‧ filters

Lr‧‧‧Resonant Inductors

QA‧‧‧First power switch

QB‧‧‧second power switch

QC‧‧‧ third power switch

QD‧‧‧fourth power switch

Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8‧‧‧ rectifier switch

S1, S2, S3, S4, SR1, SR2, SR3, SR4, SR5, SR6, SR7, SR8‧‧ ‧ gate

SW1, SW2, SW3, SW4‧‧‧ output switch

Vi‧‧‧ input voltage

Vo‧‧‧ output voltage

Vp‧‧‧ primary side voltage

VQ4‧‧‧fourth power switch 汲 source voltage across

1 is a circuit block diagram of a power conversion system according to a first embodiment of the present invention; FIG. 2 is a circuit diagram of a power conversion system according to a first embodiment of the present invention; and FIG. 3 is a diagram showing an output current of a power conversion system corresponding to the present invention. Switching timing diagram of the rectifier switch and the output switch; FIG. 4a and FIG. 4b illustrate the primary side current and voltage waveforms corresponding to the first to fourth power switch gate control signal poles of the power conversion system of the present invention; 5a and 5b illustrate the primary side current and voltage waveforms corresponding to the first to fourth power switch gate control signal poles of the power conversion system of the present invention; FIG. 6a and FIG. 6b illustrate the power supply of the present invention. The primary side current and voltage waveforms corresponding to the first to fourth power switch gate control signals at the full load of the conversion system; FIG. 7 is a cross-sectional view of the isolation transformer of the present invention; FIG. 8 is the first isolation transformer of the present invention. The leakage inductance and the magnetic flux density distribution diagram of the operating state; FIG. 9 is the leakage inductance and the magnetic flux density distribution diagram of the isolated transformer in the second operating state; FIG. 10 is the leakage of the isolated transformer in the third operating state. Sense and magnetic flux density map; and FIG. 11 is a circuit diagram of the power conversion system of the second embodiment of the present invention.

Please refer to FIG. 1 , which is a circuit block diagram of a power conversion system according to a first embodiment of the present invention. The power conversion system receives the input voltage Vi and generates a plurality of sets of output voltages Vo. In FIG. 1, the power conversion system includes an isolation transformer 30 divided into a primary side and a secondary side. The isolation transformer 30 includes a primary winding 310 and secondary windings 320a-320d. The primary side of the power conversion system includes a full bridge switching module 10, a resonant module 20, and a primary winding 310. The secondary side of the power conversion system includes an output control device 40 and secondary windings 320a-320d coupled to the primary winding 310, wherein The output control device 40 includes output control modules 400a-400d, and each of the output control modules 400a-400d includes a synchronous rectification unit (first to fourth synchronous rectification units 410a to 410d as shown in FIG. 1) and an output switch SW1~. SW4.

Referring to FIG. 2, a circuit diagram of the power conversion system of the first embodiment of the present invention is shown. The full-bridge switching module 10 is electrically connected to the input voltage Vi, and includes a first power switch QA, a second power switch QB, a third power switch QC, and a fourth power switch QD; the first to fourth power switches QA-QD are respectively Metal oxide semiconductor field effect transistor. The first power switch QA is connected to the drain of the third power switch QC to the input voltage Vi, the source of the first power switch QA is electrically connected to the drain of the second power switch QB and the resonant module 20, and the third power switch QC The source is electrically connected to the drain of the fourth power switch QD and the primary winding 310 of the isolation transformer 30. The sources of the second power switch QB and the fourth power switch QD are connected to the input voltage Vi.

As shown in FIG. 2, the first to fourth power switches QA~QD are respectively connected in parallel with the diode D, wherein the drains of the first to fourth power switches QA~QD are connected to the cathode of the diode D, first to the first The sources of the four power switches QA~QD are connected to the anode of the diode D; the diode D can be, for example, the body diode of the first to fourth power switches QA~QD. Further, the capacitor C is connected in parallel between the drain and the source of the first to fourth power switches QA to QD, and the capacitor C may be, for example, a parasitic capacitor inside the first to fourth power switches QA to QD.

The resonant module 20 includes a resonant inductor Lr, an isolated DC capacitor Cb, and a magnetizing inductor connected in series. In the present embodiment, the magnetizing inductor is implemented with the primary winding 310 of the isolation transformer 30. The resonant module 20 is configured to achieve the switching characteristics of the first to fourth power switches QA-QD to zero voltage, reduce switching losses and increase the efficiency of the power conversion system.

The output control device 40 includes first to fourth synchronous rectification units 410a to 410d and first to fourth output switches SW1 to SW4 corresponding to the secondary windings 320a-320d. Figure 1 and As shown in FIG. 2, the first synchronous rectifying unit 410a is connected to the secondary winding 320a and the first output switch SW1, the second synchronous rectifying unit 410b is connected to the secondary winding 320b and the second output switch SW2, and the third synchronous rectifying unit 410c is connected. The fourth synchronous rectifying unit 410d is connected to the secondary winding 320d and the fourth output switch SW4 to the secondary winding 320c and the third output switch SW3.

As shown in FIG. 2, the first synchronous rectification unit 410a includes rectification switches Q1, Q2, the second synchronous rectification unit 410b includes rectification switches Q3, Q4, and the third synchronous rectification unit 410c includes rectification switches Q5, Q6, and a fourth synchronous rectification unit. 410d includes rectifier switches Q7, Q8. The source of the rectifier switch Q1 is connected to the source of the rectifier switch Q2 and the output capacitor Co, and the drains of the rectifier switches Q1 and Q2 are electrically connected to the secondary winding 320a, respectively. The source of the rectifier switch Q3 is connected to the source of the rectifier switch Q4, and the drains of the rectifier switches Q3 and Q4 are electrically connected to the secondary winding 320b, respectively. The source of the rectifier switch Q5 is connected to the source of the rectifier switch Q6, and the drains of the rectifier switches Q5 and Q6 are electrically connected to the secondary winding 320c, respectively. The source of the rectifier switch Q7 is connected to the source of the rectifier switch Q8, and the drains of the rectifier switches Q7 and Q8 are electrically connected to the secondary winding 320d, respectively. The gates SR1 to SR8 of the rectifier switches Q1 to Q8 are electrically connected to the controller 420, respectively, and receive a control signal outputted by the controller 420 to perform a switching operation of turning on or off, thereby providing an effect of synchronous rectification.

The power conversion system can further include filters L1~L8. As shown in FIG. 2, the filters L1 to L8 are respectively inductors. The filter L1 and the filter L2 are connected to both ends of the secondary winding 320a and the output switch SW1. The filter L3 and the filter L4 are connected to both ends of the secondary winding 320b and the output switch SW2, and the filter L5 and the filter L6 are connected. At both ends of the secondary winding 320c and The output switch SW3, the filter L7 and the filter L8 are connected to both ends of the secondary winding 320d and the output switch SW4.

The first to fourth output switches SW1 to SW4 are turned off or turned on by the control of the controller 420, respectively. It should be particularly noted that the power conversion system of the present invention is mainly for providing a plurality of required powers of the electronic device under different operating states, so that the controller 420 drives at least at least one of the output control devices according to the operating state of the electronic device. An output control module 400a-400d outputs required power when the electronic device is operating. The controller 420 may select to allow the power conversion system to output the power required for the electronic device to operate by controlling the first to fourth synchronous rectification units 410a to 410d or the first to fourth output switches SW1 to SW4.

The resonant inductor Lr of the resonant module 20 and the isolating transformer 30 cooperate to provide a fixed leakage inductance. In order to generate resonance and complete zero voltage switching, there is a clear dead time between the control signals of the first power switch QA and the second power switch QB (or the third power switch QC and the fourth power switch QD). The so-called dead time is that during one switching cycle, the control circuit (not shown) causes the first power switch QA and the second power switch time QB (the third power switch QC and the fourth power switch QD) to be simultaneously turned off (turn) Off) the duration of the state (wherein the control circuit is electrically connected to the gates S1 to S4 of the first to fourth power switches QA to QD, and outputs a control signal to turn the first to fourth power switches QA to QD on or off) , as shown in Figure 4a, the time interval t2~t3 (t4~t5). In general, the greater the leakage inductance, the longer the dead time.

Please refer to FIG. 2 and FIG. 4a simultaneously, wherein FIG. 4a illustrates the primary side current and voltage waveforms of the power conversion system when the electronic device is operated at a light load (for example, 20% of full load). In the first shape State (ie, time t1 to t2 shown in FIG. 4a), the first power switch QA and the fourth power switch QD shown in FIG. 2 are turned off, and the second power switch QB and the third power switch QC are turned on (turn) On, the input voltage Vi is coupled to the secondary windings 320a-320d by the primary winding 310 via the second power switch QB, the third power switch QC, and the resonant capacitor Cb resonant inductor Lr. During this period, the primary side current (Ip) of the isolation transformer 30 rises slowly, and the resonant inductor Lr is simultaneously charged to store energy.

In the second state (ie, time t2 to t3 shown in FIG. 4a), the second power switch QB shown in FIG. 2 is turned off (the first power switch QA and the fourth power switch QD remain off, and the third power switch QC remains turned on). The primary side current (Ip) of the isolation transformer 30 stops rising. According to Lenz's law, the current of the resonant inductor Lr must be kept constant, so the current of the resonant inductor Lr continues to flow in the same direction. At this time, the primary side current (Ip) charges the capacitor C connected in parallel between the source of the second power switch QB汲, and discharges the capacitor C connected in parallel between the source of the first power switch QA汲 until the second power switch QB is connected in parallel. The voltage of the capacitor C between the source and the source is equal to the input voltage Vi.

At time t3 in the third state (ie, time t3~t4 shown in FIG. 4a), the zero voltage interval ends, at which time the source-to-voltage discharge of the first power switch QA drops to zero voltage, and then jumps over The diode D between the source of the first power switch QA and the source is turned on, and the source of the first power switch QA is clamped to zero voltage, so that the first power switch QA achieves zero voltage switching (Zero Voltage Switching, ZVS). ), thereby reducing switching losses. At the same time, the primary side voltage (Vp) of the isolation transformer 30 is zero.

In the fourth stage (ie, time t4~t5 shown in FIG. 4a), the resonance state begins with the third power switch QC being turned off (ie, time t4), because the current of the resonant inductor Lr must be maintained, the primary The side current (Ip) charges the capacitor C connected in parallel with the source of the third power switch QC汲, and discharges the capacitor C connected in parallel between the source of the fourth power switch QD汲 until the fourth power switch QC is connected in parallel. The voltage of the capacitor C between the poles is equal to the input voltage Vi, and the source-to-voltage discharge of the fourth power switch QD is reduced to zero voltage (as shown by the VQ4 curve).

At time t5 shown in FIG. 4a, the voltage across the capacitor C parallel to the source of the third power switch QC汲 is equal to the input voltage, and the voltage across the capacitor C across the source of the fourth power switch QD汲 is across. Zero, so that the diode D connected in parallel between the source of the fourth power switch QD汲 is turned on to complete the resonance. At the same time, after the diode D connected in parallel with the source of the fourth power switch QD汲 is turned on, the fourth power switch QD is turned on, and the voltage across the source of the fourth power switch QD汲 is zero potential, so the fourth power switch QD It switches to zero voltage.

In the fifth stage (i.e., time t5 to t7 shown in Fig. 4a), since the voltage across the resonant inductor Lr is the same as the input voltage Vi, the primary side current (Ip) decreases linearly. Wherein, at time t6, the primary side voltage (Vp) is not converted to a negative potential at the moment when the fourth power switch QD is turned on, and this section is called a duty cycle loss; wherein, the leakage inductance is greater , the greater the work cycle loss. It should be specially stated here that the work cycle loss can be expressed as follows: Where: Lr is the inductance of the resonant inductor; Ip is the primary side current of the power conversion system; and Vp is the primary side voltage of the power conversion system.

The power conversion system shown in FIG. 4a is a primary side current and voltage waveform when the supply electronic device operates at a light load (for example, 20% of full load), and FIG. 5a and FIG. 6a respectively illustrate the operation of the electronic device in the middle. Primary side current and voltage waveforms (eg, 50% of full load) and primary side current and voltage waveforms when the electronic device is operating at full load. It should be particularly noted that when the demand current of the electronic device increases and the current output from the power conversion system also increases correspondingly, the duty cycle loss increases due to the current increase. The aforementioned duty cycle loss reduces the hold-up time of the input voltage Vi, resulting in a decrease in the overall efficiency of the power conversion system.

In order to further reduce the duty cycle loss to improve the sorting efficiency of the power conversion system, the control method of the output control modules 400a to 400d of the output control device 40 must be further changed.

In general, the electronic device requires the most power during full load operation, so the current output from the power conversion system to the electronic device is also large; the electronic device requires minimal power during light load operation, so the power conversion system outputs to the electronic device. The current is relatively small.

The power conversion system of the present invention can adjust the operation mode of the synchronous rectification device 40 according to the current demanded by the electronic device, so that the power conversion system provides a large current when the electronic device is in full load operation, and when the electronic device operates at light load, Provides less current to reduce power consumption.

In one of the operational states of the present output control device, if the controller 420 determines whether the output power is synchronously rectified by the synchronous rectification units 410a to 410d in the output control modules 400a to 400d, the power conversion system includes The following four operating modes are available. Referring to FIG. 2, in the first operation mode, the controller 420 controls the rectifier switches Q1~Q8. The operating states of the gates SR1 to SR8 cause one of the first to fourth synchronous rectifying units 410a to 410d to perform synchronous rectification, and the power conversion system outputs the first current I1. Here, for example, the rectifier switches Q1 and Q2 can be synchronously rectified (as shown in the range of 0 to t1 in FIG. 3) by switching between on and off in accordance with a control signal output from the controller 420 to allow coupling to the secondary winding 320a. Power can be passed to the output.

In the second operation mode, the controller 420 controls the operation states of the gates SR1 to SR8 of the rectifier switches Q1 to Q8 to synchronously rectify the two of the first to fourth synchronous rectifier units 410a to 410d (as shown in FIG. 3). The interval between t1 and t2) causes the power conversion system to output a second current I2, wherein the second current I2 is greater than the first current I1.

In the third operation mode, the controller 420 controls the operation states of the gates SR1 to SR8 of the rectifier switches Q1 to Q8 to synchronously rectify the three of the first to fourth synchronous rectifier units 410a to 410d (see t2 in FIG. 3). The ~t3 interval shows that the power conversion system outputs a third current I3, wherein the third current I3 is greater than the second current I2.

In the fourth operation mode, the controller 420 controls the operation states of the gates SR1 to SR8 of the rectifier switches Q1 to Q8, so that the first to fourth synchronous rectification units 410a to 410d simultaneously perform synchronous rectification (such as the interval after t3 in FIG. 3). The power conversion system outputs a fourth current I4, wherein the fourth current I4 is greater than the third current I3. Figure 3 shows the switching timing diagram of the output current and rectifier switch of the power conversion system. The first to fourth synchronous rectifying units 410a to 410d are driven in sections according to the operation mode of the electronic device, which can effectively reduce the power loss of the power conversion system when the electronic device operates at a light load, thereby achieving an energy saving effect.

In one of the operational states of the present output control device, if the controller 420 is to control the first to fourth output switches of the output control modules 400a-400d When SW1~SW4 are synchronously turned on to determine the output power, the power conversion system includes the following four operation modes as an illustrative example. It should be particularly noted that, when operating in the four operation modes, the controller 420 causes the first to fourth synchronous rectification units 410a to 410d to perform synchronous rectification. Referring to FIG. 2 and FIG. 3, in the first operation mode, the controller 420 turns on the first output switch SW1, and causes the power conversion system to output the first current I1; in the second operation mode, the controller 420 makes the first output switch SW1. And the second output switch SW2 is turned on, and the power conversion system outputs the second current I2; in the third operation mode, the controller 420 turns on the first to third output switches SW1~SW3, and causes the power conversion system to output the third current I3; In the fourth mode of operation, the controller 420 turns on the first to fourth output switches SW1 SW SW4 to cause the power conversion system to output the fourth current I4.

Further, in conjunction with the arrangement of the primary winding 310 and the secondary windings 320a-320d of the isolation transformer 30, the overall power consumption can be more effectively controlled.

Please refer to FIG. 7, which is a cross-sectional view of the isolation transformer of the present invention. The isolation transformer 30 further includes a bobbin 330 and a magnetic core 340. The magnetic core 340 is sleeved on the periphery of the bobbin 330. The primary winding 310 and the secondary windings 320a-320d are respectively disposed on the bobbin 330. It should be noted that, in FIG. 7, the isolation transformer 30 includes a single primary winding 310 and four secondary windings 320a-320d, and the secondary windings 320a-320d are equally spaced on the bobbin 330, the primary winding. 310 is wound on the bobbin 330 and is located on one side (for example, the left side) of each of the secondary windings 320a to 320d, and is viewed from the side section of the isolation transformer 30, the primary winding 310 and the secondary windings 320a to 320d. Staggered.

When power is applied to the primary winding 310 of the isolation transformer 30, the secondary side circuit can have different power outputs depending on the different operations of the output control modules 400a-400d of the output control device 40, as described below in three different operational states.

Referring to FIG. 2, in the first operation state, the rectification switches Q1 to Q8 of the first to fourth synchronous rectification units 410a to 410d respectively receive the control signals of the controller 420 for synchronous rectification, or the first to fourth output switches SW1. When the SW4 receives the control signal from the controller 420 and is turned on (as shown in the interval after t3 in FIG. 3), the secondary windings 320a to 320d generate an electric power output by electromagnetic induction. At the same time, the magnetic flux coupling is incomplete between the primary winding 310 and the secondary windings 320a-320d, and the leakage inductance is generated. FIG. 8 is a diagram showing the leakage inductance, magnetic flux density and temperature distribution of the isolation transformer 30 corresponding to FIG. As can be seen from FIG. 8, the leakage inductance of the isolation transformer 30 is the lowest at a short coupling distance between the primary winding 310 and the secondary windings 320a-320d, and the leakage inductance is away from the primary winding 310 and the secondary windings 320a-320d. The coupling distance increases and increases. Since the primary winding 310 and the secondary windings 320a to 320d shown in FIG. 7 are staggered, the leakage inductance of the isolation transformer 30 varies within a certain range.

In the second operational state, only the rectifier switches SR1, SR2 of the first synchronous rectification unit 410a shown in FIG. 7 receive the control signal of the controller 420 for synchronous rectification, and the rectifier switches SR3, SR4, SR5, SR6, SR7, When the SR8 is turned off, or the first output switch SW1 is turned on by the control signal of the controller 420 (as shown in the range of 0 to t1 in FIG. 3), only the secondary winding 320a generates electric power by electromagnetic induction. As shown in FIG. 9, the coupling distance between the primary winding 310 and the secondary winding 320a is short, the leakage inductance of the isolation transformer 30 is low, and the leakage inductance of the isolation transformer 30 increases as the coupling distance between the primary winding 310 and the secondary winding 320a increases. Also increased.

In the third operational state, only the rectifier switches SR3, SR4, SR5, SR6 of the first synchronous rectification unit 410a and the fourth synchronous rectification unit 410d shown in FIG. 7 receive the control signal of the controller 420 for synchronous rectification, and the rectification switch When SR1, SR1, SR7, and SR8 are all turned off, or the first output switch SW1 and the fourth output switch SW4 are turned on by the control signal of the controller 420, only the secondary windings 320b and 320c are electromagnetically induced to generate electric power. . As shown in FIG. 9, in the short coupling distance between the primary winding 310 and the secondary windings 320a to 320d, the leakage inductance of the isolation transformer 30 is the lowest, and as the coupling distance between the primary winding 310 and the secondary windings 320a, 320d increases, The leakage inductance of the isolation transformer 30 also increases.

It can be known from the foregoing that by controlling the number of synchronous rectifications of the secondary windings 320a-320d of the isolation transformer 30 and the coupling distance with the primary winding 310, the leakage inductance of the isolation transformer 30 can be effectively adjusted. In one case, the power conversion system can output corresponding operating power according to the power required by the electronic device. In order for the secondary windings 320a-320d to be turned on and electromagnetically coupled to the primary winding 310 and output operating power, the synchronous rectifying unit connected to the rear end of the secondary windings 320a-320d must be synchronously rectified; for example, as shown in FIG. When a synchronous rectification unit 410a performs synchronous rectification, electric energy coupled to the secondary winding 320a by the primary winding 310 can be output via the inductors L1, L2, and a leakage inductance is generated to reduce duty cycle loss. In other words, the leakage inductance of the isolation transformer 30 can be changed by controlling the synchronous rectification of the first to fourth synchronous rectification units 410a to 410d as shown in FIG. Table 1 below (the leakage inductance value is only the test data of this example) shows the leakage inductance corresponding to the synchronous rectification of the first to fourth synchronous rectification units 410a to 410d.

In Table 1, "synchronous rectification" means that at least one of the first to fourth synchronous rectifying units performs synchronous rectification, and the primary winding 310 is coupled to the electric power output of the secondary windings 320a to 320d connected thereto. To the electronic device; "off" means that at least one of the first to fourth synchronous rectifying units 410a to 410d does not perform the synchronous rectification operation, and no operational power is output to the electronic device.

By changing the leakage inductance of the isolation transformer 30, the duty cycle loss can be effectively reduced. 4b shows the primary side current and voltage waveforms corresponding to the first to fourth power switch gate control signal poles corresponding to the power supply at 20% load. In Fig. 4b, time t5-t6' is shown by controlling the amount of conduction of the secondary windings 320a-320d of the isolation transformer 30 and its coupling distance with the primary winding 310 to change the leakage inductance of the isolation transformer 30. The subsequent duty cycle loss is shorter than the duty cycle loss shown in Figure 4a (i.e., time t5-t6); in other words, the time t6'-t6 shown in Figure 4b is the duty cycle loss change (i.e., reduction). Section of.

FIG. 5b and FIG. 6b respectively show the primary side current and voltage waveforms corresponding to the first to fourth power switch gate control signal poles of the power supply of the present invention at 50% and 100% load, wherein time t5-t6 The duty cycle loss of the secondary windings 320a-320d of the control isolation transformer 310 and its coupling distance with the primary winding 310 to change the leakage inductance of the isolation transformer 30 is shown, as shown by time t5-t6'. In order to utilize the amount of conduction of the secondary windings 320a-320d of the isolation transformer 30 and its coupling distance with the primary winding 310, the duty cycle loss after the leakage inductance of the isolation transformer 30 is changed.

In addition, in order to prevent the isolation transformer 30 from being damaged due to local heat accumulation, the order of synchronous rectification of the first to fourth synchronous rectification units 410a to 410d may be further changed according to the previous table 1. For example, the controller 420 may perform synchronous rectification. The synchronous rectification unit gradually controls the synchronous rectification unit to prevent the isolator transformer 30 from generating heat accumulation. Further, the controller 420 can further control the synchronous rectifying unit by means of gradually converge the distance between the synchronous rectifying unit that performs synchronous rectification and the central axis of the bobbin 330 to prevent the isolator transformer 30 from generating heat accumulation. That is, the synchronous rectification is performed separately by the first synchronous rectification unit 410a, the fourth synchronous rectification unit 410d, the second synchronous rectification unit 410b, and the third synchronous rectification unit 410c.

In addition, for example, in the first state and the second state shown in Table 1, only one single synchronous rectifying unit is turned on, and the other three synchronous rectifying units are stopped, and the turned-on synchronous rectifying unit is located at the center line of the isolation transformer 30 Corresponding positions on both sides, making both The difference in leakage inductance is small. Therefore, when the power conversion system is in operation, the first synchronous rectification unit 410a and the fourth synchronous rectification unit 410d may be sequentially turned on, so that the secondary windings 320a and 320d respectively transmit power to the electronic device. In this way, it is possible to effectively avoid the problem that only the secondary winding located at a specific position of the magnetic core 340 transmits power to the electronic device for a long time.

Of course, in actual operation, it is not limited to only the synchronous rectifying unit located at the corresponding position on both sides of the center line of the section of the isolation transformer 30 to perform switching according to different timings, as long as the similar leakage inductance (for example, less than 5 μH) can be provided. The corresponding synchronous rectifying units can be sequentially turned on, thereby preventing the problem that the isolation transformer 30 generates heat accumulation.

In summary, the power conversion system of the present invention can utilize the following power conversion method to provide required power of the electronic device under different operating states.

First, an isolation transformer 30 is provided. The isolation transformer 30 includes at least one primary winding 310 and a plurality of secondary windings (such as the secondary windings 320a-320d shown in FIG. 2), wherein each secondary winding 320a, 320b, 320c, 320d and The primary windings 310 have at least one coupling distance; in other words, the distance between the primary windings 310 and the secondary windings 320a-320d may be different, or the distance between each secondary winding 320a, 320b, 320c, 320d and the primary winding 310 may be the same. The primary winding 310 of the isolation transformer 30 is electrically connected to the resonant module 20, and the resonant module 20 is electrically connected to the input voltage Vi through the full bridge switching module 10. Each of the secondary windings 310 of the isolation transformer 30 is electrically connected to a synchronous rectification unit (for example, the first to fourth rectification units 410a to 410d shown in FIG. 2), and the synchronous rectification units 410a to 410d are connected to the electrons through the filters L1 to L8. Device.

Next, the operating mode of the electronic device is sensed, that is, the electronic device is operated in a light load, medium load or full load state, and according to the operating power of the electronic device in the corresponding working mode, the first to fourth synchronous rectifying units 410a, At least one of 410b, 410c, 410d performs synchronous rectification to change the leakage inductance of the isolation transformer 30.

When the leakage inductance of the isolation transformer 30 changes, the primary side current (Ip) of the isolation transformer 30 changes, and the power coupled to the isolation transformer secondary windings 320a to 320d also changes, causing the power transmitted to the electronic device to change to output compliance. The operating power of the electronic device in the corresponding operating mode.

Referring to FIG. 11, a circuit diagram of a power conversion system according to a third embodiment of the present invention is shown. The power conversion system shown in FIG. 11 includes a full bridge switching module 10, a resonant module 20, a transformer 30, and an output control device 40. The transformer 30 includes a coupled primary winding 310 and secondary windings 320a-320d.

It should be particularly noted that the circuit architecture and operation method of the full-bridge switching module 10 and the resonant module 20 shown in FIG. 11 are the same as the full-bridge switching module 10 and the resonant module 20 shown in FIG. 2; In other words, the structure of the transformer 30 and the output control device 40 shown in FIG. 11 is different from the transformer 30 and the output control module 40 shown in FIG.

In Fig. 11, the transformer 30 is a center-tapped transformer, so that it has a small volume compared to the transformer 30 shown in Fig. 2, and the transformer 30 shown in Fig. 2 has a double current characteristic. The output control module 40 is electrically connected to the secondary windings 320a-320d of the transformer 310. The output control module 40 includes first to fourth synchronous rectifying units 410a-410d, a controller 420, and first to fourth output switches SW1~SW4. . The first synchronous rectification unit 410a is connected to the secondary winding 320a, and the second synchronous rectification unit 410b is connected to The secondary winding 320b, the third synchronous rectifying unit 410c is connected to the secondary winding 320c, and the fourth synchronous rectifying unit 410d is connected to the secondary winding 320d.

The first synchronous rectification unit 410a includes rectification switches Q1 and Q2, the second synchronous rectification unit 410b includes rectification switches Q3 and Q4, the third synchronous rectification unit 410c includes rectification switches Q5 and Q6, and the fourth synchronous rectification unit 410d includes a rectification switch Q7. Q8. The sources of the rectifying switches Q1 and Q2 are respectively grounded, the drains of the rectifying switches Q1 and Q2 are electrically connected to both ends of the secondary winding 320a, and the filter L1 is connected to the center tap end of the secondary winding 320a. The sources of the rectifier switches Q3 and Q4 are respectively grounded, the drains of the rectifier switches Q3 and Q4 are electrically connected to the two ends of the secondary winding 320a, respectively, and the filter L2 is connected to the center tap terminal of the secondary winding 320b. The sources of the rectifier switches Q5 and Q6 are respectively grounded, the drains of the rectifier switches Q5 and Q6 are electrically connected to both ends of the secondary winding 320b, and the filter L3 is connected to the center tap terminal of the secondary winding 320c. The sources of the rectifying switches Q7 and Q8 are respectively grounded, the drains of the rectifying switches Q7 and Q8 are electrically connected to both ends of the secondary winding 320d, and the filter L4 is connected to the center tap end of the secondary winding 320d. The gates SR1 to SR8 of the rectifier switches Q1 to Q8 and the first to fourth output switches SW1 to SW4 are electrically connected to the controller 420, respectively. The gates SR1~SR8 of the rectifier switches Q1~Q8 receive the control signal outputted by the controller 420 to perform the switching operation of turning on or off, thereby providing the effect of synchronous rectification; the first to fourth output switches SW1~SW4 accepting the output of the controller 420 The control signal is turned on or off. The center tap end of the secondary windings 320a, 320b of the transformer 30 is electrically coupled to the output capacitor Co.

The function and related description of the other components of the power conversion system of the third embodiment of the present invention shown in FIG. 11 are actually the power conversion system of the second embodiment shown in FIG. 2 . The same, will not be described here. The power conversion system shown in FIG. 11 can at least achieve the same functions as the power conversion system shown in FIGS. 1 and 2.

Although the present invention has been disclosed in the above embodiments, it is not intended to limit the present invention, and any person skilled in the art can make various changes and refinements without departing from the spirit and scope of the present creation. The scope is subject to the definition of the scope of the patent application.

10‧‧‧Full Bridge Switching Module

20‧‧‧Resonance Module

30‧‧‧Isolation transformer

310‧‧‧Primary winding

320a, 320b, 320c, 320d‧‧‧ secondary winding

40‧‧‧Output control device

400a, 400b, 400c, 400d‧‧‧ output control module

410a‧‧‧First Synchronous Rectifier

410b‧‧‧Second synchronous rectifier unit

410c‧‧‧3rd synchronous rectification unit

410d‧‧‧fourth synchronous rectification unit

SW1, SW2, SW3, SW4‧‧‧ output switch

Vi‧‧‧ input voltage

Vo‧‧‧ output voltage

Claims (9)

An electric energy conversion system for providing a plurality of required electric power of an electronic device under different operating conditions, the electric energy conversion system comprising: an isolation transformer comprising a primary winding and a plurality of secondary windings, the secondary winding and the primary winding Having at least one coupling distance, a leakage inductance of the isolation transformer increases as the coupling distance increases; a resonant module electrically connected to the primary winding; a switching module electrically connected to the resonant module; The output control device includes a controller and a plurality of output control modules, wherein the controller is electrically connected to the output control modules, and each of the output control modules is electrically connected to one of the secondary windings, wherein the controller is configured according to the The operating state of the electronic device drives the at least one output control module of the output control device to output one of the required powers. The power conversion system of claim 1, wherein each of the output control modules comprises a synchronous rectification unit electrically connected to the synchronous rectification units, each of the secondary windings being connected to at least one of the synchronous rectifications And the controller drives the at least one synchronous rectifying unit to perform synchronous rectification according to an operating state of the electronic device and output one of the required powers corresponding to one of the required powers. The power conversion system of claim 1, wherein each of the output control modules comprises a synchronous rectification unit and an output switch, each output switch being electrically connected to one of the synchronous rectification units, the controller being according to the electronic device The operating state drives at least one of the output control devices to be turned on and outputs one of the operating powers corresponding to one of the required powers. The power conversion system of claim 2, wherein the secondary windings are respectively arranged on both sides of the primary winding, the controller electrically connecting the two sides of the primary winding to have the same coupling The synchronous rectifying units of the secondary windings are interleaved for synchronous rectification. The electric energy conversion system of claim 2, wherein the controller drives the isochronous rectifying units that cause the near leakage inductance to be synchronously rectified. The power conversion system of claim 2, wherein the isolation transformer further comprises: a winding frame, the secondary windings are equally spaced on the winding frame, and the primary winding is wound around the winding a bobbin, located on one side of each of the secondary windings, such that the primary windings are staggered with the secondary windings; and a magnetic core sleeved on the bobbin. The power conversion system of claim 6, wherein the controller causes the synchronous rectifying units to perform synchronous rectification in sequence, and between the synchronous rectifying units that perform synchronous rectification and a central axis of the bobbin The spacing gradually converges. The electrical energy conversion system of claim 1, wherein the coupling distance between the secondary windings and the primary windings is different. The power conversion system of claim 1, wherein when the leakage inductance of the isolation transformer is gradually increased, the operational power output by the electrical energy conversion system is gradually decreased.