TWM450139U - Converter with adjustable output voltage - Google Patents

Abstract

A converter with adjustable output voltage, coupled to a first power source and a second power source, including a transformer, a first switching circuit, a second switching circuit, a resonant circuit and an adjustable circuit. The first switching circuit having a plurality of first switching elements, each of the first switching elements is coupled to the transformer. The second switching circuit having a plurality of second switching elements, each of the second switching elements is coupled to the transformer. The resonant circuit contains a first inductor and at least one first capacitor and a second inductor. The first inductor coupled in series the transformer, the at least one first capacitor coupled to the second switching circuit. The second inductor coupled to the first capacitor. The adjustable circuit coupled to second power source and the second switching circuit. The adjustable circuit contain a third switching element and fourth switching element. The third switching element coupled to the first capacitor. The fourth switching element coupled to the second power source and the second inductor.

Description

Converter with adjustable output voltage

This creation relates to a converter that regulates the output voltage, and in particular to a converter that regulates the output voltage for energy savings.

Recently, since converters with generally adjustable output voltages are used for resonance applications, one of the converter circuits on both sides of the transformer is often recoupled to a boost (bost), a buck (buck) or a buck. Regulator circuit design for Buck/Boost Circuit.

Generally, when the converter that regulates the output voltage operates, there is often energy loss in the process of transmitting power through a converter that generally regulates the output voltage, whereby one of the transformer side switching circuits is coupled to the circuit design of the regulating circuit, Increase the complexity of the circuit. However, complex circuit designs can increase power consumption or increase manufacturing costs.

In view of this, the present invention provides a converter that can adjust the output voltage, using the first capacitor and the second inductor and the regulating circuit in the LCL resonant circuit to form a buck, boost or buck/boost The circuit, thereby adjusting the proportional relationship between the input and output voltages, thereby increasing the opportunity for the power conversion efficiency of the converter that regulates the output voltage.

The present invention provides a converter capable of regulating an output voltage, coupled between a first power supply side and a second power supply side, including a transformer, a first conversion circuit, a second conversion circuit, a resonant circuit, and a Adjust the circuit. The first conversion circuit has a plurality of first switching elements, and each of the first switching elements is coupled to the transformer. Second conversion The circuit has a plurality of second switching elements, and each of the second switching elements is coupled to the transformer. The resonant circuit has a first inductor, at least one first capacitor and a second inductor, the first inductor is connected in series with the transformer, the first capacitor is connected in parallel to the second converter circuit, the second inductor is coupled to the first capacitor, and the adjustment circuit is coupled Between the second power supply side and the second conversion circuit, the adjustment circuit has a third switching element and a fourth switching element, the third switching element is connected in parallel with the first capacitor, and the fourth switching element is coupled to the second power supply side. Between the second inductor and the second inductor.

In an embodiment of the present invention, the third switching element has a diode of a switching switch and a parallel switching switch, and the fourth switching element has a diode of a switching switch and a parallel switching switch.

In an embodiment of the present invention, the third switching element has a diode of a switching switch and a parallel switching switch, and the fourth switching element is a diode.

In an embodiment of the present invention, the third switching element is a diode, and the fourth switching element has a diode of a switching switch and a parallel switching switch.

In an embodiment of the present invention, the first inductor is a voltage leakage inductance of the voltage device.

In an embodiment of the present invention, the first conversion circuit is a full bridge circuit, a half bridge circuit, or a push-pull circuit.

In an embodiment of the present invention, the second conversion circuit is a full bridge circuit, a half bridge circuit, or a push-pull circuit.

In an embodiment of the present invention, each of the first switching elements includes a switching switch and a diode of a parallel switching switch, and each of the second switching elements includes a switching switch and a diode of a parallel switching switch.

In an embodiment of the present invention, the current is transmitted from the first power source side to the second power source side, and at least one of the first switching elements is turned on to discharge the first conversion circuit and transmitted through the transformer, and the second switching elements are At least one of being turned on to charge the second conversion circuit, and the on-period of the switching switch of at least one of the first switching elements is large The resonant period is the same as the resonant period of the first inductor and the at least one first capacitor, and the current is limited by the first inductance of the resonant circuit to reduce power loss.

In an embodiment of the present invention, the current is transmitted from the second power source side to the first power source side, and at least one of the first switching elements is turned on to charge the first conversion circuit and transmitted through the transformer, and the second switching elements are At least one of being turned on to discharge the second conversion circuit, wherein the on-period of at least one of the first switching elements is substantially the same as the current resonance of the resonant circuit, and the current resonates to a zero value or a near zero value. Reduce power loss.

In an embodiment of the present invention, when at least one of the switching elements of the first switching elements is turned on, at least one of the switching elements of the second switching elements is turned off; and at least one of the first switching elements is switched When the switch is turned off and the parallel diode is turned on, at least one of the switching elements of the second switching elements is turned on.

In summary, the basic working principle of the converter of the adjustable output voltage of the present invention is to control the circuit design of the first conversion circuit and the second conversion circuit on both sides of the transformer to realize bidirectional or one-way flow of current, and reuse The first capacitor, the second inductor and the regulating circuit form a buck, boost or buck/boost circuit to adjust the proportional relationship between the input and output voltages, thereby increasing the power conversion of the converter that can adjust the output voltage The opportunity for efficiency.

The above and other objects, features and advantages of the present invention will become more apparent and understood.

In order to fully understand the present invention, the embodiments are described in detail below with reference to the accompanying drawings, and are not intended to limit the present invention.

The technical content, the purpose of the invention and the effects achieved by this creation are based on The schema is illustrated in the following:

[First Embodiment]

1 is a circuit diagram of a converter of an adjustable output voltage of the present embodiment. Please refer to Figure 1. The converter 1 with an adjustable output voltage is coupled between a first power supply side P1 and a second power supply side P2, and includes a transformer 10, a first conversion circuit 11, a second conversion circuit 12, and a resonant circuit. And adjustment circuit 16. The converter 1 of the present invention can adjust the output voltage to transmit electric energy bidirectionally, for example, the electric energy is transmitted from the first power supply side P1 to the second power supply side P2, wherein the adjustment circuit 16 can generate the boosting effect or the electric energy from the second power supply. The side P2 is passed to the first power supply side P1, wherein the regulation circuit 16 can produce a buck-effect, whereby the input is proportional to the output voltage.

In other embodiments, the presently configurable output voltage converter 1 can also transmit electrical energy in one direction, for example, electrical energy is transferred from the first power supply side P1 to the second power supply side P2, wherein the regulating circuit 16 can generate boosting power. For convenience of description, in the embodiment, the converter 1 with adjustable output voltage can transmit power bidirectionally. The embodiment does not limit the aspect of the converter 1 that can adjust the output voltage.

The transformer 10 has a primary side winding N1 and a secondary side winding N2 corresponding to magnetic coupling. In practice, the transformer 10 transmits or converts energy through the magnetically coupled primary side winding N1 and the secondary side winding N2, for example, the number of turns of the primary side winding N1 is larger than the number of turns of the secondary side winding N2, thereby using the transformer 10 voltage drop, for example, to reduce the voltage of 120 volts to a voltage of 12V volts. Of course, the number of turns of the primary side winding N1 may be equal to or less than the number of turns of the secondary side winding N2, whereby the transformer 10 delivers energy or boosts the voltage, and the embodiment does not limit the aspect of the transformer 10, and the rest is the same. , I will not repeat them here.

The first switching circuit 11 has a plurality of first switching elements 111, 112, 113, 114, and each of the first switching elements 111, 112, 113, 114 includes a switching switch S1 , S2, S3, S4 and a diode D1, D2, D3, D4 of the anti-parallel switch S1, S2, S3, S4, each of the first switching elements 111, 112, 113, 114 is coupled to the transformer 10 Primary side winding N1.

In practice, the first switching elements 111, 112, 113, 114 are used to turn the first switching circuit 11 on or off, whereby the first switching circuit 11 can be discharged or charged. The switching switches S1, S2, S3, and S4 of the first switching elements 111, 112, 113, and 114 are connected in parallel with the diodes D1, D2, D3, and D4, thereby switching the switches S1, S2, S3, and S4 to be turned off. The diodes D1, D2, D3, and D4 connected in anti-parallel are turned on, or the switches S1, S2, S3, and S4 are turned on, and the diodes D1, D2, D3, and D4 in the anti-parallel are turned off. The switch S1, S2, S3, S4 is used to turn on or off the circuit of the first switching element 111, 112, 113, 114, and the switch S1, S2, S3, S4 can be realized by a power transistor or a field effect transistor. This embodiment does not limit the aspects of the first switching elements 111, 112, 113, 114, the switches S1, S2, S3, S4 and the diodes D1, D2, D3, D4.

The second conversion circuit 12 has a plurality of second switching elements 115, 116, 117, 118, and each of the second switching elements 115, 116, 117, 118 includes a switching switch S5, S6, S7, S8 and an anti-parallel switching switch The diodes D5, D6, D7, and D8 of S5, S6, S7, and S8, and the second switching elements 115, 116, 117, and 118 are coupled to the secondary winding N2 of the transformer 10.

In practice, the second switching element 115, 116, 117, 118 is used to turn the second switching circuit 12 on or off, whereby the second switching circuit 12 can be discharged or charged. The switching switches S5, S6, S7, and S8 of the second switching elements 115, 116, 117, and 118 are connected in parallel with the diodes D5, D6, D7, and D8, thereby switching the switches S5, S6, S7, and S8 to be turned off. The diodes D5, D6, D7, and D8 connected in anti-parallel are turned on; or when the switches S5, S6, S7, and S8 are turned on, and the diodes D5, D6, D7, and D8 in the anti-parallel are turned off. The switch S5, S6, S7, S8 is used to turn on or off the second switch The circuits of the elements 115, 116, 117, 118, and the switch S5, S6, S7, S8 can be realized by a power transistor or a field effect transistor, and the second switching element 115, 116, 117, 118 is not limited in this embodiment. The switches S5, S6, S7, S8 and the diodes D5, D6, D7, D8 are switched.

In detail, when the first conversion circuit 11 is discharged, energy is transferred or converted via the primary side winding N1 of the transformer 10 and the secondary side winding N2, whereby the second conversion circuit 12 is charged. Conversely, when the first conversion circuit 11 is charged, energy is transferred or converted via the primary side winding N1 of the transformer 10 and the secondary side winding N2, whereby the second conversion circuit 12 is discharged. Further, the first conversion circuit 11 is a full bridge circuit, and the second conversion circuit 12 is a full bridge circuit, thereby forming a converter 1 of an adjustable output voltage of the two full bridge circuits.

In other embodiments, the first conversion circuit 11 is a full bridge circuit, a half bridge circuit, or a push-pull circuit, and the second conversion circuit 12 is a full bridge circuit, a half bridge circuit, or a push-pull circuit. This constitutes a converter 1 which regulates the output voltage. This embodiment does not limit the aspect of the first conversion circuit 11 and the second conversion circuit 12 in FIG.

The resonant circuit has a first inductor 13, at least a first capacitor 14 and a second inductor 15, the first inductor 13 is connected in series with the secondary winding N2 of the transformer 10, and the at least one first capacitor 14 is connected in parallel with the second converter circuit 12, The second inductor 15 is coupled between the second power supply side P2 and the second conversion circuit 12 . In practice, the adjustable output voltage converter 1 of the present embodiment includes an LCL resonant circuit design having a first inductor 13, a first capacitor 14 and a second inductor 15.

In other embodiments, the resonant circuit may also be disposed on the primary side winding N1 of the transformer 10, and for convenience of explanation, the present embodiment is described by the resonant circuit being disposed on the secondary side winding N2 of the transformer 10. This embodiment does not limit the aspect in which the resonance circuit is provided to the primary side winding N1 or the secondary side winding N2 of the transformer 10.

In detail, the first inductor 13 is, for example, a transformer leakage inductance (Leakage inductance). Used to limit the current. For example, in the transformer 10, the coupling coefficient of the primary side winding N1 and the secondary side winding N2 is less than 1, and the partial winding of the transformer 10 does not have a transformation effect, and only has a function of suppressing the inductance. The secondary side winding N2 of the transformer 10 is connected in parallel with the first capacitor 14. The first capacitor 14 is, for example, a resonant capacitor, whereby the first inductor 13 and the first capacitor 14 of the secondary winding N2 of the transformer 10 can be charged and discharged. Reciprocating operation. Of course, the second inductor 15 acts as a resonant filter of the first inductor 13 and the first capacitor 14, whereby the LCL resonant circuit can reach a current that limits the transfer of energy.

When the current is transmitted from the first power supply side P1 to the second power supply side P2, at least one of the first switching elements 111, 112, 113, 114 is turned on, the first conversion circuit 11 is discharged, and is transmitted via the transformer 10. At least one of the two switching elements 115, 116, 117, 118 is turned on to charge the second switching circuit 12, and the switching switches S1, S2, S3, S4 of at least one of the first switching elements 111, 112, 113, 114 The on period is substantially the same as the resonance period of the first inductor 13 and the at least one first capacitor 14. The on-periods of the switches S1, S2, S3, and S4 of at least one of the first switching elements 111, 112, 113, and 114 are substantially the same as the resonance period of the first inductor 13 and the at least one first capacitor 14, and the current is resonated. The first inductor 13 of the circuit is current limited to reduce power loss.

When the current is transmitted from the second power supply side P2 to the first power supply side P1, at least one of the first switching elements 111, 112, 113, and 114 is turned on, the first conversion circuit 11 is charged, and is transmitted via the transformer 10. At least one of the two switching elements 115, 116, 117, and 118 is turned on to discharge the second switching circuit 12, and at least one of the first switching elements 111, 112, 113, and 114 is diodes D1, D2, D3, and D4. The turn-on period is approximately the same as the current resonance of the resonant circuit. The on periods of the diodes D1, D2, D3, and D4 of at least one of the first switching elements 111, 112, 113, and 114 are substantially the same as the current resonance of the resonant circuit, and the current resonates to a zero value or a near zero. Value, reducing power loss.

It is worth mentioning that when at least one of the first switching elements 111, 112, 113, 114 switches the switches S1, S2, S3, S4, at least one of the second switching elements 115, 116, 117, 118 The switch S5, S6, S7, and S8 are turned off; the switches S1, S2, S3, and S4 of at least one of the first switching elements 111, 112, 113, and 114 are turned off and the diodes D1 are connected in antiparallel. When D2, D3, and D4 are turned on, the switches S5, S6, S7, and S8 of at least one of the second switching elements 115, 116, 117, and 118 are turned on. In practice, the present work is performed by the switches S1, S2, S3, S4, S5, S6, S7, S8 of the first and second switching elements 111, 112, 113, 114, 115, 116, 117, 118. The control current is bidirectionally transmitted and the current through the energy transfer is limited by a resonant circuit.

The adjustment circuit 16 is coupled between the second power supply side P2 and the second conversion circuit 12 . The adjustment circuit 16 has a third switching element 161 and a fourth switching element 162. The third switching element 161 is connected in parallel with the first capacitor 14. The fourth switching element 162 is coupled between the second power supply side P2 and the second inductor 15. .

In the embodiment, the third switching element 161 has a switching switch S10 and a diode D10 of the parallel switching switch S10, and the fourth switching element 162 also has a switching switch S12 and a diode D12 of the parallel switching switch S12. The first capacitor 14, the second inductor 15, the third switching element 161, and the fourth switching element 162 form a buck/boost circuit. When power is transmitted from the first capacitor 14 to the second power source side P2, thereby forming a boost circuit; when power is transferred from the second power source side P2 to the first capacitor 14, thereby forming a buck type Circuit (Buck Circuit). Of course, the buck and boost circuits of this creation work in the same way as the general buck and boost circuits.

In detail, the general adjustment circuit is buck, boost or buck. / boost circuit, which increases circuit complexity and power loss. The adjustment circuit 16 of the present invention is composed only of the third switching element 161 and the fourth switching element 162. Compared with the general adjustment circuit, the present invention replaces the general adjustment circuit through the first capacitor 14 and the second inductor 15. The capacitance and inductance, thereby reducing the complexity of the circuit and the power loss, and achieving the effect of regulating the output voltage.

In other embodiments, the third switching element 161 has a switching switch S10 and a diode D10 of the parallel switching switch S10, and the fourth switching element 162 is a diode D12, whereby the first capacitor 14 and the second The inductor 15 and the adjusting circuit 16 form a boosting circuit; or the third switching element 161 is a diode D10, and the fourth switching element 162 has a switching switch S12 and a diode D12 of the parallel switching switch S12, thereby The first capacitor 14, the second inductor 15 and the regulating circuit 16 form a buck circuit. This embodiment does not limit the aspect of the adjustment circuit 16.

Based on the above, the basic working principle of the converter 1 of the present adjustable output voltage is to control the circuit design of the first conversion circuit 11 and the second conversion circuit 12 on both sides of the transformer 10 to realize bidirectional or one-way flow of current. The first capacitor 14, the second inductor 15 and the regulating circuit 16 are used to form a buck, boost or buck/boost circuit to adjust the proportional relationship between the input and output voltages, thereby increasing the adjustable output voltage. The opportunity for the power conversion efficiency of converter 1.

Next, the circuit operation of the converter that can adjust the output voltage is further explained. 2A, 2B, 2C and 2D are circuit operation diagrams of the converter of the present invention with adjustable output voltage. Please refer to FIG. 2A, FIG. 2B, FIG. 2C and FIG. 2D.

The circuit operation of the converter 2 of the adjustable output voltage of the present invention can be divided into four stages, and the current flow of the circuit can be distinguished into two cases, one being "first The power supply side P1 is transmitted to the second power supply side P2P2", and the adjustment circuit 26, the first capacitor 24 and the second inductor 25 form a boosting circuit; and the other is "transferred from the second power supply side P2P2 to the first power supply side P1" And the adjusting circuit 26, the first capacitor 24 and the second inductor 25 form a buck circuit. In other embodiments, the circuit operation of the converter 2 that can adjust the output voltage can be divided into one, two or more stages, and the current flow direction of the circuit can be distinguished as a one-way transmission case, and the embodiment does not limit the adjustable. The output voltage of the converter 2 is operated in a circuit.

In phase one, the first and second switching elements 211, 214, 215, 218 are turned on, and the first and second switching elements 212, 213, 216, 217 are turned off. As shown in FIG. 2A, when the current is transmitted from the first power supply side P1 to the second power supply side P2, the first power supply side P1 is discharged, and the current flows out from the positive terminal of the first power supply side P1, flowing through the first switching element 211. The switch S1 enters the end point of the primary side winding N1 of the transformer 20, flows out from the end point b of the primary side winding N1 of the transformer 20, flows through the changeover switch S4 of the first switching element 214, and flows into the first power supply side P1. Negative terminal. On the second power supply side P2, the current flows from the c-terminal end of the secondary side winding N2 of the transformer 20, and sequentially flows through a first inductor 23, a reverse parallel diode D5 of the second switching element 215, and a first The capacitor 24 and the anti-parallel diode D8 of the second switching element 218 flow into the d-end of the secondary winding N2 of the transformer 20, and at this time, the second power supply side P2 is filtered by a second inductor 25 to achieve charging. .

Next, the adjustment circuit 26 adjusts the output voltage according to the charging current of the second conversion circuit 22, and the charging current is transmitted from the first capacitor 24 to the second power supply side P2, whereby the switching switch S12 of the fourth switching element 262 is turned off. And the switch S10 of the third switching element 261 is controlled to be turned on or off, so that the adjusting circuit 26, the first capacitor 24 and the second inductor 25 form a boosting circuit, thereby adjusting the output voltage.

In detail, when the diode D12 of the fourth switching element 262 is reverse biased and the switching switch S10 of the third switching element 261 is turned on, the second inductor 25 stores energy, A capacitor 24 supplies power to the second power supply side P2 as shown in FIG. 2A. When the diode D12 of the fourth switching element 262 is turned on, and the switching switch S10 of the third switching element 261 is turned off, the second inductor 25 supplies power to the second power supply side P2 through the diode D12, and to the first capacitor 24 Charging, as shown in Figure 2B.

Next, as shown in FIG. 2C, when current is transmitted from the second power supply side P2 to the first power supply side P1, the anti-parallel diodes D1, D4 of the first switching elements 211, 214 are turned on, and the first power supply side P1 is charged. The current flows from the negative terminal of the first power supply side P1, flows through the reverse parallel diode D4 of the first switching element 214, enters the b-end of the primary side winding N1 of the transformer 20, and then passes from the primary winding N1 of the transformer 20. The end point of a flows out, flows through the anti-parallel body D1 of the first switching element 211, and flows into the positive terminal of the first power supply side P1; and on the second power supply side P2, the current flows from the secondary side winding N2 of the transformer 20 After the c-end point flows in, and then flows out from the d-end point of the secondary side winding N2 of the transformer 20, the switch S8 of the second switching element 218, the switching switch of the first capacitor 24 and the second switching element 215 are sequentially flowed. S5 and a first inductor 23 are further flowed into the c-terminal end of the secondary winding N2 of the transformer 20. At this time, the second power supply side P2 is filtered by a second inductor 25 to achieve discharge.

Next, the adjustment circuit 26 adjusts the output voltage according to the discharge current of the second conversion circuit 22, and the discharge current is transmitted from the second power supply side P2 to the first capacitor 24, whereby the changeover switch S10 of the third switching element 261 is turned off. And the switching switch S12 of the fourth switching element 262 is controlled to be turned on or off, so that the adjusting circuit 26, the first capacitor 24 and the second inductor 25 form a step-down circuit, thereby adjusting the output voltage.

In detail, when the diode D10 of the third switching element 261 is reverse biased and the switching switch S12 of the fourth switching element 262 is turned on, the second inductor 25 stores energy, as shown in FIG. 2C. When the diode D10 of the third switching element 261 is turned on and the switching switch S12 of the fourth switching element 262 is turned off, the second inductor 25 discharges power, as shown in FIG. 2D. It can be seen that the creation switch S10, S12 through the adjustment circuit 26 The control is actuated to regulate the output voltage.

It is worth mentioning that, because the on-time of the switching switches S1, S4 of the first switching elements 211, 214 and the resonant period of the first inductor 23 and the first capacitor 24 are the same, the switching switch S1 of the first switching elements 211, 214 When S4 is turned on, the current value is extremely small due to the current limiting action of the first inductor 23. Similarly, since the on-times of the diodes D1, D4 of the first switching elements 211, 214 are exactly equal to the resonance period, the switching switches S1, S4 of the first switching elements 211, 214 are turned off and the dipoles D1, D4 are inverted. When turned on, the current resonates to a value of zero or a small current value close to zero, so that the circuit current values of the switching switches S1, S4 of the first switching elements 211, 214 are both turned on and off, whereby the first switching elements 211, 214 The energy loss is also small.

Of course, when the switching switches S1, S4 of the first switching elements 211, 214 are turned on, the switching switches S5, S8 of the second switching elements 215, 218 are turned off, whereby the first switching circuit 21 is charged, and the second switching circuit 22 is discharged. Similarly, when the changeover switches S1, S4 of the first switching elements 211, 214 are turned off, the switching switches S5, S8 of the second switching elements 215, 218 are turned on, whereby the first switching circuit 21 is discharged, and the second switching circuit 22 is charged. It can be seen from this that the present invention realizes the bidirectional current transmission by controlling the first conversion circuit 21 and the second conversion circuit 22 on both sides of the transformer 20.

In phase two, all of the switches S1, S2, S3, S4, S5, S6, S7, S8 of the first and second switching elements 211, 212, 213, 214, 215, 216, 217, 218 are all turned off. There is no energy transfer on either side of the transformer 20. If the transformer 20 is regarded as an ideal transformer, no current flows on both sides of the transformer 20.

Similarly, the operation mode in the third phase is substantially the same as the phase one, for example, the first conversion circuit 21 is charging, and the second conversion circuit 22 is discharging; or the first conversion circuit 21 is discharging, and the second conversion circuit 22 is discharging. For charging, the first and second switching elements 212, 213, 216, 217 are turned on, the first and second switching elements 211, 214, 215, 218 are turned off, and the rest are the same, and will not be described herein.

Similarly, Stage 4 works in the same way as Phase 2, and after Phase 4, the circuit operation will loop back to Phase 1, and so on.

In summary, referring to FIG. 1, the converter 1 capable of adjusting the output voltage is based on the voltage relationship between the first power supply side P1 and the second power supply side P2 to automatically realize energy transfer. It is assumed that the number of turns of the a-end to the b-end of the primary winding N1 of the transformer 10 is W1, and the number of turns of the c-end to the d-end of the secondary winding N2 is W2, and the voltage of the first power supply side P1 When Vdc1, the voltage of the second power supply side P2 is Vdc2, when Vdc1/W1>Vdc2/W2, energy is transferred from the first power supply side P1 to the second power supply side P2, and when Vdc1/W1<Vdc2/W2 The energy is transmitted from the second power source side P2 to the first power source side P1.

The basic working principle of the converter 2 with adjustable output voltage is to control the circuit design on both sides of the transformer 20 to realize bidirectional flow of current, and to reuse the first capacitor 24, the second inductor 25 and the regulating circuit 26 to form a buck and boost. A buck or boost circuit that regulates the proportional relationship between the input and output voltages, thereby increasing the power conversion efficiency of the converter 2 that regulates the output voltage.

In addition, this creation uses resonance to limit the current during each energy transfer. When determining the direction of energy transfer, it is also possible to select only the switching element on the side of the transformer 20 to be controlled, while the switching element on the other side maintains the off state, and only the natural on-current of the diode exists. For example, if it is determined that energy is transmitted from the first power source side P1 to the second power source side P2, based on the above-described operation principle, only the first switching elements 211, 212, 213, 214 need to be controlled, and the second switching element 215 is controlled. The switches S5, S6, S7, and S8 of 216, 217, and 218 may be maintained in an off state.

In summary, the present invention can adjust the output voltage based on the LCL resonant circuit design, through the first capacitor, the second inductor and the regulating circuit to form a buck, boost or buck / boost The circuit regulates the proportional relationship between the input and output voltages, thus increasing the power conversion efficiency of the converter that regulates the output voltage.

[Second embodiment]

3 is a circuit diagram of a converter of an adjustable output voltage of another embodiment of the present invention. Please refer to FIG. 3 and FIG. The converter 3 of the adjustable output voltage of the present embodiment is similar to the converter 1 of the first embodiment capable of regulating the output voltage. For example, the converter 3 capable of regulating the output voltage can also transfer power bidirectionally, and the first capacitor 34 The second inductor 35 and the regulating circuit 36 form a buck/boost circuit. However, there is still a difference between the converters 3, 1 that can regulate the output voltage, in that the first conversion circuit 31 is a half bridge circuit, and the second conversion circuit 32 is a push-pull circuit.

In detail, the converter 3 that can adjust the output voltage is based on an LCL resonant circuit design including a first inductor 33, a second inductor 35, and a first capacitor 34. The adjustable output voltage converter 3 further includes a half bridge circuit composed of the first switching elements 313, 314 and the capacitors 311, 312, and a push-pull circuit composed of the second switching elements 315, 316, a transformer 30 and an adjustment circuit 36.

Referring to FIG. 3, the primary side winding N1 and the secondary side winding N2 of the converter 3 with adjustable output voltage are respectively connected to a first conversion circuit 31 and a second conversion circuit 32, wherein the first conversion circuit 31 is coupled to the first A power supply side P1 and a second conversion circuit 32 are coupled to the adjustment circuit 36, and the adjustment circuit 36 is coupled to a second power supply side P2. The first conversion circuit 31 is composed of a first switching element 313, 314 and a capacitor 311, 312. The second power supply side P2 is coupled to the first capacitor 33 through the first inductor 33 and the second inductor 35. A push-pull circuit composed of second switching elements 315, 316.

In detail, the first inductor 33 is coupled between the e-end of the secondary winding N2 of the transformer 30 and the second inductor 35, and the second switching element 315 is coupled to the c-end of the secondary winding N2 of the transformer 30. Between the first capacitors 34, the second switching element 316 is coupled between the d-end of the secondary winding N2 of the transformer 30 and the first capacitor 34. The converter 3 with adjustable output voltage operates: the capacitor 312 and the first switching element 313 are guided In the on state, the first switching element 314 of the capacitor 311 is in an off state; or the capacitor 311 and the first switching element 314 are in an on state, and the capacitor 312 and the first switching element 313 are in an off state, and the rest are the same, where Do not repeat them.

In addition to the above differences, those skilled in the art should be aware that the operational portion of the second embodiment is substantially equivalent to the first embodiment, and those skilled in the art have reference to the first embodiment and the above differences, It should be easy to infer, so I won't go into details here.

[Third embodiment]

4 is a circuit diagram of a converter of an adjustable output voltage of another embodiment of the present invention. Please refer to FIG. 4 and FIG. 1. The converter 4 of the adjustable output voltage of the present embodiment is similar to the converter 1 of the first embodiment capable of regulating the output voltage. For example, the converter 4 whose output voltage can be adjusted can also transmit power bidirectionally, and the first capacitor 44 45, the second inductor 46 and the regulating circuit 47 form a buck/boost circuit. However, there is still a difference between the converters 4, 1 that can regulate the output voltage, in that the first conversion circuit 41 is a push-pull circuit and the second conversion circuit 42 is a half bridge circuit.

The converter 4 with adjustable output voltage is based on an LCL resonant circuit design including a first inductor 43, a first capacitor 44, 45 and a second inductor 46. The adjustable output voltage converter 4 further includes a push-pull circuit composed of the first switching elements 411, 412 and a half bridge circuit composed of the second switching elements 413, 414, a transformer 40 and an adjusting circuit 47.

Referring to FIG. 4, the primary side winding N1 and the secondary side winding N2 of the converter 4 with adjustable output voltage are respectively connected to the first conversion circuit 41 and the second conversion circuit 42, wherein the first conversion circuit 41 is coupled to a first power supply. The side P1 and the second conversion circuit 42 are coupled to a second power supply side P2. The positive terminal of the first power supply side P1 is coupled to the e-terminal end of the primary side winding N1 of the transformer 40, and the first switching element 411 is coupled to the transformer 40 once. The c-terminal end of the side winding N1 is opposite to the negative terminal of the first power supply side P1, and the first switching element 412 is coupled between the end point of the primary side winding N1 of the transformer 40 and the negative terminal of the first power supply side P1. Thereby a push-pull circuit is formed.

The positive terminal of the second power supply side P2 is coupled to the second conversion circuit 42 via the second inductor 46, the second switching element 413, 414 and the half bridge circuit composed of the first capacitors 44, 45, and the half bridge circuit Then, the first inductor 43 is coupled to the secondary side winding N2 of the transformer 40. The converter 4 of the adjustable output voltage operates in a state in which the first and second switching elements 411, 414 are in an on state, the first and second switching elements 412, 613 are in an off state, or the first and second switching elements 412 are 413 is in an on state, and the first and second switching elements 411 and 414 are in an off state, and the rest are the same, and will not be described herein.

In addition to the above differences, those skilled in the art should appreciate that the operational portion of the third embodiment is substantially equivalent to the first embodiment, and those skilled in the art have reference to the first embodiment and the above differences, It should be easy to infer, so I won't go into details here.

[Fourth embodiment]

Figure 5 is a circuit diagram of a converter of an adjustable output voltage in accordance with another embodiment of the present invention. Please refer to FIG. 5 and FIG. 3. The converter 5 of the adjustable output voltage of the present embodiment is similar to the converter 3 of the second embodiment capable of regulating the output voltage. For example, the first conversion circuit 51 of the converter 5 that can adjust the output voltage is a half bridge circuit. And the second conversion circuit 52 is a push-pull circuit. However, there is still a difference between the converters 5 and 3 that can regulate the output voltage, in that the fourth switching element 562 of the regulating circuit 56 is a diode, whereby the first capacitor 54, the second inductor 55, and the third The switching element 561 and the fourth switching element 562 form a boost circuit, so that the electric energy can be transmitted only by the first capacitor 54 to the second power supply side P2.

In addition to the above differences, those skilled in the art should know that the operational portion of the fourth embodiment is substantially equivalent to the second embodiment, and those skilled in the art have reference to the second embodiment and the above differences. It should be easy to infer, so I won't go into details here.

[Fifth Embodiment]

6 is a circuit diagram of a converter of an adjustable output voltage of another embodiment of the present invention. Please refer to FIG. 6 and FIG. 4. The converter 6 of the adjustable output voltage of the present embodiment is similar to the converter 4 of the third embodiment capable of regulating the output voltage. For example, the first conversion circuit 61 of the converter 6 for adjusting the output voltage is a push-pull circuit. And the second conversion circuit 62 is a half bridge circuit. However, there is still a difference between the converters 6, 4 that can regulate the output voltage, in that the third switching element 671 of the adjusting circuit 67 is a diode, whereby the first capacitor 64, 65, the second inductor 66, The third switching element 671 and the fourth switching element 672 form a Buck circuit, so that the electrical energy can only be transmitted unidirectionally to the first capacitance 64, 65 by the second power supply side P2.

In addition to the above differences, those skilled in the art should be aware that the operational portion of the fifth embodiment is substantially equivalent to the third embodiment, and those skilled in the art have reference to the third embodiment and the above differences, It should be easy to infer, so I won't go into details here.

As described above, the circuit on both sides of the transformer in the converter of the adjustable output voltage of the present invention can be applied to a full bridge circuit, a half bridge circuit or a push-pull circuit, and the first capacitor, the second inductor and the adjustment circuit can be applied. The combination of the voltage circuit, the boost circuit, and the buck/boost circuit is shown in the following table:

In summary, the author is based on the LCL resonant circuit design of an adjustable output voltage converter, by controlling the first and second conversion circuits on both sides of the transformer to achieve two-way or one-way transmission of energy, while transmitting The first capacitor, the second inductor, and the regulating circuit form a buck, boost or buck/boost circuit to regulate the input The proportional relationship with the output voltage, thus increasing the opportunity for the power conversion efficiency of the converter that regulates the output voltage.

In addition, the on-time of the switching switch of each of the switching elements in the first and second conversion circuits and the first inductance of the resonant circuit are coincident with the resonant period of the first capacitor, so that when the switching switch is turned on, the first in the resonant circuit The current limit of the inductor is very small. Similarly, when the switch is turned off, the current resonates to a value of zero or a small value close to zero. As a result, the circuit current value is small when the switch is turned on and off. The energy loss of the switch is also small, which can improve the circuit efficiency.

1, 2, 3, 4, 5, 6‧‧‧ converters with adjustable output voltage

10, 20, 30, 40, 50, 60‧‧‧ transformers

11, 21, 31, 41, 51, 61‧‧‧ first conversion circuit

12, 22, 32, 42, 52, 62‧‧‧ second conversion circuit

13, 23, 33, 43, 53, 63‧‧‧ first inductance

14, 24, 34, 44, 45, 54, 64, 65‧‧‧ first capacitor

15, 25, 35, 46, 55, 66‧‧‧ second inductance

16, 26, 36, 47, 56, 67‧‧‧ adjustment circuits

111, 112, 113, 114, 211, 212, 213, 214, 313, 314, 411, 412, 413, 414, 513, 514, 611, 612 ‧ ‧ first switching element

115, 116, 117, 118, 215, 216, 217, 218, 315, 316, 515, 516, 613, 614 ‧ ‧ second switching element

161, 261, 361, 471, 561, 671‧‧‧ third switching element

162, 262, 362, 472, 562, 672‧‧‧ fourth switching element

311, 312, 511, 512‧‧‧ capacitors

a, b, c, d, e‧‧‧ endpoints

P1‧‧‧ first power side

P2‧‧‧second power side

N1‧‧‧ primary winding

N2‧‧‧ secondary winding

S1, S2, S3, S4, S5, S6, S7, S8, S10, S12‧‧‧ switch

D1, D2, D3, D4, D5, D6, D7, D8, D10, D12‧‧‧ diodes

1 is a circuit diagram of a converter for adjusting an output voltage according to an embodiment of the present invention; FIG. 2A is a schematic diagram of an operation of a converter for adjusting an output voltage of the present invention; and FIG. 2B is a converter for adjusting an output voltage of the present invention; Schematic diagram of the operation description; FIG. 2C is a schematic diagram of the operation of the converter of the adjustable output voltage of the present invention; FIG. 2D is a schematic diagram of the operation of the converter of the adjustable output voltage of the present invention; FIG. FIG. 4 is a circuit diagram of a converter that can adjust an output voltage according to another embodiment of the present invention; FIG. 5 is a circuit diagram of an adjustable output voltage of another embodiment of the present invention; Circuit diagram of the device; 6 is a circuit diagram of a converter of an adjustable output voltage of another embodiment of the present invention.

1‧‧‧Converter with adjustable output voltage

10‧‧‧Transformers

11‧‧‧First conversion circuit

12‧‧‧Second conversion circuit

13‧‧‧First inductance

14‧‧‧first capacitor

15‧‧‧second inductance

16‧‧‧Adjustment circuit

111, 112, 113, 114‧‧‧ first switching element

115, 116, 117, 118‧‧‧ second switching element

161‧‧‧ Third switching element

162‧‧‧fourth switching element

a, b, c, d‧‧‧ endpoints

P1‧‧‧ first power side

P2‧‧‧second power side

N1‧‧‧ primary winding

N2‧‧‧ secondary winding

S1, S2, S3, S4, S5, S6, S7, S8, S10, S12‧‧‧ switch

D1, D2, D3, D4, D5, D6, D7, D8, D10, D12‧‧‧ diodes

Claims (12)

An adjustable output voltage converter is coupled between a first power supply side and a second power supply side, and includes: a transformer; a first conversion circuit having a plurality of first switching elements, each of the first switches An element is coupled to the transformer; a second conversion circuit having a plurality of second switching elements, each of the second switching elements being coupled to the transformer; and a resonant circuit having a first inductance, at least a first capacitance, and a second inductor, the first inductor is connected in series with the transformer, the at least one first capacitor is connected in parallel to the second conversion circuit, the second inductor is coupled to the at least one first capacitor, and an adjustment circuit is coupled to the second inductor Between the second power supply side and the second conversion circuit, the adjustment circuit has a third switching element and a fourth switching element, the third switching element is connected in parallel to the at least one first capacitor, and the fourth switching element is coupled Connected between the second power source side and the second inductor. The converter of claim 1, wherein the third switching element has a switching switch and a diode connected in parallel with the switching switch. A converter for regulating an output voltage according to claim 1 or 2, wherein the fourth switching element has a switching switch and a diode connected in parallel with the switching switch. The converter of claim 1, wherein the fourth switching element is a diode. Conversion of the adjustable output voltage as described in claim 1 The third switching element is a diode, and the fourth switching element has a switching switch and a diode connected in parallel with the switching switch. The converter of claim 1, wherein the first inductor is a voltage leakage inductance. The converter of claim 1, wherein the first conversion circuit is a full bridge circuit, a half bridge circuit or a push-pull circuit. The converter of claim 1, wherein the second conversion circuit is a full bridge circuit, a half bridge circuit or a push-pull circuit. The converter of claim 1, wherein each of the first switching elements comprises a switching switch and a diode connected in parallel with the switching switch, each of the second switching elements comprising a switch Connect the diode of the switch in parallel with one. The converter of claim 12, wherein the current is transmitted from the first power source side to the second power source side, and at least one of the first switching elements is turned on to enable the first conversion And discharging the circuit through the transformer, wherein at least one of the second switching elements is turned on to charge the second switching circuit, and the switching period of at least one of the first switching elements is substantially the same as the first inductance During a resonant period of the at least one first capacitor, current is limited by the first inductance of the resonant circuit to reduce power loss. The converter of claim 9, wherein the current is transmitted from the second power source side to the first power source side, and at least one of the first switching elements is turned on, so that the first a conversion circuit is charged, transmitted through the transformer, and the second switching elements are One of the first switching circuits is turned on, and the on-period of at least one of the first switching elements is substantially the same as the current resonance of the resonant circuit, and the current resonates to a zero value or a near zero Value, reducing power loss. The converter of the adjustable output voltage according to claim 9, wherein when at least one of the switching elements of the first switching elements is turned on, at least one of the switching elements of the second switching elements is turned off; When at least one of the switching elements of the first switching elements is turned off and the parallel diodes are turned on, at least one of the switching switches of the second switching elements is turned on.