M440615 五、新型說明： 【新型所屬之技術領域】 本創作係有關-種驅動裝置，特別是關於—種應用於發光沐體驅動 之無損失轉換驅動裝置。 【先前技術】 因發光二極體為單向導電树，且爲保證發光二極狀件的可靠性， 驅動發光二極體㈣流必須低於發光：極體败㈣要求，因此當發光> 極體aED)應雜㈣與背統倾日_，f要對其驅動在岐電流下， 以避免驅動電流超出最大額定值，影響發光二極體可#度，故目前係_ 具有脈波寬度爾模組（PWM)的軸電路來鶴發光二極體。 如第i圖师’現有的發光二極體，轉裝置之基本組成大多是利用脈 波寬度調變（PWM)電路K)搭配電晶體開件12以及電感u、電容 C】 ' 電阻Rs、R7〜R8等被動元件’以利用〇p放大器14產生的電壓差來 推動脈波寬度爾電路1G輸出調變控舰號，並藉此來切雜接於發光二 極體串列LEm〜LEDn之電晶體_元件12的導通械止；調變控制信號 可以使流過發光二極體㈣LED1〜LEDn的電流縣在歡值，並利用其 責任週期（Duty Cycle)比例來調節流經發光二極體串列⑽卜匕胸的 電流。然而’此類驅動裝置通常使用之脈波寬度調變電路W係具有限流之 設計’使其責任·控制在大約98%以下，以避免過高的責任週期導致電 晶體開關元件，卿程編__需調整線性 跨屢VS時’則谨能再並聯—個電阻R〇來調整，相當麻煩。 口此本創作遂針對上逑之困擾，提出_種無損失轉換驅動裝置，以 3 解決上述問題。 【新型内容】 本創作之主要目的係在提供_種無損失轉換驅動裝置 ，其係藉由責任 週期0〜1GG%的脈波寬度調路來綱關元件得以1齡導通，進而使輸 入電壓與發光二極體電翻當，乎無損耗產生以達财效狀電流控 制效益。 本創作之另目的係在提供—種可微調整控制電壓的無損失轉換驅動 裝置。 本創作提出之無損失轉接驅動裝置主要包括有··—發光二極體負載係 連接並接收—輸人紐；—_元件係電性連接至發光二極❹載；-取 樣電路電性連接輸入嫩發光二極體負載，以取樣此發光二極體負載盥 輸入電壓間產生的線㈣壓，並產生—取樣電流；—比流㈣電性連接取 樣電路’以根據線性賴來決定是否輸出取樣電流至一可調式電阻组，此 可調式電阻組接收翁樣電鱗可產生—控制《至其所連接之-責任週 期為〇〜職的脈波寬度爾電路，使脈波寬度調變電路可根據此控制電 壓來控制開關元件的導通與截止。 之可變 再者，為調整控制電壓的大小，可進一步調整可調式電阻組中 電阻的阻值大小。 底下藉由具體實施例配合所附的圖式詳加說明，當更容易瞭解本創作 之目的、技術内容、特點及其所達成之功效。 【實施方式】 首先，請參閱第2圖之無損失轉換驅動裝置的電路示意圖，如圖所示， M440615 此無損失轉換驅動裝置主要包括有—發光二極體負載2G ' —開關元件22、 一取樣電路24、一比流器26 一可調式電阻組28以及一責任週期為〇〜1〇〇 %之脈波寬度調變電路3〇。此發光二極體貞載Μ係連接並接收—輸入電壓 Vin另步而則电性連接一開關元件22，此開關元件22係可為NMOS電晶 體元件例:δ N型金氧半導體場效電晶體取樣電路％係電 性連接輸人電壓Vin及發光二極體負載2G，以根據發光二極體負載2〇的工 作電壓與輸人電壓Vin的壓差產生—線性跨壓Vs，並產生—取樣電流ι;比 流器26係電性連接輸入電壓Vin及前述取樣電路24，以根據此線性跨壓 Vs決定是魏蛛樣電流丨；—可調式電阻组28電性連接比流^ %及脈 波寬度·电路30 ’以根據取樣電流丨產生-控制電壓vl至脈波寬度調 文電路30，其中取樣電路24及比流器％係為—電流鏡電路（⑶細mb —it);此脈波寬度調變電路3G係紐連接可調式電阻組Μ及開關元件 22，以根據接收到的控制輕VL來控制開關元件22的導通與截止。M440615 V. New description: [New technical field] This creation is related to a kind of driving device, especially for the lossless conversion driving device applied to the luminous body driving. [Prior Art] Since the light-emitting diode is a unidirectional conductive tree, and to ensure the reliability of the light-emitting diode, the driving light-emitting diode (four) flow must be lower than the light-emitting: polar body (four) requirement, so when the light is emitted> The polar body aED) should be mixed with the backing system _, f should be driven under the 岐 current to avoid the driving current exceeding the maximum rated value, affecting the light-emitting diode can be # degree, so the current system _ has pulse wave The width module (PWM) of the axis circuit comes to the crane light-emitting diode. For example, the i-tutor's existing light-emitting diodes, the basic components of the transfer device are mostly using the pulse width modulation (PWM) circuit K) with the transistor opening 12 and the inductor u, the capacitor C] 'resistors Rs, R7 ~R8 and other passive components' use the voltage difference generated by the 〇p amplifier 14 to push the arterial wave width circuit 1G output modulation control ship number, and thereby connect to the light emitting diode series LEm~LEDn The conduction of the crystal_element 12 is controlled; the modulation control signal can cause the current flowing through the LEDs (4) LED1 to LEDn to be happy, and the ratio of the duty cycle (Duty Cycle) is used to adjust the flow through the LED string. Column (10) dip the current of the chest. However, 'the pulse width modulation circuit W used in such a drive device has a current-limiting design', so that its responsibility is controlled to be less than about 98%, so as to avoid an excessive duty cycle leading to the transistor switching element. Edit __ need to adjust the linear crossover VS when 'then can be paralleled again - a resistor R 〇 to adjust, quite troublesome. In response to the troubles of the Shangyu, this creation proposes a kind of lossless conversion drive device to solve the above problems. [New content] The main purpose of this creation is to provide a loss-free conversion drive device, which is turned on by the pulse width adjustment channel with a duty cycle of 0~1GG% to enable the element to be turned on at the age of one, thereby making the input voltage and The light-emitting diode is turned over and the loss-free generation has the effect of controlling the current of the financial effect. Another object of the present invention is to provide a lossless conversion drive that can finely adjust the control voltage. The lossless transfer drive device proposed by the present invention mainly comprises: - the light-emitting diode load system is connected and received - the input button; the - - component is electrically connected to the light-emitting diode load; - the sampling circuit is electrically connected Input a light-emitting diode load to sample the line (four) voltage generated between the input voltage of the light-emitting diode and generate a sampling current; - the current flow (four) is electrically connected to the sampling circuit to determine whether to output according to the linear dependence Sampling current to an adjustable resistor group, the adjustable resistor group receiving the Weng scale can generate - control "to the connected - the duty cycle is the pulse width circuit of the job, so that the pulse width is modulated The circuit can control the on and off of the switching element according to the control voltage. Variable Further, in order to adjust the size of the control voltage, the resistance of the resistor in the adjustable resistor group can be further adjusted. The purpose of the present invention, the technical content, the features, and the effects achieved by the present invention will be more readily understood by the specific embodiments and the accompanying drawings. [Embodiment] First, please refer to the circuit diagram of the lossless conversion driving device of FIG. 2, as shown in the figure, the M440615 is a lossless conversion driving device mainly including a light-emitting diode load 2G' - a switching element 22, a The sampling circuit 24, a current comparator 26, an adjustable resistor group 28, and a pulse width modulation circuit 3 having a duty cycle of 〇~1〇〇%. The light-emitting diode is connected and received - the input voltage Vin is electrically connected to a switching element 22, and the switching element 22 can be an NMOS transistor element: δ N-type MOSFET The crystal sampling circuit % is electrically connected to the input voltage Vin and the light-emitting diode load 2G to generate a linear cross-over voltage Vs according to the voltage difference between the operating voltage of the light-emitting diode load and the input voltage Vin, and generate - The sampling current ι; the current comparator 26 is electrically connected to the input voltage Vin and the sampling circuit 24 to determine the Wei-like current 根据 according to the linear voltage Vs; the adjustable resistor group 28 is electrically connected to the flow rate and The pulse width circuit 30' generates a control voltage v1 to a pulse width modulating circuit 30 according to the sampling current ,, wherein the sampling circuit 24 and the comparator % are - a current mirror circuit ((3) thin mb - it); The pulse width modulation circuit 3G is connected to the adjustable resistor group 开关 and the switching element 22 to control the on and off of the switching element 22 according to the received control light VL.
5羊5之，在本實施例所不之第2圖中，上述之發光二極體負載更包 括-發光二極體㈣L則〜LEDn，其係並聯一輸出電扣以及串接一儲 能電感L，並有-整流二極體D1跨接於取樣電路24之跨壓電阻Rs以及儲 能電感L與_元件22之間。在取樣電路24中之跨壓電阻Rs係具有第一 端A及第二端B，跨壓電阻以之第1A電性連接輸入電壓Vin，跨壓電 阻Rs之第二端⑽電性連接至發光：極體負載2()之發光二極射列测 〜LEDN ’此跨壓電阻RS胁駐發生時會對應產生雜跨壓％，一第三 電阻R3電性連接跨壓電阻Rs之第—端A以及比流器％中之一運算放大 器OP之正端， 一弟四電阻R4電性連接跨壓 電阻Rs之第二端B以及運算 M440615 放大器OP之負端。在比流器26中之電晶體q係為PNp電晶體，其基極係 連接運算放大器0p之輸出端，集極連接至該第三電阻R3，以接收取樣電 流I，射極連接至可調式電阻組28。在可調式電阻組28中，第一電阻Ri 一端連接至比流器26之電晶體Q，另一端則連接至一可變電阻Rv，可變電 阻Rv之另一端則連接至接地端，以及一第二電阻幻之一端連接至電晶體 Q與6亥第一電阻R1 ’另一端則連接至脈波寬度調變電路，使第一電阻 R1及可變電阻Rv可根據取樣電流I產生控制電壓v L回饋至脈波寬度調變 電路30，進而藉此控制開關元件22之作動。 當然，為了製程差異或其他因素而需調整控制電壓VL時，可輕易藉由 可變電阻Rv來調整至所需之電阻值，相當便利。 繼續參考第2圖所示，當跨壓電阻Rs之線性跨壓Vs產生時，取樣電 路24亦會產生取樣變流1= Vs/R3，此時因為有線性跨壓Vs的產生，使運 具放大器0P產生輸出使電晶體Q導通，此時取樣電流J得以通過電晶體Q 而流至可調式電阻組28 ;取樣電流I流經第一電阻R1及可變電阻Rv而產 生控制電壓VL，此控制電壓即提供給脈波寬度調變電路3〇，其具體關係如 下： VL=P(R1+Rv)=(Vs/R3)*(ri+rv) 此即表示控制電壓VL與第一電阻Ri和可變電阻Rv呈線性關係；此 時，脈波寬度調變電路30根據接收到的控制電壓VL來控制開關元件22 開啟程度。由於脈波寬度調變電路30係具有〇〜1〇〇%的責任週期，當責任 週期為100%時，會使得輸入電壓Vin與發光二極體工作電壓％印相當而 幾乎無線性跨壓Vs產生，故此時可視為幾乎無損耗產生。對比流器％及 M440615 可調式電阻組28而言，可偵測取樣電流I來進行定電流控制，且控制電壓 VL可進一步控制驅動脈波寬度調變電路3〇輸出之責任週期；當線性跨壓 Vs較大時，產生較大的控制變壓VL，進而控制脈波寬度調變電路30將電 晶體Q的開啟脈寬調高，以提高發光二極體負載2〇的工作電流，且脈波寬 度調變電路30最高可輸出為100%的責任週期。 綜上所述，本創作係為一種可調整控制電壓之無損失轉換驅動裝置， 且其藉由責任 〇〜卿％的脈波寬度調魏路令開關元件得以满％導 #通，進而使輸入電塵與發光二極體電壓相當而幾乎無損耗產生，故可達到 有效的定電流控制效益。 以上所述之鶴為制本卿之技聽想及特點，1目的在使 =此項技藝之人该_解本猶之够並細魏料能以之限定 ^ 細’即纽依本創作所揭示之精神所作之均等變化或修 年仍應涵盖在本創作之專利範圍内。 【圖式簡單說明】In the second embodiment of the present embodiment, the above-mentioned light-emitting diode load further includes a light-emitting diode (four) L-LEDn, which is connected in parallel with an output electric buckle and a series-connected energy storage inductor. L, and the rectifying diode D1 is connected across the voltage across the resistor Rs of the sampling circuit 24 and the energy storage inductor L and the _ element 22. The voltage across the resistor Rs in the sampling circuit 24 has a first end A and a second end B. The voltage across the resistor is connected to the input voltage Vin, and the second end (10) of the voltage across the resistor Rs is electrically connected to the light. : The polar body load 2 () of the light-emitting diode detection ~ LEDN 'this cross-voltage resistor RS threat occurs when the corresponding generation of the cross-span pressure, a third resistor R3 is electrically connected to the first end of the voltage across the resistor Rs A and the positive terminal of one of the comparators OP, the fourth resistor R4 is electrically connected to the second terminal B of the voltage across the resistor Rs and the negative terminal of the M440615 amplifier OP. The transistor q in the current comparator 26 is a PNp transistor, the base of which is connected to the output of the operational amplifier 0p, the collector is connected to the third resistor R3 to receive the sampling current I, and the emitter is connected to the adjustable Resistor group 28. In the adjustable resistor group 28, one end of the first resistor Ri is connected to the transistor Q of the comparator 26, the other end is connected to a variable resistor Rv, and the other end of the variable resistor Rv is connected to the ground, and The second resistor is connected to the transistor Q and the sixth resistor R1', and the other end is connected to the pulse width modulation circuit, so that the first resistor R1 and the variable resistor Rv can generate the control voltage according to the sampling current I. v L is fed back to the pulse width modulation circuit 30, thereby controlling the actuation of the switching element 22. Of course, when the control voltage VL needs to be adjusted for process variation or other factors, it is easy to adjust to the required resistance value by the variable resistor Rv, which is quite convenient. Continuing to refer to FIG. 2, when the linear voltage across the voltage across the voltage resistor Rs is generated, the sampling circuit 24 also generates a sampled current change 1 = Vs/R3, at which time the carrier is generated due to the linear cross-over voltage Vs. The amplifier 0P generates an output to turn on the transistor Q. At this time, the sampling current J flows through the transistor Q to the adjustable resistor group 28; the sampling current I flows through the first resistor R1 and the variable resistor Rv to generate the control voltage VL. The control voltage is supplied to the pulse width modulation circuit 3〇, and the specific relationship is as follows: VL=P(R1+Rv)=(Vs/R3)*(ri+rv) This indicates the control voltage VL and the first resistance. Ri and the variable resistor Rv have a linear relationship; at this time, the pulse width modulation circuit 30 controls the degree of opening of the switching element 22 in accordance with the received control voltage VL. Since the pulse width modulation circuit 30 has a duty cycle of 〇~1〇〇%, when the duty cycle is 100%, the input voltage Vin is equivalent to the operating voltage of the LED, and the wireless crossover is almost instantaneous. Vs is generated, so it can be considered as almost no loss. For the comparator and the M440615 adjustable resistor group 28, the sampling current I can be detected to perform constant current control, and the control voltage VL can further control the duty cycle of the output of the pulse width modulation circuit 3; When the voltage across the Vs is large, a large control voltage VL is generated, and then the pulse width modulation circuit 30 is controlled to increase the opening pulse width of the transistor Q to increase the operating current of the LED load of 2 ,. And the pulse width modulation circuit 30 can output a maximum duty cycle of 100%. In summary, the creation is a lossless conversion driving device capable of adjusting the control voltage, and the switching force of the pulse width is adjusted by the 〇 卿 卿 卿 卿 卿 卿 , , , , , , , , , , , , , , , , , It is equivalent to the voltage of the light-emitting diode and has almost no loss, so that effective constant current control efficiency can be achieved. The above-mentioned crane is the skill and characteristics of the company, and the purpose is to make = the skill of the person. The solution is still enough and the fine material can be limited by it. Equal changes or years of rehearsal should still be covered by the scope of this creation. [Simple description of the map]
1圖細㈣以輸戰置的電路示意圖 2圖係為本創作之電路示意圖。 【主要元件符號說明】 10脈波寬度調變（PWM)電路 12電晶體開關元件 M OP放大器 2〇發光二極體負载 22開關元件 7 M440615 24取樣電路 26 比流器 28 可調式電阻組 30脈波寬度調變電路 C1電容 D1整流二極體 I 取樣電流 L 儲能電感 L1電感 LED1〜LEDn 發光二極體串列 OP運算放大器 Q 電晶體 R0、R5〜R8 電阻 R1第一電阻 R2第二電阻 R3第三電阻 R4第四電阻1 Figure (4) Schematic diagram of the circuit placed in the battle. 2 The diagram is the circuit diagram of the creation. [Main component symbol description] 10 pulse width modulation (PWM) circuit 12 transistor switching element M OP amplifier 2 〇 LED load 22 switching element 7 M440615 24 sampling circuit 26 current transformer 28 adjustable resistor group 30 pulse Wave width modulation circuit C1 capacitor D1 rectifier diode I sampling current L energy storage inductor L1 inductor LED1 ~ LEDn LED diode OP op amp Q transistor R0, R5 ~ R8 resistor R1 first resistor R2 second Resistor R3 third resistor R4 fourth resistor
Rs跨壓電阻Rs voltage across resistor
Rv可變電阻Rv variable resistor
Vin輸入電壓 VL控制電壓Vin input voltage VL control voltage
Vs線性跨壓Vs linear cross pressure