TWI787977B - Loudspeaker controller for estimating fundamental resonance frequency of loudspeaker and method for estimating fundamental resonance frequency of loudspeaker - Google Patents
Loudspeaker controller for estimating fundamental resonance frequency of loudspeaker and method for estimating fundamental resonance frequency of loudspeaker Download PDFInfo
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本發行係有關頻率估測,且尤指一種用以估測一揚聲器之一基本共振頻率的方法以及相關揚聲器控制器。 This publication relates to frequency estimation, and in particular to a method for estimating a fundamental resonant frequency of a loudspeaker and related loudspeaker controllers.
揚聲器係具有音圈(voice coil)的裝置,其中音圈移動一振膜(diaphragm)並且將電子訊號轉換為聲音訊號,然而,對於導致振膜位移較大的輸入訊號來說,較大的振膜位移可能會損壞揚聲器,為了避免上述問題,可以在揚聲器的基本共振頻率(fundamental resonance frequency)中控制揚聲器的一操作頻率。為了找到揚聲器的基本共振頻率,可以先取得揚聲器的阻抗(impedance)曲線圖,其中阻抗曲線圖的橫軸係為頻率,以及阻抗曲線圖的縱軸係為阻抗,再者,揚聲器的基本共振頻率可藉由辨認對應於阻抗曲線之最大值的一頻率來自阻抗曲線圖中找出,要注意的是,揚聲器的阻抗曲線可能隨著溫度改變,因此,揚聲器的基本共振頻率不是一固定值。 A loudspeaker is a device with a voice coil that moves a diaphragm and converts electrical signals into sound signals, however, for input signals that cause larger diaphragm displacements, larger diaphragms Membrane displacement may damage the speaker. To avoid the above problems, an operating frequency of the speaker can be controlled within the fundamental resonance frequency of the speaker. In order to find the basic resonance frequency of the speaker, you can first obtain the impedance curve of the speaker, where the horizontal axis of the impedance curve is the frequency, and the vertical axis of the impedance curve is the impedance. Furthermore, the basic resonance frequency of the speaker It can be found from the impedance graph by identifying a frequency corresponding to the maximum value of the impedance curve. Note that the impedance curve of a speaker may change with temperature, therefore, the fundamental resonant frequency of a speaker is not a fixed value.
為了取得揚聲器的阻抗曲線圖以及自阻抗曲線圖找出基本共振頻率,可以在揚聲器上進行一種典型的時域阻抗量測或一種典型的頻域阻抗量測,該典型的時域阻抗量測具有低成本以及高準確度的優點,然而,該典型的時域阻抗量測於揚聲器用以進行音訊播放而被驅動的期間不可動態地監控阻抗以及基本共振頻率並且需要掃頻。針對該典型的頻域阻抗量測來說,雖然阻抗以及基本共振頻率於揚聲器用以進行音訊播放而被驅動的期間可以被動態地監控並且無需掃頻,在頻域阻抗量測中的快速傅立葉轉換(fast fourier transformation,FFT)相當複雜並且可能導致較高的硬體成本。 In order to obtain the impedance curve of the loudspeaker and the self-impedance curve to find the fundamental resonance frequency, a typical time-domain impedance measurement or a typical frequency-domain impedance measurement can be performed on the loudspeaker. The typical time-domain impedance measurement has Advantages of low cost and high accuracy, however, the typical time-domain impedance measurement cannot dynamically monitor the impedance and fundamental resonant frequency while the speaker is being driven for audio playback and requires a frequency sweep. For this typical frequency-domain impedance measurement, although the impedance and fundamental resonant frequency can be dynamically monitored and no frequency sweep is required while the loudspeaker is being driven for audio playback, the fast Fourier transform in the frequency-domain impedance measurement Transformation (fast fourier transformation, FFT) is quite complicated and may result in high hardware cost.
因此,本發明之一目的在於提供一種用以估測一揚聲器之一基本共振頻率的方法,此外,為了達到低成本以及高準確度的優點,該方法另可於揚聲器用以進行音訊播放而被驅動的期間動態地監控阻抗(尤指基本共振頻率)。 Therefore, an object of the present invention is to provide a method for estimating a fundamental resonance frequency of a loudspeaker. In addition, in order to achieve the advantages of low cost and high accuracy, the method can also be used for audio playback by the loudspeaker. The impedance (especially the fundamental resonant frequency) is dynamically monitored during driving.
根據本發明之一實施例,揭露了一種用以估測一揚聲器之一基本共振頻率的方法,該方法可包含有:根據一音訊輸入訊號來產生該揚聲器之一驅動訊號;感測該驅動訊號之特性以產生一量測訊號;藉由具有不同通帶之複數個帶通濾波器來濾波該量測訊號,以產生複數個濾波器輸出;以及根據該複數個濾波器輸出來估測該基本共振頻率。 According to an embodiment of the present invention, a method for estimating a fundamental resonance frequency of a loudspeaker is disclosed, the method may include: generating a driving signal of the loudspeaker according to an audio input signal; sensing the driving signal characteristics to generate a measurement signal; filter the measurement signal by a plurality of bandpass filters with different passbands to generate a plurality of filter outputs; and estimate the basic Resonance frequency.
除了上述方法,本發明另揭露了一種揚聲器控制器,該揚聲器控制器可包含有:一放大器電路,用以根據一音訊輸入訊號來產生該揚聲器之一驅動訊號;一感測電路,用以感測該驅動訊號之特性來產生一量測訊號;複數個帶通濾波器電路,用以分別濾波該量測訊號來產生複數個濾波器輸出,其中該 複數個帶通濾波器具有不同通帶;以及一估測電路,用以根據該複數個濾波器輸出來估測該基本共振頻率。 In addition to the above method, the present invention further discloses a speaker controller, which may include: an amplifier circuit for generating a driving signal of the speaker according to an audio input signal; a sensing circuit for sensing Measuring the characteristics of the driving signal to generate a measurement signal; a plurality of bandpass filter circuits are used to respectively filter the measurement signal to generate a plurality of filter outputs, wherein the A plurality of bandpass filters have different passbands; and an estimation circuit is used for estimating the fundamental resonance frequency according to the outputs of the plurality of filters.
本發明至少可具有以下的優點/好處。與典型的時域阻抗量測相比,本發明所揭露的利用一組具有以不同頻率為中心之通帶的帶通濾波器電路的基本共振頻率估測方案可於揚聲器用以進行音訊播放而被驅動的期間動態地監控阻抗(尤指基本共振頻率),並且不需要掃頻。與典型的頻域阻抗量測相比,本發明所揭露的利用一組具有以不同頻率為中心之通帶的帶通濾波器電路的基本共振頻率估測方案不需要進行複雜的快速傅立葉轉換,並且可以以低硬體成本來實現。 The present invention may have at least the following advantages/benefits. Compared with typical time-domain impedance measurements, the disclosed basic resonant frequency estimation scheme using a set of bandpass filter circuits with passbands centered at different frequencies can be used in loudspeakers for audio playback. Impedance (especially the fundamental resonant frequency) is dynamically monitored while being driven, and frequency sweeping is not required. Compared with typical frequency-domain impedance measurements, the disclosed basic resonant frequency estimation scheme using a set of bandpass filter circuits with passbands centered at different frequencies does not require complex fast Fourier transforms, And can be implemented with low hardware cost.
10:揚聲器控制器 10:Speaker controller
12:放大器電路 12: Amplifier circuit
14:感測電路 14: Sensing circuit
28_1~28_N:帶通濾波器電路 28_1~28_N: Bandpass filter circuit
30:估測電路 30: Estimation circuit
50:揚聲器 50: speaker
A_IN:音訊輸入訊號 A_IN: audio input signal
A_DRV:驅動訊號 A_DRV: drive signal
S_M:量測訊號 S_M: Measurement signal
BPFOUT_1~BPFOUT_N:濾波器輸出 BPFOUT_1~BPFOUT_N: filter output
Fo:基本共振頻率 F o : Fundamental resonance frequency
16:電流感測電路 16: Current sensing circuit
18:電壓感測電路 18: Voltage sensing circuit
20:預處理電路 20: Preprocessing circuit
22:低通濾波器電路 22: Low-pass filter circuit
23_1,23_2:低通濾波器 23_1, 23_2: low pass filter
I(t):量測電流訊號 I(t): measurement current signal
I’(t):低通濾波電流訊號 I'(t): Low-pass filtered current signal
V(t):量測電壓訊號 V(t): Measurement voltage signal
V’(t):低通濾波電壓訊號 V’(t): Low-pass filtered voltage signal
24:降低取樣電路 24: Downsampling circuit
S_I:降低取樣電流訊號 S_I: Reduce the sampling current signal
S_V:降低取樣電壓訊號 S_V: Reduced sampling voltage signal
29_11~29_N1,29_12~29_N2:帶通濾波器 29_11~29_N1, 29_12~29_N2: bandpass filter
BPFI_1~BPFI_N:帶通濾波電流訊號 BPFI_1~BPFI_N: bandpass filter current signal
BPFV_1~BPFV_N:帶通濾波電壓訊號 BPFV_1~BPFV_N: Band-pass filtered voltage signal
32:平滑濾波器電路 32: Smoothing filter circuit
36_1~36_N:阿爾發濾波器電路 36_1~36_N: Alpha filter circuit
37_11~37_N1,37_12~37_N2:阿爾發濾波器 37_11~37_N1, 37_12~37_N2: Alpha filter
SFI_1~SFI_N:平滑電流訊號 SFI_1~SFI_N: Smooth current signal
SFV_1~SFV_N:平滑電壓訊號 SFV_1~SFV_N: Smooth voltage signal
38:處理電路 38: Processing circuit
40:強度門檻電路 40: Intensity Threshold Circuit
MAG:強度 MAG: Strength
TH:強度門檻 TH: Intensity Threshold
S80~S96,S98:步驟 S80~S96, S98: steps
第1圖為依據本發明一實施例之用以估測揚聲器之基本共振頻率的揚聲器控制器的方塊圖。 FIG. 1 is a block diagram of a speaker controller for estimating the fundamental resonance frequency of a speaker according to an embodiment of the present invention.
第2圖為依據本發明一實施例之第1圖所示之揚聲器控制器的一實施範例的示意圖。 FIG. 2 is a schematic diagram of an implementation example of the speaker controller shown in FIG. 1 according to an embodiment of the present invention.
第3圖為依據本發明一實施例之用以估測揚聲器之基本共振頻率的方法流程圖。 FIG. 3 is a flowchart of a method for estimating the fundamental resonance frequency of a speaker according to an embodiment of the present invention.
第4圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器之阻抗曲線的示意圖。 FIG. 4 is a schematic diagram of an impedance curve of a loudspeaker obtained by frequency-domain impedance measurement with fast Fourier transform.
第5圖為依據本發明一第一實施例之藉由第3圖所示之方法的揚聲器之基本共振頻率的估測示意圖。 FIG. 5 is a schematic diagram of estimating the fundamental resonance frequency of the loudspeaker by the method shown in FIG. 3 according to a first embodiment of the present invention.
第6圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器之另一阻抗曲線的示意圖。 FIG. 6 is a schematic diagram of another impedance curve of a loudspeaker obtained by frequency-domain impedance measurement with fast Fourier transform.
第7圖為依據本發明一第二實施例之藉由第3圖所示之方法的揚聲器之基本共振頻率的估測示意圖。 FIG. 7 is a schematic diagram of estimation of the fundamental resonant frequency of the loudspeaker by the method shown in FIG. 3 according to a second embodiment of the present invention.
第8圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器之再另一阻抗曲線的示意圖。 FIG. 8 is a schematic diagram of yet another impedance curve of a loudspeaker obtained by frequency-domain impedance measurement with fast Fourier transform.
第9圖為依據本發明一第三實施例之藉由第3圖所示之方法的揚聲器之基本共振頻率的估測示意圖。 FIG. 9 is a schematic diagram of estimating the fundamental resonance frequency of the loudspeaker by the method shown in FIG. 3 according to a third embodiment of the present invention.
第10圖為依據本發明一實施例之第1圖所示之揚聲器控制器的另一實施範例的示意圖。 FIG. 10 is a schematic diagram of another implementation example of the speaker controller shown in FIG. 1 according to an embodiment of the present invention.
第11圖為依據本發明一實施例之用以估測揚聲器之基本共振頻率的另一方法流程圖。 FIG. 11 is a flow chart of another method for estimating the fundamental resonant frequency of a loudspeaker according to an embodiment of the present invention.
第12圖為依據本發明一實施例之第1圖所示之揚聲器控制器的再另一實施範例的示意圖。 FIG. 12 is a schematic diagram of yet another implementation example of the speaker controller shown in FIG. 1 according to an embodiment of the present invention.
第1圖為依據本發明一實施例之用以估測揚聲器50之基本共振頻率Fo的揚聲器控制器10的方塊圖。如第1圖所示,揚聲器控制器10係耦接於揚聲器50,並且用以估測揚聲器50之基本共振頻率Fo,要注意的是,揚聲器50在其基本共振頻率Fo時具有最高阻抗,因此,估測揚聲器50之基本共振頻率Fo可藉由估測揚聲器50之最高阻抗來實現。揚聲器控制器10可包含有一放大器電路12、一感測電路14、複數個帶通濾波器(band pass filter,BPF)電路28_1、28_2、...、28_N(為簡潔起見,分別標記為“BPF電路”)以及一估測電路30,其中“N”可代表大於一的正整數(亦即N≧2)。放大器電路12係用以接收一音訊輸入訊號A_IN並且根據音訊輸入訊號A_IN來產生揚聲器50的一驅動訊號A_DRV。感測電路14係耦接於放大器電路12以及揚聲器50,並且用以感測驅動訊號A_DRV的特性以
及產生一量測訊號S_M。帶通濾波器電路28_1~28_N係耦接於感測電路14,並且用以濾波量測訊號S_M以及分別產生複數個濾波器輸出BPFOUT_1~BPFOUT_N,其中帶通濾波器電路28_1~28_N具有不同通帶(passband),因此,當相同的量測訊號S_M輸入至帶通濾波器電路28_1~28_N時,濾波器輸出BPFOUT_1~BPFOUT_N可以是不同的。估測電路30係耦接於帶通濾波器電路28_1~28_N,並且用以根據濾波器輸出BPFOUT_1~BPFOUT_N來估測揚聲器50的基本共振頻率Fo,此外,於揚聲器50用以進行音訊播放而被驅動的期間,揚聲器控制器10可利用即時(real-time)的方式來估測揚聲器50的基本共振頻率Fo。
FIG. 1 is a block diagram of a
與典型的時域阻抗量測相比,本發明所揭露的利用一組具有以不同頻率為中心之通帶的帶通濾波器電路28_1~28_N的基本共振頻率估測方案可於揚聲器50用以進行音訊播放而被驅動的期間動態地監控阻抗(尤指基本共振頻率),並且不需要掃頻。
Compared with the typical time-domain impedance measurement, the basic resonant frequency estimation scheme disclosed by the present invention using a set of bandpass filter circuits 28_1~28_N with passbands centered at different frequencies can be used in the
與典型的頻域阻抗量測相比,本發明所揭露的利用一組具有以不同頻率為中心之通帶的帶通濾波器電路28_1~28_N的基本共振頻率估測方案不需要進行複雜的快速傅立葉轉換,並且可以以低硬體成本來實現。以下參照附圖來描述本發明所揭露之基本共振頻率估測方案之進一步的細節。 Compared with typical frequency-domain impedance measurements, the basic resonant frequency estimation scheme disclosed in the present invention using a set of bandpass filter circuits 28_1~28_N with passbands centered on different frequencies does not require complicated fast Fourier transform, and can be implemented with low hardware cost. Further details of the basic resonance frequency estimation scheme disclosed in the present invention are described below with reference to the accompanying drawings.
第2圖為依據本發明一實施例之第1圖所示之揚聲器控制器的一實施範例的示意圖。如上所述,感測電路14係用以感測驅動訊號A_DRV的特性並且產生量測訊號S_M,舉例來說,驅動訊號A_DRV的特性可包含有一電壓值以及一電流值,如第2圖所示,感測電路14可包含有一電流感測電路16、一電壓感測電路18以及一預處理電路20。電流感測電路16可量測流過揚聲器50之一音圈的
一電流來產生一量測電流訊號I(t),電壓感測電路18可量測揚聲器50之音圈兩端的一電壓來產生一量測電壓訊號V(t),預處理電路20係用以根據量測電流訊號I(t)以及量測電壓訊號V(t)來產生量測訊號S_M。
FIG. 2 is a schematic diagram of an implementation example of the speaker controller shown in FIG. 1 according to an embodiment of the present invention. As mentioned above, the
在本實施例中,預處理電路20可包含有一低通濾波器(low pass filter,LPF)電路22(為簡潔起見,標記為“LPF電路”)以及一降低取樣電路24,其中降低取樣電路24係耦接於低通濾波器電路22。低通濾波器電路22可包含有一第一低通濾波器23_1以及一第二濾波器23_2(為簡潔起見,分別標記為“LPF1”以及為“LPF2”),其中第一低通濾波器23_1可接收電流感測電路16所產生的量測電流訊號I(t),並且可低通濾波量測電流訊號I(t)來產生一低通濾波電流訊號I’(t),以及第二濾波器23_2可接收電壓感測電路18所產生的量測電壓訊號V(t),並且可低通濾波量測電壓訊號V(t)來產生一低通濾波電壓訊號V’(t)。為了減少計算複雜度以及/或增加準確度,降低取樣電路24可接收低通濾波電流訊號I’(t)以及低通濾波電壓訊號V’(t),並且分別降低取樣(downsample)低通濾波電流訊號I’(t)以及低通濾波電壓訊號V’(t)以產生一降低取樣電流訊號S_I以及一降低取樣電壓訊號S_V,其中第1圖所示之量測訊號S_M可包含有第2圖所示之降低取樣電流訊號S_I以及降低取樣電壓訊號S_V。
In this embodiment, the
根據本實施例,感測電路14可將量測訊號S_M傳送至複數個帶通濾波器電路28_1~28_N,其中量測訊號S_M可包含有一電流訊號以及一電壓訊號(亦即降低取樣電流訊號S_I以及降低取樣電壓訊號S_V)。要注意的是,取決於實際設計考量,實作在揚聲器控制器10中的帶通濾波器電路28_1~28_N的數量、帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路之頻寬(bandwidth)以及/或帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路之通帶的中心頻率(亦
即帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路之通帶的位置)皆可以被調整,舉例來說,帶通濾波器電路28_1~28_N可根據揚聲器50的製造商所提供的揚聲器50之標稱(nominal)基本共振頻率來配置為具有固定位於/分布在一頻率範圍內之各自的通帶,又例如,帶通濾波器電路28_1~28_N可根據於揚聲器50用以進行音訊播放而被驅動的期間所量測的揚聲器50之時變(time-varying)基本共振頻率來配置為具有動態地位於/分布在一頻率範圍內之各自的通帶。簡單來說,任何利用具有以不同頻率為中心之通帶的一組帶通濾波器電路來進行基本共振頻率估測(或阻抗估測)的揚聲器控制器皆落入本發明的範疇。
According to this embodiment, the
此外,帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路可包含有兩個帶通濾波器,舉例來說,帶通濾波器電路28_1包含有一第一帶通濾波器29_11以及一第二帶通濾波器29_12(為簡潔起見,分別標記為“BPF11”以及為“BPF12”);帶通濾波器電路28_2包含有一第一帶通濾波器29_21以及一第二帶通濾波器29_22(為簡潔起見,分別標記為“BPF21”以及為“BPF22”);以及帶通濾波器電路28_N包含有一第一帶通濾波器29_N1以及一第二帶通濾波器29_N2(為簡潔起見,分別標記為“BPFN1”以及為“BPFN2”)。同一個帶通濾波器電路的第一帶通濾波器以及第二帶通濾波器具有相同的中心頻率(亦即位於相同的位置),其中第一帶通濾波器可用以自感測電路14接收電流訊號(亦即降低取樣電流訊號S_I),並且藉由濾波電流訊號來產生一帶通濾波電流訊號,第二帶通濾波器可用以自感測電路14接收電壓訊號(亦即降低取樣電壓訊號S_V),並且藉由濾波電壓訊號來產生一帶通濾波電壓訊號,以及帶通濾波器電路的一濾波器輸出包含有帶通濾波電流訊號以及帶通濾波電壓訊號。舉例來說,濾波器輸出BPFOUT_1包含有帶通濾波電流訊號BPFI_1以及帶通濾波電壓訊號BPFV_1,濾波器輸出BPFOUT_2包含有帶通濾波電流訊號BPFI_2以及帶通濾波電壓訊號BPFV_2,以
及濾波器輸出BPFOUT_N包含有帶通濾波電流訊號BPFI_N以及帶通濾波電壓訊號BPFV_N。
In addition, each of the band-pass filter circuits 28_1~28_N may include two band-pass filters. For example, the band-pass filter circuit 28_1 includes a first band-pass filter 29_11 and a first band-pass filter 29_11. The second band-pass filter 29_12 (labeled as "BPF 11 " and "BPF 12 " respectively for the sake of brevity); the band-pass filter circuit 28_2 includes a first band-pass filter 29_21 and a second band-pass filter device 29_22 (for brevity, respectively marked as "BPF 21 " and "BPF 22 "); and the bandpass filter circuit 28_N includes a first bandpass filter 29_N1 and a second bandpass filter 29_N2 (for For brevity, labeled "BPF N1 " and "BPF N2 " respectively). The first band-pass filter and the second band-pass filter of the same band-pass filter circuit have the same center frequency (that is, they are located at the same position), wherein the first band-pass filter can be used to receive signals from the
應注意的是,對於估測揚聲器50的時變基本共振頻率,在基本共振頻率估測開始之前,帶通濾波器電路28_1~28_N可以根據揚聲器50之標稱基本共振頻率來被預先放置(pre-position)於一頻率範圍中,然而,此僅作為範例說明之用,本發明並不以此為限。
It should be noted that, for estimating the time-varying fundamental resonant frequency of the
揚聲器控制器10的估測電路30可包含有一平滑濾波器電路32以及一處理電路38,平滑濾波器電路32可用以自帶通濾波器電路28_1~28_N接收濾波器輸出BPFOUT_1~BPFOUT_N,並且藉由分別平整(smooth)濾波器輸出BPFOUT_1~BPFOUT_N來產生複數個平滑濾波器輸出。在本實施例中,平滑濾波器電路可包含有複數個阿爾發濾波器(alpha filter)電路36_1、36_2、...、36_N(為簡潔起見,分別標記為“α濾波器電路”),其中阿爾發濾波器電路36_1~36_N分別耦接於帶通濾波器電路28_1~28_N。此外,阿爾發濾波器電路36_1~36_N中的每一個阿爾發濾波器電路可包含有一第一阿爾發濾波器以及一第二阿爾發濾波器(為簡潔起見,分別標記為“α filter1”以及為“α filter2”),舉例來說,阿爾發濾波器電路36_1包含有第一濾波器37_11以及第二阿爾發濾波器37_12(其分別耦接於第一帶通濾波器29_11以及第二帶通濾波器29_12),阿爾發濾波器電路36_2包含有第一濾波器37_21以及第二阿爾發濾波器37_22(其分別耦接於第一帶通濾波器29_21以及第二帶通濾波器29_22),以及阿爾發濾波器電路36_N包含有第一濾波器37_N1以及第二阿爾發濾波器37_N2(其分別耦接於第一帶通濾波器29_N1以及第二帶通濾波器29_N2)。
The
由於一阿爾發濾波器電路所接收的濾波器輸出包含有一電流訊號以及一電壓訊號,因此一阿爾發濾波器電路所產生的平滑濾波器輸出包含有一電流訊號以及一電壓訊號。對於每一個平滑濾波器輸出其包含有一平滑電流訊號以及一平滑電壓訊號來說,阿爾發濾波器電路的第一阿爾發濾波器可用以自帶通濾波器電路接收帶通濾波電流訊號並且產生平滑電流訊號,並且阿爾發濾波器電路的第二阿爾發濾波器可用以自帶通濾波器電路接收帶通濾波電壓訊號並且產生平滑電壓訊號。如第2圖所示,阿爾發濾波器電路36_1所產生的平滑濾波器輸出包含有平滑電流訊號SFI_1以及平滑電壓訊號SFV_1,其中平滑電流訊號SFI_1藉由將帶通濾波電流訊號BPFI_1通過第一阿爾發濾波器37_11來取得,以及平滑電壓訊號SFV_1藉由將帶通濾波電壓訊號BPF V_1通過第二阿爾發濾波器37_12來取得;阿爾發濾波器電路36_2所產生的平滑濾波器輸出包含有平滑電流訊號SFI_2以及平滑電壓訊號SFV_2,其中平滑電流訊號SFI_2藉由將帶通濾波電流訊號BPFI_2通過第一阿爾發濾波器37_21來取得,以及平滑電壓訊號SFV_2藉由將帶通濾波電壓訊號BPF V_2通過第二阿爾發濾波器37_22來取得;以及阿爾發濾波器電路36_N所產生的平滑濾波器輸出包含有平滑電流訊號SFI_N以及平滑電壓訊號SFV_N,其中平滑電流訊號SFI_N藉由將帶通濾波電流訊號BPFI_N通過第一阿爾發濾波器37_N1來取得,以及平滑電壓訊號SFV_N藉由將帶通濾波電壓訊號BPF V_N通過第二阿爾發濾波器37_N2來取得。 Since the filter output received by an alpha filter circuit includes a current signal and a voltage signal, the smoothing filter output generated by an alpha filter circuit includes a current signal and a voltage signal. For each smoothing filter output which includes a smoothed current signal and a smoothed voltage signal, the first alpha filter of the alpha filter circuit can be used with a bandpass filter circuit to receive the bandpass filtered current signal and generate the smoothed The current signal, and the second alpha filter of the alpha filter circuit can be used for the band-pass filter circuit to receive the band-pass filtered voltage signal and generate a smoothed voltage signal. As shown in FIG. 2, the smoothing filter output generated by the alpha filter circuit 36_1 includes a smoothed current signal SFI_1 and a smoothed voltage signal SFV_1, wherein the smoothed current signal SFI_1 is obtained by passing the band-pass filtered current signal BPFI_1 through the first alpha and the smoothed voltage signal SFV_1 is obtained by passing the band-pass filtered voltage signal BPF V_1 through the second alpha filter 37_12; the smoothing filter output generated by the alpha filter circuit 36_2 includes the smoothed current The signal SFI_2 and the smoothed voltage signal SFV_2, wherein the smoothed current signal SFI_2 is obtained by passing the band-pass filtered current signal BPFI_2 through the first alpha filter 37_21, and the smoothed voltage signal SFV_2 is obtained by passing the band-pass filtered voltage signal BPF V_2 through the first alpha filter 37_21 Two alpha filters 37_22 are obtained; and the smoothing filter output generated by the alpha filter circuit 36_N includes a smoothed current signal SFI_N and a smoothed voltage signal SFV_N, wherein the smoothed current signal SFI_N is obtained by passing the band-pass filtered current signal BPFI_N The first alpha filter 37_N1 is obtained, and the smoothed voltage signal SFV_N is obtained by passing the band-pass filtered voltage signal BPF V_N through the second alpha filter 37_N2 .
平滑濾波器電路32中的阿爾發濾波器電路可以將一濾波器輸出轉換成一平滑濾波器輸出,以避免或減輕電流訊號以及電壓訊號之間的相位差,也就是說,藉由阿爾發濾波器電路所產生的平滑濾波器輸出之中的電流訊號以及電壓訊號之間的相位差係小於傳送至阿爾發濾波器電路的濾波器輸出之中電流訊號以及電壓訊號之間的相位差,如此一來,基本共振頻率估測的準確度可以
被改善。
The alpha filter circuit in the smoothing
對於平滑濾波器電路32(尤指平滑濾波器電路32中的阿爾發濾波器電路36_1~36_N)所產生的每一個平滑濾波器輸出來說,處理電路38可用以將平滑電壓訊號除以平滑電流訊號以產生一阻抗值,此外,處理電路38另可用以藉由比較自平滑濾波器輸出取得的複數個阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}來估測揚聲器50的基本共振頻率Fo。
For each smoothing filter output generated by the smoothing filter circuit 32 (especially the alpha filter circuits 36_1~36_N in the smoothing filter circuit 32), the
在自阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}中找到了一個最大值的案例中,揚聲器50的基本共振頻率Fo係被估測為涉及該最大值之推導的帶通濾波器電路之中心頻率,舉例來說,如果對應於在阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}之中的最大值的帶通濾波器電路之中心頻率係為200赫茲(hertz,Hz),則揚聲器50的基本共振頻率Fo可被估測為200赫茲。
In the case where a maximum is found among the self-impedance values {SFV_1/SFI_1, SFV_2/SFI_2, ..., SFV_N/SFI_N}, the fundamental resonance frequency F o of the
在自阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}中找到了具有相同最大值之兩個阻抗值的另一個案例中,揚聲器50的基本共振頻率Fo可被估測為涉及具有相同最大值之該兩個阻抗值之推導的兩個帶通濾波器電路之中心頻率的一平均,舉例來說,如果對應於在阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}之中的最大值的一帶通濾波器電路之中心頻率係為200赫茲,以及對應於在阻抗值{SFV_1/SFI_1、SFV_2/SFI_2、...、SFV_N/SFI_N}之中的相同最大值的另一個帶通濾波器電路之中心頻率係為210赫茲,則揚聲器50的基本共振頻率Fo可被估測為205赫茲,然而,此僅作為範例說明之用,本發明並不以此為限。或者,揚聲器50的基本共振頻率Fo可被估測為
自200赫茲至210赫茲的一頻率範圍中的任一頻率值。
In another case where two impedance values with the same maximum value are found among the self-impedance values {SFV_1/SFI_1, SFV_2/SFI_2, ..., SFV_N/SFI_N}, the fundamental resonance frequency F o of the
第3圖為依據本發明一實施例之用以估測揚聲器之基本共振頻率的方法流程圖。假若可以得到相同的結果,則步驟不一定要完全遵照第3圖所示的流程來依序執行,舉例來說,第3圖所示之方法可由第2圖所示之揚聲器控制器10來加以實現。
FIG. 3 is a flowchart of a method for estimating the fundamental resonance frequency of a speaker according to an embodiment of the present invention. If the same result can be obtained, the steps do not have to be executed sequentially according to the flow shown in Figure 3. For example, the method shown in Figure 3 can be implemented by the
在步驟S80中,根據音訊輸入訊號A_IN來產生揚聲器50的驅動訊號A_DRV。
In step S80 , a driving signal A_DRV of the
在步驟S82中,量測流過揚聲器50之音圈的電流來產生量測電流訊號I(t)。
In step S82 , the current flowing through the voice coil of the
在步驟S84中,量測揚聲器50之音圈兩端的電壓來產生量測電壓訊號V(t)。
In step S84 , the voltage across the voice coil of the
在步驟S86中,低通濾波量測電流訊號I(t)來產生低通濾波電流訊號I’(t),並且低通濾波量測電壓訊號V(t)來產生低通濾波電壓訊號V’(t)。 In step S86, the measured current signal I(t) is low-pass filtered to generate a low-pass filtered current signal I'(t), and the measured voltage signal V(t) is low-pass filtered to generate a low-pass filtered voltage signal V' (t).
在步驟S88中,分別降低取樣低通濾波電流訊號I’(t)以及低通濾波電壓訊號V’(t)來產生降低取樣電流訊號S_I以及降低取樣電壓訊號S_V。 In step S88, the low-pass filtered current signal I'(t) and the low-pass filtered voltage signal V'(t) are respectively down-sampled to generate a down-sampled current signal S_I and a down-sampled voltage signal S_V.
在步驟S90中,利用具有不同通帶(例如具有不同中心頻率的通帶)的帶通濾波器電路28_1~28_N來產生帶通濾波電流訊號BPFI_1~BPFI_N以及帶 通濾波電壓訊號BPFV_1~BPFV_N,其中一帶通濾波電流訊號以及一帶通濾波電壓訊號係自帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路來產生。 In step S90, bandpass filter circuits 28_1~28_N with different passbands (for example, passbands with different center frequencies) are used to generate bandpass filtered current signals BPFI_1~BPFI_N and bandpass filter circuits BPFI_1~BPFI_N The pass-filtered voltage signals BPFV_1-BPFV_N, wherein the band-pass-filtered current signal and the band-pass-filtered voltage signal are generated by each of the band-pass filter circuits 28_1-28_N.
在步驟S92中,平整帶通濾波電流訊號BPFI_1~BPFI_N來產生平滑電流訊號SFI_1~SFI_N,並且平整帶通濾波電壓訊號BPFV_1~BPFV_N來產生平滑電壓訊號SFV_1~SFV_N。 In step S92 , the band-pass filtered current signals BPFI_1 ˜ BPFI_N are flattened to generate smooth current signals SFI_1 ˜ SFI_N, and the band-pass filtered voltage signals BPFV_1 ˜ BPFV_N are flattened to generate smooth voltage signals SFV_1 ˜ SFV_N.
在步驟S94中,根據平滑電流訊號SFI_1~SFI_N以及平滑電壓訊號SFV_1~SFV_N來產生複數個阻抗值,其中對於包含有一平滑電流訊號以及一平滑電壓訊號的每一個平滑濾波器輸出,將該平滑電壓訊號除以該平滑電流訊號以產生一阻抗值。 In step S94, a plurality of impedance values are generated according to the smoothed current signals SFI_1~SFI_N and the smoothed voltage signals SFV_1~SFV_N, wherein for each smoothing filter output including a smoothed current signal and a smoothed voltage signal, the smoothed voltage The signal is divided by the smoothed current signal to generate an impedance value.
在步驟S96中,根據對應於該複數個阻抗值中之最大值的一或多個帶通濾波器電路之中心頻率來估測揚聲器50的基本共振頻率Fo。
In step S96 , the fundamental resonant frequency F o of the
由於熟習技藝者可透過有關第1圖以及第2圖所示之揚聲器控制器10的說明書內容而輕易瞭解第3圖所示各步驟的操作,為了簡潔起見,於本實施例中類似的內容在此不重複贅述。
Since those skilled in the art can easily understand the operation of each step shown in Fig. 3 through the contents of the instruction manual of the
為了闡明與利用快速傅立葉轉換分析來取得基本共振頻率的方式相比,本發明亦可在高準確度以及低成本的情況下估測基本共振頻率,以下分別利用具有快速傅立葉轉換的頻域阻抗量測以及本發明的方法來分析並且取得一揚聲器播放一組特定音樂時的基本共振頻率。請搭配參照第4圖以及第5圖,第4圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器50之阻抗曲線的
示意圖。第5圖為依據本發明一第一實施例之藉由第3圖所示之方法的揚聲器50之基本共振頻率Fo的估測示意圖。如第4圖所示,藉由具有快速傅立葉轉換的頻域阻抗量測,可得知揚聲器50之基本共振頻率Fo係大約等於190赫茲。如第5圖所示,藉由第3圖所示之方法,在估測揚聲器50之基本共振頻率Fo之前,五個帶通濾波器電路28_1~28_5(N=5)可以根據標稱基本共振頻率來被分別預先放置在200赫茲、210赫茲、220赫茲、230赫茲以及240赫茲,但是本發明不限於此。
In order to clarify that compared with the method of obtaining the fundamental resonance frequency by using fast Fourier transform analysis, the present invention can also estimate the fundamental resonance frequency with high accuracy and low cost. The following uses frequency domain impedance quantities with fast Fourier transform respectively The basic resonant frequency of a loudspeaker playing a set of specific music is analyzed and obtained through the measurement and the method of the present invention. Please refer to FIG. 4 and FIG. 5 together. FIG. 4 is a schematic diagram of the impedance curve of the
如第5圖所示,在200赫茲的帶通濾波器電路(亦即帶通濾波器電路28_1)對應於最高阻抗值,其中最高阻抗值係大約等於19歐姆,因此,揚聲器50之基本共振頻率Fo可被估測為最接近200赫茲。在揚聲器之基本共振頻率的估測中,一誤差通常係在小於50赫茲的容忍範圍中,而200赫茲以及190赫茲的差距(亦即10赫茲)係小於50赫茲,因此,與具有快速傅立葉轉換的頻域阻抗量測相比,第3圖所示之方法可以在高準確度以及低成本的情況下估測揚聲器50之基本共振頻率Fo。
As shown in FIG. 5, the band-pass filter circuit (ie, band-pass filter circuit 28_1) at 200 Hz corresponds to the highest impedance value, wherein the highest impedance value is approximately equal to 19 ohms. Therefore, the fundamental resonance frequency of the loudspeaker 50 F o can be estimated to the nearest 200 Hz. In the estimation of the fundamental resonant frequency of the loudspeaker, an error is usually within the tolerance range of less than 50 Hz, and the difference between 200 Hz and 190 Hz (that is, 10 Hz) is less than 50 Hz. Compared with the frequency-domain impedance measurement of , the method shown in FIG. 3 can estimate the fundamental resonant frequency F o of the
請搭配參照第6圖以及第7圖,第6圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器50之另一阻抗曲線的示意圖。第7圖為依據本發明一第二實施例之藉由第3圖所示之方法的揚聲器50之基本共振頻率Fo的估測示意圖。如第6圖所示,藉由具有快速傅立葉轉換的頻域阻抗量測,可得知揚聲器50之基本共振頻率Fo係大約等於95赫茲。如第7圖所示,藉由第3圖所示之方法,雖然第6圖所示之基本共振頻率Fo係大約等於95赫茲,在估測揚聲器50之基本共振頻率Fo之前,五個帶通濾波器電路28_1~28_5(N=5)仍可以被分別預先放置在200赫茲、210赫茲、220赫茲、230赫茲以及240赫茲,其中這些頻率皆遠於第6圖所示之基本共振頻率Fo,但是本發明不限於此。
Please refer to FIG. 6 and FIG. 7 together. FIG. 6 is a schematic diagram of another impedance curve of the
如第7圖所示,在200赫茲的帶通濾波器電路(亦即帶通濾波器電路28_1)對應於最高阻抗值,其中最高阻抗值係大約等於14歐姆,因此,揚聲器50之基本共振頻率Fo可被估測為最接近200赫茲。在揚聲器之基本共振頻率的估測中,一誤差通常係在小於50赫茲的容忍範圍中,而200赫茲以及95赫茲的差距(亦即105赫茲)係大於50赫茲,雖然藉由本發明之第3圖所示之方法無法利用帶通濾波器電路的中心頻率設置來準確地估測揚聲器50之基本共振頻率Fo,由於帶通濾波器電路所被放置的頻率越接近揚聲器50之基本共振頻率Fo,則該帶通濾波器電路所對應的阻抗值越大,因此揚聲器50之基本共振頻率Fo的趨勢仍可藉由第3圖所示之方法來得知。揚聲器50之基本共振頻率Fo的電流估測結果可被利用來作為適應地調整帶通濾波器電路之中心頻率設置的一參考,如此一來,在根據揚聲器50之基本共振頻率Fo的趨勢來適當地調整帶通濾波器電路之中心頻率設置之後,藉由本發明之第3圖所示之方法可以準確地估測揚聲器50之基本共振頻率Fo。
As shown in FIG. 7, the band-pass filter circuit (ie, band-pass filter circuit 28_1) at 200 Hz corresponds to the highest impedance value, wherein the highest impedance value is approximately equal to 14 ohms. Therefore, the fundamental resonance frequency of the loudspeaker 50 F o can be estimated to the nearest 200 Hz. In the estimation of the fundamental resonant frequency of the loudspeaker, an error is usually within the tolerance range of less than 50 Hz, and the difference between 200 Hz and 95 Hz (that is, 105 Hz) is greater than 50 Hz, although by the third method of the present invention The method shown in the figure cannot use the central frequency setting of the band-pass filter circuit to accurately estimate the fundamental resonance frequency F o of the
請搭配參照第8圖以及第9圖,第8圖為藉由具有快速傅立葉轉換的頻域阻抗量測所取得的揚聲器50之再另一阻抗曲線的示意圖。第9圖為依據本發明一第三實施例之藉由第3圖所示之方法的揚聲器50之基本共振頻率Fo的估測示意圖。如第8圖所示,藉由具有快速傅立葉轉換的頻域阻抗量測,可得知揚聲器50之基本共振頻率Fo係大約等於205赫茲。如第9圖所示,藉由第3圖所示之方法,在估測揚聲器50之基本共振頻率Fo之前,五個帶通濾波器電路28_1~28_5(N=5)可以根據標稱基本共振頻率來被分別預先放置在200赫茲、210赫茲、220赫茲、230赫茲以及240赫茲,但是本發明不限於此。
Please refer to FIG. 8 and FIG. 9 together. FIG. 8 is a schematic diagram of yet another impedance curve of the
如第9圖所示,自位於200赫茲的帶通濾波器電路(例如帶通濾波器電路28_1)之濾波器輸出所取得的阻抗值與自位於210赫茲的帶通濾波器電路(例如帶通濾波器電路28_2)之濾波器輸出所取得的阻抗值相當接近,因此,要判斷哪個帶通濾波器電路具有最高阻抗值相當困難。在此案例中,揚聲器50之基本共振頻率Fo可以被估測為在200赫茲以及210赫茲之間的中間頻率(亦即205赫茲),在揚聲器之基本共振頻率的估測中,一誤差通常係在小於50赫茲的容忍範圍中,而本實施例的估測結果正好與第8圖所示之揚聲器之基本共振頻率相同,因此,與具有快速傅立葉轉換的頻域阻抗量測相比,第3圖所示之方法可以在高準確度以及低成本的情況下估測揚聲器50之基本共振頻率Fo。
As shown in FIG. 9, the impedance value obtained from the filter output of the band-pass filter circuit (for example, band-pass filter circuit 28_1) at 200 Hz is the same as that obtained from the filter output of the band-pass filter circuit (for example, band-pass filter circuit 28_1) at 210 Hz. The impedance values obtained by the filter outputs of the filter circuit 28_2) are quite close, so it is quite difficult to determine which bandpass filter circuit has the highest impedance value. In this case, the fundamental resonant frequency F o of the
應注意的是,當揚聲器用以進行音訊播放而被驅動於一低音量時,第3圖所示之方法的估測結果可能會有誤差,舉例來說,在第9圖所示之第10秒~第15秒的時間中,在200赫茲的帶通濾波器電路(亦即帶通濾波器電路28_1)對應於最高阻抗值,其與自位於200赫茲的帶通濾波器電路(例如帶通濾波器電路28_1)之濾波器輸出所取得的阻抗值與自位於210赫茲的帶通濾波器電路(例如帶通濾波器電路28_2)之濾波器輸出所取得的阻抗值相當接近的上述案例不相同。為了解決此問題,一強度門檻可以被加入至揚聲器控制器,以避免當揚聲器用以進行音訊播放而被驅動於低音量時發生誤差。 It should be noted that when the speaker is driven at a low volume for audio playback, the estimation result of the method shown in Fig. 3 may have errors, for example, in Fig. In the time from second to the 15th second, the band-pass filter circuit at 200 Hz (that is, the band-pass filter circuit 28_1) corresponds to the highest impedance value, which is different from the band-pass filter circuit at 200 Hz (such as the band-pass filter circuit 28_1). The impedance value obtained from the filter output of the filter circuit 28_1) is not the same as the above case in which the impedance value obtained from the filter output of the band-pass filter circuit at 210 Hz (for example, the band-pass filter circuit 28_2) is quite close . To solve this problem, an intensity threshold can be added to the speaker controller to avoid errors when the speaker is driven at a low volume for audio playback.
第10圖為依據本發明一實施例之第1圖所示之揚聲器控制器10的另一實施範例的示意圖。為了避免當揚聲器50用以進行音訊播放而被驅動於低音量時發生誤差,第10圖所示之估測電路30另包含有一強度門檻電路40,強度門檻電路40係耦接於放大器電路12、平滑濾波器電路32以及處理電路38,並且用以將驅動訊號A_DRV的一強度(magnitude)MAG與一強度門檻(magnitude
threshold)TH進行比較。當驅動訊號A_DRV的強度MAG超過強度門檻TH時,估測電路30根據帶通濾波器電路28_1~28_N的濾波器輸出來估測基本共振頻率Fo,舉例來說,當驅動訊號A_DRV的強度MAG超過強度門檻TH時,處理電路38藉由對自平滑電流訊號SFI_1~SFI_N以及平滑電壓訊號SFV_1~SFV_N所取得的阻抗值進行比較來估測基本共振頻率Fo,其中平滑電流訊號SFI_1~SFI_N係藉由濾波帶通濾波電流訊號BPFI_1~BPFI_N來取得,以及平滑電壓訊號SFV_1~SFV_N係藉由濾波帶通濾波電壓訊號BPFV_1~BPFV_N來取得。當驅動訊號A_DRV的強度MAG不超過強度門檻TH時,估測電路30不會根據帶通濾波器電路28_1~28_N的濾波器輸出來估測基本共振頻率Fo,如此一來,可以避免上述在低音量時的估測誤差。
FIG. 10 is a schematic diagram of another implementation example of the
第11圖為依據本發明一實施例之用以估測揚聲器之基本共振頻率的另一方法流程圖。假若可以得到相同的結果,則步驟不一定要完全遵照第11圖所示的流程來依序執行,舉例來說,第11圖所示之方法可由第10圖所示之揚聲器控制器10來加以實現。第3圖所示之方法以及第11圖所示之方法之間的差別在於第11圖所示之方法另包含有步驟S98,在步驟S98中,當驅動訊號A_DRV的強度MAG超過強度門檻TH時,流程進入步驟S96;當驅動訊號A_DRV的強度MAG不超過強度門檻TH時,流程回到步驟S80。
FIG. 11 is a flow chart of another method for estimating the fundamental resonant frequency of a loudspeaker according to an embodiment of the present invention. If the same result can be obtained, the steps do not have to be executed sequentially according to the flow shown in Figure 11. For example, the method shown in Figure 11 can be implemented by the
在本發明的某些實施例中,只有當驅動訊號A_DRV之一電流強度或一電壓強度大於強度門檻TH時,感測電路14才可感測驅動訊號A_DRV的特性來產生量測訊號S_M(其可包含量測電流訊號I(t)以及量測電壓訊號V(t)),舉例來說,強度門檻TH可被設置為一電流門檻,並且只有當驅動訊號之電流強度大於強度門檻TH時,感測電路14才被允許感測驅動訊號A_DRV的特性來產生量測訊
號S_M,但是本發明不限於此。
In some embodiments of the present invention, only when the current intensity or a voltage intensity of the driving signal A_DRV is greater than the intensity threshold TH, the
第12圖為依據本發明一實施例之第1圖所示之揚聲器控制器10的再另一實施範例的示意圖。在本實施例中,電壓可被設置為一固定值,並且電流與阻抗之間的關係為倒數,因此,如第12圖所示,感測電路14可包含有電流感測電路16以及預處理電路20,電流感測電路16可量測流過揚聲器50之音圈的一電流來產生量測電流訊號I(t),並且預處理電路20係用以根據量測電流訊號I(t)來產生量測訊號S_M。在本實施例中,預處理電路20可包含有低通濾波器電路22以及降低取樣電路24,其中降低取樣電路24係耦接於低通濾波器電路22。低通濾波器電路22可包含有一低通濾波器23_1(為簡潔起見,標記為“LPF1”),其中低通濾波器23_1可接收電流感測電路16所產生的量測電流訊號I(t),並且可低通濾波量測電流訊號I(t)來產生低通濾波電流訊號I’(t)。為了減少計算複雜度以及/或增加準確度,降低取樣電路24可接收低通濾波電流訊號I’(t)來產生降低取樣電流訊號S_I,其中第1圖所示之量測訊號S_M可包含有第12圖所示之降低取樣電流訊號S_I。
FIG. 12 is a schematic diagram of yet another implementation example of the
感測電路14可以將量測訊號S_M傳送至帶通濾波器電路28_1~28_N,其中量測訊號S_M可包含有一電流訊號(亦即降低取樣電流訊號S_I),此外,帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路可包含有一帶通濾波器,舉例來說,帶通濾波器電路28_1包含有一帶通濾波器29_11(為簡潔起見,標記為“BPF11”);帶通濾波器電路28_2包含有一帶通濾波器29_21(為簡潔起見,標記為“BPF21”);以及帶通濾波器電路28_N包含有一帶通濾波器29_N1(為簡潔起見,標記為“BPFN1”)。在帶通濾波器電路28_1~28_N中的每一個帶通濾波器電路中的帶通濾波器可用以自感測電路14接收電流訊號(例如降
低取樣電流訊號S_I),並且藉由濾波電流訊號來產生一帶通濾波電流訊號,以及帶通濾波器電路的一濾波器輸出包含有該帶通濾波電流訊號。舉例來說,濾波器輸出BPFOUT_1包含有帶通濾波電流訊號BPFI_1,濾波器輸出BPFOUT_2包含有帶通濾波電流訊號BPFI_2,以及濾波器輸出BPFOUT_N包含有帶通濾波電流訊號BPFI_N。
The
揚聲器控制器10之估測電路30可包含有一平滑濾波器電路32以及一處理電路38,平滑濾波器電路32可用以自帶通濾波器電路28_1~28_N接收濾波器輸出並且藉由分別平整濾波器輸出來產生複數個平滑濾波器輸出。在本實施例中,平滑濾波器電路32可包含有複數個阿爾發濾波器電路36_1、36_2、...、36_N,其中阿爾發濾波器電路36_1~36_N分別耦接於帶通濾波器電路28_1~28_N。此外,阿爾發濾波器電路36_1~36_N中的每一個阿爾發濾波器電路可包含有一阿爾發濾波器(為簡潔起見,標記為“α filter”),舉例來說,阿爾發濾波器電路36_1包含有阿爾發濾波器37_11(其耦接於帶通濾波器29_11),阿爾發濾波器電路36_2包含有阿爾發濾波器37_21(其耦接於帶通濾波器29_21),以及阿爾發濾波器電路36_N包含有阿爾發濾波器37_N1(其耦接於帶通濾波器29_N1)。
The
如第12圖所示,阿爾發濾波器電路36_1所產生的一平滑濾波器輸出包含有平滑電流訊號SFI_1,其中平滑電流訊號SFI_1藉由將帶通濾波電流訊號BPFI_1通過阿爾發濾波器37_11來取得;阿爾發濾波器電路36_2所產生的一平滑濾波器輸出包含有平滑電流訊號SFI_2,其中平滑電流訊號SFI_2藉由將帶通濾波電流訊號BPFI_2通過阿爾發濾波器37_21來取得;以及阿爾發濾波器電路36_N所產生的一平滑濾波器輸出包含有平滑電流訊號SFI_N,其中平滑電流訊號SFI_N藉由將帶通濾波電流訊號BPFI_N通過阿爾發濾波器37_N1來取得。 As shown in FIG. 12, a smoothing filter output generated by the alpha filter circuit 36_1 includes a smoothed current signal SFI_1, wherein the smoothed current signal SFI_1 is obtained by passing the band-pass filtered current signal BPFI_1 through the alpha filter 37_11 ; A smoothing filter output generated by the alpha filter circuit 36_2 includes a smooth current signal SFI_2, wherein the smooth current signal SFI_2 is obtained by passing the band-pass filtered current signal BPFI_2 through the alpha filter 37_21; and the alpha filter A smoothing filter output generated by the circuit 36_N includes the smoothed current signal SFI_N, wherein the smoothed current signal SFI_N is obtained by passing the band-pass filtered current signal BPFI_N through the alpha filter 37_N1.
在本實施例中,由於電壓係被設置為一固定值,對於平滑濾波器電路32(尤指平滑濾波器電路32中的阿爾發濾波器電路36_1~36_N)所產生的每一個平滑濾波器輸出(尤指平滑電流訊號)來說,處理電路38可用以比較每一個平滑電流訊號的強度,其中當平滑電流訊號的強度越小時,則藉由處理電路38所估測出來的揚聲器50之基本共振頻率Fo越大,因此,在自複數個平滑電流訊號{SFI_1、SFI_2、...、SFI_N}的強度中找到了一個最小值的案例中,揚聲器50的基本共振頻率Fo係被估測為涉及該最小值之推導的帶通濾波器電路之中心頻率,舉例來說,如果對應於在複數個平滑電流訊號{SFI_1、SFI_2、...、SFI_N}的強度之中的最小值的帶通濾波器電路之中心頻率係為200赫茲,則揚聲器50的基本共振頻率Fo可被估測為200赫茲。為簡潔起見,於本實施例中類似的內容在此不重複贅述。
In this embodiment, since the voltage is set to a fixed value, each smoothing filter output generated by the smoothing filter circuit 32 (especially the alpha filter circuits 36_1~36_N in the smoothing filter circuit 32) (especially the smooth current signal), the
以上所述僅為本發明之較佳實施例,凡依本發明申請專利範圍所做之均等變化與修飾,皆應屬本發明之涵蓋範圍。 The above descriptions are only preferred embodiments of the present invention, and all equivalent changes and modifications made according to the scope of the patent application of the present invention shall fall within the scope of the present invention.
10:揚聲器控制器 10:Speaker controller
12:放大器電路 12: Amplifier circuit
14:感測電路 14: Sensing circuit
28_1~28_N:帶通濾波器電路 28_1~28_N: Bandpass filter circuit
30:估測電路 30: Estimation circuit
50:揚聲器 50: speaker
A_IN:音訊輸入訊號 A_IN: audio input signal
A_DRV:驅動訊號 A_DRV: drive signal
S_M:量測訊號 S_M: Measurement signal
BPFOUT_1~BPFOUT_N:濾波器輸出 BPFOUT_1~BPFOUT_N: filter output
Fo:基本共振頻率 F o : Fundamental resonance frequency
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US20150030169A1 (en) * | 2013-07-23 | 2015-01-29 | Analog Devices A/S | Method of Controlling Sound Reproduction of Enclosure Mounted Loudspeakers |
US20150030167A1 (en) * | 2013-07-23 | 2015-01-29 | Analog Devices A/S | Method of Detecting Enclosure Leakage of Enclosure Mounted Loudspeakers |
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