TWI741050B - Sending device, sending method, receiving device, and receiving method - Google Patents
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- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
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- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/068—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission using space frequency diversity
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- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
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- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
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- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
- H04B7/0619—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side
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- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0667—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal
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- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0682—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission using phase diversity (e.g. phase sweeping)
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- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
- H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
- H04B7/0842—Weighted combining
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- H04B7/00—Radio transmission systems, i.e. using radiation field
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- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
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- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/0078—Avoidance of errors by organising the transmitted data in a format specifically designed to deal with errors, e.g. location
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- H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
- H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
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- H04L27/00—Modulated-carrier systems
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- H04L27/2601—Multicarrier modulation systems
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- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
- H04L27/2634—Inverse fast Fourier transform [IFFT] or inverse discrete Fourier transform [IDFT] modulators in combination with other circuits for modulation
- H04L27/2636—Inverse fast Fourier transform [IFFT] or inverse discrete Fourier transform [IDFT] modulators in combination with other circuits for modulation with FFT or DFT modulators, e.g. standard single-carrier frequency-division multiple access [SC-FDMA] transmitter or DFT spread orthogonal frequency division multiplexing [DFT-SOFDM]
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Abstract
本發明採用下述構成:一種發送裝置,具備:預編碼部,對第1基頻訊號與第2基頻訊號施行預編碼處理,以生成第1預編碼訊號與第2預編碼訊號;順序反轉部,使構成第2預編碼訊號的符號之順序反轉,而生成第2反轉訊號;相位變更部,生成第2相位變更訊號,且該第2相位變更訊號是對第2反轉訊號施行了相位變更的訊號;及發送部,分別從不同的天線發送第1預編碼訊號與第2相位變更訊號。The present invention adopts the following configuration: a transmitting device including: a precoding unit that performs precoding processing on a first baseband signal and a second baseband signal to generate a first precoding signal and a second precoding signal; the order is reversed The turning part inverts the order of the symbols constituting the second precoding signal to generate a second inversion signal; the phase changing part generates a second phase change signal, and the second phase change signal is the second inversion signal The signal with the phase change implemented; and the transmitting part, which respectively transmits the first precoding signal and the second phase change signal from different antennas.
Description
發明領域 本揭示是有關於一種進行使用了多天線(multi-antenna)的通訊之發送裝置、發送方法、接收裝置、及接收方法。FIELD OF THE INVENTION The present disclosure relates to a transmitting device, a transmitting method, a receiving device, and a receiving method for communication using multi-antenna.
發明背景 無線LAN相關規格的一種、即IEEE802.11ad規格,是有關於利用60GHz頻段的毫米波之無線通訊的規格(非專利文獻1)。在IEEE802.11ad規格中,規定有藉由單載波(Single Carrier)進行的發送。BACKGROUND OF THE INVENTION One of the standards related to wireless LAN, the IEEE802.11ad standard, is a standard for wireless communication using millimeter waves in the 60 GHz band (Non-Patent Document 1). In the IEEE802.11ad specification, transmission by a single carrier (Single Carrier) is specified.
又,關於利用了多天線的通訊技術之1種,有MIMO(多輸入多輸出,Multiple-Input Multiple-Output)(非專利文獻2)。藉由利用MIMO,可提高空間分集(space diversity)效果,且提升接收品質。 先前技術文獻 非專利文獻In addition, one type of communication technology using multiple antennas is MIMO (Multiple-Input Multiple-Output) (Non-Patent Document 2). By using MIMO, the space diversity effect can be improved, and the reception quality can be improved. Previous technical literature Non-patent literature
非專利文獻1:IEEE802.11adTM -2012,2012年12月28日 非專利文獻2:“MIMO for DVB-NGH, the next generation mobile TV broadcasting,” IEEE Commun. Mag., vol.57, no.7, pp.130-137,2013年7月 非專利文獻3:IEEE802.11-16/0631r0,2016年5月15日 非專利文獻4:IEEE802.11-16/0632r0,2016年5月15日Non-Patent Document 1: IEEE802.11ad TM -2012, December 28, 2012 Non-Patent Document 2: "MIMO for DVB-NGH, the next generation mobile TV broadcasting," IEEE Commun. Mag., vol.57, no. 7, pp.130-137, July 2013 Non-Patent Document 3: IEEE802.11-16/0631r0, May 15, 2016 Non-Patent Document 4: IEEE802.11-16/0632r0, May 15, 2016
發明概要 發明欲解決之課題 但是,在利用單載波的MIMO通訊中,會有無法充分地得到頻率分集(frequency diversity)效果的情況。Summary of the Invention Problems to be Solved by the Invention However, in MIMO communication using a single carrier, there may be cases where the frequency diversity effect cannot be sufficiently obtained.
本揭示之非限定的實施例有助於提供一種可提高利用了單載波之MIMO通訊中的頻率分集效果的發送裝置、發送方法、接收裝置、及接收方法。 用以解決課題之手段The non-limiting embodiments of the present disclosure help to provide a transmitting device, a transmitting method, a receiving device, and a receiving method that can improve the frequency diversity effect in MIMO communication using a single carrier. Means to solve the problem
本揭示之一態様的發送裝置,具備:預編碼部,對第1基頻訊號與第2基頻訊號施行預編碼處理,以生成第1預編碼訊號與第2預編碼訊號;順序反轉部,使構成前述第2預編碼訊號的符號序列之順序反轉,而生成第2反轉訊號;相位變更部,生成第2相位變更訊號,且該第2相位變更訊號是對前述第2反轉訊號施行了相位變更之訊號;及發送部,分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。The transmitting device of one aspect of the present disclosure includes: a precoding unit that performs precoding processing on the first baseband signal and the second baseband signal to generate the first precoding signal and the second precoding signal; and the sequence reversal unit , The sequence of the symbol sequence constituting the second precoding signal is reversed to generate a second inversion signal; the phase changing section generates a second phase change signal, and the second phase change signal is the second inversion signal The signal undergoes a phase change signal; and the transmitting unit transmits the first precoding signal and the second phase change signal from different antennas.
本揭示之一態様的接收裝置,具備:接收部,以不同的天線來分別接收第1接收訊號及第2接收訊號;及解調部,從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號,在前述第1接收訊號及前述第2接收訊號中,包含有第1預編碼訊號及第2相位變更訊號,前述第1預編碼訊號,是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號,前述第2相位變更訊號是下述之訊號:前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號,且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號,並對該生成的第2反轉訊號施行相位變更而生成的訊號。A receiving device in one aspect of the present disclosure includes: a receiving unit that uses different antennas to receive the first received signal and the second received signal, respectively; and a demodulation unit that generates from the first received signal and the second received signal The first baseband signal and the second baseband signal. The first received signal and the second received signal include a first precoding signal and a second phase change signal. The first precoding signal is a transmitting device. The first baseband signal and the second baseband signal are pre-encoded to generate a signal, and the second phase change signal is the following signal: The frequency signal is pre-encoded to generate a second pre-encoded signal, and the sequence of the symbol sequence constituting the second pre-encoded signal is reversed to generate a second inverted signal, and the generated second inverted signal The signal generated by the implementation of the phase change.
再者,這些全面的或具體的態樣可以利用系統、方法、積體電路、電腦程式、或者記錄媒體來實現,亦可藉系統、裝置、方法、積體電路、電腦程式及記錄媒體的任意的組合來實現。 發明效果Furthermore, these comprehensive or specific aspects can be implemented using systems, methods, integrated circuits, computer programs, or recording media, or any of systems, devices, methods, integrated circuits, computer programs, and recording media. The combination to achieve. Invention effect
根據本揭示的一態樣,可以提高利用了單載波之MIMO通訊中的頻率分集效果。According to an aspect of the present disclosure, the frequency diversity effect in MIMO communication using a single carrier can be improved.
本揭示的一態様中的進一步之優點及效果,從說明書及圖式中可清楚地了解。雖然所述優點及/或效果是藉由一些實施形態以及說明書及圖式所記載之特徵來分別地提供,然而為了得到1個或其以上的相同的特徵,並不一定需要全部都提供。The further advantages and effects of the one aspect of the present disclosure can be clearly understood from the description and the drawings. Although the advantages and/or effects are separately provided by some embodiments and the features described in the specification and drawings, in order to obtain one or more of the same features, it is not necessary to provide all of them.
用以實施發明之形態 以下,參照圖式並詳細地說明本揭示的實施形態。Modes for Carrying Out the Invention Hereinafter, embodiments of the present disclosure will be described in detail with reference to the drawings.
(實施形態1) 圖1為顯示MIMO通訊系統的構成之一例的圖。發送裝置具備複數個發送天線。接收裝置具備複數個接收天線。(Embodiment 1) Fig. 1 is a diagram showing an example of the configuration of a MIMO communication system. The transmitting device includes a plurality of transmitting antennas. The receiving device includes a plurality of receiving antennas.
將各發送天線與各接收天線之間的無線傳遞路徑稱為通道。在圖1中,在第1發送天線與第1接收天線之間、第1發送天線與第2接收天線之間、第2發送天線與第1接收天線之間、及第2發送天線與第2接收天線之間,分別有通道H11 (k)、通道H12 (k)、通道H21 (k)、及通道H22 (k)。在各通道中,可合成例如直接波、反射波、繞射波、及/或散射波。通道H11 (k)、H12 (k)、H21 (k)、及H22 (k)的值為各通道的頻率響應。頻率響應是頻率的指數k中之複數(complex number)。The wireless transmission path between each transmitting antenna and each receiving antenna is called a channel. In Figure 1, between the first transmitting antenna and the first receiving antenna, between the first transmitting antenna and the second receiving antenna, between the second transmitting antenna and the first receiving antenna, and between the second transmitting antenna and the second transmitting antenna Among the receiving antennas, there are channel H 11 (k), channel H 12 (k), channel H 21 (k), and channel H 22 (k). In each channel, for example, direct waves, reflected waves, diffracted waves, and/or scattered waves can be synthesized. The values of channels H 11 (k), H 12 (k), H 21 (k), and H 22 (k) are the frequency response of each channel. The frequency response is the complex number in the frequency index k.
發送裝置是從各發送天線中將不同的發送資料同時地、亦即在D/A轉換器中以相同的取樣定時(sampling timing)來發送。接收裝置具備複數個接收天線。接收裝置是以各接收天線對接收資料同時地、亦即在A/D轉換器中以相同的取樣定時來進行接收。但是,由於各通道的延遲不同,因此發送裝置已同時發送的發送資料不一定會被接收裝置同時地接收。The transmitting device simultaneously transmits different transmission data from each transmitting antenna, that is, at the same sampling timing in the D/A converter. The receiving device includes a plurality of receiving antennas. In the receiving device, each receiving antenna simultaneously receives the received data, that is, receives the same sampling timing in the A/D converter. However, due to the different delays of each channel, the transmission data that has been sent by the sending device at the same time may not be received by the receiving device at the same time.
圖2是顯示頻率響應之振幅成分的例子之圖。在圖2中,所顯示的是每個通道的頻率響應不同,且通道間的相關較低的狀態之一例。Fig. 2 is a diagram showing an example of the amplitude component of the frequency response. In Figure 2, what is shown is an example of a state where the frequency response of each channel is different, and the correlation between the channels is low.
接收裝置在接收來自第1發送天線的發送資料x1 (b,n)之情況下,會進行例如如下的處理。也就是說,接收裝置是對第1接收天線的接收資料與第2接收天線的接收資料乘上複數(complex number)之加權係數,並對資料進行加法運算,以增強來自通道H11 (k)及通道H12 (k)的接收訊號,並抑制來自通道H21 (k)及通道H22 (k)的接收訊號。加權係數是利用例如後述的MMSE(最小均方誤差,Minimum Mean Square Error)而算出。When the receiving device receives the transmission data x 1 (b, n) from the first transmission antenna, for example, the following processing is performed. In other words, the receiving device multiplies the received data from the first receiving antenna and the received data from the second receiving antenna by a complex number weighting coefficient, and adds the data to enhance the signal from the channel H 11 (k) And channel H 12 (k) reception signal, and suppress the reception signal from channel H 21 (k) and channel H 22 (k). The weighting coefficient is calculated using, for example, MMSE (Minimum Mean Square Error) described later.
圖3是顯示發送裝置100的構成之一例的圖。在圖3中,發送裝置100具備MAC部101、流(stream)生成部102、編碼部103a、103b、資料調變部104a、104b、預編碼部105、GI(保護間隔(Guard Interval))附加部106a、106b、符號順序反轉部107、資料符號緩衝器108a、108b、相位旋轉部109、發送F/E電路(濾波D/A轉換RF電路)110a、110b、及發送天線111a、111b。FIG. 3 is a diagram showing an example of the configuration of the transmission device 100. In FIG. 3, the transmitting device 100 includes a
發送裝置100是在資料調變部104a、104b中進行π/2-BPSK調變,且從發送天線111a、111b分別發送不同的資料。The transmitting device 100 performs π/2-BPSK modulation in the
MAC部101是生成發送資料,且將該生成的發送資料輸出至流生成部102。The
流生成部102是將發送資料分割成第1流資料與第2流資料等2個。例如,流生成部102是將發送資料的第奇數個之位元分配至第1流資料,且將發送資料的第偶數個之位元分配至第2流資料。並且,流生成部102會將第1流資料輸出至編碼部103a,且將第2流資料輸出至編碼部103b。流生成部102也可以算出發送資料的CRC(循環冗餘檢查,Cyclic Redundancy Check),且由將該CRC附加於發送資料的最後來生成流資料。The
將對於從流生成部102輸出的第1流資料的處理,稱為第1發送流處理。第1發送流處理是藉由編碼部103a及資料調變部104a來進行。The processing of the first stream data output from the
將對於從流生成部102輸出的第2流資料的處理,稱為第2發送流處理。第2發送流處理是藉由編碼部103b及資料調變部104b來進行。The processing of the second stream data output from the
編碼部103a、103b會對各流資料進行糾錯編碼處理。編碼部103a、103b亦可將例如LDPC(低密度奇偶檢查,Low Density Parity Check)碼利用於糾錯編碼方式上。The
資料調變部104a、104b是對已藉由編碼部103a、103b進行過糾錯編碼處理的各流資料,施行調變處理。資料調變部104a、104b是將例如π/2-BPSK利用於資料調變方式。The
圖4A是顯示符號指數(symbol index)m為奇數的π/2-BPSK(二元相移鍵控,Binary Phase Shift Keying)之星象圖(constellation)的例子。圖4B是顯示符號指數m為偶數的π/2-BPSK之星象圖的例子。將資料調變部104a輸出的資料(也稱為「調變訊號」)表示成調變符號s1
(m)。又,將資料調變部104b輸出的資料表示成調變符號s2
(m)。在此,m是表示符號指數,且為正整數。FIG. 4A is an example of a constellation of π/2-BPSK (Binary Phase Shift Keying) with an odd symbol index m. Fig. 4B is an example showing a π/2-BPSK horoscope with an even symbol index m. The data output by the
在資料調變部104a進行π/2-BPSK調變的情況下,調變符號s1
(m)、s2
(m)會成為以下之值。 在m為奇數的情況下,s1
(m)及s2
(m)是配置在I軸上,且成為+1或-1之任一值。 在m為偶數的情況下,s1
(m)及s2
(m)是配置在Q軸上,且成為+j或-j之任一值。在此,j為虛數單位。When the
如算式1所示,預編碼部105是對資料調變部104a、104b的調變符號s1
(m)、s2
(m)乘上2行2列的矩陣,而算出預編碼符號x1
(m)、x2
(m)。(算式1)As shown in
在算式1中,將被相乘於s1
(m)、s2
(m)的2行2列之矩陣,稱為預編碼矩陣(以下表示為「G」)。亦即,預編碼矩陣G是以算式2來表現。(算式2)In
但是,算式2的預編碼矩陣僅為一例,也可以將其他矩陣利用於預編碼矩陣G。例如,也可以將其他的么正矩陣(unitary matrix)利用於預編碼矩陣G。在此,所謂的么正矩陣是滿足算式2-1的矩陣。在算式2-1中,GH
是表示矩陣G的複共軛轉置(complex conjugate transpose),而I是表示單位矩陣。(算式2-1)However, the precoding matrix of
由於算式2的預編碼矩陣G滿足算式2-1,因此是么正矩陣的一例。Since the precoding matrix G of
利用了算式2的預編碼矩陣G的情況下,x1
(m)、x2
(m)會滿足算式2-2的關係。再者,記號「*」是表示複共軛。(算式2-2)When the precoding matrix G of
接著,在算式2-3中表示其他的預編碼矩陣G之例子。(算式2-3)Next, another example of the precoding matrix G is shown in Equation 2-3. (Equation 2-3)
利用了算式2-3的預編碼矩陣G的情況下,x1 (m)、x2 (m)會滿足算式2-4的關係。(算式2-4)When the precoding matrix G of Equation 2-3 is used, x 1 (m) and x 2 (m) satisfy the relationship of Equation 2-4. (Equation 2-4)
接著,在算式2-5中表示其他的預編碼矩陣G之例子。在算式2-5中, a為實數,b為複數的常數。又,ρ是表示相位位移量的常數。(算式2-5)Next, another example of the precoding matrix G is shown in Equation 2-5. In formula 2-5, a is a real number and b is a constant of a complex number. In addition, ρ is a constant representing the amount of phase shift. (Equation 2-5)
利用了算式2-5的預編碼矩陣G的情況下,x1 (m)、x2 (m)會滿足算式2-6的關係。(算式2-6)When the precoding matrix G of Equation 2-5 is used, x 1 (m) and x 2 (m) satisfy the relationship of Equation 2-6. (Equation 2-6)
在算式2-5中,將a、b都設為1,且將ρ設為-π/4的情況下,算式2-5會變得與算式2相等。In Equation 2-5, when both a and b are set to 1, and ρ is set to -π/4, Equation 2-5 becomes equal to
圖4C是顯示預編碼部105的輸出資料x1
(m)、x2
(m)之星象圖的一例之圖。圖4C與QPSK調變的星象圖是相同的。也就是說,預編碼部105是利用算式1,將以π/2-BPSK調變過的2個調變符號s1
(m)、s2
(m),轉換為相當於QPSK符號的2個預編碼符號x1
(m)、x2
(m)。FIG. 4C is a diagram showing an example of a star map of the output data x 1 (m) and x 2 (m) of the precoding unit 105. The astrological diagrams of Fig. 4C and QPSK modulation are the same. In other words, the
對於從預編碼部105輸出的預編碼符號x1
(m)的處理,是稱為第1發送RF鏈(chain)處理。第1發送RF鏈(chain)處理是藉由GI附加部106a、資料符號緩衝器108a、發送F/E(前端,Front End)電路110a、及發送天線111a來進行。 The processing of the precoding symbol x 1 (m) output from the
對於從預編碼部105輸出的預編碼符號x2
(m)的處理,是稱為第2發送RF鏈處理。第2發送RF鏈處理是藉由複共軛GI附加部106b、符號順序反轉部107、資料符號緩衝器108b、相位旋轉部109、發送F/E電路110b、及發送天線111b來進行。 The processing of the precoding symbol x 2 (m) output from the
圖5A是顯示GI附加部106a、複共軛GI附加部106b中的GI附加方法的一例之圖。FIG. 5A is a diagram showing an example of a GI adding method in the
GI附加部106a是將預編碼符號x1
(m)分割成每個448個符號的資料區塊。例如,將x1
(m)之最初的448個符號分割成第1資料區塊(x1
(1,n)),且將其接著的448個符號分割成第2資料區塊(x1
(2,n)),…,並將第b的448個符號分割成第b資料區塊(x1
(b,n))。在此,在本實施形態的情況下,n為1以上且448以下的整數,b為正整數。也就是說,x1
(b,n)是表示第b資料區塊內的第n個預編碼符號。再者,這些符號數僅是一例,本實施形態也可以是這些以外的符號數。The
GI附加部106a是在各資料區塊的前段附加64個符號的GI。GI是對習知的序列進行了π/2-BPSK調變的符號序列。此外,GI附加部106a是在最後的資料區塊之後段附加64個符號的GI。藉此,可生成如圖5A所示的發送符號u1。The
同樣地,複共軛GI附加部106b也是將預編碼符號x2
(m)分割成每個448個符號的資料區塊,且在各資料區塊的前段附加64個符號的GI,並在最後的資料區塊之後段附加64個符號的GI。但是,複共軛GI附加部106b所附加的GI,是GI附加部106a所附加的GI之複共軛。藉此,可生成如圖5A所示的發送符號u2。Similarly, the complex conjugate
在此,將GI附加部106a所附加的GI之第p個符號表示為GI1
(p)。又,將複共軛GI附加部106b所附加的GI之第p個符號表示為GI2
(p)。在本實施形態的情況下,p為1以上且64以下的整數。在此情況下,GI1
(p)與GI2
(p)存有算式3所示的關係。再者,記號「*」是表示複共軛。(算式3)Here, the p-th symbol of the GI added by the
圖5B是顯示對符號區塊(參照圖5A的發送符號u1)進行DFT(Discrete Fourier Transform,離散傅立葉轉換)之後的DFT訊號X1
(b,k)的例子,其中該符號區塊是在預編碼符號x1
(b,n)中附加有GI(p)的符號區塊。圖5C是顯示對符號區塊(參照圖5A的發送符號u2)進行DFT之後的DFT訊號X2
(b,k)的例子,其中該符號區塊是在預編碼符號x2
(b,n)中附加有GI*
(p)的符號區塊。接著,利用DFT訊號X1
(b,k),來說明從GI附加部106a中輸出的訊號之頻率特性。又,利用DFT訊號X2
(b,k),來說明從複共軛GI附加部106b中輸出的訊號之頻率特性。 Fig. 5B is an example showing the DFT signal X 1 (b,k) after DFT (Discrete Fourier Transform) is performed on the symbol block (refer to the transmission symbol u1 in Fig. 5A), where the symbol block is in the pre- A symbol block of GI(p) is added to the coded symbol x 1 (b, n). FIG. 5C is an example showing the DFT signal X 2 (b,k) after DFT is performed on the symbol block (refer to the transmission symbol u2 in FIG. 5A), where the symbol block is in the precoding symbol x 2 (b,n) A symbol block with GI * (p) appended to it. Next, the DFT signal X 1 (b, k) is used to illustrate the frequency characteristics of the signal output from the
在利用了算式2之預編碼矩陣G的情況下,由於x2
(b,n)及GI*
(p)是x1
(b,n)及GI(p)的複共軛,因此DFT訊號X2
(b,k)會成為對DFT訊號X1
(b,k)的複共軛進行頻率反轉,且在頻率區域施加有相位旋轉的訊號。也就是說,X2
(b,k)可用算式3-1來表示。(算式3-1)In the case of using the precoding matrix G of
再者,如下述內容,將算式3-1中的相位旋轉量(exp(j×2πk/N))表示為W。(算式3-2)In addition, the amount of phase rotation (exp(j×2πk/N)) in Equation 3-1 is expressed as W as described below. (Equation 3-2)
藉由預編碼處理,可以將2個調變符號s1 (m)、s2 (m)混合,並利用2個不同的發送天線來發送。藉此,即可得到空間分集效果。又,藉由預編碼處理,可以將2個調變符號s1 (m)、s2 (m)混合,並利用2個不同的頻率指數k、-k來發送。藉此,即可得到頻率分集效果。Through the precoding process, two modulation symbols s 1 (m) and s 2 (m) can be mixed and transmitted using two different transmitting antennas. In this way, the space diversity effect can be obtained. In addition, through the precoding process, two modulation symbols s 1 (m) and s 2 (m) can be mixed and transmitted using two different frequency indices k and -k. In this way, the frequency diversity effect can be obtained.
再者,在圖5B及圖5C中,在2個不同的頻率指數k、-k之絕對值|k|為較小的情況下,由於2個頻率是相接近的,因此會使頻率分集效果減少。在以下,針對抑制像這樣2個頻率相接近,而使頻率分集效果減少的情形之技術進行說明。Furthermore, in Fig. 5B and Fig. 5C, when the absolute value of two different frequency indices k and -k |k| is small, since the two frequencies are close, the frequency diversity effect will be achieved. Reduce. In the following, a technique for suppressing such a case where two frequencies are close to each other and reducing the frequency diversity effect will be described.
圖6A是顯示符號順序反轉部107中的符號順序反轉處理的一例。FIG. 6A shows an example of the sign order reversal processing in the sign
如圖6A所示,符號順序反轉部107是針對各符號區塊,而使預編碼符號x2
(b,n)的順序反轉,並使附加於該預編碼符號x2
(b,n)的GI(p)之順序反轉。為了使說明更容易理解,是將順序已反轉的預編碼符號x2 (time reversal)
(b,n),表示成如算式4。也就是說,以「-n」來表示順序已反轉的符號序列。(算式4)6A, the symbol sequence is reversed for each
又,將順序已反轉的GI2 (time reversal) (p),表示成如算式5。也就是說,以「-p」來表示順序已反轉的符號序列。(算式5) Also, GI 2 (time reversal) (p) whose order has been reversed is expressed as Equation 5. In other words, use "-p" to indicate a sequence of symbols whose order has been reversed. (Equation 5)
圖6C是對符號區塊(參照圖5A的發送符號u1)進行DFT之後的DFT訊號X1
(b,k)的例子,其中該符號區塊是在預編碼符號x1
(b,n)中附加有GI(p)的符號區塊。圖6C與圖5B是同樣的。又,圖6D是對反轉符號x2
(-m)進行DFT後的反轉DFT訊號X2r
(b,k)之例子。在此,反轉符號x2
(-m)包含符號順序反轉後的預編碼符號訊號x2
(b,-n)、以及對GI的複共軛進行了符號順序反轉的GI*
(p)。接著,利用反轉DFT訊號X2r
(b,k),來說明從符號順序反轉部107所輸出的訊號之頻率特性。 6C is an example of the DFT signal X 1 (b,k) after DFT is performed on the symbol block (refer to the transmission symbol u1 in FIG. 5A), where the symbol block is in the precoding symbol x 1 (b,n) A symbol block with GI(p) attached. Fig. 6C is the same as Fig. 5B. Moreover, FIG. 6D is an example of the inverted DFT signal X 2r (b,k) after performing DFT on the inverted symbol x 2 (-m). Here, the reversal sign x 2 (-m) includes the pre-encoded sign signal x 2 (b, -n) after the sign order is reversed, and the GI * (p ). Next, the inverted DFT signal X 2r (b, k) is used to illustrate the frequency characteristics of the signal output from the sign
在利用了算式2之預編碼矩陣G的情況下,由於x2
(b,-n)及GI*
(-p)是將x1
(b,n)及GI(p)的順序反轉而成之符號區塊的複共軛,因此X2r
(b,k)是以算式5-2來表示。(算式5-2)In the case of using the precoding matrix G of
反轉DFT訊號X2r (b,k),是對DFT訊號X1 (b,k)的複共軛施予相位旋轉的訊號。又,在算式5-2中,包含於W的N是DFT尺寸(例如,符號區塊的長度「512」)。The inverted DFT signal X 2r (b,k) is a signal for applying phase rotation to the complex conjugate of the DFT signal X 1 (b,k). In addition, in Equation 5-2, N included in W is the DFT size (for example, the length of the symbol block is "512").
在圖6C、圖6D所示的例子中,與圖5B、圖5C的情況不同,並將第1發送RF鏈處理的DFT訊號X1 (b,k)、以及第2發送RF鏈處理的反轉DFT訊號X2r (b,k)=X1 * (b,k)×W,以相同的頻率指數k來發送。從而,可以得到空間分集效果。In the examples shown in Figs. 6C and 6D, different from the cases of Figs. 5B and 5C, the DFT signal X 1 (b, k) processed by the first transmission RF chain and the reverse of the processing of the second transmission RF chain are combined. The converted DFT signal X 2r (b,k)=X 1 * (b,k)×W, which is sent with the same frequency index k. Thus, the space diversity effect can be obtained.
圖6B是顯示符號順序反轉部107中的符號順序反轉處理的另一例。FIG. 6B shows another example of the sign order reversal processing in the sign
如圖6B所示,符號順序反轉部107是針對各符號區塊,使符號區塊整體的符號序列之順序(符號序列的排列)反轉。此時,符號順序反轉部107為了在符號順序的反轉前之符號區塊、及符號順序的反轉後之符號區塊之間,使GI的位置相等,會移除於最後的資料區塊之後段所附加的GI,並在最初的資料區塊之前附加已使符號順序反轉的GI。再者,如已提出的,符號區塊是例如將64個符號的GI與448個符號的資料區塊合在一起而成的512個符號的區塊。As shown in FIG. 6B, the symbol
符號順序反轉部107亦可在複共軛GI附加部106b所輸出的發送符號u2當中,依序將448個符號份量的資料符號保存至資料符號緩衝器108b,並且以和保存時不同的順序(相反的順序)來從該資料符號緩衝器108b中讀出資料符號,藉此來實現符號順序的反轉。也就是說,資料符號緩衝器108b亦為相當於LIFO(後進先出,Last In, First Out)緩衝器之緩衝器。再者,資料符號緩衝器108b亦可為記憶體、RAM、或暫存器(register)等。The symbol
由於是在符號順序反轉部107中,進行使發送符號u2的符號順序反轉的處理,因此會產生輸出資料相對於輸入資料的延遲。於是,利用資料符號緩衝器108a,可在GI附加部106a所輸出的發送符號u2當中,對資料符號(例如x2
(b,n))施予與在符號順序反轉部107所產生的延遲相同的時間之延遲。藉此,GI附加部106a所輸出的發送符號u1與複共軛GI附加部106b所輸出的發送符號u2會以相同的定時(timing)來發送。再者,在以下的說明中,有時將符號順序反轉部107已使發送符號u2反轉而成的符號區塊,表示為反轉符號u2r。Since the sign
相位旋轉部109在符號順序反轉部107所輸出的反轉符號u2r當中,是按每個符號對資料符號(例如x2
(b,n))施予不同的相位旋轉。亦即,相位旋轉部109是按每個符號來施行不同的相位變更。相位旋轉部109是利用算式6來對資料符號(例如x2
(b,n))施予相位旋轉,並利用算式7來對GI(例如GI2
(p))施予相位旋轉。再者,在算式6、算式7中,θ是表示相位旋轉量。(算式6)(算式7) The phase rotation unit 109 applies a different phase rotation to the data symbol (for example, x 2 (b, n)) for each symbol among the inverted symbols u2r output by the symbol
發送裝置100在預編碼部105所輸出的發送符號當中,對x1(b,n)並未施予相位旋轉,而是對x2(b,n)施予相位旋轉。相位旋轉後的發送符號是以算式8來表示。(算式8)Among the transmission symbols output by the
再者,在圖3中,雖然是將相位旋轉部109配置在第2發送RF鏈處理中,但將相位旋轉部配置在第1發送RF鏈處理及第2發送RF鏈處理之兩者中亦可。在此配置的情況下,可以利用算式9所示的相位旋轉之矩陣。(算式9)Furthermore, in FIG. 3, although the
再者,在算式8中,n為1以上且448以下的情況也可以視為是有關於資料符號的算式(例如算式6),而n為449以上且512以下的情況也可以視為是有關於GI的算式(例如,將從算式8的n減去448後的值設為p的情況下之算式7)。在此情況下,算式8是成為n為1以上且512以下,且x1 (b,n)及x2 (b,-n)會包含資料符號與GI之雙方。Furthermore, in Equation 8, the case where n is 1 or more and 448 or less can also be regarded as an expression related to the data symbol (for example, Equation 6), and the case where n is 449 or more and 512 or less can also be considered as having Regarding the formula for GI (for example, formula 7 when the value obtained by subtracting 448 from n in formula 8 is set to p). In this case, the formula 8 is that n is 1 or more and 512 or less, and x 1 (b,n) and x 2 (b,-n) will include both the data symbol and the GI.
圖6E是顯示按每個符號區塊對相位旋轉後符號t1 (b,n)進行了DFT之DFT訊號T1 (b,k)的圖。圖6F是顯示按每個符號區塊對相位旋轉後符號t2 (b,n)進行了DFT之DFT訊號T2 (b,k)的圖。接著,利用T1 (b,k)、T2 (b,k)來說明相位旋轉後的訊號之頻率特性。 FIG. 6E is a diagram showing the DFT signal T 1 (b, k) after the phase rotation of the symbol t 1 (b, n) is DFT performed for each symbol block. FIG. 6F is a diagram showing the DFT signal T 2 (b, k) after the phase rotation of the symbol t 2 (b, n) is DFT performed for each symbol block. Next, use T 1 (b,k) and T 2 (b,k) to illustrate the frequency characteristics of the phase-rotated signal.
根據算式8,X1 (b,k)與T1 (b,k)是相等的。亦即,圖6C與圖6E除了將記號從X1 置換為T1 這點之外,其餘是相同的。According to Equation 8, X 1 (b,k) and T 1 (b,k) are equal. That is, FIG. 6C and FIG. 6E are the same except that the symbol is replaced from X 1 to T 1 .
圖6F所示的T2 (b,k)是在時間區域中對X2r (b,k)施予了相位旋轉的訊號。利用算式8而在時間區域中施予了相位旋轉的情況下,在頻率區域中,會使頻率指數以算式9-1所算出的頻格(frequency bin)d之份量而位移。N是DFT尺寸(例如,符號區塊的長度「512」)。(算式9-1) T 2 (b,k) shown in FIG. 6F is a signal that X 2r (b,k) is phase-rotated in the time region. When the phase rotation is applied to the time zone using Equation 8, the frequency index will be shifted in the frequency zone by the amount of the frequency bin d calculated in Equation 9-1. N is the DFT size (for example, the length of the symbol block is "512"). (Equation 9-1)
從而,X1 (b,k)是藉由算式9-2,而在T1 (b,k)、T2 (b,k+d)中,利用2個發送天線及2個頻率指數k、k+d來發送。也就是說,可得到空間分集效果及頻率分集效果。(算式9-2)Therefore, X 1 (b,k) is calculated by Equation 9-2, and in T 1 (b,k) and T 2 (b,k+d), two transmitting antennas and two frequency indices k, k+d to send. In other words, the space diversity effect and frequency diversity effect can be obtained. (Equation 9-2)
發送裝置100是將相位旋轉量θ設定成接近於π弧度(180度)或-π弧度(-180度)之值,藉此可以提高頻率分集效果,並提高資料流通量(data throughput)。The transmitting device 100 sets the phase rotation amount θ to a value close to π radians (180 degrees) or -π radians (-180 degrees), thereby improving the frequency diversity effect and increasing data throughput.
再者,發送裝置100也可以將相位旋轉量θ設定成與π弧度(180度)不同的值。藉此,使發送天線111a的發送訊號、與發送天線111b的發送訊號之間的訊號分離變容易。又,資料流通量也會變高。Furthermore, the transmitting device 100 may set the phase rotation amount θ to a value different from π radians (180 degrees). Thereby, the signal separation between the transmission signal of the
對於OFDM中的發送符號施予和π弧度不同的相位旋轉之方法,已在非專利文獻2中作為PH(跳相,Phase Hopping)技術而揭示。但是,本揭示的發送裝置100與非專利文獻2的情況不同,是利用單載波發送,且在第2發送流處理中進行符號順序反轉。藉此,使2個發送訊號之間的訊號分離變容易。又,可得到比較高的頻率分集效果。The method of applying a phase rotation different from π radians to transmission symbols in OFDM has been disclosed in
發送裝置100也可以將相位旋轉量θ設定成例如,-7π/8弧度(d為-224)、-15π/16弧度(d為240)等之值。The transmitting device 100 may also set the phase rotation amount θ to, for example, -7π/8 radians (d is -224), -15π/16 radians (d is 240), and the like.
發送F/E電路110a、110b包含數位及類比濾波器、D/A轉換器、及RF(無線)電路。發送F/E電路110a會將從資料符號緩衝器108a輸出的發送資料v1(包含圖8所示的GI(p)及t1(b,n)之訊號)轉換成無線訊號,並輸出至發送天線111a。發送F/E電路110b會將從相位旋轉部109所輸出的發送資料v2(包含圖8所示的GI*
(-p)及t2(b,-n)之訊號)轉換成無線訊號,並輸出至發送天線111b。The transmitting F/
發送天線111a會發送從發送F/E電路110a輸出的無線訊號。發送天線111b會發送從發送F/E電路110b輸出的無線訊號。也就是說,發送天線111a及111b會分別發送不同的無線訊號。The transmitting
像這樣,發送裝置100是在對2個發送流資料施行了預編碼之後,對其中一個發送流資料施行符號順序反轉及相位旋轉。藉此,可以提升空間分集效果與頻率分集效果。又,可以降低資料通訊中的錯誤率,並使資料流通量提升。In this way, the transmitting device 100 performs precoding on the two transmission stream data, and then performs sign order inversion and phase rotation on one of the transmission stream data. In this way, the space diversity effect and the frequency diversity effect can be improved. In addition, the error rate in data communication can be reduced, and the data circulation can be increased.
圖7是顯示接收裝置200的構成之圖。FIG. 7 is a diagram showing the structure of the receiving device 200. As shown in FIG.
接收天線201a、201b是分別接收無線訊號。將於接收天線201a中對接收訊號的處理,稱為第1接收RF鏈處理。第1接收RF鏈處理是藉由接收F/E電路202a、時間區域同步部203a、及DFT部205a而進行。將於接收天線201b對接收訊號的處理,稱為第2接收RF鏈處理。第2接收RF鏈處理是藉由接收F/E電路202b、時間區域同步部203b、及DFT部205b而進行。The receiving
接收F/E電路202a、202b包含例如RF電路、A/D轉換器、數位濾波器、類比濾波器、及降低取樣處理部,且將無線訊號轉換成數位基頻訊號。The receiving F/
時間區域同步部203a、203b會進行接收封包的定時同步。再者,時間區域同步部203a與時間區域同步部203b也可以相互地交換定時資訊,而取得第1接收RF鏈處理與第2接收RF鏈處理之間的定時同步。The time
通道估測部204是利用第1接收RF鏈處理的接收訊號、及第2接收RF鏈處理的接收訊號,來算出發送裝置與接收裝置之間的無線通道之頻率響應。亦即,按每個頻率指數k來算出圖1的H11
(k)、H12
(k)、H21
(k)、及H22
(k)。The
DFT部205a、205b是將接收資料分割成DFT區塊,並進行DFT。DFT區塊例如是512個符號。圖8是顯示在DFT部205a、205b中將接收資料分割成DFT區塊的方法之圖。The
將第1接收RF鏈處理的接收資料(對DFT部205a的輸入資料)設為y1
(n),且將第2接收RF鏈處理的接收資料(對DFT部205b的輸入資料)設為y2
(n)。接著,利用圖8來說明y1
(n)之處理。再者,針對y2
(n)的處理也是同樣。Set the received data processed by the first receiving RF chain (input data to the
如前所述,發送裝置100是利用2個發送天線111a、111b,來發送2個無線訊號(圖8所示的發送資料v1、發送資料v2)。又,2個無線訊號會有下述之情況:分別在通道中產生直接波與複數個延遲波,而到達接收天線201a及201b。As mentioned above, the transmitting device 100 uses two transmitting
再者,接收訊號除了直接波及延遲波之外,也可以分別包含有例如繞射波及散射波。Furthermore, in addition to the direct wave and the delayed wave, the received signal may also include, for example, diffracted waves and scattered waves, respectively.
DFT部205a是將第1之DFT區塊的時間決定成包含發送資料v1的資料區塊t1
(1,n)、及發送資料v2的資料區塊t2
(1,n)之直接波及延遲波。將第1之DFT區塊的DFT計算結果表示為Y1
(1,k)。如已提出的,k是表示頻率指數,為例如1以上且512以下的整數。DFT is the
同樣地,將DFT部205a、205b中的第b之DFT區塊的DFT計算結果,分別表示為Y1
(b,k)、Y2
(b,k)(b為1以上的整數)。Similarly, the DFT calculation results of the b-th DFT block in the
接收裝置200會利用MMSE權重計算部206、MMSE濾波器部207、逆相位旋轉部208、IDFT(逆DFT)部209a、IDFT及符號順序反轉部209b、及逆預編碼部210,來算出已發送的調變符號s1
(n)、s2
(n)的估測值。接著,針對算出已發送的調變符號s1
(n)、s2
(n)的估測值之方法進行說明。The receiving device 200 uses the MMSE
接收裝置200的DFT部205a、205b之輸出訊號Y1
(b,k)、Y2
(b,k),是利用通道之值,並如算式10地表示。(算式10) The output signals Y 1 (b,k) and Y 2 (b,k) of the
在此,T1 (b,k)是對發送裝置100的符號區塊(算式8的t1 (b,n))進行了DFT的訊號。T2 (b,k)是對發送裝置100的符號區塊(算式8的t2 (b,n))進行了DFT的訊號。Z1 (b,k)是對第1之RF鏈部中的雜訊進行了DFT的訊號。Z2 (b,k)是對第2之RF鏈部中的雜訊進行了DFT的訊號。Here, T 1 (b, k) is a signal obtained by performing DFT on the symbol block of the transmitting device 100 (t 1 (b, n) in Equation 8). T 2 (b, k) is a signal obtained by performing DFT on the symbol block of the transmitting device 100 (t 2 (b, n) in Equation 8). Z 1 (b,k) is a signal obtained by DFT of the noise in the first RF chain. Z 2 (b,k) is a signal obtained by DFT of the noise in the second RF chain.
以矩陣來表示算式10的情況下,會成為算式11。(算式11)When Formula 10 is expressed as a matrix, it becomes
在算式11中,通道矩陣H2x2
(k)是如算式12地制定。(算式12)In
MMSE權重計算部206會根據算式12-1來算出權重矩陣W2x2
(k)。(算式12-1)The MMSE
在算式12-1中,HH 是表示矩陣H的複共軛轉置。又,σ2 是雜訊Z1 (b,k)、Z2 (b,k)的分散。又,I2 ×2 是2行2列的單位矩陣。In Equation 12-1, H H represents the complex conjugate transpose of the matrix H. Furthermore, σ 2 is the dispersion of the noise Z 1 (b,k) and Z 2 (b,k). In addition, I 2 ×2 is an identity matrix with 2 rows and 2 columns.
MMSE濾波器部207會利用算式12-2來算出T1
(b,k)、T2
(b,k)的估測值T^ 1
(b,k)、T^ 2
(b,k)。再者,將對估測值T^ 1
(b,k)的處理稱為第1接收流處理,且將對T^ 2
(b,k)的處理稱為第2接收流處理。(算式12-2)The
將算式12-2的計算稱為MMSE方式。MMSE濾波器部207是根據MMSE方式,而從包含於發送資料v1的t1
(b,n)、包含於發送資料v2的t2
(b,n)、及與各自的直接波及延遲波相混合而成的接收資料y1及y2(參照圖8)中,得到相位旋轉後的資料符號t1
(b,n)、t2
(b,n)的估測值。但是,MMSE濾波器部207會為了活用通道估測值(通道的頻率響應之估測值)H11
(k)、H12
(k)、H21
(k)、及H22
(k),並容易進行計算,而如算式12-2所示,對頻率區域訊號進行計算。The calculation of Equation 12-2 is called the MMSE method. MMSE MMSE filter unit according to
逆相位旋轉部208是進行和圖3的相位旋轉部109相反的處理。相位旋轉部109的處理是相當於在頻率區域中,如圖6F所示,使頻率指數k、-k位移頻格d的份量之處理。在此,d是藉由算式9-1而算出。於是,逆相位旋轉部208會將從MMSE濾波器部207輸出的第2接收流的頻率區域訊號,位移-d的份量。也就是說,逆相位旋轉部208是在頻率區域中進行算式12-3的處理。(算式12-3)The reverse
再者,接收裝置200亦可將IDFT部209a、IDFT及符號順序反轉部209b、及逆相位旋轉部208對調,而在對來自MMSE濾波器部的輸出進行IDFT之後,施予逆相位旋轉。在此情況下,逆相位旋轉部208是在時間區域中進行算式12-4的處理。(算式12-4)Furthermore, the receiving device 200 may swap the
亦即,逆相位旋轉部208雖然是對第2接收流資料施予逆相位旋轉,但由於將符號順序以IDFT及符號順序反轉部209b進行反轉,因此會進行和算式9所制定的矩陣P之乘法運算相同的處理。That is, although the inverse
IDFT部209a會對從逆相位旋轉部208輸出的第1接收流資料進行IDFT。又,IDFT及符號順序反轉部209b會對從逆相位旋轉部208輸出的第2接收流資料進行IDFT,且針對各DFT區塊來反轉符號順序。The
逆預編碼部210是對第1接收流資料及第2接收流資料乘上圖3的預編碼部105所利用的預編碼矩陣G之逆矩陣,來算出s1(b,n)、s2(b,n)的估測值。在算式12-5中表示逆預編碼部210的處理。(算式12-5)The
資料解調部211a、211b會對從逆預編碼部210輸出的s1(b,n)、s2(b,n)之估測值進行資料解調,來算出位元資料的估測值。The data demodulation
解碼部212a、212b會對位元資料的估測值進行由LDPC碼形成的糾錯處理。The
流整合部213是整合第1接收流資料與第2接收流資料,且作為接收資料而通知給MAC部215。The
標頭資料提取部214是從接收資料中提取出標頭資料,來決定例如MCS(調變與編碼方案,Modulation and Coding Scheme)、圖3的相位旋轉部109所利用的相位旋轉量θ。又,標頭資料提取部214亦可控制:適用於逆預編碼部210的預編碼矩陣G、IDFT及符號順序反轉部209b中的符號反轉處理之有無、及逆相位旋轉部208所利用的相位旋轉量θ。The header
在接收裝置200中,由於MMSE濾波器部207是利用將第2發送流資料經頻率位移而成的發送訊號T1
(b,k)、T2
(b,k)來進行估測,因此可以得到更高的頻率分集效果。又,可降低接收錯誤率,且提升資料流通量。In the receiving device 200, since the
<實施形態1之效果> 在實施形態1中,發送裝置100是對第2預編碼符號附加GI的複共軛,且反轉符號順序,而施予相位旋轉(相位變更),其中該GI的複共軛是附加於第1預編碼符號之GI的複共軛。<Effects of the first embodiment> In the first embodiment, the transmitting device 100 adds the complex conjugate of GI to the second precoding symbol, reverses the order of the symbols, and applies phase rotation (phase change). The complex conjugate is the complex conjugate of the GI added to the first precoding symbol.
藉此,在MIMO通道中,可以得到較高的頻率分集效果。又,可以降低通訊資料的錯誤率,並使資料流通量提升。In this way, in the MIMO channel, a higher frequency diversity effect can be obtained. In addition, the error rate of communication data can be reduced, and the data circulation can be increased.
(實施形態2) 在實施形態1中,是針對下述的情況來說明:發送裝置100藉由在資料調變部104a、104b中進行π/2-BPSK調變,而進行MIMO發送。在實施形態2中,是針對下述的情況來說明:發送裝置300(參照圖9)在資料調變部104a、104b中,切換複數個資料調變方式(例如π/2-BPSK調變與π/2-QPSK調變),而進行MIMO發送。(Embodiment 2) In
圖9是顯示實施形態2之發送裝置300的構成之圖。再者,對於與圖3相同的構成要素會賦與相同的編號,並省略說明。Fig. 9 is a diagram showing the structure of a transmitting device 300 according to the second embodiment. In addition, the same reference numerals are assigned to the same components as those in FIG. 3, and the description is omitted.
資料調變部104c、104d會對編碼部103a、103b所輸出的編碼資料,進行因應於MAC部101的控制之資料調變。The
接著,針對預編碼部105a依據π/2-BPSK調變與π/2-QPSK調變來切換預編碼處理的例子進行說明。Next, an example in which the
圖10A是顯示π/2-QPSK調變的星象圖之一例的圖。從資料調變部104c、104d輸出的調變符號s1
(m)及s2
(m)是分別成為+1、-1、+j、-j之任一值。再者,π/2-BPSK調變的星象圖是如圖4A所示。Fig. 10A is a diagram showing an example of a constellation diagram of π/2-QPSK modulation. The modulation symbols s 1 (m) and s 2 (m) output from the
預編碼部105a是因應於在資料調變部104c、104d中所使用的資料調變方式,來變更預編碼矩陣,並進行算式13所示的預編碼處理。(算式13)The
在資料調變部104c、104d中使用π/2-BPSK的情況下,預編碼部105a是利用例如算式2、算式2-3、或算式2-5所示的預編碼矩陣G。When π/2-BPSK is used in the
在資料調變部104c、104d中使用π/2-QPSK的情況下,預編碼部105a是利用例如算式14所示的預編碼矩陣G。(算式14)When π/2-QPSK is used in the
預編碼部105a在利用算式2來對π/2-BSPK符號進行預編碼的情況下,星象圖是成為與π/2-QPSK相同(參照圖4C)。又,預編碼部105a在利用算式14來對π/2-QSPK符號(參照圖10A)進行預編碼的情況下,星象圖是成為與16QAM相同(參照圖10B)。When the
π/2-BPSK之符號候補點的數量為2,π/2-QPSK之符號候補點的數量為4,而π/2-16QAM之符號候補點的數量為16。亦即,藉由進行預編碼,星象圖中的符號候補點的數量即會增加。The number of symbol candidates for π/2-BPSK is 2, the number of symbol candidates for π/2-QPSK is 4, and the number of symbol candidates for π/2-16QAM is 16. That is, by performing precoding, the number of symbol candidate points in the astrological chart will increase.
第2發送RF鏈處理會因調變方式及預編碼矩陣G的種類而不同。在資料調變部104c、104d中使用π/2-BPSK,且在預編碼部105a中使用算式2、算式2-3、或算式2-5所示的預編碼矩陣G的情況下,發送裝置300會與圖3的發送裝置100同樣地,利用複共軛GI附加部106b及符號順序反轉部107,來進行第2發送RF鏈處理。The processing of the second transmit RF chain will vary depending on the modulation method and the type of the precoding matrix G. When π/2-BPSK is used in the
複共軛GI附加部106b是對預編碼部105a的輸出x2
(m)附加GI的複共軛。符號順序反轉部107是對附加有GI的複共軛之輸出x2
(n),進行符號順序反轉處理。The complex conjugate
在資料調變部104c、104d中使用π/2-QPSK,且在預編碼部105a中使用算式14所示的預編碼矩陣G的情況下,發送裝置300與圖3的發送裝置100不同,是利用GI附加部106c來進行第2發送RF鏈處理。When π/2-QPSK is used in the
GI附加部106c會對預編碼部105a的輸出x2
(m)附加GI,該GI是與第1之RF鏈處理中GI附加部106a所附加的GI相同。The
再者,GI附加部106c亦可附加與GI附加部106a所附加的GI(GI1)不同的GI(GI2)。亦可將相互地正交的序列(互相關(cross correlation)為0)用於GI1與GI2。例如,亦可於GI1中使用規定於11ad規格(參照非專利文獻1)的Ga64序列,且亦可於GI2中使用規定於11ad規格的Gb64序列。Furthermore, the
將π/2-BPSK調變、以及算式2、算式2-3、或算式2-5的預編碼矩陣G之組合,稱為第1預編碼方式類型。將π/2-QPSK調變、以及算式14的預編碼矩陣G的組合,稱為第2預編碼方式類型。再者,針對第1預編碼方式類型與第2預編碼方式類型的判別方法,將於後文描述。The combination of π/2-BPSK modulation and the precoding matrix G of
在第1預編碼方式類型的情況下,選擇部112a是選擇資料符號緩衝器108a的輸出,而選擇部112b是選擇符號順序反轉部107的輸出。In the case of the first precoding method type, the
在第2預編碼方式類型的情況下,選擇部112a是選擇GI附加部106a的輸出,而選擇部112b是選擇GI附加部106c的輸出。In the case of the second precoding method type, the selecting
再者,選擇部112a也可以配置於GI附加部106a的後段。又,選擇部112b也可以配置於預編碼部105a的後段。In addition, the
接著,針對發送裝置300因應於預編碼方式來變更第2發送RF鏈處理的理由進行說明。Next, the reason why the transmission device 300 changes the second transmission RF chain processing in accordance with the precoding method will be described.
在第1預編碼方式類型中,如算式2-2、算式2-4、或算式2-6所示,x1 (b,n)與x2 (b,n)為複共軛的關係,且更進一步地為形成常數因子的關係。從而,如圖5B及圖5C所示,在頻率區域中,第2發送RF鏈處理的訊號是將第1發送RF鏈處理的訊號之頻率反轉而成的訊號,且和第1發送RF鏈處理的訊號為複共軛的關係。In the first type of precoding method, as shown in Equation 2-2, Equation 2-4, or Equation 2-6, x 1 (b,n) and x 2 (b,n) have a complex conjugate relationship, And further to form a constant factor relationship. Therefore, as shown in FIGS. 5B and 5C, in the frequency region, the signal processed by the second transmission RF chain is a signal obtained by inverting the frequency of the signal processed by the first transmission RF chain, and is the same as that of the first transmission RF chain. The signal processed is a complex conjugate relationship.
另一方面,在第2預編碼方式類型中,x1 (b,n)與x2 (b,n)並不具有複共軛的關係。從而,如圖11A及圖11B所示,在頻率區域中,第1發送RF鏈處理的訊號與第2發送RF鏈處理的訊號,是以相同的頻率來發送。例如,X1 (b,k)與X2 (b,k)是以相同的頻率來發送,且X1 (b,-k)與X2 (b,-k)是以相同的頻率來發送。On the other hand, in the second precoding method type, x 1 (b, n) and x 2 (b, n) do not have a complex conjugate relationship. Therefore, as shown in FIGS. 11A and 11B, in the frequency region, the signal processed by the first transmission RF chain and the signal processed by the second transmission RF chain are transmitted at the same frequency. For example, X 1 (b,k) and X 2 (b,k) are transmitted at the same frequency, and X 1 (b,-k) and X 2 (b,-k) are transmitted at the same frequency .
滿足算式15的複數b存在的情況下,即符合第1預編碼方式類型。(算式15)When the complex number b that satisfies Equation 15 exists, it corresponds to the first precoding method type. (Equation 15)
從以上的考察,發送裝置300在第1預編碼方式類型中,是在第2發送RF鏈處理中附加複共軛的GI,並反轉符號順序。亦即,選擇部112b是選擇來自符號順序反轉部107的輸出。另一方面,在第2預編碼方式類型中,是在第2之RF鏈處理中附加和第1之RF鏈處理相同的GI,而不進行符號順序的反轉。亦即,選擇部112b是選擇來自GI編碼部106c的輸出。From the above considerations, in the first precoding method type, the transmitting device 300 adds the complex conjugate GI to the second transmit RF chain process and reverses the sign order. That is, the
藉此,不論資料調變方式及預編碼矩陣的種類如何,發送裝置300都可以如圖6E、圖6F所示,實現因應於相位旋轉部109所施予的相位旋轉θ(以及由θ利用算式9-1換算而得的d)之頻率分集效果。Thereby, regardless of the type of data modulation method and precoding matrix, the transmitting device 300 can realize the phase rotation θ given by the
在π/2-BPSK中,藉由利用算式2的預編碼矩陣,預編碼後的星象圖會成為和QPSK為同等(參照圖4B)。此情況即符合第1預編碼方式類型。又,在π/2-QPSK中,藉由利用算式14的預編碼矩陣,預編碼後的星象圖會成為和16QAM為同等(參照圖10B)。此情況即符合第2預編碼方式類型。In π/2-BPSK, by using the precoding matrix of
再者,選擇部112a、112b亦可在π/2-BPSK調變中,因應於預編碼方式的類型來選擇輸入資料。Furthermore, the
又,發送裝置300亦可利用與不進行預編碼的發送時之π/2-QPSK及π/2-16QAM為相同的發送參數來發送。發送參數包含例如發送F/E電路110a、110b的RF放大器的後退操作點(Backoff)之設定值。也就是說,發送裝置300亦可因應於調變方式,而利用算式2或算式14之任一個來進行預編碼。藉此,即可以在不變更發送F/E電路110a、110b的構成之情形下進行發送。以下,說明其理由。In addition, the transmission device 300 may also transmit using the same transmission parameters as π/2-QPSK and π/2-16QAM in transmission without precoding. The transmission parameter includes, for example, the setting value of the backoff operation point (Backoff) of the RF amplifier of the transmission F/
在一般的毫米波通訊中,發送F/E電路中的RF放大器的後退操作點之設定值,可因應於發送星象圖配置(圖10A、圖10B等)而適當地設定及變更。例如,在如圖10B的16QAM中,由於相對於平均電力的峰值電力(PAPR)會變大,因此會將RF放大器的後退操作點(Backoff)設得較大,而設定成在RF放大器中不使訊號飽和。又,由於藉由施行預編碼處理而改變發送訊號的星象圖之配置,因此發送F/E電路的設定會被變更。In general millimeter wave communication, the setting value of the backward operating point of the RF amplifier in the transmitting F/E circuit can be appropriately set and changed according to the transmitting astrological diagram configuration (Figure 10A, Figure 10B, etc.). For example, in 16QAM as shown in FIG. 10B, since the peak power (PAPR) relative to the average power becomes larger, the backoff operation point (Backoff) of the RF amplifier is set to be larger, and the RF amplifier is not Saturate the signal. In addition, since the configuration of the astrogram of the transmission signal is changed by performing the precoding process, the setting of the transmission F/E circuit will be changed.
相對於此,在本實施形態的發送裝置300中,是藉由利用例如算式2及算式14,來施行預編碼處理,藉此成為與預編碼處理之前的星象圖配置不同,但與習知的調變相同的星象圖配置。也就是說,由於無論預編碼處理的有無,發送訊號都成為習知的星象圖配置,因此變得不需要發送F/E電路的構成及設定之變更,且控制變容易。On the other hand, in the transmitting device 300 of the present embodiment, the precoding process is performed by using, for example,
<實施形態2之效果> 在實施形態2中,發送裝置300是在第1預編碼符號與第2預編碼符號為複共軛的關係之情況下,對第2預編碼符號附加GI的複共軛,且反轉符號順序,並施予相位旋轉(相位變更),其中該GI的複共軛是附加於第1預編碼符號的GI的複共軛。<Effects of
藉此,可以在MIMO通道中,切換複數個資料調變方式,且可以得到較高的頻率分集效果。又,可以降低通訊資料的錯誤率,並使資料流通量提升。In this way, a plurality of data modulation methods can be switched in the MIMO channel, and a higher frequency diversity effect can be obtained. In addition, the error rate of communication data can be reduced, and the data circulation can be increased.
(實施形態2的變形例) 在實施形態2中所說明的是,發送裝置300在π/2-BPSK調變的情況下,在符號順序反轉部107中對資料符號及GI的符號進行符號順序反轉之MIMO發送。在實施形態2的變形例中要說明的是,發送裝置400(參照圖12)在GI附加部106d、106e中,按每個流而附加有不同的序列(例如正交的序列)的MIMO發送。(Modification of Embodiment 2) As explained in
圖12是顯示實施形態2的變形例之發送裝置400的構成之圖。再者,對於與圖9相同的構成要素會賦與相同的編號,並省略說明。FIG. 12 is a diagram showing the configuration of a transmitting device 400 according to a modification of the second embodiment. In addition, the same components as those in FIG. 9 will be assigned the same reference numerals, and the description will be omitted.
GI附加部106d、106e是配置在比選擇部112a、112b及相位旋轉部109更後段。與圖9的發送裝置300不同,無論調變方式如何,發送裝置400都附加按每個流來制定的GI符號亦可。The
圖13及圖14是顯示發送裝置400的GI附加部106d、106e的輸出(v3、v4)之發送符號格式的一例之圖。圖13是顯示資料符號的調變為π/2-BPSK調變的情況,而圖14是顯示資料符號的調變為π/2-BPSK調變以外的情況。13 and 14 are diagrams showing an example of the transmission symbol format of the output (v3, v4) of the
GI附加部106d是將預編碼符號x1 (m)分割成每個448個符號的資料區塊,且在各資料區塊的前段附加64個符號的GI(GI1 (p))。GI是對習知的序列進行了π/2-BPSK調變的符號序列。進而,GI附加部106d是在最後的資料區塊之後段附加64個符號的GI。藉此,可生成如圖13及圖14所示的發送符號v3。再者,這些符號數僅是一例,本實施形態也可以是這些以外的符號數。The GI adding unit 106d divides the precoding symbol x 1 (m) into data blocks of 448 symbols each, and adds 64 symbols of GI (GI 1 (p)) to the front of each data block. GI is a symbol sequence modulated by π/2-BPSK on a conventional sequence. Furthermore, the GI adding unit 106d adds 64 symbols of GI to the end of the last data block. In this way, the transmission symbol v3 as shown in FIG. 13 and FIG. 14 can be generated. In addition, the number of these symbols is only an example, and the number of symbols other than these may be used in this embodiment.
同樣地,GI附加部106e也是將預編碼符號x2
(m)分割成每個448個符號的資料區塊,且在各資料區塊的前段附加64個符號的GI(GI2
(p)),並在最後的資料區塊之後段附加64個符號的GI。藉此,可生成如圖13及圖14所示的發送符號v4。GI附加部106e所附加的GI,亦可與GI附加部106d所附加的GI為不同的序列。Similarly, the
接收裝置200亦可在接收了具有圖13及圖14的格式之發送裝置400的發送訊號的情況下,如實施形態1所示,利用算式12-2來進行MMSE等化,並進行接收處理。When the receiving device 200 receives the transmission signal of the transmitting device 400 having the format shown in FIG. 13 and FIG. 14, as shown in the first embodiment, the MMSE equalization is performed using Equation 12-2 and the receiving process is performed.
接收裝置200亦可比較已進行MMSE等化的GI符號(MMSE濾波器部207的輸出當中與GI相關的部分)、以及習知的GI符號,來檢測通道估測矩陣的誤差,並進行通道估測矩陣的補正。可在GI1 (p)與GI2 (p)為正交序列的情況下,算出藉由MMSE等化而估測的GI1 (p)、及習知的GI1 (p)之相關性。在此算出中,可減輕MMSE等化的殘餘誤差,並且可高精度地算出例如相位偏移之值。因此,可以高精度地補正通道估測矩陣,並改善接收性能。The receiving device 200 can also compare the GI symbols (the GI-related part of the output of the MMSE filter unit 207) that has been MMSE equalized with the conventional GI symbols to detect the error of the channel estimation matrix, and perform channel estimation. The correction of the measurement matrix. When GI 1 (p) and GI 2 (p) are orthogonal sequences, the correlation between GI 1 (p) estimated by MMSE equalization and the conventional GI 1 (p) can be calculated. In this calculation, the residual error of MMSE equalization can be reduced, and the value of, for example, the phase offset can be calculated with high accuracy. Therefore, the channel estimation matrix can be corrected with high accuracy and the reception performance can be improved.
接著,針對接收裝置200的MMSE濾波器部207接收具有圖13及圖14的格式之發送裝置400的發送訊號之其他方法進行說明。Next, another method for the
接收裝置200會藉由算式16來生成GI1 (p)及GI2 (p)的副本訊號(replica signal)。在此,所謂副本訊號是指,在發送了習知型樣(pattern)(例如GI1 (p)及GI2 (p))的情況下,以接收天線接收的訊號之估測值,且是藉由在習知型樣上乘上通道矩陣(參照算式12)而算出。(算式16)The receiving device 200 generates GI 1 (p) and GI 2 (p) replica signals by using Equation 16. Here, the so-called duplicate signal refers to the estimated value of the signal received by the receiving antenna when conventional patterns (such as GI 1 (p) and GI 2 (p)) are transmitted, and it is It is calculated by multiplying the conventional pattern by the channel matrix (refer to Equation 12). (Equation 16)
在算式16中,XG1 (k)及XG2 (k)是對GI時間區域訊號(符號)GI1 (p)及GI2 (p)進行了DFT的訊號(GI的頻率區域訊號)。又,YG1 (k)及YG2 (k)是接收裝置200接收了GI1 (p)及GI2 (p)時的頻率區域訊號。藉由對YG1 (k)及YG2 (k)賦與記號「^」,以顯示其為估測值。In Equation 16, X G1 (k) and X G2 (k) are signals (the frequency region signals of GI) obtained by performing DFT on the GI time zone signals (symbols) GI 1 (p) and GI 2 (p). In addition, Y G1 (k) and Y G2 (k) are frequency region signals when the receiving device 200 receives GI 1 (p) and GI 2 (p). By assigning the mark "^" to Y G1 (k) and Y G2 (k) to show that they are estimated values.
接收裝置200是藉由算式17,而從接收訊號Y1 (b,k)減去Y^G1 (k)來估測包含於接收訊號的資料訊號成分Y^D1 (k),且從Y2 (b,k)減去Y^G2 (k)來估測資料訊號成分Y^D2 (k)。(算式17)The receiving device 200 uses Equation 17 to subtract Y^G1 (k) from the received signal Y 1 (b,k) to estimate the data signal component Y^ D1 (k) included in the received signal, and from Y 2 (b,k) Subtract Y^ G2 (k) to estimate the data signal component Y^ D2 (k). (Equation 17)
接收裝置200會將已估測的資料訊號成分Y^D1 (k)及Y^D2 (k)設為輸入並進行MMSE等化,藉此算出發送資料符號的估測值T^D1 (k)及T^D2 (k)。(算式18)The receiving device 200 sets the estimated data signal components Y^ D1 (k) and Y^ D2 (k) as inputs and performs MMSE equalization, thereby calculating the estimated value T^ D1 (k) of the transmitted data symbol And T^ D2 (k). (Equation 18)
雖然在算式18中進行的計算處理與算式12-2是同樣的,但是下述之點不同:相對於算式12-2的輸入Y1 (b,k)及Y2 (b,k)包含資料及GI的訊號成分之情形,算式18的輸入Y^D1 (k)及Y^D2 (k)是包含有減去了GI的訊號成分之資料的訊號成分。Although the calculation process performed in equation 18 is the same as that in equation 12-2, the following points are different: the input Y 1 (b,k) and Y 2 (b,k) of equation 12-2 contains data In the case of the signal component of GI, the input Y^ D1 (k) and Y^ D2 (k) of Equation 18 are the signal components that include the data of the signal component minus GI.
由於MMSE濾波器部207在接收發送裝置400的發送訊號之情況下,每個流的GI並不是複共軛及時間順序反轉的關係,因此在GI的符號之解調中,要得到與實施形態1同樣的頻率分集效果是困難的。據此,會有下述情況:從GI的符號到資料符號的符號間干涉於MMSE等化後殘留,而使接收性能降低。Since the
在此,MMSE濾波器部207是在接收發送裝置400的發送訊號之情況下,利用算式16、算式17、及算式18而從接收訊號中減去GI的符號副本(symbol replica),並進行MMSE等化。也就是說,減輕GI的影響來進行資料符號的MMSE等化。Here, the
接收裝置200是對於MMSE濾波器部207利用算式18所生成的發送資料符號之估測值T^D1
(k)及T^D2
(k),進行包含逆相位旋轉及逆預編碼之與實施形態1及實施形態2同樣的接收處理。 The receiving device 200 uses the estimated values T ^ D1 (k) and T ^ D2 (k) of the transmitted data symbol generated by the
<實施形態2的變形例之效果> 在實施形態2的變形例中,發送裝置400是在第1預編碼符號與第2預編碼符號為複共軛的關係之情況下,對第2預編碼符號來反轉符號順序,並施予相位旋轉(相位變更)。又,在第1預編碼符號與第2預編碼符號插入不同的GI。<Effects of the modification of the second embodiment> In the modification of the second embodiment, the transmitting device 400 performs the second precoding when the first precoding symbol and the second precoding symbol are in a complex conjugate relationship. Sign to reverse the order of signs and apply phase rotation (phase change). In addition, different GIs are inserted between the first precoding symbol and the second precoding symbol.
藉此,可以在MIMO通道中,切換複數個資料調變方式,且可以得到較高的頻率分集效果。又,可以降低通訊資料的錯誤率,並使資料流通量提升。In this way, a plurality of data modulation methods can be switched in the MIMO channel, and a higher frequency diversity effect can be obtained. In addition, the error rate of communication data can be reduced, and the data circulation can be increased.
<實施形態的總結> 本揭示之第1態様的發送裝置,具備:預編碼部,對第1基頻訊號與第2基頻訊號施行預編碼處理,以生成第1預編碼訊號與第2預編碼訊號;順序反轉部,使構成前述第2預編碼訊號的符號序列之順序反轉,而生成第2反轉訊號;相位變更部,生成第2相位變更訊號,且該第2相位變更訊號是對前述第2反轉訊號施行了相位變更之訊號;及發送部,分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。<Summary of the embodiment> The transmitting device of the first aspect of the present disclosure includes a precoding unit that performs precoding processing on the first baseband signal and the second baseband signal to generate the first precoding signal and the second precoding signal. Encoding signal; sequence reversing section, which reverses the sequence of the symbol sequence constituting the second pre-encoding signal to generate a second reversal signal; phase changing section, generating a second phase change signal, and the second phase change signal It is a signal in which the phase of the second inversion signal is changed; and the transmitting unit transmits the first precoding signal and the second phase change signal from different antennas.
本揭示之第2態様的發送裝置,是在第1態様的發送裝置中,具備:第1附加部,在前述第1預編碼訊號中附加第1習知訊號;及第2附加部,在前述第2預編碼訊號中附加與前述第1習知訊號為複共軛的關係的第2習知訊號。The transmitting device of the second aspect of the present disclosure, in the transmitting device of the first aspect, includes: a first addition section for adding a first conventional signal to the first precoding signal; and a second addition section for adding To the second precoding signal, a second conventional signal having a complex conjugate relationship with the aforementioned first conventional signal is added.
本揭示之第3態様的發送裝置,是在第2態様的發送裝置中,前述順序反轉部是使構成前述第2習知訊號的符號序列之順序反轉,且在已反轉的第2習知訊號上連結已反轉的第2預編碼訊號,來生成前述第2反轉訊號。The third aspect of the transmission device of the present disclosure is that in the second aspect of the transmission device, the sequence reversing unit reverses the sequence of the symbol sequence constituting the second conventional signal, and the sequence is reversed in the reversed second The inverted second precoding signal is connected to the conventional signal to generate the aforementioned second inverted signal.
本揭示之第4態様的發送裝置,是在第2態様的發送裝置中,前述順序反轉部是讓已使前述第2習知訊號連結於前述第2預編碼訊號的符號序列的順序反轉,而生成前述第2反轉訊號。In the transmitting device of the fourth aspect of the present disclosure, in the transmitting device of the second aspect, the sequence reversing unit reverses the sequence of the symbol sequence that has connected the second conventional signal to the second precoding signal , And generate the aforementioned second inversion signal.
本揭示之第5態様的發送裝置,是在第2至第4態様的任一態様之發送裝置中,具備:第3附加部,在前述第2預編碼訊號中附加第3習知訊號;及選擇部,根據前述第1基頻訊號與前述第2基頻訊號是否為複共軛的關係,來選擇是否使前述第2反轉訊號、及已附加有前述第3習知訊號的前述第2預編碼訊號的任一個輸入至前述相位變更部。The transmitting device of the fifth aspect of the present disclosure is the transmitting device of any one of the second to fourth states, and includes: a third addition part for adding a third conventional signal to the second precoding signal; and The selection unit selects whether to make the second inversion signal and the second signal to which the third conventional signal has been added based on the relationship between whether the first fundamental frequency signal and the second fundamental frequency signal are complex conjugate. Any one of the precoding signals is input to the aforementioned phase changing unit.
本揭示之第6態様的發送方法,是對第1基頻訊號與第2基頻訊號施行預編碼處理,以生成第1預編碼訊號與第2預編碼訊號,且使構成前述第2預編碼訊號的符號序列之順序反轉,而生成第2反轉訊號,並生成對前述第2反轉訊號施行了相位變更的第2相位變更訊號,且分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。The transmission method of the sixth aspect of the present disclosure is to perform precoding processing on the first baseband signal and the second baseband signal to generate the first precoding signal and the second precoding signal, and to form the aforementioned second precoding The sequence of the symbol sequence of the signal is reversed to generate a second inversion signal, and a second phase change signal that performs phase change on the second inversion signal is generated, and the first precoding signal is transmitted from different antennas. It is the same as the aforementioned second phase change signal.
本揭示之第7態様的接收裝置,具備:接收部,分別以不同的天線來接收第1接收訊號及第2接收訊號;及解調部,從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號,在前述第1接收訊號及前述第2接收訊號中,包含有第1預編碼訊號及第2相位變更訊號,前述第1預編碼訊號,是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號,前述第2相位變更訊號是下述之訊號:前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號,且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號,並對該生成的第2反轉訊號施行相位變更而生成的訊號。The receiving device of the seventh aspect of the present disclosure includes: a receiving unit, which uses different antennas to receive the first received signal and the second received signal; and a demodulation unit, from the first received signal and the second received signal Generate the first baseband signal and the second baseband signal. In the first received signal and the second received signal, the first precoding signal and the second phase change signal are included. The first precoding signal is the transmission The device performs precoding processing on the first baseband signal and the second baseband signal to generate a signal, and the second phase change signal is the following signal: The baseband signal is pre-encoded to generate a second pre-encoded signal, and the sequence of the symbol sequence constituting the second pre-encoded signal is reversed to generate a second inverted signal, and the generated second is inverted The signal is generated by changing the phase of the signal.
本揭示之第8態様的接收方法,是分別以不同的天線來接收第1接收訊號及第2接收訊號,且從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號,在前述第1接收訊號及前述第2接收訊號中,包含有第1預編碼訊號及第2相位變更訊號,前述第1預編碼訊號,是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號,前述第2相位變更訊號是下述之訊號:前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號,且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號,並對該生成的第2反轉訊號施行相位變更而生成的訊號。The receiving method of the eighth aspect of the present disclosure uses different antennas to receive the first received signal and the second received signal, and generates the first baseband signal and the second received signal from the first received signal and the second received signal. 2 Base frequency signal. The first received signal and the second received signal include the first precoding signal and the second phase change signal. The first precoding signal is the transmission device's response to the first And the signal generated by precoding the second baseband signal, the second phase change signal is the following signal: the transmitting device performs precoding processing on the first baseband signal and the second baseband signal, and A second precoding signal is generated, and the sequence of the symbol sequence constituting the generated second precoding signal is reversed to generate a second inverted signal, and the generated second inverted signal is phase-changed to generate a signal .
以上,雖然參照著圖式對各種實施形態作了說明,但是本揭示當然並不限定於所述例子。顯然地,只要是本發明所屬技術領域中具有通常知識者,應可以在專利申請範圍中所記載的範疇内想到各種變更例或修正例,且理應了解的是,關於該等亦當屬於本揭示的技術性範圍。又,在不脫離本揭示之要旨的範圍內,亦可將上述實施形態中的各構成要素任意組合。Although various embodiments have been described above with reference to the drawings, the present disclosure is of course not limited to the examples. Obviously, anyone with ordinary knowledge in the technical field to which the present invention belongs should be able to think of various changes or amendments within the scope of the patent application, and it should be understood that these also belong to this disclosure. Technical scope. In addition, it is also possible to arbitrarily combine the constituent elements in the above-mentioned embodiments within a range that does not deviate from the gist of the present disclosure.
在上述各實施形態中,雖然本揭示是舉利用硬體而構成的例子來作説明,但本揭示亦可在與硬體的協同合作下以軟體來實現。In each of the above embodiments, although the present disclosure is an example constructed by using hardware for explanation, the present disclosure can also be implemented by software in cooperation with hardware.
又,於上述各實施形態的説明中所用到的各個功能方塊,典型上是作為具有輸入端子及輸出端子的積體電路之LSI而實現。這些可以個別地集成為1個晶片,亦可以藉包含一部分或全部的方式來集成1個晶片。在此,雖然是做成LSI,但按照集成度的差異,也會有稱為IC、System LSI(系統LSI)、Super LSI(特大型LSI)與Ultra LSI(超大型LSI)之情形。In addition, each functional block used in the description of each of the above-mentioned embodiments is typically realized as an LSI having an integrated circuit with input terminals and output terminals. These can be individually integrated into one chip, or a part or all of them can be integrated into one chip. Here, although it is made as LSI, depending on the degree of integration, there may be cases called IC, System LSI (System LSI), Super LSI (Extra Large LSI), and Ultra LSI (Ultra Large LSI).
又,積體電路化的手法並不限於LSI,亦可利用專用電路或通用處理器來實現。亦可在LSI製造後,利用可程式設計的FPGA(現場可程式閘陣列,Field Programmable Gate Array)、可再構成LSI內部之電路電池的連接或設定之可重組態處理器(Reconfigurable Processor)。In addition, the method of integrated circuitization is not limited to LSI, and it can also be realized by a dedicated circuit or a general-purpose processor. It is also possible to use a programmable FPGA (Field Programmable Gate Array) after the LSI is manufactured, and a reconfigurable processor (Reconfigurable Processor) that can reconfigure the connection or setting of the battery inside the LSI.
此外,若是因為半導体技術之進歩或藉由其衍生之其他技術而有可替換LSI之積體電路化的技術出現,當然亦可使用該技術來進行功能方塊的集成化。本發明可具有生物技術之應用等的可能性。 産業上之可利用性In addition, if there is an integrated circuit technology that can replace LSI due to advances in semiconductor technology or other technologies derived from it, of course, this technology can also be used to integrate functional blocks. The present invention may have the possibility of application of biotechnology and the like. Industrial availability
本揭示可以廣泛地應用於從複數個天線發送調變訊號的通訊系統中。The present disclosure can be widely used in a communication system that transmits modulated signals from a plurality of antennas.
100、300、400‧‧‧發送裝置101、215‧‧‧MAC部102‧‧‧流生成部103a、103b‧‧‧編碼部104a、104b、104c、104d‧‧‧資料調變部105、105a‧‧‧預編碼部106a、106c、106d、106e‧‧‧GI附加部106b‧‧‧複共軛GI附加部107‧‧‧符號順序反轉部108a、108b‧‧‧資料符號緩衝器109‧‧‧相位旋轉部110a、110b‧‧‧發送F/E電路111a、111b‧‧‧發送天線112a、112b‧‧‧選擇部200‧‧‧接收裝置201a、201b‧‧‧接收天線202a、202b‧‧‧接收F/E電路203a、203b‧‧‧時間區域同步部204‧‧‧通道估測部205a、205b‧‧‧DFT部206‧‧‧MMSE權重計算部207‧‧‧MMSE濾波部208‧‧‧逆相位旋轉部209a‧‧‧IDFT部209b‧‧‧IDFT及符號順序反轉部210‧‧‧逆預編碼部211a、211b‧‧‧資料解調部212a、212b‧‧‧解碼部213‧‧‧流整合部214‧‧‧標頭資料提取部H11(k)、H12(k)、H21(k)、H22(k)‧‧‧通道100, 300, 400‧‧‧Transmitting device 101, 215‧‧‧MAC unit 102‧‧‧Stream generation unit 103a, 103b‧‧‧Encoding unit 104a, 104b, 104c, 104d‧‧‧Data modulation unit 105, 105a ‧‧‧Precoding part 106a, 106c, 106d, 106e‧‧‧GI addition part 106b‧‧‧Complex conjugate GI addition part 107‧‧‧Symbol sequence reversal part 108a, 108b‧‧‧Data symbol buffer 109‧ ‧‧Phase rotation part 110a, 110b‧‧‧Transmitting F/E circuit 111a, 111b‧‧‧Transmitting antenna 112a, 112b‧‧‧Selecting part 200‧‧‧Receiving device 201a, 201b‧‧‧Receiving antenna 202a, 202b‧ ‧‧Receiving F/E circuit 203a, 203b‧‧‧Time zone synchronization unit 204‧‧‧Channel estimation unit 205a, 205b‧‧‧DFT unit 206‧‧‧MMSE weight calculation unit 207‧‧‧MMSE filter unit 208‧ ‧‧Inverse phase rotation unit 209a‧‧‧IDFT unit 209b‧‧‧IDFT and symbol order inversion unit 210‧‧‧Inverse precoding unit 211a, 211b‧‧‧Data demodulation unit 212a, 212b‧‧‧Decoding unit 213 ‧‧‧Stream Integration Unit 214‧‧‧Header Data Extraction Unit H11(k), H12(k), H21(k), H22(k)‧‧‧Channel
圖1是顯示實施形態1之MIMO通訊系統的構成之一例的圖。 圖2是顯示頻率響應之振幅成分的例子之圖。 圖3是顯示實施形態1之發送裝置的構成之一例的圖。 圖4A是顯示符號指數(symbol index)為奇數的π/2-BPSK(二元相移鍵控,Binary Phase Shift Keying)之星象圖(constellation)的例子之圖。 圖4B是顯示符號指數(symbol index)為偶數的π/2-BPSK之星象圖的例子之圖。 圖4C是顯示預編碼部的輸出資料之星象圖的例子之圖。 圖5A是顯示GI附加方法的一例之圖。 圖5B是顯示對預編碼的符號中附加有GI的符號區塊進行了DFT之DFT訊號的例子之圖。 圖5C是顯示對預編碼的符號中附加有GI* 的符號區塊進行了DFT時的DFT訊號的例子之圖。 圖6A是顯示符號順序反轉部中的符號順序反轉處理的一例之圖。 圖6B是顯示符號順序反轉部中的符號順序反轉處理的另一例之圖。 圖6C是顯示對預編碼的符號中附加有GI的符號區塊進行了DFT時的DFT訊號的例子之圖。 圖6D是顯示對反轉符號進行了DFT時的反轉DFT訊號的例子之圖。 圖6E是顯示按每個符號區塊對相位旋轉後符號進行了DFT的DFT訊號之圖。 圖6F是顯示按每個符號區塊對相位旋轉後符號進行了DFT的DFT訊號之圖。 圖7是顯示接收裝置的構成之一例的圖。 圖8是顯示在DFT部中將接收資料分割成DFT區塊的方法之圖。 圖9是顯示實施形態2之發送裝置的構成之圖。 圖10A是顯示π/2-QPSK調變的星象圖之一例的圖。 圖10B是顯示16QAM調變的星象圖之一例的圖。 圖11A是顯示第1發送RF鏈(chain)處理之DFT訊號的例子之圖。 圖11B是顯示第2發送RF鏈(chain)處理之DFT訊號的例子之圖。 圖12是顯示實施形態2之變形例的發送裝置的構成之圖。 圖13是顯示實施形態2之變形例的GI附加方法之一例的圖。 圖14是顯示實施形態2之變形例的GI附加方法之另一例的圖。Fig. 1 is a diagram showing an example of the configuration of the MIMO communication system according to the first embodiment. Fig. 2 is a diagram showing an example of the amplitude component of the frequency response. Fig. 3 is a diagram showing an example of the configuration of the transmitting device of the first embodiment. 4A is a diagram showing an example of a constellation of π/2-BPSK (Binary Phase Shift Keying) with an odd symbol index. Fig. 4B is a diagram showing an example of a π/2-BPSK astrological chart with an even symbol index. Fig. 4C is a diagram showing an example of a star map of the output data of the precoding unit. Fig. 5A is a diagram showing an example of a GI adding method. FIG. 5B is a diagram showing an example of a DFT signal in which DFT is performed on a symbol block with GI added to a pre-encoded symbol. FIG. 5C is a diagram showing an example of a DFT signal when DFT is performed on a symbol block with GI* added to a pre-encoded symbol. FIG. 6A is a diagram showing an example of the sign order reversal processing in the sign order reversal unit. Fig. 6B is a diagram showing another example of the sign order reversal processing in the sign order reversal unit. FIG. 6C is a diagram showing an example of a DFT signal when DFT is performed on a symbol block with GI added to a pre-encoded symbol. FIG. 6D is a diagram showing an example of an inverted DFT signal when DFT is performed on an inverted symbol. FIG. 6E is a diagram showing a DFT signal in which the symbol is DFT performed after the phase is rotated for each symbol block. FIG. 6F is a diagram showing a DFT signal in which the symbol is DFT performed after the phase is rotated for each symbol block. Fig. 7 is a diagram showing an example of the configuration of the receiving device. FIG. 8 is a diagram showing a method of dividing the received data into DFT blocks in the DFT section. Fig. 9 is a diagram showing the structure of a transmitting device according to the second embodiment. Fig. 10A is a diagram showing an example of a constellation diagram of π/2-QPSK modulation. Fig. 10B is a diagram showing an example of a constellation diagram of 16QAM modulation. FIG. 11A is a diagram showing an example of the DFT signal processed by the first transmit RF chain (chain). FIG. 11B is a diagram showing an example of the DFT signal processed by the second transmit RF chain (chain). Fig. 12 is a diagram showing the configuration of a transmission device according to a modification of the second embodiment. Fig. 13 is a diagram showing an example of a GI adding method according to a modification of the second embodiment. Fig. 14 is a diagram showing another example of the GI adding method according to the modification of the second embodiment.
100‧‧‧發送裝置 100‧‧‧Sending device
101‧‧‧MAC部 101‧‧‧MAC Department
102‧‧‧流生成部 102‧‧‧Stream Generation Department
103a、103b‧‧‧編碼部 103a, 103b‧‧‧Coding Department
104a、104b‧‧‧資料調變部 104a, 104b‧‧‧Data Modulation Department
105‧‧‧預編碼部 105‧‧‧Precoding section
106a‧‧‧GI附加部 106a‧‧‧GI Additional Department
106b‧‧‧複共軛GI附加部 106b‧‧‧Additional part of complex conjugate GI
107‧‧‧符號順序反轉部 107‧‧‧Symbol sequence reversal part
108a、108b‧‧‧資料符號緩衝器 108a, 108b‧‧‧Data symbol buffer
109‧‧‧相位旋轉部 109‧‧‧Phase Rotation Unit
110a、110b‧‧‧發送F/E電路 110a, 110b‧‧‧Sending F/E circuit
111a、111b‧‧‧發送天線 111a, 111b‧‧‧transmitting antenna
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WO2018203461A1 (en) * | 2017-05-03 | 2018-11-08 | パナソニック インテレクチュアル プロパティ コーポレーション オブ アメリカ | Transmission device, transmission method, reception device, and reception method |
KR102337196B1 (en) * | 2019-08-27 | 2021-12-09 | 국민대학교 산학협력단 | Method and apparatus for implementing transmit diversity using a single transmitter |
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KR101733489B1 (en) * | 2010-01-17 | 2017-05-24 | 엘지전자 주식회사 | Apparatus and method of transmitting control information in wireless communication system |
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- 2017-10-13 JP JP2017199541A patent/JP7015136B2/en active Active
- 2017-10-24 TW TW106136505A patent/TWI741050B/en active
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WO2008018703A1 (en) * | 2006-08-08 | 2008-02-14 | Lg Electronics Inc. | Data transmission method in multiple antenna system |
US20090298544A1 (en) * | 2007-02-16 | 2009-12-03 | Sloka Telecom Pvt. Ltd. | Software defined base station |
US20100104037A1 (en) * | 2007-03-30 | 2010-04-29 | Joengren George | Method And Device For Interference Suppression In User Terminal |
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US20150304013A1 (en) * | 2011-06-24 | 2015-10-22 | Panasonic Intellectual Property Corporation Of America | Transmission device, transmission method, receiving device and receiving method |
JP2016146635A (en) * | 2011-06-24 | 2016-08-12 | パナソニック インテレクチュアル プロパティ コーポレーション オブ アメリカPanasonic Intellectual Property Corporation of America | Transmitter and transmission method, receiver and reception method |
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JP2018074573A (en) | 2018-05-10 |
JP7015136B2 (en) | 2022-02-02 |
WO2018084035A1 (en) | 2018-05-11 |
TW201820802A (en) | 2018-06-01 |
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