TWI635776B - Controller for switching regulator, switching regulator and led lighting system - Google Patents
Controller for switching regulator, switching regulator and led lighting system Download PDFInfo
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Abstract
用於LED照明系統之開關穩壓器的控制器,其具有電流監視器、分壓器、積分電路和比較器電路。電流監視器用於檢測通過開關穩壓器的電流感測電阻的LED電流,並產生感測電流。分壓器用於接收感測電流以產生第一至第三分壓,其中第一分壓大於第二分壓,且第二分壓大於第三分壓。積分電路用於將第二分壓與參考電壓進行比較,並且相應地在其RC電路的兩端產生積分電壓。比較器電路用於將積分電壓與第一分壓和第三分壓進行比較,並產生驅動信號。 A controller for a switching regulator of an LED lighting system having a current monitor, a voltage divider, an integrating circuit, and a comparator circuit. A current monitor is used to sense the LED current through the current sense resistor of the switching regulator and generate a sense current. The voltage divider is configured to receive the sensing current to generate first to third partial pressures, wherein the first partial pressure is greater than the second partial pressure, and the second partial pressure is greater than the third partial pressure. The integrating circuit is for comparing the second divided voltage with the reference voltage and correspondingly generating an integrated voltage across the RC circuit. The comparator circuit is for comparing the integrated voltage with the first divided voltage and the third divided voltage, and generates a driving signal.
Description
本發明涉及一種用於光源的開關穩壓器,且特別涉及一種用於開關穩壓器的控制器、開關穩壓器和LED照明系統。 The present invention relates to a switching regulator for a light source, and more particularly to a controller for a switching regulator, a switching regulator, and an LED illumination system.
LED照明系統包括開關穩壓器和LED,其中開關穩壓器具有控制器於其中。開關穩壓器由其控制器控制以向LED提供電流。控制器包括根據電流和LED電流時間週期的有效時間週期來計算傳送到LED系統的實際充電量的元件,其中LED電流時間週期是以大於50Hz的速率調製的佔空比,並用以利用實際充電量來修改及提供在LED電流時間週期的未來有效時間週期要傳送的期望目標充電量。 The LED lighting system includes a switching regulator and an LED, wherein the switching regulator has a controller therein. The switching regulator is controlled by its controller to supply current to the LEDs. The controller includes an element that calculates an actual amount of charge delivered to the LED system based on an effective time period of the current and the LED current time period, wherein the LED current time period is a duty cycle modulated at a rate greater than 50 Hz and utilized to utilize the actual amount of charge To modify and provide the desired target amount of charge to be transmitted during the future effective time period of the LED current time period.
LED系統還具有多個元件,以計算LED電流時間週期的有效時間週期與傳送到LED系統的實際充電量,並且LED系統還具有其他多個元件,以將用於LED電流時間週期的有效時間週期的實際充電量與期望充電量進行比較,並且在未來的有效時間週期補償實際充電量與期望充電量之間的差。為了精確地控制期望電荷量,應妥善地控制平均的LED電流,並且有效控制LED的光強度。 The LED system also has multiple components to calculate the effective time period of the LED current time period and the actual amount of charge delivered to the LED system, and the LED system also has a number of other components to be used for the effective time period of the LED current time period. The actual amount of charge is compared to the expected amount of charge, and the difference between the actual amount of charge and the desired amount of charge is compensated for in the future effective time period. In order to accurately control the desired amount of charge, the average LED current should be properly controlled and the light intensity of the LEDs be effectively controlled.
不幸的是,在LED系統中使用的一些傳統開關穩壓器具有邏輯閘和閘極驅動器(或稱為預驅動器),因此發生延遲問題,使得不能容易地控制平均的LED電流。此外,開關穩壓器中使用的電感器的電感值和LED照明系統的輸入電壓和輸出電壓(即調節器輸出)的比率也可能影響平均得LED電流的控制。 Unfortunately, some conventional switching regulators used in LED systems have logic gates and gate drivers (or pre-drivers), so delay problems occur that make it impossible to easily control the average LED current. In addition, the ratio of the inductance of the inductor used in the switching regulator to the input voltage and output voltage (ie, regulator output) of the LED lighting system may also affect the control of the average LED current.
請參考第1圖,第1圖是傳統LED照明系統的方塊圖。傳統LED系統包括開關穩壓器和LED 12,其中開關穩壓器是降壓型穩壓器,並且包括控制器10、第一電流感測電阻11、第二電流感測電阻13、齊納二極體14和電感L。控制器10連接到第一電流感測電阻11、LED 12、第二電流感測電阻13、齊納二極體14和電感L。第一電流感測電阻11的一端用於接收輸入電壓Vin,並且第一電流感測電阻11的另一端連接到電感L的一端。齊納二極體14的陽極連接到電感L的另一端,齊納二極體的陰極14連接到第二電流感測電阻13的一端。LED12的陽極和陰極分別連接到第二電流感測電阻13的另一端和接地電壓GND。 Please refer to Figure 1, which is a block diagram of a conventional LED lighting system. The conventional LED system includes a switching regulator and an LED 12, wherein the switching regulator is a buck regulator, and includes a controller 10, a first current sensing resistor 11, a second current sensing resistor 13, and Zener Polar body 14 and inductor L. The controller 10 is connected to the first current sensing resistor 11, the LED 12, the second current sensing resistor 13, the Zener diode 14, and the inductor L. One end of the first current sensing resistor 11 is for receiving the input voltage Vin, and the other end of the first current sensing resistor 11 is connected to one end of the inductor L. The anode of the Zener diode 14 is connected to the other end of the inductor L, and the cathode 14 of the Zener diode is connected to one end of the second current sensing resistor 13. The anode and cathode of the LED 12 are connected to the other end of the second current sensing resistor 13 and the ground voltage GND, respectively.
控制器包括誤差信號產生電路101、快速電流監測器102、遲滯控制器103、電阻104、遲滯比較器105、閘極驅動器106和NMOS開關電晶體107。快速電流監測器102並聯連接第一電流感測電阻11,以感測第一電流感測電阻11兩端的電壓並相應地產生第一感測電流。誤差信號發生電路101並聯連接第二電流感測電阻13,以感測第二電流感測電阻13兩端的電壓,並產生相應的誤差信號,其中誤差信號表示期望的穩壓器輸出和實際的穩壓器輸出之間的誤差。 The controller includes an error signal generating circuit 101, a fast current monitor 102, a hysteresis controller 103, a resistor 104, a hysteresis comparator 105, a gate driver 106, and an NMOS switch transistor 107. The fast current monitor 102 is connected in parallel with the first current sensing resistor 11 to sense the voltage across the first current sensing resistor 11 and correspondingly generate a first sensing current. The error signal generating circuit 101 is connected in parallel with the second current sensing resistor 13 to sense the voltage across the second current sensing resistor 13 and generate a corresponding error signal, wherein the error signal indicates the desired regulator output and the actual stability. The error between the output of the press.
遲滯控制器103連接到遲滯比較器105的負輸入端和輸出端,遲滯比較器105的正輸入端和遲滯控制器103接收參考電壓Vref,使得遲滯控制器103和遲滯比較器105形成用於控制NMOS開關電晶體107的導通/截止狀態的遲滯比較電路。遲滯比較器105的負輸入端還接收電阻104兩端的電壓,其中電阻104的 兩端分別連接遲滯控制器103分別連接遲滯比較器105的負輸入端與接地電壓GND,以及電阻104兩端間的電壓是根據誤差信號、第一感測電流與遲滯控制器103輸出的遲滯控制信號而形成。閘極驅動器106用於接收遲滯比較器105的輸出信號,以產生送到NMOS開關電晶體107的閘極端的驅動信號。NMOS開關電晶體107的漏極端和源極端分別連接到電感L的另一端和接地電壓GND。 The hysteresis controller 103 is connected to the negative input terminal and the output terminal of the hysteresis comparator 105, and the positive input terminal of the hysteresis comparator 105 and the hysteresis controller 103 receive the reference voltage Vref such that the hysteresis controller 103 and the hysteresis comparator 105 are formed for control. A hysteresis comparison circuit of the on/off state of the NMOS switch transistor 107. The negative input of hysteresis comparator 105 also receives the voltage across resistor 104, where resistor 104 The two ends of the hysteresis controller 103 are respectively connected to the negative input terminal of the hysteresis comparator 105 and the ground voltage GND, and the voltage between the two ends of the resistor 104 is based on the error signal, the first sensing current and the hysteresis control outputted by the hysteresis controller 103. Formed by a signal. The gate driver 106 is operative to receive the output signal of the hysteresis comparator 105 to generate a drive signal to the gate terminal of the NMOS switch transistor 107. The drain terminal and the source terminal of the NMOS switch transistor 107 are connected to the other end of the inductor L and the ground voltage GND, respectively.
誤差信號產生電路101包括積分器1011、精確電流監視器1012、減法單元1013和需求電流源1014。精確電流監視器1012並聯連接第二電流感測電阻13,用於感測跨越第二電流感測電阻13的電壓,以便相應地產生第二感測電流。減法單元1013連接到積分器1011和需求電流源1014,用於將第二感測電流減去需求電流以產生送到積分器1011的減法電流。需求電流源1014用於接收參考電壓Vref,以相應地產生需求電流。積分器1011還連接到遲滯比較器105的負輸入端,並用於對減法電流進行積分以產生誤差信號。誤差信號是需求電流和第二感測電流之差異的積分,這意味著誤差信號表示所需的穩壓器輸出和實際的穩壓器輸出之間的誤差。 The error signal generating circuit 101 includes an integrator 1011, a precision current monitor 1012, a subtraction unit 1013, and a demand current source 1014. The precision current monitor 1012 is connected in parallel with the second current sensing resistor 13 for sensing the voltage across the second current sensing resistor 13 to generate a second sensing current accordingly. A subtraction unit 1013 is coupled to the integrator 1011 and the demand current source 1014 for subtracting the demand current from the second sense current to produce a subtraction current to the integrator 1011. The demand current source 1014 is for receiving the reference voltage Vref to generate the demand current accordingly. Integrator 1011 is also coupled to the negative input of hysteresis comparator 105 and is used to integrate the subtraction current to produce an error signal. The error signal is the integral of the difference between the demand current and the second sense current, which means that the error signal represents the error between the desired regulator output and the actual regulator output.
注意,儘管傳統的開關穩壓器及其控制器10可以解決上述影響平均LED電流的問題,但是需要兩個電流監視器(即,快速監視器102和精確電流監視器1012),因此增加電路硬體成本,特別是精確電流監視器1012的成本。具更簡單的電路之開關穩壓器及其控制器仍然被市場所需求。 Note that although the conventional switching regulator and its controller 10 can solve the above problems affecting the average LED current, two current monitors (ie, the fast monitor 102 and the precision current monitor 1012) are required, thus increasing the circuit hard Body cost, especially the cost of the precision current monitor 1012. Switching regulators with simpler circuits and their controllers are still in demand.
本發明的示範實施例提供了一種用於LED照明系統之開關穩壓器的控制器,其具有電流監視器、分壓器、積分電路和比較器電路,其中分壓器 連接電流監視器,積分電路連接分壓器,以及比較器電路連接積分電路與分壓器。電流監視器用於檢測通過開關穩壓器的電流感測電阻的LED電流,並產生感測電流。分壓器用於接收感測電流以產生第一至第三分壓,其中第一分壓大於第二分壓,且第二分壓大於第三分壓。積分電路用於將第二分壓與參考電壓進行比較,並且相應地在其RC電路的兩端產生積分電壓。比較器電路用於將積分電壓與第一分壓和第三分壓進行比較,並產生驅動信號。。 An exemplary embodiment of the present invention provides a controller for a switching regulator of an LED lighting system having a current monitor, a voltage divider, an integrating circuit, and a comparator circuit, wherein the voltage divider A current monitor is connected, an integrating circuit is connected to the voltage divider, and a comparator circuit is connected to the integrating circuit and the voltage divider. A current monitor is used to sense the LED current through the current sense resistor of the switching regulator and generate a sense current. The voltage divider is configured to receive the sensing current to generate first to third partial pressures, wherein the first partial pressure is greater than the second partial pressure, and the second partial pressure is greater than the third partial pressure. The integrating circuit is for comparing the second divided voltage with the reference voltage and correspondingly generating an integrated voltage across the RC circuit. The comparator circuit is for comparing the integrated voltage with the first divided voltage and the third divided voltage, and generates a driving signal. .
本發明的示範實施例還提供了包括前述控制器的開關穩壓器。 Exemplary embodiments of the present invention also provide a switching regulator including the aforementioned controller.
本發明的示範實施例還提供了包括前述開關穩壓器的LED照明系統。 Exemplary embodiments of the present invention also provide an LED illumination system including the aforementioned switching regulator.
綜上所述,所提供的用於LED照明系統的開關穩壓器的控制器可以解決實際的平均LED電流偏離期望的平均LED電流的問題。 In summary, the controller of the switching regulator provided for the LED lighting system can solve the problem of the actual average LED current deviating from the desired average LED current.
為了進一步理解本發明的技術、手段和效果,可以參考以下詳細描述和附圖,從而可以徹底和具體地理解本發明的目的、特徵和概念。然而,以下詳細描述和附圖僅用於參考和說明本發明的實現方式,其並非用於限制本發明。 The objects, features, and concepts of the present invention will be more fully understood and understood by the appended claims. However, the following detailed description and drawings are merely for the purpose of illustration
10‧‧‧控制器 10‧‧‧ Controller
101‧‧‧誤差信號產生電路 101‧‧‧Error signal generation circuit
1011‧‧‧積分器 1011‧‧‧ integrator
1012‧‧‧精確電流監視器 1012‧‧‧Precise current monitor
1013‧‧‧減法單元 1013‧‧‧Subtraction unit
1014‧‧‧需求電流源 1014‧‧‧Required current source
102‧‧‧快速電流監測器 102‧‧‧ fast current monitor
103‧‧‧遲滯控制器 103‧‧‧hysteresis controller
104‧‧‧電阻 104‧‧‧resistance
105‧‧‧遲滯比較器 105‧‧‧hysteresis comparator
106‧‧‧閘極驅動器 106‧‧‧gate driver
107‧‧‧NMOS開關電晶體 107‧‧‧ NMOS switch transistor
11‧‧‧第一電流感測電阻 11‧‧‧First current sense resistor
12、LD1‧‧‧LED 12, LD1‧‧‧LED
13‧‧‧第二電流感測電阻 13‧‧‧Second current sensing resistor
14‧‧‧齊納二極體 14‧‧‧Zina diode
20‧‧‧LED照明系統 20‧‧‧LED Lighting System
21‧‧‧電流監視器 21‧‧‧ Current monitor
22‧‧‧分壓器 22‧‧‧Divider
23‧‧‧積分電路 23‧‧‧Integral Circuit
24‧‧‧比較器電路 24‧‧‧ Comparator Circuit
25‧‧‧邏輯電路 25‧‧‧Logical Circuit
26‧‧‧齊納二極體 26‧‧‧Zina diode
A1~A4‧‧‧區域 A1~A4‧‧‧Area
Avg_Current‧‧‧期望的電流值 Avg_Current‧‧‧ Expected current value
C1‧‧‧電容 C1‧‧‧ capacitor
CMP1‧‧‧比較器 CMP1‧‧‧ comparator
CUV1‧‧‧理想的LED電流曲線 CUV1‧‧‧Ideal LED current curve
CUV2、CUV3‧‧‧非理想的LED電流曲線 CUV2, CUV3‧‧‧ non-ideal LED current curve
delay1‧‧‧導通延遲 Delay1‧‧‧ conduction delay
delay2‧‧‧截止延遲 Delay2‧‧‧ cutoff delay
GND‧‧‧接地電壓 GND‧‧‧ Grounding voltage
K‧‧‧比值 K‧‧ ratio
L、L1‧‧‧電感 L, L1‧‧‧ inductance
M1‧‧‧NMOS電晶體 M1‧‧‧NMOS transistor
M2‧‧‧NMOS開關電晶體 M2‧‧‧ NMOS switch transistor
OP1、OP2‧‧‧運算放大器 OP1, OP2‧‧‧Operational Amplifier
R1~R5‧‧‧電阻 R1~R5‧‧‧ resistance
Rs‧‧‧電流感測電阻 Rs‧‧‧ current sense resistor
Vin‧‧‧輸入電壓 Vin‧‧‧Input voltage
Vref‧‧‧參考電壓 Vref‧‧‧reference voltage
Vs‧‧‧電流感測電阻Rs之兩端的電壓 Vs‧‧‧ voltage across the current sense resistor Rs
Vs_avg‧‧‧Vs的平均電壓 Average voltage of Vs_avg‧‧‧Vs
Vx‧‧‧穩壓器輸出 Vx‧‧‧ voltage regulator output
提供的附圖用以使本發明所屬技術領域具有通常知識者可以進一步理解本發明,並且被併入與構成本發明之說明書的一部分。附圖示出了本發明的示範實施例,並且用以與本發明之說明書一起用於解釋本發明的原理。 The drawings are provided to enable a person of ordinary skill in the art to have a further understanding of the invention, and are incorporated in and constitute a part of the specification. The drawings illustrate exemplary embodiments of the invention and, together,
第1圖是傳統LED照明系統的方塊圖。 Figure 1 is a block diagram of a conventional LED lighting system.
第2圖是本發明示範實施例的用於LED照明系統中的開關穩壓器的控制器的示意圖。 2 is a schematic diagram of a controller for a switching regulator in an LED lighting system in accordance with an exemplary embodiment of the present invention.
第3圖是使用本發明示範實施例提供的控制器之實際LED電流與不使用前述控制器之非理想LED電流的波形圖。 Figure 3 is a waveform diagram of the actual LED current of the controller provided with the exemplary embodiment of the present invention and the non-ideal LED current without the aforementioned controller.
現在將詳細參考本發明的示範實施例,其示範實施例會在附圖中被繪示出。在可能的情況下,在附圖和說明書中使用相同的元件符號來指代相同或相似的部件。 Reference will now be made in detail to the exemplary embodiments embodiments embodiments Wherever possible, the same reference numerals are in the
本發明的示範實施例提供了一種用於LED照明系統中的開關穩壓器(註:開關穩壓器可以是降壓型穩壓器)之控制器。控制器具有電流監視器、分壓器、積分電路和比較器電路。電流監視器並聯連接電流檢測電阻,其中電流感測電阻用以感測通過LED的LED電流。分壓器連接電流監視器,並用以接收電流監視器的感測電流輸出。分壓器用於根據感測電流產生第一分壓、第二分壓和第三分壓,其中第一分壓大於第二分壓,且第二分壓大於第三分壓。 An exemplary embodiment of the present invention provides a controller for a switching regulator in an LED lighting system (note that the switching regulator can be a buck regulator). The controller has a current monitor, a voltage divider, an integrating circuit, and a comparator circuit. The current monitor is connected in parallel with the current sense resistor, wherein the current sense resistor is used to sense the LED current through the LED. The voltage divider is connected to the current monitor and is used to receive the sense current output of the current monitor. The voltage divider is configured to generate a first partial pressure, a second partial pressure, and a third partial pressure according to the sensing current, wherein the first partial pressure is greater than the second partial pressure, and the second partial pressure is greater than the third partial pressure.
積分器電路連接到分壓器和比較器電路,並且用於比較第二分壓和參考電壓,以在具有串聯連接之電阻和電容的RC積分電路的兩端產生積分電壓。比較器電路連接到分壓器,並將積分電壓與第一分壓和第三分壓進行比較,以產生驅動信號以控制NMOS開關電晶體來調節LED電流。 An integrator circuit is coupled to the voltage divider and comparator circuit and is operative to compare the second partial voltage and the reference voltage to produce an integrated voltage across the RC integrating circuit having series connected resistors and capacitors. A comparator circuit is coupled to the voltage divider and compares the integrated voltage to the first divided voltage and the third divided voltage to generate a drive signal to control the NMOS switching transistor to regulate the LED current.
透過使用積分電路,可以減少對期望的平均LED電流的非理想效應。具體來說,邏輯電路的延遲、電感的電感值以及LED照明系統的輸入電壓和輸出電壓(即穩壓器輸出)的比例等影響(即存在非理想效應)可以被補償,使 得實際的平均LED電流近似於所需的平均電流。此外,透過使用積分電路,LED的正向電壓對實際的平均LED電流沒有影響。 By using an integrating circuit, the non-ideal effect on the desired average LED current can be reduced. Specifically, the delay of the logic circuit, the inductance value of the inductor, and the ratio of the input voltage of the LED illumination system to the output voltage (ie, the regulator output) (ie, the presence of non-ideal effects) can be compensated for The actual average LED current is approximated to the desired average current. Furthermore, by using an integrating circuit, the forward voltage of the LED has no effect on the actual average LED current.
請參照第2圖,第2圖是本發明示範實施例的用於LED照明系統中的開關穩壓器的控制器的示意圖。第2圖的LED照明系統20包括開關穩壓器和LED LD1,其中開關穩壓器連接到LED LD1,並用以調節通過LED LD1的LED電流。 Referring to FIG. 2, FIG. 2 is a schematic diagram of a controller for a switching regulator in an LED lighting system according to an exemplary embodiment of the present invention. The LED illumination system 20 of Figure 2 includes a switching regulator and an LED LD1, wherein the switching regulator is coupled to the LED LD1 and is used to regulate the LED current through the LED LD1.
開關穩壓器包括控制器、電流感測電阻Rs、電感L1和齊納二極體26。所述控制器包括電流監視器21、分壓器22、積分電路23、比較器電路24、邏輯電路25和NMOS開關電晶體M2。控制器用於控制開關穩壓器來調節LED電流,使得實際的平均LED電流為預期者。 The switching regulator includes a controller, a current sensing resistor Rs, an inductor L1, and a Zener diode 26. The controller includes a current monitor 21, a voltage divider 22, an integration circuit 23, a comparator circuit 24, a logic circuit 25, and an NMOS switch transistor M2. The controller is used to control the switching regulator to regulate the LED current so that the actual average LED current is expected.
輸入電壓Vin施加在電流感測電阻Rs的一端。LED LD1的陽極連接到電流感測電阻Rs的另一端,LED LD1的陰極連接到電感L1的一端。齊納二極體26的陽極和陰極分別連接到電感L1的另一端和電流感測電阻Rs的該一端。電感L1的另一端用於產生穩壓器輸出Vx。 The input voltage Vin is applied to one end of the current sensing resistor Rs. The anode of the LED LD1 is connected to the other end of the current sensing resistor Rs, and the cathode of the LED LD1 is connected to one end of the inductor L1. The anode and cathode of the Zener diode 26 are connected to the other end of the inductor L1 and the one end of the current sense resistor Rs, respectively. The other end of the inductor L1 is used to generate the regulator output Vx.
電流感測電阻Rs並聯連接電流監視器21,即電流感測電阻Rs的兩端連接到電流監視器21的輸入端。分壓器22連接到電流監視器21的輸出端。積分器電路23的兩個輸入端分別連接到分壓器22的內部端並施加參考電壓K * Vs_avg,其中K是常數,Vs_avg是電流感測電阻Rs之兩端的電壓Vs的平均電壓值。比較器電路24的三個輸入端分別連接到分壓器22的輸入端、分壓器22的另一個內部端和積分器電路23的輸出端。 The current sensing resistor Rs is connected in parallel to the current monitor 21, that is, both ends of the current sensing resistor Rs are connected to the input terminal of the current monitor 21. The voltage divider 22 is connected to the output of the current monitor 21. The two input terminals of the integrator circuit 23 are respectively connected to the inner terminals of the voltage divider 22 and apply a reference voltage K*Vs_avg, where K is a constant, and Vs_avg is the average voltage value of the voltage Vs across the current sense resistor Rs. The three inputs of comparator circuit 24 are coupled to the input of voltage divider 22, the other internal of voltage divider 22, and the output of integrator circuit 23, respectively.
邏輯電路25的輸入端和輸出端分別連接到比較器電路24的輸出端和NMOS開關電晶體M2的閘極端,NMOS開關晶體M2的汲極端和源極端分別連接到電感L1的另一端和接地電壓GND。 The input terminal and the output terminal of the logic circuit 25 are respectively connected to the output terminal of the comparator circuit 24 and the gate terminal of the NMOS switch transistor M2, and the 汲 terminal and the source terminal of the NMOS switch crystal M2 are respectively connected to the other end of the inductor L1 and the ground voltage. GND.
電流監視器21用於接收電流感測電阻Rs兩端的電壓Vs,因此通過電流檢測電阻Rs的LED電流可以被電流監視器21所感測。如此,電流監視器21可以依據LED電流輸出感測電流。電流監視器21可以由電阻R1、運算放大器OP1和NMOS電晶體M1來實現,但本發明不限於此。 The current monitor 21 is for receiving the voltage Vs across the current sensing resistor Rs, so the LED current passing through the current detecting resistor Rs can be sensed by the current monitor 21. As such, the current monitor 21 can sense the current based on the LED current output. The current monitor 21 can be realized by the resistor R1, the operational amplifier OP1, and the NMOS transistor M1, but the present invention is not limited thereto.
電阻R1的一端與電流感測電阻Rs的該一端連接,運算放大器OP1的正輸入端和負輸入端分別連接電流感測電阻Rs的另一端與電阻R1的另一端。運算放大器OP1的輸出端連接到NMOS電晶體M1的閘極端,NMOS電晶體M1的汲極端和源極端分別連接到電阻R1的該另一端和分壓器22的一輸入端。 One end of the resistor R1 is connected to the one end of the current sensing resistor Rs, and the positive input terminal and the negative input terminal of the operational amplifier OP1 are respectively connected to the other end of the current sensing resistor Rs and the other end of the resistor R1. The output of the operational amplifier OP1 is connected to the gate terminal of the NMOS transistor M1, and the NMOS terminal and the source terminal of the NMOS transistor M1 are connected to the other end of the resistor R1 and an input terminal of the voltage divider 22, respectively.
通過上述電流監視器21之元件的連接方式,負反饋迴路存在於電流監視器21中,因此感測電流實際上大約是Vs/R1。分壓器22用於接收感測電流,並在其輸入端和兩個內部端產生第一至第三分壓,其中第一分壓大於第二分壓,第二分壓大於第三分電壓。 The negative feedback loop is present in the current monitor 21 by the connection of the elements of the current monitor 21 described above, so the sense current is actually approximately Vs/R1. The voltage divider 22 is configured to receive the sensing current and generate first to third partial voltages at the input end and the two internal ends, wherein the first partial pressure is greater than the second partial pressure, and the second partial pressure is greater than the third partial voltage .
分壓器22可以由串聯的電阻R2、R3和R4來實現,並且本發明不限於此。實際上,第一分壓大約是(Vs/R1)*(R2+R3+R4),第二分壓實際上大約是(Vs/R1)*(R3+R4),第三分壓實際上大約是(Vs/R1)*R4。當電阻R2、R3與與R4經適當設計時,第一至第三分壓分別約為1.1K * Vs、K * Vs和0.9K * Vs,其中K為(R3+R4)/R1的比值。 The voltage divider 22 can be implemented by resistors R2, R3, and R4 connected in series, and the present invention is not limited thereto. In fact, the first partial pressure is approximately (Vs/R1)*(R2+R3+R4), and the second partial pressure is actually approximately (Vs/R1)*(R3+R4), and the third partial pressure is actually approximately Yes (Vs/R1)*R4. When resistors R2, R3 and R4 are suitably designed, the first to third partial voltages are approximately 1.1 K * Vs, K * Vs, and 0.9 K * Vs, respectively, where K is the ratio of (R3 + R4) / R1.
積分電路23將第二分壓(即K * Vs)與參考電壓K * Vs_avg進行比較,並根據比較結果產生積分電壓。具體地說,當第二分壓比參考電壓大時,正電壓會施加在積分電路23的RC電路上,使得RC電路之兩端的積分電壓增加;當第二分壓不大於參考電壓時,負電壓會施加在積分器電路23的RC電路上,使得RC電路之兩端的積分電壓降低。 The integrating circuit 23 compares the second divided voltage (i.e., K*Vs) with the reference voltage K*Vs_avg, and generates an integrated voltage based on the comparison result. Specifically, when the second divided voltage is larger than the reference voltage, a positive voltage is applied to the RC circuit of the integrating circuit 23, so that the integrated voltage across the RC circuit increases; when the second divided voltage is not greater than the reference voltage, negative The voltage is applied to the RC circuit of the integrator circuit 23 such that the integrated voltage across the RC circuit is lowered.
積分電路23可以由運算放大器OP2、電阻R5和電容C1來實現。電阻R5和電容C1串聯連接以形成RC電路。運算放大器OP2的正輸入端連接到分壓 器22的內部端以接收第二分壓,運算放大器OP2的負輸入端施加參考電壓K * Vs_avg,運算放大器OP2的輸出端連接到比較器電路24的正輸入端。電阻R5的一端連接到運算放大器OP2的輸出端,電容C1的兩端分別連接到電阻R5的另一端和接地電壓GND。 The integrating circuit 23 can be realized by an operational amplifier OP2, a resistor R5, and a capacitor C1. Resistor R5 and capacitor C1 are connected in series to form an RC circuit. The positive input of op amp OP2 is connected to the partial voltage The internal terminal of the device 22 receives the second divided voltage, the negative input of the operational amplifier OP2 applies the reference voltage K*Vs_avg, and the output of the operational amplifier OP2 is connected to the positive input of the comparator circuit 24. One end of the resistor R5 is connected to the output terminal of the operational amplifier OP2, and both ends of the capacitor C1 are respectively connected to the other end of the resistor R5 and the ground voltage GND.
比較器電路24將積分電壓與第一和第三分壓進行比較,從而輸出驅動信號。比較器電路24可以由具有兩個負輸入端和一個正輸入端的比較器CMP1來實現,並且本發明不限於此。比較器CMP1的兩個負輸入端分別連接到分壓器22的輸入端和其另一個內部端,比較器CMP1的正輸入端連接到積分電路23的輸出端。比較器CMP1的輸出端連接到邏輯電路25的輸入端。 The comparator circuit 24 compares the integrated voltage with the first and third divided voltages to output a drive signal. The comparator circuit 24 can be implemented by a comparator CMP1 having two negative inputs and one positive input, and the invention is not limited thereto. The two negative inputs of the comparator CMP1 are connected to the input of the voltage divider 22 and the other internal terminal thereof, respectively, and the positive input of the comparator CMP1 is connected to the output of the integrating circuit 23. The output of comparator CMP1 is coupled to the input of logic circuit 25.
具有多個邏輯閘的邏輯電路25用於接收驅動信號並相應地在其輸出端產生開關信號,以便控制NMOS開關電晶體M2的導通/截止狀態。當積分電壓小於第三分壓時,NMOS開關晶體M2截止,LED電流增加。當積分電壓大於第一分壓時,NMOS開關電晶體M2導通,LED電流降低。 A logic circuit 25 having a plurality of logic gates is operative to receive the drive signal and accordingly generate a switching signal at its output to control the on/off state of the NMOS switch transistor M2. When the integrated voltage is less than the third divided voltage, the NMOS switch crystal M2 is turned off, and the LED current is increased. When the integrated voltage is greater than the first divided voltage, the NMOS switching transistor M2 is turned on, and the LED current is lowered.
請參照第3圖,第3圖是使用本發明示範實施例提供的控制器之實際LED電流與不使用前述控制器之非理想LED電流的波形圖。非理想LED的電流曲線CUV2顯示NMOS開關電晶體M2的導通和截止延遲delay1、delay2會影響平均LED電流。在此請注意,導通延遲delay1和截止延遲delay2彼此不相同,並且第3圖中所示的區域A1和A2彼此不相同,使得實際的平均LED電流不能是期望的電流值Avg_Current。 Referring to FIG. 3, FIG. 3 is a waveform diagram of actual LED current of the controller provided by the exemplary embodiment of the present invention and non-ideal LED current without using the foregoing controller. The current curve CUV2 of the non-ideal LED shows that the on and off delays delay1 and delay2 of the NMOS switch transistor M2 affect the average LED current. Note here that the on-delay delay1 and the off-delay delay2 are different from each other, and the regions A1 and A2 shown in FIG. 3 are different from each other such that the actual average LED current cannot be the desired current value Avg_Current.
進一步考慮到LED照明系統的輸入電壓和輸出電壓(即穩壓器輸出Vx)的比例,非理想LED電流可被非理想LED電流曲線CUV3所表示,其中當NMOS開關電晶體M2截止時,非理想的LED電流曲線CUV3的斜率為(Vin-Vout)/L,並且當NMOS開關電晶體M2導通時,非理想的LED電流曲線CUV3的斜率為Vout/L。應注意的是,由於上述多個影響彼此不相同,第3圖所示的區域A3和A4 會彼此相同,所以實際的平均LED電流不為期望的電流值Avg_Current。然而,通過使用積分電路,可以減少對期望的平均LED電流的非理想效應,並且實際的LED電流曲線可以類似於理想的LED電流曲線CUV1。 Further considering the ratio of the input voltage of the LED illumination system and the output voltage (ie, the regulator output Vx), the non-ideal LED current can be represented by the non-ideal LED current curve CUV3, wherein when the NMOS switch transistor M2 is turned off, it is not ideal. The slope of the LED current curve CUV3 is (Vin-Vout) / L, and when the NMOS switching transistor M2 is turned on, the slope of the non-ideal LED current curve CUV3 is Vout / L. It should be noted that since the above multiple effects are different from each other, the areas A3 and A4 shown in Fig. 3 Will be identical to each other, so the actual average LED current is not the desired current value Avg_Current. However, by using an integrating circuit, the non-ideal effect on the desired average LED current can be reduced, and the actual LED current curve can be similar to the ideal LED current curve CUV1.
因此,在本發明的示範實施例中,所提供的用於LED照明系統的開關穩壓器的控制器可以解決實際的平均LED電流偏離期望的平均LED電流的問題。延遲、輸入電壓、穩壓器輸出,甚至LED的正向電壓都不會影響實際的平均LED電流。 Thus, in an exemplary embodiment of the invention, the provided controller for a switching regulator for an LED lighting system can address the problem of the actual average LED current deviating from the desired average LED current. The delay, input voltage, regulator output, and even the forward voltage of the LED do not affect the actual average LED current.
上述描述僅僅是本發明的示範實施例,而不意圖限制本發明的範圍。因此,基於本發明的權利要求的各種等效的改變、替代或修改都被視為被本發明之範圍所包含。 The above description is only exemplary embodiments of the invention and is not intended to limit the scope of the invention. Accordingly, various equivalents, modifications, and alterations of the present invention are intended to be included within the scope of the present invention.
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TW201043078A (en) * | 2009-03-27 | 2010-12-01 | Diodes Zetex Semiconductors Ltd | Controller for switching regulator, switching regulator and light source |
US20120249000A1 (en) * | 2011-03-29 | 2012-10-04 | Semiconductor Components Industries, Llc | Led dimmer circuit |
TW201325316A (en) * | 2011-12-09 | 2013-06-16 | Hon Hai Prec Ind Co Ltd | LED controlling circuit |
CN106851892A (en) * | 2011-08-11 | 2017-06-13 | 半导体元件工业有限责任公司 | The control circuit of light-emitting component |
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CN101668370A (en) * | 2008-07-15 | 2010-03-10 | 英特赛尔美国股份有限公司 | Transient suppression for boost regulator |
TW201043078A (en) * | 2009-03-27 | 2010-12-01 | Diodes Zetex Semiconductors Ltd | Controller for switching regulator, switching regulator and light source |
US20120249000A1 (en) * | 2011-03-29 | 2012-10-04 | Semiconductor Components Industries, Llc | Led dimmer circuit |
CN106851892A (en) * | 2011-08-11 | 2017-06-13 | 半导体元件工业有限责任公司 | The control circuit of light-emitting component |
TW201325316A (en) * | 2011-12-09 | 2013-06-16 | Hon Hai Prec Ind Co Ltd | LED controlling circuit |
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