TWI539729B - Ac-dc converter and power factor correction circuit thereof - Google Patents
Ac-dc converter and power factor correction circuit thereof Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Description
本發明是有關於一種轉換器的技術,特別是有關於一種交流-直流轉換器及其功因校正電路。 The present invention relates to a converter technology, and more particularly to an AC-DC converter and its power factor correction circuit.
交流-直流轉換器已普遍應用於各種電子產品,且技術不斷精進。為了提高交流-直流轉換器的工作效率,一般都在交流-直流轉換器中加裝功因校正電路(Power Factor Correction;PFC)來進行功率因數的改善。 AC-DC converters have been widely used in a variety of electronic products, and the technology continues to improve. In order to improve the efficiency of the AC-DC converter, power factor correction (PFC) is generally added to the AC-DC converter to improve the power factor.
然而,傳統的交流-直流轉換器皆未抑制其電感電流的大小,因此會有電感電流的峰值過大的問題。 However, the conventional AC-DC converter does not suppress the magnitude of its inductor current, so there is a problem that the peak value of the inductor current is excessive.
本發明提出一種功因校正電路,其可幫助交流-直流轉換器抑制其電感電流的峰值。 The present invention proposes a power factor correction circuit that helps the AC-DC converter to suppress the peak value of its inductor current.
本發明另提出一種包含上述功因校正電路的交流-直流轉換器。 The present invention further provides an AC-DC converter including the above-described power factor correction circuit.
本發明所提供的一種功因校正電路,適用於交流-直流轉換器,功因校正電路包括:時脈產生器、壓控震盪器、時脈訊號選擇器、重置訊號產生電路、閂鎖器及比較器。時脈產生器用以產生第一時脈。壓控震盪器用以產生第二時脈與三角波訊號。時脈訊號選擇器用以接收第一時脈與第二時 脈,並輸出第一時脈與第二時脈中頻率較高者。重置訊號產生電路用以依據交流-直流轉換器的輸出電壓的反饋電壓、交流-直流轉換器的電感電流的第一取樣訊號與三角波訊號來產生重置訊號。閂鎖器具有設置端、重置端與輸出端,設置端用以接收時脈訊號選擇器所輸出的時脈訊號,重置端用以接收重置訊號,而輸出端用以輸出脈寬調變訊號至交流-直流轉換器的開關的一控制端。比較器用以比較第一取樣訊號與電流上限訊號,電流上限訊號的電壓大小對應至電感電流臨界值,且每當第一取樣訊號的大小達到電流上限訊號所對應的電感電流臨界值時,比較器便控制壓控震盪器將第二時脈的頻率與三角波訊號的頻率提高至大於第一時脈的頻率,並控制壓控震盪器依第一取樣訊號達到電感電流臨界值的次數來遞增第二時脈與三角波訊號的頻率。 The utility model provides a power factor correction circuit suitable for an AC-DC converter, and the power factor correction circuit comprises: a clock generator, a voltage controlled oscillator, a clock signal selector, a reset signal generating circuit, and a latch And comparator. The clock generator is used to generate the first clock. The voltage controlled oscillator is used to generate the second clock and triangular wave signals. The clock signal selector is configured to receive the first clock and the second time Pulse, and output the first clock and the second clock in the higher frequency. The reset signal generating circuit is configured to generate a reset signal according to a feedback voltage of an output voltage of the AC-DC converter, a first sampling signal of the inductor current of the AC-DC converter, and a triangular wave signal. The latch has a setting end, a reset end and an output end, the setting end is for receiving a clock signal output by the clock signal selector, the reset end is for receiving the reset signal, and the output end is for outputting the pulse width adjustment The variable signal to a control terminal of the switch of the AC-DC converter. The comparator is configured to compare the first sampling signal with the current upper limit signal, and the voltage of the current upper limit signal corresponds to the inductor current threshold, and each time the magnitude of the first sampling signal reaches the inductor current threshold corresponding to the current upper limit signal, the comparator The control voltage controlled oscillator increases the frequency of the second clock and the frequency of the triangular wave signal to be greater than the frequency of the first clock, and controls the voltage controlled oscillator to increase the second according to the number of times the first sampling signal reaches the critical value of the inductor current. The frequency of the clock and triangle wave signals.
本發明還提供一種交流-直流轉換器,其包括:橋式整流器、電感、二極體、開關及如前所述的功因校正電路。橋式整流器具有第一交流輸入端、第二交流輸入端、正輸出端與負輸出端,第一交流輸入端與第二交流輸入端用以耦接至交流電源。電感的一端耦接正輸出端。二極體的陽極耦接電感的另一端,而其陰極用以作為交流-直流轉換器的第一電壓輸出端。開關具有第一端、第二端與控制端,第一端耦接電感的另一端,第二端耦接負輸出端,其中負輸出端用以作為交流-直流轉換器的第二電壓輸出端。 The present invention also provides an AC-DC converter comprising: a bridge rectifier, an inductor, a diode, a switch, and a power factor correction circuit as described above. The bridge rectifier has a first AC input terminal, a second AC input terminal, a positive output terminal and a negative output terminal, and the first AC input terminal and the second AC input terminal are coupled to the AC power source. One end of the inductor is coupled to the positive output. The anode of the diode is coupled to the other end of the inductor and its cathode is used as the first voltage output of the AC-DC converter. The switch has a first end, a second end and a control end, the first end is coupled to the other end of the inductor, the second end is coupled to the negative output end, and the negative output end is used as the second voltage output end of the AC-DC converter .
上述實施例中的重置訊號產生電路包括:電壓誤差放大器、乘法器、電流誤差放大器及脈寬調變比較器。電壓誤差放大器用以比較反饋電壓與參考電壓,並據以產生第一誤差訊號。乘法器用以依據第一誤差訊號與交流-直流轉換器的輸入電壓於全波整流後所取得的第二取樣訊號而產生基準電流訊號。電流誤差放大器用以比較基準電流訊號與第一 取樣訊號,並據以產生第二誤差訊號。脈寬調變比較器用以比較第二誤差訊號與三角波訊號,並據以產生重置訊號。 The reset signal generating circuit in the above embodiment includes a voltage error amplifier, a multiplier, a current error amplifier, and a pulse width modulation comparator. The voltage error amplifier is configured to compare the feedback voltage with the reference voltage and generate a first error signal accordingly. The multiplier is configured to generate a reference current signal according to the second sampling signal obtained after the full-wave rectification according to the first error signal and the input voltage of the AC-DC converter. Current error amplifier for comparing reference current signal with first The signal is sampled and a second error signal is generated accordingly. The pulse width modulation comparator is configured to compare the second error signal with the triangular wave signal and generate a reset signal accordingly.
在本發明中,每當第一取樣訊號的大小達到電流上限訊號所對應的電感電流臨界值時,功因校正電路的比較器便控制壓控震盪器將第二時脈的頻率與三角波訊號的頻率提高至大於第一時脈的頻率,並控制壓控震盪器依第一取樣訊號達到電感電流臨界值的次數來遞增第二時脈與三角波訊號的頻率。因此,每當第一取樣訊號的大小達到電流上限訊號所對應的電感電流臨界值時,壓控震盪器的頻率便升高以適時地調整開關的切換頻率,進而使電感電流的振幅減小而改變電感電流的峰值,以致於電感電流的峰值低於電流上限值。 In the present invention, the comparator of the power factor correction circuit controls the frequency of the second clock and the triangular wave signal whenever the size of the first sampling signal reaches the critical value of the inductor current corresponding to the current upper limit signal. The frequency is increased to be greater than the frequency of the first clock, and the voltage controlled oscillator is controlled to increase the frequency of the second clock and the triangular wave signal according to the number of times the first sampling signal reaches the inductor current threshold. Therefore, each time the size of the first sampling signal reaches the critical value of the inductor current corresponding to the current upper limit signal, the frequency of the voltage controlled oscillator is increased to adjust the switching frequency of the switch in a timely manner, thereby reducing the amplitude of the inductor current. The peak value of the inductor current is changed so that the peak value of the inductor current is lower than the current upper limit value.
100‧‧‧交流-直流轉換器 100‧‧‧AC-DC converter
10‧‧‧橋式整流器 10‧‧‧Bridge rectifier
11‧‧‧正輸出端 11‧‧‧ positive output
12‧‧‧負輸出端 12‧‧‧negative output
20‧‧‧電感 20‧‧‧Inductance
30‧‧‧二極體 30‧‧‧ diode
40‧‧‧開關 40‧‧‧ switch
41‧‧‧第一端 41‧‧‧ first end
42‧‧‧第二端 42‧‧‧second end
43‧‧‧控制端 43‧‧‧Control terminal
50‧‧‧功因校正電路 50‧‧‧Power factor correction circuit
51‧‧‧時脈產生器 51‧‧‧ Clock Generator
52‧‧‧壓控震盪器 52‧‧‧Voltage-controlled oscillator
53‧‧‧時脈訊號選擇器 53‧‧‧clock signal selector
54‧‧‧重置訊號產生電路 54‧‧‧Reset signal generation circuit
542‧‧‧電壓誤差放大器 542‧‧‧Voltage error amplifier
544‧‧‧乘法器 544‧‧‧Multiplier
546‧‧‧電流誤差放大器 546‧‧‧ Current Error Amplifier
548‧‧‧脈寬調變比較器 548‧‧‧ Pulse width modulation comparator
55‧‧‧閂鎖器 55‧‧‧Latch
551、SET‧‧‧設置端 551, SET‧‧‧Setting end
552、RESET‧‧‧重置端 552, RESET‧‧‧ reset end
553、Q‧‧‧輸出端 553, Q‧‧‧ output
56‧‧‧比較器 56‧‧‧ comparator
60、549‧‧‧電容 60, 549‧‧‧ capacitor
70‧‧‧電感電流值 70‧‧‧Inductor current value
71‧‧‧電感電流的平均值 71‧‧‧Average of the inductor current
72‧‧‧電感電流臨界值 72‧‧‧Inductance current threshold
80‧‧‧電壓取樣電路 80‧‧‧Voltage sampling circuit
90、91、92、93‧‧‧電流取樣電路 90, 91, 92, 93‧‧‧ current sampling circuit
901、911‧‧‧電流感應線圈 901, 911‧‧‧ current induction coil
902、912‧‧‧二極體 902, 912‧‧ ‧ diode
903‧‧‧整流波形取樣電路 903‧‧‧Rected Waveform Sampling Circuit
AC‧‧‧交流電源 AC‧‧‧AC power supply
S1‧‧‧電流上限訊號 S 1 ‧‧‧ current limit signal
S2‧‧‧第一取樣訊號 S 2 ‧‧‧first sampling signal
S3‧‧‧第二取樣訊號 S 3 ‧‧‧Second sampling signal
S54‧‧‧重置訊號 S 54 ‧‧‧Reset signal
S522‧‧‧三角波訊號 S 522 ‧‧‧ triangle wave signal
S543‧‧‧第一誤差訊號 S 543 ‧‧‧First error signal
S545‧‧‧基準電流訊號 S 545 ‧‧‧reference current signal
S547‧‧‧第二誤差訊號 S 547 ‧‧‧second error signal
S57‧‧‧脈寬調變訊號 S 57 ‧‧‧ Pulse width modulation signal
CLK1‧‧‧第一時脈 CLK1‧‧‧ first clock
CLK2‧‧‧第二時脈 CLK2‧‧‧ second clock
VOUT‧‧‧輸出電壓 V OUT ‧‧‧ output voltage
VFB‧‧‧反饋電壓 V FB ‧‧‧ feedback voltage
VREF‧‧‧參考電壓 V REF ‧‧‧reference voltage
R1、R2、R3、R4‧‧‧電阻 R 1 , R 2 , R 3 , R 4 ‧‧‧ resistance
T1、T2、T3‧‧‧時間區段 T1, T2, T3‧‧‧ time zone
GND‧‧‧接地電位 GND‧‧‧ Ground potential
圖1為本發明一實施例的交流-直流轉換器的示意圖。 1 is a schematic diagram of an AC-DC converter according to an embodiment of the present invention.
圖2為本發明一實施例的電感電流的變化的示意圖。 2 is a schematic diagram showing changes in inductor current according to an embodiment of the present invention.
圖3繪示有電流取樣電路的另一種實施態樣。 FIG. 3 illustrates another embodiment of a current sampling circuit.
圖4繪示有電流取樣電路的再一種實施態樣。 Figure 4 illustrates yet another embodiment of a current sampling circuit.
圖5繪示有電流取樣電路的又再一種實施態樣。 Figure 5 illustrates yet another embodiment of a current sampling circuit.
圖1為本發明一實施例的交流-直流轉換器的示意圖。請參照圖1,交流-直流轉換器100包括有橋式整流器10、電感20、二極體30、開關40、功因校正電路50、電容60、電壓取樣電路80、電流取樣電路90與整流波形取樣電路903。 1 is a schematic diagram of an AC-DC converter according to an embodiment of the present invention. Referring to FIG. 1 , the AC-DC converter 100 includes a bridge rectifier 10 , an inductor 20 , a diode 30 , a switch 40 , a power factor correction circuit 50 , a capacitor 60 , a voltage sampling circuit 80 , a current sampling circuit 90 , and a rectification waveform . Sampling circuit 903.
橋式整流器10具有第一交流輸入端、第二交流輸入端、正輸出端11與負輸出端12,第一交流輸入端與第二交流輸入端用以耦接至交流電源AC。電感20的一端透過電流取樣電路90耦接正輸出端11。二極體30的陽極耦接電感20的另一端,而其陰極用以作為交流-直流轉換器100的第一電壓輸出端。開關40具有第一端41、第二端42與控制端43,第一端41耦接電感20的另一端,第二端42耦接負輸出端12,其中負輸出端12用以作為交流-直流轉換器100的第二電壓輸出端。在此例中,第二電壓輸出端乃是耦接接地電位GND。開關40例如可採用一NMOS電晶體來實現,其中NMOS電晶體的閘極用以作為前述的控制端43。然本發明不以此為限,在符合電路動作原理下,開關40亦可以其他型態實現,如以PMOS電晶體來實現。另外,電容60耦接於交流-直流轉換器100的第一電壓輸出端與第二電壓輸出端之間。 The bridge rectifier 10 has a first AC input terminal, a second AC input terminal, a positive output terminal 11 and a negative output terminal 12, and the first AC input terminal and the second AC input terminal are coupled to the AC power source AC. One end of the inductor 20 is coupled to the positive output terminal 11 through a current sampling circuit 90. The anode of the diode 30 is coupled to the other end of the inductor 20, and the cathode thereof is used as the first voltage output of the AC-DC converter 100. The switch 40 has a first end 41, a second end 42 and a control end 43, the first end 41 is coupled to the other end of the inductor 20, the second end 42 is coupled to the negative output end 12, and the negative output end 12 is used as an AC A second voltage output of the DC converter 100. In this example, the second voltage output terminal is coupled to the ground potential GND. The switch 40 can be implemented, for example, by an NMOS transistor, wherein the gate of the NMOS transistor is used as the aforementioned control terminal 43. However, the present invention is not limited thereto. Under the principle of circuit operation, the switch 40 can also be implemented in other types, such as a PMOS transistor. In addition, the capacitor 60 is coupled between the first voltage output end and the second voltage output end of the AC-DC converter 100.
電壓取樣電路80耦接於交流-直流轉換器100的第一電壓輸出端與接地電位之間,以便取得反饋電壓VFB。此電壓取樣電路80乃是以電阻R1與R2來實現。電流取樣電路90則是以電流感應線圈901及二極體902來實現,此電流取樣電路90用以對電感20的電感電流進行取樣而取得第一取樣訊號S2。至於整流波形取樣電路903,其用以對橋式整流器10的輸出訊號(即橋式整流器10對來自交流電源AC的輸入電壓進行全波整流後所產生的訊號)進行取樣而取得第二取樣訊號S3。此整流波形取樣電路903乃是以電阻R3與R4來實現。 The voltage sampling circuit 80 is coupled between the first voltage output terminal of the AC-DC converter 100 and the ground potential to obtain the feedback voltage V FB . This voltage sampling circuit 80 is implemented with resistors R 1 and R 2 . The current sampling circuit 90 is implemented by a current sensing coil 901 and a diode 902. The current sampling circuit 90 is configured to sample the inductor current of the inductor 20 to obtain a first sampling signal S 2 . The rectified waveform sampling circuit 903 is configured to sample the output signal of the bridge rectifier 10 (that is, the signal generated by the bridge rectifier 10 after full-wave rectification of the input voltage from the AC power source AC) to obtain the second sampling signal. S 3 . This rectified waveform sampling circuit 903 is realized by resistors R 3 and R 4 .
功因校正電路50包括有時脈產生器51、壓控震盪器52、時脈訊號選擇器53、重置訊號產生電路54、閂鎖器55及比較器56。時脈產生器51用以產生第一時脈CLK1。壓控震盪器52用以產生第二時脈CLK2與三角波訊號S522。時 脈訊號選擇器53用以接收第一時脈CLK1與第二時脈CLK2,並輸出第一時脈CLK1與第二時脈CLK2中頻率較高者。重置訊號產生電路54用以依據交流-直流轉換器100的輸出電壓VOUT的反饋電壓VFB、電感20的電感電流的第一取樣訊號S2與三角波訊號S522來產生重置訊號S54。閂鎖器55具有設置端551、重置端552與輸出端553,設置端551用以接收時脈訊號選擇器53所輸出的時脈訊號,重置端552用以接收重置訊號S54,而輸出端553用以輸出脈寬調變訊號S57至開關40的控制端43,進而控制開關40的啟閉狀態。比較器56用以比較第一取樣訊號S2與電流上限訊號S1,且每當第一取樣訊號S2的大小達到電流上限訊號S1所對應的電感電流臨界值時,比較器56便控制壓控震盪器52將第二時脈CLK2的頻率與三角波訊號S522的頻率提高至大於第一時脈CLK1的頻率,並控制壓控震盪器52依第一取樣訊號S2達到電感電流臨界值的次數來遞增第二時脈CLK2與三角波訊號S522的頻率。 The power factor correction circuit 50 includes a time pulse generator 51, a voltage controlled oscillator 52, a clock signal selector 53, a reset signal generating circuit 54, a latch 55, and a comparator 56. The clock generator 51 is configured to generate the first clock CLK1. The voltage controlled oscillator 52 is used to generate the second clock CLK2 and the triangular wave signal S 522 . The clock signal selector 53 is configured to receive the first clock CLK1 and the second clock CLK2, and output the higher frequency of the first clock CLK1 and the second clock CLK2. The reset signal generating circuit 54 is configured to generate the reset signal S 54 according to the feedback voltage V FB of the output voltage V OUT of the AC-DC converter 100, the first sampling signal S 2 of the inductor current of the inductor 20, and the triangular wave signal S 522 . . The latching device 55 has a setting end 551, a reset end 552 and an output end 553. The setting end 551 is configured to receive a clock signal output by the clock signal selector 53, and the reset end 552 is configured to receive the reset signal S54 . The output terminal 553 is configured to output the pulse width modulation signal S 57 to the control terminal 43 of the switch 40, thereby controlling the opening and closing state of the switch 40. The comparator 56 is configured to compare the first sampling signal S 2 with the current upper limit signal S 1 , and the comparator 56 controls each time the size of the first sampling signal S 2 reaches the inductor current threshold corresponding to the current upper limit signal S 1 . The voltage controlled oscillator 52 increases the frequency of the second clock CLK2 and the frequency of the triangular wave signal S 522 to be greater than the frequency of the first clock CLK1, and controls the voltage controlled oscillator 52 to reach the inductor current threshold according to the first sampling signal S 2 . The number of times increases the frequency of the second clock CLK2 and the triangular wave signal S 522 .
在本實施例中,重置訊號產生電路54包括有電壓誤差放大器542、乘法器544、電流誤差放大器546、脈寬調變比較器548與電容549。電壓誤差放大器542用以比較反饋電壓VFB與參考電壓VREF,並據以產生第一誤差訊號S543。乘法器544用以依據第一誤差訊號S543與第二取樣訊號S3而產生基準電流訊號S545。電流誤差放大器546用以比較基準電流訊號S545與第一取樣訊號S2,並據以產生第二誤差訊號S547。脈寬調變比較器548用以比較第二誤差訊號S547與三角波訊號S522,並據以產生重置訊號S54。 In the present embodiment, the reset signal generating circuit 54 includes a voltage error amplifier 542, a multiplier 544, a current error amplifier 546, a pulse width modulation comparator 548, and a capacitor 549. The voltage error amplifier 542 is configured to compare the feedback voltage V FB with the reference voltage V REF and accordingly generate a first error signal S 543 . The multiplier 544 is configured to generate the reference current signal S 545 according to the first error signal S 543 and the second sampling signal S 3 . The current error amplifier 546 is configured to compare the reference current signal S 545 with the first sample signal S 2 and generate a second error signal S 547 . The pulse width modulation comparator 548 is configured to compare the second error signal S 547 with the triangular wave signal S 522 and generate a reset signal S 54 accordingly .
在其他實施例中,壓控震盪器52所產生的三角波訊號S522可以是鋸齒波訊號。此外,前述的閂鎖器55可採用SR閂鎖器來實現。然本發明不以此為限,在符合電路動作 原理下,閂鎖器55亦可採用其他型態的閂鎖器或替代電路來實現。 In other embodiments, the triangular wave signal S 522 generated by the voltage controlled oscillator 52 may be a sawtooth wave signal. Further, the aforementioned latch 55 can be implemented using an SR latch. However, the present invention is not limited thereto, and the latch 55 may be implemented by other types of latches or alternative circuits in accordance with the principle of circuit operation.
圖2為本發明一實施例的電感電流的變化的示意圖。請合併參照圖1及圖2。如時間區段T1所示,在電感20的電感電流隨著電壓的變化而逐漸上升時,由於在這段期間中比較器56會判斷出第一取樣訊號S2所對應的電感電流值70的峰值尚未達到電流上限訊號S1所對應的電感電流臨界值72,使得比較器56不會去控制壓控震盪器52將第二時脈CLK2的頻率與三角波訊號S522的頻率提高至大於第一時脈CLK1的頻率,因此閂鎖器55會依據時脈訊號選擇器53所輸出的第一時脈CLK1與重置訊號S54來產生頻率較低的脈寬調變訊號S57,以利用脈寬調變訊號S57來控制開關40的啟閉狀態。 2 is a schematic diagram showing changes in inductor current according to an embodiment of the present invention. Please refer to FIG. 1 and FIG. 2 together. As shown in the time segment T1, when the inductor current of the inductor 20 gradually rises with the change of the voltage, the comparator 56 determines the inductor current value 70 corresponding to the first sample signal S 2 during this period. It has not yet reached a peak inductor current threshold value corresponding to the current limit signal S 72, so that the comparator 56 does not control the VCO 52 to increase the frequency of the second clock CLK2 and the triangular wave signal S 522 is greater than the first frequency The frequency of the clock CLK1, so the latch 55 generates a lower frequency pulse width modulation signal S 57 according to the first clock CLK1 and the reset signal S 54 output by the clock signal selector 53 to utilize the pulse The wide adjustment signal S 57 controls the opening and closing state of the switch 40.
而如時間區段T2所示,隨著電感電流的平均值(如標號71所示)逐漸逼近電感電流臨界值72,由於在這段期間中比較器56會判斷出第一取樣訊號S2所對應的電感電流值70的峰值已達到電流上限訊號S1所對應的電感電流臨界值72,使得比較器56會去控制壓控震盪器52將第二時脈CLK2的頻率與三角波訊號S522的頻率提高至大於第一時脈CLK1的頻率,因此閂鎖器55會依據時脈訊號選擇器53所輸出的第二時脈CLK2與重置訊號S54來產生頻率較高的脈寬調變訊號S57,以利用脈寬調變訊號S57來提高開關40的切換頻率,以便減小電感電流的振幅,進而抑制電感電流的峰值。 As indicated by time period T2, as the average value of the inductor current (as indicated by reference numeral 71) gradually approaches the inductor current threshold 72, the comparator 56 determines the first sampled signal S 2 during this period. corresponding to the peak value of the inductor current 70 has reached a threshold value corresponding to the current inductor current limit signal S 72, so that the comparator 56 to control the voltage controlled oscillator 52 will be the second clock CLK2, the frequency of the triangular wave signal S 522 The frequency is increased to be greater than the frequency of the first clock CLK1, so the latch 55 generates a higher frequency pulse width modulation signal according to the second clock CLK2 and the reset signal S 54 output by the clock signal selector 53. S 57, to take advantage of the PWM signal S 57 to increase the switching frequency of the switch 40, so as to reduce the amplitude of the inductor current, thereby suppressing the peak inductor current.
接下來,如時間區段T3所示,在電感20的電感電流隨著電壓的變化而逐漸下降時,由於在這段期間中比較器56又會判斷出第一取樣訊號S2所對應的電感電流值70的峰值未達到電流上限訊號S1所對應的電感電流臨界值72,使得比較器56不會去控制壓控震盪器52將第二時脈CLK2的 頻率與三角波訊號S522的頻率提高至大於第一時脈CLK1的頻率,因此閂鎖器55會依據時脈訊號選擇器53所輸出的第一時脈CLK1與重置訊號S54來產生頻率較低的脈寬調變訊號S57,以利用脈寬調變訊號S57來控制開關40的啟閉狀態。 Next, as shown in the time segment T3, when the inductor current of the inductor 20 gradually decreases with the change of the voltage, the comparator 56 determines the inductance corresponding to the first sample signal S 2 during this period. 70 the peak current value does not reach a threshold value corresponding to the current inductor current limit signal S 72, so that the comparator 56 does not control the voltage controlled oscillator 52 to the second clock CLK2, the frequency of the triangular wave signal S 522 increases the frequency Up to a frequency greater than the frequency of the first clock CLK1, the latch 55 generates a lower frequency pulse width modulation signal S 57 according to the first clock CLK1 and the reset signal S 54 output by the clock signal selector 53. The opening and closing state of the switch 40 is controlled by the pulse width modulation signal S 57 .
請參照圖3至圖5。圖3至圖5分別繪示出電流取樣電路的其他實施態樣。如圖3所示,電流取樣電路91乃是由電流感應線圈911及二極體912所組成,而此電流取樣電路91的耦接方式與電流取樣電路90的耦接方式不同。而如圖4所示,電流取樣電路92乃是以一電阻來實現。至於圖5所示的電流取樣電路93,其亦以一電阻來實現,而電流取樣電路93的耦接方式與電流取樣電路92的耦接方式不同。由於圖3至圖5皆已清楚繪示出各電流取樣電路的耦接方式,在此便不再贅述。 Please refer to FIG. 3 to FIG. 5. 3 to 5 illustrate other embodiments of the current sampling circuit, respectively. As shown in FIG. 3, the current sampling circuit 91 is composed of a current sensing coil 911 and a diode 912, and the current sampling circuit 91 is coupled to the current sampling circuit 90 in a different manner. As shown in FIG. 4, the current sampling circuit 92 is implemented by a resistor. As for the current sampling circuit 93 shown in FIG. 5, it is also implemented by a resistor, and the current sampling circuit 93 is coupled to the current sampling circuit 92 in a different manner. Since the coupling manners of the current sampling circuits are clearly illustrated in FIG. 3 to FIG. 5, details are not described herein again.
綜上所述,在本發明中,每當第一取樣訊號的大小達到電流上限訊號所對應的電感電流臨界值時,功因校正電路的比較器便控制壓控震盪器將第二時脈的頻率與三角波訊號的頻率提高至大於第一時脈的頻率,並控制壓控震盪器依第一取樣訊號達到電感電流臨界值的次數來遞增第二時脈與三角波訊號的頻率。因此,每當第一取樣訊號的大小達到電流上限訊號所對應的電感電流臨界值時,壓控震盪器的頻率便升高以適時地調整開關的切換頻率,進而使電感電流的振幅減小而改變電感電流的峰值,以致於電感電流的峰值低於電流上限值。藉由限制電感電流而使電感不容易飽和,進而得以使用較低額定的電感元件及功率開關。 In summary, in the present invention, whenever the size of the first sampling signal reaches the critical value of the inductor current corresponding to the current upper limit signal, the comparator of the power factor correcting circuit controls the voltage controlled oscillator to the second clock. The frequency and the frequency of the triangular wave signal are increased to be greater than the frequency of the first clock, and the voltage controlled oscillator is controlled to increase the frequency of the second clock and the triangular wave signal according to the number of times the first sampling signal reaches the critical value of the inductor current. Therefore, each time the size of the first sampling signal reaches the critical value of the inductor current corresponding to the current upper limit signal, the frequency of the voltage controlled oscillator is increased to adjust the switching frequency of the switch in a timely manner, thereby reducing the amplitude of the inductor current. The peak value of the inductor current is changed so that the peak value of the inductor current is lower than the current upper limit value. By limiting the inductor current, the inductor is not easily saturated, allowing the use of lower rated inductor components and power switches.
雖然本發明已以較佳實施例揭露如上,然其並非用以限定本發明,任何熟習此技藝者,在不脫離本發明的精神和範圍內,當可作些許的更動與潤飾,因此本發明的保護範圍當視後附的申請專利範圍所界定者為準。 While the invention has been described above by way of a preferred embodiment, it is not intended to limit the invention, and the invention may be modified and modified without departing from the spirit and scope of the invention. The scope of protection is subject to the definition of the scope of the patent application.
100‧‧‧交流-直流轉換器 100‧‧‧AC-DC converter
10‧‧‧橋式整流器 10‧‧‧Bridge rectifier
11‧‧‧正輸出端 11‧‧‧ positive output
12‧‧‧負輸出端 12‧‧‧negative output
20‧‧‧電感 20‧‧‧Inductance
30‧‧‧二極體 30‧‧‧ diode
40‧‧‧開關 40‧‧‧ switch
41‧‧‧第一端 41‧‧‧ first end
42‧‧‧第二端 42‧‧‧second end
43‧‧‧控制端 43‧‧‧Control terminal
50‧‧‧功因校正電路 50‧‧‧Power factor correction circuit
51‧‧‧時脈產生器 51‧‧‧ Clock Generator
52‧‧‧壓控震盪器 52‧‧‧Voltage-controlled oscillator
53‧‧‧時脈訊號選擇器 53‧‧‧clock signal selector
54‧‧‧重置訊號產生電路 54‧‧‧Reset signal generation circuit
542‧‧‧電壓誤差放大器 542‧‧‧Voltage error amplifier
544‧‧‧乘法器 544‧‧‧Multiplier
546‧‧‧電流誤差放大器 546‧‧‧ Current Error Amplifier
548‧‧‧脈寬調變比較器 548‧‧‧ Pulse width modulation comparator
55‧‧‧閂鎖器 55‧‧‧Latch
551、SET‧‧‧設置端 551, SET‧‧‧Setting end
552、RESET‧‧‧重置端 552, RESET‧‧‧ reset end
553、Q‧‧‧輸出端 553, Q‧‧‧ output
56‧‧‧比較器 56‧‧‧ comparator
60、549‧‧‧電容 60, 549‧‧‧ capacitor
80‧‧‧電壓取樣電路 80‧‧‧Voltage sampling circuit
90‧‧‧電流取樣電路 90‧‧‧ Current sampling circuit
901‧‧‧電流感應線圈 901‧‧‧current induction coil
902‧‧‧二極體 902‧‧‧ diode
903‧‧‧整流波形取樣電路 903‧‧‧Rected Waveform Sampling Circuit
AC‧‧‧交流電源 AC‧‧‧AC power supply
S1‧‧‧電流上限訊號 S 1 ‧‧‧ current limit signal
S2‧‧‧第一取樣訊號 S 2 ‧‧‧first sampling signal
S3‧‧‧第二取樣訊號 S 3 ‧‧‧Second sampling signal
S54‧‧‧重置訊號 S 54 ‧‧‧Reset signal
S522‧‧‧三角波訊號 S 522 ‧‧‧ triangle wave signal
S543‧‧‧第一誤差訊號 S 543 ‧‧‧First error signal
S545‧‧‧基準電流訊號 S 545 ‧‧‧reference current signal
S547‧‧‧第二誤差訊號 S 547 ‧‧‧second error signal
S57‧‧‧脈寬調變訊號 S 57 ‧‧‧ Pulse width modulation signal
CLK1‧‧‧第一時脈 CLK1‧‧‧ first clock
CLK2‧‧‧第二時脈 CLK2‧‧‧ second clock
VOUT‧‧‧輸出電壓 V OUT ‧‧‧ output voltage
VFB‧‧‧反饋電壓 V FB ‧‧‧ feedback voltage
VREF‧‧‧參考電壓 V REF ‧‧‧reference voltage
R1、R2、R3、R4‧‧‧電阻 R 1 , R 2 , R 3 , R 4 ‧‧‧ resistance
GND‧‧‧接地電位 GND‧‧‧ Ground potential
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