TWI425748B - A control circuit for a power converter - Google Patents
A control circuit for a power converter Download PDFInfo
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Description
本發明係有關於一種電源轉換器,特別是指一種電源轉換器之控制電路。The invention relates to a power converter, in particular to a control circuit of a power converter.
現今由於科技的進步,進而發展出許多電子產品,以因應民眾的需求,該些電子產品的功能越來越為強大,而帶給現今民眾在生活上許多便利。現今電子裝置大部分皆需要一電源轉換器,其接收一輸入電源,而依據輸入電源輸出一調整之輸出電源,以提供電子裝置所需的電源。Nowadays, due to the advancement of science and technology, many electronic products have been developed to meet the needs of the people. The functions of these electronic products are becoming more and more powerful, and bring convenience to the people today. Most of today's electronic devices require a power converter that receives an input power source and outputs an adjusted output power source based on the input power source to provide the power required by the electronic device.
請參閱第1圖,其為習用技術之電源轉換器的電路圖。如圖所示,習用之電源轉換器包含一變壓器T1 ,其具有一一次側繞組NP 與一二次側繞組NS ,一次側繞組NP 之一端耦接一輸入電壓VIN ,一次側繞組NP 之另一端耦接一開關Q1 ,開關Q1 透過一電阻RS 耦接於接地端,電阻RS 用於感測開關Q1 之一切換電流IP ,而產生一電流訊號VCS 。變壓器T1 之二次側繞組NS 的一端耦接一整流器DO 之一端,一電容CO 耦接於整流器DO 之另一端與二次側繞組NS 的另一端之間,電容CO 亦耦接於電源轉換器之輸出端,電源轉換器之輸出端用於提供一輸出電壓VO 。Please refer to FIG. 1 , which is a circuit diagram of a power converter of the prior art. As shown, the conventional power converter includes a transformer T 1 having a primary side winding N P and a secondary side winding N S , and one end of the primary side winding N P is coupled to an input voltage V IN , once The other end of the side winding N P is coupled to a switch Q 1 , the switch Q 1 is coupled to the ground through a resistor R S , and the resistor R S is used to sense a switching current I P of the switch Q 1 to generate a current signal. V CS . One end of the secondary winding N S of the transformer T 1 is coupled to one end of a rectifier D O , and a capacitor C O is coupled between the other end of the rectifier D O and the other end of the secondary winding N S , the capacitor C O Also coupled to the output of the power converter, the output of the power converter is used to provide an output voltage V O .
復參閱第1圖,習用之電源轉換器之控制電路包含一鋸齒波產生電路10,鋸齒波產生電路10包含一充放電電路,其包含一電阻RT 、一電容CT 、一開關115和一放電電流源117。電阻RT 之一端耦接一參考電壓VREF ,電容CT 耦接在接地端與電阻RT 之另一端之間,參考電壓VREF 用於對電容CT 進行充電。開關115之一端耦接電容CT ,開關115之另一端耦接放電電流源117的一端,放電電流源117的另一端耦接接地端,以用於對電容CT 進行放電。鋸齒波產生電路10藉由參考電壓VREF 與放電電流源117對電容CT 進行充放電,即可產生鋸齒波訊號VSAW 。Referring to FIG. 1 , the control circuit of the conventional power converter includes a sawtooth wave generating circuit 10 , and the sawtooth wave generating circuit 10 includes a charging and discharging circuit including a resistor R T , a capacitor C T , a switch 115 , and a A discharge current source 117. One end of the resistor R T is coupled to a reference voltage V REF , and the capacitor C T is coupled between the ground terminal and the other end of the resistor R T , and the reference voltage V REF is used to charge the capacitor C T . One end of the switch 115 is coupled to the capacitor C T , the other end of the switch 115 is coupled to one end of the discharge current source 117 , and the other end of the discharge current source 117 is coupled to the ground for discharging the capacitor C T . The sawtooth wave generating circuit 10 charges and discharges the capacitor C T by the reference voltage V REF and the discharge current source 117 to generate the sawtooth wave signal V SAW .
復參閱第1圖,鋸齒波產生電路10更包含一第一比較器121、一第二 比較器123與一正反器,正反器包含反及閘125與127。第一比較器121比較鋸齒波訊號VSAW 與一高臨界訊號VH ,而產生一第一比較訊號。第二比較器123比較鋸齒波訊號VSAW 與一低臨界訊號VL ,且產生一第二比較訊號。第一比較訊號與第二比較訊號分別傳送至正反器之反及閘125與127,而產生脈波訊號PLS,以用於控制開關115。Referring to FIG. 1, the sawtooth wave generating circuit 10 further includes a first comparator 121, a second comparator 123 and a flip-flop, and the flip-flop includes anti-gates 125 and 127. The first comparator 121 compares the sawtooth wave signal V SAW with a high threshold signal V H to generate a first comparison signal. The second comparator 123 compares the sawtooth wave signal V SAW with a low threshold signal V L and generates a second comparison signal. The first comparison signal and the second comparison signal are respectively transmitted to the opposite gates 125 and 127 of the flip-flop to generate a pulse signal PLS for controlling the switch 115.
復參閱第1圖,習用之電源轉換器之控制電路除了包含鋸齒波產生電路10之外,更包含比較器21、22、反或閘32、34及一正反器36,以用於控制電源轉換器之開關Q1 ,以控制電源轉換器之輸出電壓VO ,即用於控制電源轉換器之輸出功率。鋸齒波產生電路10所產生之鋸齒波訊號VSAW ,其用於控制電源轉換器之最大輸出功率。比較器21之負輸入端耦接至電容CT ,以接收鋸齒波訊號VSAW ,比較器21之正輸入端輸入一參考電壓以與鋸齒波訊號VSAW 進行比較,而用以輸出一控制訊號MDC。另一比較器22則用以比較回授訊號VFB 以及電流訊號VCS ,用以輸出一保護訊號VST 。反或閘32耦接至比較器21、22之輸出端,以接收控制訊號MDC與保護訊號VST 。正反器36之設定端S耦接至反或閘32之輸出端,正反器36之重置端R接收控制訊號MDC。反或閘34則根據正反器36之輸出端Q的輸出訊號以及控制訊號MDC,用以輸出一切換訊號VPWM ,而控制開關Q1 。Referring to FIG. 1, the control circuit of the conventional power converter includes, in addition to the sawtooth wave generating circuit 10, comparators 21, 22, anti-gates 32, 34 and a flip-flop 36 for controlling the power supply. The switch Q 1 of the converter controls the output voltage V O of the power converter, that is, the output power of the power converter. The sawtooth wave signal V SAW generated by the sawtooth wave generating circuit 10 is used to control the maximum output power of the power converter. The negative input terminal of the comparator 21 is coupled to the capacitor C T to receive the sawtooth wave signal V SAW , and the positive input terminal of the comparator 21 inputs a reference voltage It is compared with the sawtooth wave signal V SAW to output a control signal MDC. The other comparator 22 is configured to compare the feedback signal V FB and the current signal V CS for outputting a protection signal V ST . The inverse gate 32 is coupled to the outputs of the comparators 21, 22 to receive the control signal MDC and the protection signal V ST . The set terminal S of the flip-flop 36 is coupled to the output of the inverse OR gate 32, and the reset terminal R of the flip-flop 36 receives the control signal MDC. The inverse gate 34 is used to output a switching signal V PWM according to the output signal of the output terminal Q of the flip-flop 36 and the control signal MDC, and to control the switch Q 1 .
請參閱第2圖,其為習用之電源轉換器的電路圖之脈波示意圖。如圖所示,其中該切換訊號VPWM 之切換週期的最大導通時間是由控制訊號MDC所決定。習用之控制電路利用鋸齒波產生電路10所產生的鋸齒波訊號VSAW 與參考電壓進行比較,以產生控制訊號MDC,而控制切換訊號VPWM 之最大導通時間,即控制開關Q1 之最大導通時間,進而控制電源轉換器之最大輸出功率。然而,當高臨界訊號VH 、低臨界訊號VL 與參考電壓準位其中之一參數漂移時,控制訊號MDC之脈寬即會漂移,所以切換訊號VPWM 之切換週期將隨之漂移。此外,由於鋸齒波產生電路10容易受到干擾或者受其他因素影響,所以無法產生精確之鋸齒波訊號VSAW ,如此與參 考電壓進行比較後,而所產生之控制訊號MDC的脈寬即無法精確固定,如此切換訊號VPWM 之最大導通時間即會受到影響,如此即無法精確控制開關Q1 之最大導通時間,而無法精確控制電源轉換器之最大輸出功率。Please refer to FIG. 2, which is a schematic diagram of a pulse diagram of a circuit diagram of a conventional power converter. As shown in the figure, the maximum on-time of the switching period of the switching signal V PWM is determined by the control signal MDC. The conventional control circuit uses the sawtooth wave signal V SAW generated by the sawtooth wave generating circuit 10 and the reference voltage Compared to generate a control signal the MDC, to control the maximum on-time of the switching signal V PWM, i.e. the control of the switch Q 1 is turned on the maximum time, thereby controlling the maximum power output of the power converter. However, when one of the parameters of the high threshold signal V H , the low threshold signal V L and the reference voltage level drifts, the pulse width of the control signal MDC will drift, so the switching period of the switching signal V PWM will drift. In addition, since the sawtooth wave generating circuit 10 is susceptible to interference or other factors, accurate sawtooth wave signal V SAW cannot be generated, and thus the reference voltage After the comparison, the pulse width of the generated control signal MDC cannot be accurately fixed, so that the maximum on-time of the switching signal V PWM is affected, so that the maximum on-time of the switch Q 1 cannot be accurately controlled, and the precise control cannot be accurately controlled. The maximum output power of the power converter.
因此,本發明即針對上述問題而提出一種電源轉換器之控制電路,其可改善上述缺點,而精確控制電源轉換器之最大輸出功率,又可增加穩定性,以解決上述問題。Therefore, the present invention has been directed to a control circuit for a power converter that solves the above problems, which can improve the above disadvantages, and accurately control the maximum output power of the power converter, and can increase stability to solve the above problem.
本發明之主要目的,在於提供一種電源轉換器之控制電路,其藉由除頻器產生具固定脈寬之控制訊號,而精確控制電源轉換器之開關的最大導通時間,以達確實控制電源轉換器之最大輸出功率的目的。The main object of the present invention is to provide a control circuit for a power converter, which generates a control signal with a fixed pulse width by a frequency divider, and precisely controls the maximum on-time of the switch of the power converter to achieve a true control power conversion. The purpose of the maximum output power of the device.
本發明係有關於一種電源轉換器之控制電路,控制電路用於輸出一切換訊號以控制一電源轉換器之一開關,其包含有一震盪器與一除頻器,該震盪器用於產生一脈波訊號,並提供脈波訊號至除頻器,除頻器除頻脈波訊號而產生具有一固定脈寬之一控制訊號,切換訊號具有一切換週期,且切換週期之一最大導通時間受控於控制訊號之固定脈寬。本發明藉由除頻器所產生之控制訊號的固定脈寬,可確實控制切換訊號之最大導通時間,而可確實控制電源轉換器之最大輸出功率。The invention relates to a control circuit for a power converter, wherein the control circuit is configured to output a switching signal to control a switch of a power converter, comprising an oscillator and a frequency divider, wherein the oscillator is used to generate a pulse wave Signal, and providing a pulse signal to the frequency divider, the frequency divider removes the pulse signal to generate a control signal having a fixed pulse width, the switching signal has a switching period, and one of the switching periods is controlled by the maximum conduction time. The fixed pulse width of the control signal. The invention can surely control the maximum on-time of the switching signal by the fixed pulse width of the control signal generated by the frequency divider, and can surely control the maximum output power of the power converter.
茲為使 貴審查委員對本發明之技術特徵及所達成之功效更有進一步之瞭解與認識,謹佐以較佳之實施例圖及配合詳細之說明,說明如後: 請參閱第3圖,其為本發明之一較佳實施例之電源轉換器的電路圖。如圖所示,本發明之電源轉換器包含一變壓器T1 ,變壓器T1 從一次側轉移能量至二次側,以提供經調整之一輸出電壓VO 。變壓器T1 之一次側與二次側分別具有一一次側繞組NP 與一二次側繞組NS ,一次側繞組NP 之一端耦 接一輸入電壓VIN ,一次側繞組NP 之另一端耦接一開關Q1 ,開關Q1 串聯一感測元件,感測元件於本實施例中為一電阻RS ,開關Q1 之一端耦接電阻RS 之一端,電阻RS 之另一端耦接於接地端,電阻RS 用於感測開關Q1 之一切換電流IP ,而產生一電流訊號VCS 。上述之開關Q1 用於控制變壓器T1 ,其一較佳實施例可為一電晶體。變壓器T1 之二次側繞組NS 的一端耦接一整流器DO 之一端,整流器DO 之另一端與二次側繞組NS 的另一端之間耦接一電容CO ,電容CO 亦耦接於電源轉換器之輸出端,電源轉換器之輸出端用於提供輸出電壓VO 。For a better understanding and understanding of the technical features of the present invention and the efficacies achieved, please refer to the preferred embodiment and the detailed description, as follows: Please refer to Figure 3, which is A circuit diagram of a power converter in accordance with a preferred embodiment of the present invention. As shown, the power converter according to the present invention comprises a transformer T 1, T 1 of the transformer to transfer energy from the primary side to the secondary side, one to provide an adjusted output voltage V O. The primary side and the secondary side of the transformer T 1 respectively have a primary side winding N P and a secondary side winding N S , one end of the primary side winding N P is coupled to an input voltage V IN , and the primary side winding N P is another one end is coupled to a switch Q 1, the switch Q 1 in series a sensing element, the sensing element in the present embodiment is a resistor R S, switch Q one end of a coupling end of the resistor R S, the other end of the resistor R S of Coupled to the ground, the resistor R S is used to sense a switching current I P of the switch Q 1 to generate a current signal V CS . The above-mentioned switch Q 1 is used to control the transformer T 1 , and a preferred embodiment thereof may be a transistor. One end of the secondary winding N S of the transformer T 1 is coupled to one end of a rectifier D O , and the other end of the rectifier D O and the other end of the secondary winding N S are coupled to a capacitor C O , and the capacitor C O is also The output of the power converter is coupled to the output of the power converter to provide an output voltage V O .
復參閱第3圖,本發明之電源轉換器的控制電路包含一震盪器40與一除頻器50,以產生一控制訊號MDC,而用於產生一切換訊號VPWM ,以控制電源轉換器之開關Q1 ,而控制電源轉換器之輸出電壓VO ,即控制電源轉換器之輸出功率。震盪器40用於產生一脈波訊號PLS,除頻器50耦接震盪器40,其除頻脈波訊號PLS而產生具有一固定脈寬之控制訊號MDC,以用於產生切換訊號VPWM ,而控制開關Q1 之切換,即控制開關Q1 之導通與截止。本發明藉由除頻器50對震盪器40所產生之脈波訊號PLS進行除頻,如此可產生具有固定脈寬之控制訊號MDC,以藉由固定脈寬確實控制切換訊號VPWM 之一切換週期的一最大導通時間,而確實控制開關Q1 之最大導通時間,即確實控制電源轉換器之最大輸出功率。於本發明之一實施例中,控制訊號MDC之一導通時間等於控制訊號MDC之一截止時間,如此即可精確控制切換訊號VPWM 之最大導通時間等於切換訊號號VPWM 之切換週期的一截止時間,即控制開關Q1 之一最大導通時間等於開關Q1 之一截止時間。Referring to FIG. 3, the control circuit of the power converter of the present invention includes an oscillator 40 and a frequency divider 50 for generating a control signal MDC for generating a switching signal V PWM for controlling the power converter. The switch Q 1 controls the output voltage V O of the power converter, that is, controls the output power of the power converter. The oscillator 40 is configured to generate a pulse signal PLS, and the frequency divider 50 is coupled to the oscillator 40. The frequency divider signal PLS generates a control signal MDC having a fixed pulse width for generating the switching signal V PWM . controlling the switching of the switch Q 1, i.e. the control switch is turned on and off of Q 1. The frequency division signal PLS generated by the oscillator 40 is de-frequencyed by the frequency divider 50, so that the control signal MDC having a fixed pulse width can be generated to control the switching of the switching signal V PWM by the fixed pulse width. a maximum on time period, and surely control switch Q 1 of the maximum on time, i.e., does the control maximum output power of the power converter. One embodiment of the present invention, in the embodiment, one of the control pilot signal is equal to one of the control-time MDC MDC deadline signal, thus to accurately control the maximum on the switching signal V PWM on-time is equal to the switching period of the switching signal V PWM resolution of a cutoff time, i.e., one control switch Q 1 is equal to the maximum on time of the switch Q 1 is turned off one time.
復參閱第3圖,本發明之電源轉換器的控制電路更包含一保護電路,其包含有一比較器60,而分別接收一回授訊號VFB 以及電流訊號VCS ,用以比較回授訊號VFB 以及電流訊號VCS ,以輸出一保護訊號VST 。上述得知回授訊號VFB之方式,其可藉由一光耦合器或一回授電路耦接於變壓器T1 之一輔助繞組(圖中未示),以偵測電源轉換器之輸出訊號VO,而得知回授 訊號VFB,由於輔助繞組之電壓相關於電源轉換器之輸出電壓VO,因此,回授訊號VFB係關聯於輸出電壓VO。Referring to FIG. 3, the control circuit of the power converter of the present invention further includes a protection circuit including a comparator 60 for receiving a feedback signal V FB and a current signal V CS for comparing the feedback signal V. FB and current signal V CS to output a protection signal V ST . That the above-described embodiment of the feedback signal VFB, which may be an opto-coupler or by a return to one of a feedback circuit is coupled to an auxiliary winding of the transformer T (not shown) to detect the power converter output signal VO When the feedback signal VFB is known, since the voltage of the auxiliary winding is related to the output voltage VO of the power converter, the feedback signal VFB is associated with the output voltage VO.
承接上述,本發明之控制電路藉由一切換電路,而依據控制訊號MDC產生切換訊號VPWM 。切換電路包含有一第一邏輯閘72、一正反器74與一第二邏輯閘76,第一邏輯閘72與第二邏輯閘76於此實施例中為反或閘。反或閘72之兩輸入端分別耦接至比較器60之輸出端與除頻器50之輸出端,以接收保護訊號VST 與控制訊號MDC,而產生一設定訊號VSET 。正反器74之設定端S耦接至反或閘72之輸出端,以接收設定訊號VSET ,正反器74之重置端R耦接至除頻器50之輸出端而接收控制訊號MDC。反或閘76之兩輸入端則耦接至正反器74之輸出端Q與除頻器50之輸出端,而根據正反器74之一輸出訊號以及控制訊號MDC,用以輸出切換訊號VPWM 。切換訊號VPWM 即用於控制電源轉換器之開關Q1 ,以控制電源轉換器之輸出電壓VO ,即用於控制電源轉換器之輸出功率。In response to the above, the control circuit of the present invention generates the switching signal V PWM according to the control signal MDC by a switching circuit. The switching circuit includes a first logic gate 72, a flip-flop 74 and a second logic gate 76. The first logic gate 72 and the second logic gate 76 are inverted or gated in this embodiment. The two input terminals of the inverse gate 72 are respectively coupled to the output end of the comparator 60 and the output terminal of the frequency divider 50 to receive the protection signal V ST and the control signal MDC to generate a setting signal V SET . The set terminal S of the flip-flop 74 is coupled to the output of the inverse gate 72 to receive the set signal V SET , and the reset terminal R of the flip-flop 74 is coupled to the output of the frequency divider 50 to receive the control signal MDC. . The two input terminals of the inverse gate 76 are coupled to the output terminal Q of the flip-flop 74 and the output terminal of the frequency divider 50, and output a switching signal V according to one of the output signals of the flip-flop 74 and the control signal MDC. PWM . The switching signal V PWM is used to control the switch Q 1 of the power converter to control the output voltage V O of the power converter, that is, to control the output power of the power converter.
請參閱第4圖,其為本發明之一較佳實施例之震盪器與除頻器的電路圖。如圖所示,在本實施例中,該除頻器在本實施例是為一除四電路(然不以此為限,亦可為除二電路),由兩級的除二電路串聯組成,以依據脈波訊號PLS產生控制訊號MDC,且控制訊號MDC之週期是為脈波訊號PLS之偶數倍。震盪器40包含一充放電電路與一脈波訊號產生電路,充放電電路包含有一電阻RT 、一電容CT 、一放電開關415與一放電電流源417,以用於產生一鋸齒波訊號VSAW 。脈波訊號產生電路則包含有一第一比較器421、一第二比較器423與一正反器,正反器包括有反及閘425、427,脈波訊號產生電路用於依據鋸齒波訊號VSAW 而產生脈波訊號PLS。充放電電路之電阻RT 之一端耦接一參考電壓VREF ,電容CT 耦接在接地端與電阻RT 之另一端之間,參考電壓VREF 用於對電容CT 進行充電。放電開關415耦接在電容CT 與放電電流源417的一端之間,放電電流源417的另一端耦接到接地端,以用於對電容CT 進行放電。充放電電路藉由參考電壓VREF 與放電電流源417對電容CT 進行充放電,即可產生鋸齒波訊號VSAW 。Please refer to FIG. 4, which is a circuit diagram of an oscillator and a frequency divider according to a preferred embodiment of the present invention. As shown in the figure, in this embodiment, the frequency divider is a divide-by-four circuit in this embodiment (but not limited thereto, it may also be a divide-by-two circuit), and is composed of two stages of two divided circuits. The control signal MDC is generated according to the pulse signal PLS, and the period of the control signal MDC is an even multiple of the pulse signal PLS. The oscillator 40 includes a charge and discharge circuit and a pulse signal generating circuit. The charge and discharge circuit includes a resistor R T , a capacitor C T , a discharge switch 415 and a discharge current source 417 for generating a sawtooth signal V. SAW . The pulse signal generating circuit comprises a first comparator 421, a second comparator 423 and a flip-flop, the flip-flop includes a reverse gate 425, 427, and the pulse signal generating circuit is used for the sawtooth signal V. The SAW generates a pulse signal PLS. One end of the resistor R T of the charge and discharge circuit is coupled to a reference voltage V REF , and the capacitor C T is coupled between the ground terminal and the other end of the resistor R T , and the reference voltage V REF is used to charge the capacitor C T . The discharge switch 415 is coupled between the capacitor C T and one end of the discharge current source 417, and the other end of the discharge current source 417 is coupled to the ground for discharging the capacitor C T . The charge and discharge circuit charges and discharges the capacitor C T by the reference voltage V REF and the discharge current source 417 to generate the sawtooth wave signal V SAW .
復參閱第4圖,脈波訊號產生電路之第一比較器421之正輸入端與負輸入端分別接收一高臨界訊號VH 與鋸齒波訊號VSAW ,以比較鋸齒波訊號VSAW 與高臨界訊號VH ,而在輸出端產生一第一比較訊號。第二比較器423之正輸入端與負輸入端分別接收鋸齒波訊號VSAW 與一低臨界訊號VL ,以比較鋸齒波訊號VSAW 與低臨界訊號VL ,而在輸出端產生一第二比較訊號。第一比較訊號與第二比較訊號傳送至正反器,而產生脈波訊號PLS。第一比較器421與第二比較器423之輸出端分別耦接至第一反及閘425與第二反及閘427之第一輸入端,即第一反及閘425與第二反及閘427之第一輸入端分別接收第一比較訊號與第二比較訊號,第二反及閘427之輸出端耦接至第一反及閘425之第二輸入端,第一反及閘425之輸出端耦接至第二反及閘427之第二輸入端,並產生脈波訊號PLS,且用於控制放電開關415。Referring to FIG. 4, the positive input terminal and the negative input terminal of the first comparator 421 of the pulse wave signal generating circuit respectively receive a high threshold signal V H and a sawtooth wave signal V SAW to compare the sawtooth wave signal V SAW with a high threshold. Signal V H and a first comparison signal is generated at the output. The positive input terminal and the negative input terminal of the second comparator 423 receive the sawtooth wave signal V SAW and a low threshold signal V L respectively to compare the sawtooth wave signal V SAW with the low critical signal V L and generate a second at the output end. Compare signals. The first comparison signal and the second comparison signal are transmitted to the flip-flop to generate the pulse signal PLS. The output ends of the first comparator 421 and the second comparator 423 are respectively coupled to the first input terminals of the first anti-gate 425 and the second anti-gate 427, that is, the first anti-gate 425 and the second anti-gate The first input end of the 427 receives the first comparison signal and the second comparison signal respectively, and the output end of the second anti-gate 427 is coupled to the second input end of the first anti-gate 425, and the output of the first anti-gate 425 The terminal is coupled to the second input of the second anti-gate 427 and generates a pulse signal PLS for controlling the discharge switch 415.
復參閱第4圖,除頻器50包含一反相器51與正反器53、55。反相器51之輸入端接收脈波訊號PLS,以產生反相脈波訊號/PLS。正反器53與55相串聯,以依據脈波訊號PLS產生具固定脈寬之控制訊號MDC。正反器53之時脈輸入端ck耦接反相器51之輸出端,以接收反相脈波訊號/PLS,正反器53之輸入端D耦接至正反器53之反相輸出端QN,正反器53之輸出端Q耦接至正反器55之時脈輸入端ck,正反器55之輸入端D耦接至正反器55之反相輸出端QN,正反器55之輸出端Q輸出控制訊號MDC。此外,本發明之一較佳實施例,係可將震盪器與40與除頻器50整合為一控制晶片,其中震盪器40之電阻RT 與電容CT 並未設置於控制晶片內,而設置於控制晶片外。Referring to Fig. 4, the frequency divider 50 includes an inverter 51 and flip-flops 53, 55. The input of the inverter 51 receives the pulse signal PLS to generate an inverted pulse signal/PLS. The flip-flops 53 and 55 are connected in series to generate a control signal MDC having a fixed pulse width in accordance with the pulse signal PLS. The clock input terminal ck of the flip-flop 53 is coupled to the output terminal of the inverter 51 to receive the inverted pulse signal/PLS, and the input terminal D of the flip-flop 53 is coupled to the inverted output terminal of the flip-flop 53. QN, the output terminal Q of the flip-flop 53 is coupled to the clock input terminal ck of the flip-flop 55, and the input terminal D of the flip-flop 55 is coupled to the inverting output terminal QN of the flip-flop 55, and the flip-flop 55 The output terminal Q outputs a control signal MDC. In addition, in a preferred embodiment of the present invention, the oscillator and the frequency divider 50 can be integrated into a control chip, wherein the resistor R T and the capacitor C T of the oscillator 40 are not disposed in the control chip. Set outside the control chip.
請參閱第5圖,其為本發明之一較佳實施例之電源轉換器之電路圖的脈波示意圖。如圖所示,本發明藉由除頻器50(請參閱第3圖)所產生之控制訊號MDC具有固定之脈波寬度,於此實施例中控制訊號MDC之導通時間相等於截止時間,如此即可精確控制切換訊號VPWM 之切換週期的最大導通時間,即控制開關Q1 (請一併參閱第3圖)之最大導通時間,如此即可確實控制電源轉換器之最大輸出功率。此外,當保護電路之比較器60(請 一併參閱第3圖)比較電流訊號VCS 大於回授訊號VFB 時,即會產生低準位之保護訊號VST ,以截止切換訊號VPWM 。Please refer to FIG. 5, which is a schematic diagram of a pulse diagram of a circuit diagram of a power converter according to a preferred embodiment of the present invention. As shown in the figure, the control signal MDC generated by the frequency divider 50 (see FIG. 3) has a fixed pulse width. In this embodiment, the on-time of the control signal MDC is equal to the cut-off time. The maximum on-time of the switching period of the switching signal V PWM can be precisely controlled, that is, the maximum on-time of the control switch Q 1 (please refer to FIG. 3 together), so that the maximum output power of the power converter can be surely controlled. In addition, when the comparator 60 of the protection circuit (please refer to FIG. 3) compares the current signal V CS with the feedback signal V FB , a low level protection signal V ST is generated to turn off the switching signal V PWM .
綜上所述,本發明電源轉換器之控制電路係用於產生切換訊號,以控制電源轉換器之開關,而控制電源轉換器之輸出功率。控制電路包含震盪器與除頻器,震盪器用於產生脈波訊號並傳送至除頻器,除頻器除頻脈波訊號而產生具固定脈寬之控制訊號,以確實控制切換訊號之切換週期的最大導通時間,以精確控制開關之最大導通時間。當溫度或製程變異,雖會造成頻率的漂移,但除頻後的脈波週期是絕對穩定,進而可確實控制電源轉換器之最大輸出功率。In summary, the control circuit of the power converter of the present invention is used to generate a switching signal to control the switching of the power converter and control the output power of the power converter. The control circuit includes an oscillator and a frequency divider, and the oscillator is configured to generate a pulse signal and transmit the pulse signal to the frequency divider, and the frequency divider removes the pulse signal to generate a control signal with a fixed pulse width to surely control the switching period of the switching signal. Maximum on-time to precisely control the maximum on-time of the switch. When the temperature or process variation, although the frequency drift, but the pulse cycle after the frequency is absolutely stable, and thus can control the maximum output power of the power converter.
故本發明實為一具有新穎性、進步性及可供產業上利用者,應符合我國專利法專利申請要件無疑,爰依法提出發明專利申請,祈 鈞局早日賜准專利,至感為禱。Therefore, the present invention is a novelty, progressive and available for industrial use. It should be in accordance with the requirements of patent applications for patent law in China. It is undoubtedly to file an invention patent application according to law, and the Prayer Council will grant patents as soon as possible.
惟以上所述者,僅為本發明一較佳實施例而已,並非用來限定本發明實施之範圍,故舉凡依本發明申請專利範圍所述之形狀、構造、特徵及精神所為之均等變化與修飾,均應包括於本發明之申請專利範圍內。However, the above description is only a preferred embodiment of the present invention, and is not intended to limit the scope of the present invention, so that the shapes, structures, features, and spirits described in the claims of the present invention are equally changed. Modifications are intended to be included in the scope of the patent application of the present invention.
10‧‧‧鋸齒波產生電路10‧‧‧Sawtooth generation circuit
115‧‧‧開關115‧‧‧ switch
117‧‧‧放電電流源117‧‧‧Discharge current source
121‧‧‧第一比較器121‧‧‧First comparator
123‧‧‧第二比較器123‧‧‧Second comparator
125‧‧‧反及閘125‧‧‧Anti-gate
127‧‧‧反及閘127‧‧‧Anti-gate
21‧‧‧比較器21‧‧‧ Comparator
22‧‧‧比較器22‧‧‧ Comparator
32‧‧‧反或閘32‧‧‧Anti-gate
34‧‧‧反或閘34‧‧‧Anti-gate
36‧‧‧正反器36‧‧‧Factor
40‧‧‧震盪器40‧‧‧ oscillator
415‧‧‧放電開關415‧‧‧discharge switch
417‧‧‧放電電流源417‧‧‧Discharge current source
421‧‧‧第一比較器421‧‧‧First comparator
423‧‧‧第二比較器423‧‧‧Second comparator
425‧‧‧反及閘425‧‧‧Anti-gate
427‧‧‧反及閘427‧‧‧Anti-gate
50‧‧‧除頻器50‧‧‧Delephone
51‧‧‧反相器51‧‧‧Inverter
53‧‧‧正反器53‧‧‧Factor
55‧‧‧正反器55‧‧‧Factor
60‧‧‧比較器60‧‧‧ comparator
72‧‧‧反或閘72‧‧‧Anti-gate
74‧‧‧正反器74‧‧‧Factor
76‧‧‧反或閘76‧‧‧Anti-gate
ck‧‧‧時脈輸入端Ck‧‧‧clock input
CO ‧‧‧電容C O ‧‧‧ capacitor
CT ‧‧‧電容C T ‧‧‧ capacitor
DO ‧‧‧整流器D O ‧‧‧Rectifier
IP ‧‧‧切換電流I P ‧‧‧Switching current
MDC‧‧‧控制訊號MDC‧‧‧ control signal
NP ‧‧‧一次側繞組N P ‧‧‧ primary winding
NS ‧‧‧二次側繞組N S ‧‧‧secondary winding
PLS‧‧‧脈波訊號PLS‧‧‧ pulse signal
/PLS‧‧‧反相脈波訊號/PLS‧‧‧Reverse pulse signal
Q1 ‧‧‧開關Q 1 ‧‧‧Switch
RS ‧‧‧電阻R S ‧‧‧resistance
RT ‧‧‧電阻R T ‧‧‧resistance
T1 ‧‧‧變壓器T 1 ‧‧‧Transformer
VCS ‧‧‧電流訊號V CS ‧‧‧current signal
VFB ‧‧‧回授訊號V FB ‧‧‧Response signal
VO ‧‧‧輸出電壓V O ‧‧‧Output voltage
VPWM ‧‧‧切換訊號V PWM ‧‧‧Switching signal
VREF ‧‧‧參考電壓V REF ‧‧‧reference voltage
VSAW ‧‧‧鋸齒波訊號V SAW ‧‧‧Sawtooth Signal
VST ‧‧‧保護訊號V ST ‧‧‧protection signal
VSET ‧‧‧設定訊號V SET ‧‧‧ setting signal
VH ‧‧‧高臨界訊號V H ‧‧‧High threshold signal
VIN ‧‧‧輸入電壓V IN ‧‧‧ input voltage
VL ‧‧‧低臨界訊號V L ‧‧‧ low threshold signal
第1圖係習用之電源轉換器的電路圖;第2圖係習用之電源轉換器之電路圖的脈波示意圖;第3圖係本發明之一較佳實施例之電源轉換器的電路圖;第4圖係本發明之一較佳實施例之震盪器與除頻器的電路圖;及第5圖係本發明之一較佳實施例之電源轉換器之電路圖的脈波示意圖。1 is a circuit diagram of a conventional power converter; FIG. 2 is a schematic diagram of a pulse diagram of a circuit diagram of a conventional power converter; and FIG. 3 is a circuit diagram of a power converter according to a preferred embodiment of the present invention; BRIEF DESCRIPTION OF THE DRAWINGS FIG. 5 is a circuit diagram of a circuit diagram of a power converter according to a preferred embodiment of the present invention; and FIG. 5 is a schematic diagram of a pulse diagram of a circuit diagram of a power converter according to a preferred embodiment of the present invention.
40‧‧‧震盪器40‧‧‧ oscillator
50‧‧‧除頻器50‧‧‧Delephone
60‧‧‧比較器60‧‧‧ comparator
72‧‧‧反或閘72‧‧‧Anti-gate
74‧‧‧正反器74‧‧‧Factor
76‧‧‧反或閘76‧‧‧Anti-gate
CO ‧‧‧電容C O ‧‧‧ capacitor
DO ‧‧‧整流器D O ‧‧‧Rectifier
IP ‧‧‧切換電流I P ‧‧‧Switching current
MDC‧‧‧控制訊號MDC‧‧‧ control signal
NP ‧‧‧一次側繞組N P ‧‧‧ primary winding
NS ‧‧‧二次側繞組N S ‧‧‧secondary winding
PLS‧‧‧脈波訊號PLS‧‧‧ pulse signal
Q1 ‧‧‧開關Q 1 ‧‧‧Switch
RS ‧‧‧電阻R S ‧‧‧resistance
T1 ‧‧‧變壓器T 1 ‧‧‧Transformer
VCS ‧‧‧電流訊號V CS ‧‧‧current signal
VFB ‧‧‧回授訊號V FB ‧‧‧Response signal
VIN ‧‧‧輸入電壓V IN ‧‧‧ input voltage
VO ‧‧‧輸出電壓V O ‧‧‧Output voltage
VPWM ‧‧‧切換訊號V PWM ‧‧‧Switching signal
VST ‧‧‧保護訊號V ST ‧‧‧protection signal
VSET ‧‧‧設定訊號V SET ‧‧‧ setting signal
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TWI230512B (en) * | 2003-08-15 | 2005-04-01 | Integrated Sys Solution Corp | Frequency converter circuit of dual frequency wireless network |
US7433210B2 (en) * | 2003-10-10 | 2008-10-07 | Thomson Licensing | Switched-mode power supply comprising an adjustable oscillator |
US7116565B1 (en) * | 2005-08-24 | 2006-10-03 | System General Corp. | Over-power protection apparatus for self-excited power converter |
US7342812B2 (en) * | 2006-07-07 | 2008-03-11 | Cambridge Semiconductor Limited | Switch mode power supply systems |
TW200820567A (en) * | 2006-08-07 | 2008-05-01 | Linear Techn Inc | Regulator for isolated flyback power supply using primary side sensing |
TW200816609A (en) * | 2006-09-22 | 2008-04-01 | Richtek Technology Corp | Switching regulator and control circuit and method therefor |
TW200838106A (en) * | 2007-03-03 | 2008-09-16 | Richtek Technology Corp | Method and circuit for reducing switching ringing in switching regulator |
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