TWI401905B - Multiple Input Multiple Output Detection Method and Detector - Google Patents
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本發明是有關於一種偵測器及其偵測方法,特別是指一種多輸入多輸出偵測器及其偵測方法。The invention relates to a detector and a detection method thereof, in particular to a multi-input multi-output detector and a detection method thereof.
多輸入多輸出(multiple-input multiple-output,MIMO)技術已廣泛地納入各種無線通訊標準,以提高頻譜效率。在多輸入多輸出系統中,傳送端將資料切割成多數字元流(symbol stream),並利用多數天線在相同時間及相同頻段分別將這些字元流傳送出去;接收端利用多數天線接收這些字元流的加總,並將這些字元流分開,以得到傳送端原先所傳送的字元。目前公認基於最大概似偵測(maximum likelihood detection,MLD)的接收端具有最佳效能(即錯誤率最低),但其計算複雜度卻非常高。2002年Kim等人提出結合QR分解(QR decomposition,QRD)及M演算法(M algorithm)的偵測技術(以下稱為QRD-M偵測),可以透過樹狀搜尋(tree search),找出最大概似的近似解,在降低計算複雜度的同時,仍然保有最大概似偵測的最佳效能。Multiple-input multiple-output (MIMO) technology has been widely incorporated into various wireless communication standards to improve spectral efficiency. In a multiple-input multiple-output system, the transmitting end cuts the data into a multi-symbol stream, and uses a plurality of antennas to respectively transmit the stream of characters at the same time and in the same frequency band; the receiving end receives the words by using a plurality of antennas. The sum of the stream flows and separates the stream of characters to obtain the characters originally transmitted by the transmitting end. It is currently recognized that the receiver based on the most likely panoramic detection (MLD) has the best performance (ie, the lowest error rate), but its computational complexity is very high. In 2002, Kim et al. proposed a combination of QR decomposition (QRD) and M algorithm (hereinafter referred to as QRD-M detection), which can be found through tree search. The most approximate approximation solution, while reducing the computational complexity, still retains the best performance that is most likely to be detected.
在一具有N t
個傳送天線及N r
個接收天線的多輸入多輸出系統中,假設傳送天線及接收天線之間的通道是一平坦衰減通道(flat fading channel),則傳送天線所傳送的字元及接收天線所收到的信號之間的關係可表示為:
藉由QR分解,通道矩陣H
可表示為H=QR
,其中,Q
是一大小為Nr
×Nt
且具有正交行的單一矩陣(unitary matrix)(滿足Q H Q=I
,上標 H
表示共軛複數轉置運算);R
是一大小為Nt
×Nt
且對角元素為實數的上三角矩陣。將單一矩陣的共軛複數轉置矩陣Q H
乘以接收信號向量y
可得一經處理的接收信號向量z=Q H y=Rx+w
,或詳述為:
參閱圖1,如果多輸入多輸出系統所使用的星座圖包括|C |個星座點,則可根據以下方式定義一具有N t +1個階層(即深度為N t )的樹狀圖:從位在第0階層的樹根延伸|C |條分枝(branch)到下一階層,然後對於到達下一階層的各個路徑(path)重覆延伸的動作,直到第N t 階層。因此,到達第i 階層(i =1,…,N t )的路徑之數目為|C | t ,且對於這些路徑中的每一個而言,其第j 條(j =0,…,|C |-1)延伸到下一階層的分枝代表可能的傳送字元為星座圖中的第j 個星座點c j 。Referring to FIG. 1, if the constellation used by the MIMO system includes | C | constellation points, a tree diagram having N t +1 levels (ie, depth N t ) can be defined as follows: in the 0th hierarchy roots extending | C | article M. (Branch) to the next class, then for each arrival path (path) extending next repeated operation class, class until N t. Therefore, the number of paths to the i-th level ( i = 1, ..., N t ) is | C | t , and for each of these paths, the jth ( j =0,...,| C |-1) Branches extending to the next level represent possible transfer characters Is the jth constellation point c j in the constellation diagram.
到達第i 階層的每一條路徑具有i 段分枝,且代表一可能的傳送字元組。因此,整個樹狀圖總共有條具有N t 段分枝的路徑,每一條路徑代表一可能的傳送字元向量x ,且此條路徑恰好分別代表傳送字元向量x 的種可能。例如:圖1是根據一具有三傳送天線及三接收天線且使用BPSK調變的多輸入多輸出系統所形成的樹狀圖,其中,粗線路徑代表可能的傳送字元向量x 為 {x 3 =-1,x 2 =1,x 1 =1}。Each path to the i-th level has i- segment branches and represents a possible transport byte . Therefore, the entire tree diagram has a total Strips with N t segment branches, each path representing a possible transfer character vector x , and this The strip paths exactly represent the transfer character vector x , respectively. Kind of possibility. For example, FIG. 1 is a tree diagram formed according to a multiple input multiple output system having three transmit antennas and three receive antennas and using BPSK modulation, wherein the thick line path represents a possible transfer character vector x is { x 3 =-1, x 2 =1, x 1 =1}.
在樹狀圖中,對於到達第i
階層(i
=1,…,N t
)的任一路徑而言,其狀態(state)定義為此路徑所代表的傳送字元組。對於樹根而言,其第j
條(j
=0,…,|C
|-1)延伸到下一階層的分枝(代表星座圖中的第j
個星座點c j
)之分枝長(branch metric,BM)定義為:
根據以上定義,式(4)中的第1項對應到樹狀圖中樹根延伸到下一階層的分枝之分枝長,式(4)中的第i 項(i =2,…,N t )對應到樹狀圖中到達第i -1階層的路徑延伸到下一階層的分枝之分枝長。顯然,任一條具有N t 段分支的路徑之路徑長為此路徑所代表的傳送字元向量x 之成本。因此,透過樹狀搜尋來找出具有N t 段分支的路徑中路徑長最短的一者,即可得到最大概似的解。According to the above definition, the first term in the formula (4) corresponds to the branch length of the branch in the tree diagram extending to the next level, and the i-th term in the formula (4) ( i = 2, ..., N t ) corresponds to the branch length of the branch that reaches the i - th level in the tree diagram and extends to the branch of the next level. Obviously, the path of any path with a N t segment branch is the cost of the transfer character vector x represented by this path. Therefore, through the tree search to find the one with the shortest path length in the path with the N t segment branch, the most approximate solution can be obtained. .
V.M演算法V.M algorithm
由於上述樹狀搜尋需計算條路徑之路徑長,當傳輸天線的數目N t 及星座圖所包括的星座點之數目|C |增加時,會使樹狀圖跟著變龐大,進而使所需計算的分支長增加,這會提高計算複雜度。為了降低計算複雜度,藉由M演算法,在樹狀圖中的第i 階層(i =1,…,N t -1),只保留M i 條最佳路徑(即M i 條路徑長最短的路徑),以各自延伸|C |條分枝到下一階層,而刪除其餘路徑,以減少所需計算的分支長。這些保留下來的路徑稱為殘存路徑(survivor path)。樹狀圖中每一階層的M i 可根據相對應的通道條件及路徑長適當地調整(此即所謂的適應性M演算法),當通道條件好時,可以調低M i ,以降低計算複雜度。Because the above tree search needs to be calculated The path of the strip path is long. When the number of transmission antennas N t and the number of constellation points included in the constellation diagram | C | increase, the tree diagram will become larger, and thus the branch length of the required calculation will increase, which will increase. Computational complexity. In order to reduce the computational complexity, by the M algorithm, in the i-th hierarchy ( i =1,..., N t -1) in the tree diagram, only the optimal path of M i is retained (ie, the path length of the M i path is the shortest) path), each extend to | C | article branches to the next class, while the remaining paths deleted to reduce the branch length calculations required. These reserved paths are called survivor paths. The M i of each level in the tree diagram can be adjusted according to the corresponding channel conditions and path length (this is called the adaptive M algorithm). When the channel conditions are good, the M i can be lowered to reduce the calculation. the complexity.
VI.QRD-M演算法之改進Improvement of VI.QRD-M algorithm
藉由QRD-M演算法,在M i 條殘存路徑各自延伸|C |條分枝到下一階層時,仍需計算M i |C |條分枝之分枝長,以從M i |C |條路徑中保留M i +1 條最佳路徑。Higuchi等人在IEEE GLOBECOM 2004第2480~2486頁”Adaptive Selection of Surviving Symbol Replica Candidates Based on Maximum Reliability in QRM-MLD for OFCDM MIMO Multiplexing”論 文中提出一種改進方法,在M i 條殘存路徑各自延伸|C |條分枝到下一階層時,利用多重象限偵測(multiple quadrant detection)來對|C |條分枝排定等級,並據此計算M i +1 條分枝之分枝長(對應到M i |C |條路徑中欲保留下來的M i +1 條最佳路徑),可以減少QRD-M演算法所需計算的分枝長。然而,多重象限偵測只適用於棋盤式排列的星座圖,例如:16-QAM星座圖,因此,此改進方法不適用於使用M-PSK(M>4)調變的多輸入多輸出系統。With the QRD-M algorithm, when the M i residual paths extend | C | branches to the next level, the branch length of the M i | C | branches still needs to be calculated to get from M i | C | The best path of M i +1 is reserved in the path. Higuchi et al. proposed an improved method in the IEEE GLOBECOM 2004 pages 2480~2486 "Adaptive Selection of Surviving Symbol Replica Candidates Based on Maximum Reliability in QRM-MLD for OFCDM MIMO Multiplexing", each of which extends in the M i residual path | C | When branching to the next level, multiple quadrant detection is used to rank | C | branches, and the branch length of M i +1 branches is calculated accordingly (corresponding to M i | C | M i +1 best path to be preserved in the path), which can reduce the branch length required for the QRD-M algorithm. However, multi-quad detection is only applicable to checkerboard constellations, such as the 16-QAM constellation. Therefore, this improved method is not suitable for multi-input multi-output systems using M-PSK (M>4) modulation.
Nagayama等人在IEEE VTC-2006 Fall”A Proposal of QRM-MLD for Reduced Complexity of MLD to detect MIMO signals in Fading Environment”論文中提出另一種改進方法,在M i 條殘存路徑延伸時,利用象限偵測使各條路徑只延伸|C | α (<|C |)條分枝到下一階層,並計算M i |C | α 條分枝之分枝長,以從M i |C | α 條路徑中保留M i +1 條最佳路徑,這可以減少QRD-M演算法所需計算的分枝長。然而,此篇論文中的|C | α 及M i 均為固定的常數。如果想要達到接近最大概似偵測的效能,則必須根據最差的通道條件來決定|C | α 及M i 。但據此決定的|C | α 及M i 通常不小。因此,計算複雜度的降低程度將非常有限。Nagayama et al. proposed another improvement method in the IEEE VTC-2006 Fall "A Proposal of QRM-MLD for Reduced Complexity of MLD to detect MIMO signals in Fading Environment", which uses quadrant detection when the surviving path of the M i is extended. Let each path extend only | C | α (<| C |) branches to the next level, and calculate the branch length of the M i | C | α branches to get from the M i | C | α path The M i +1 best path is preserved, which reduces the branch length required for the QRD-M algorithm. However, | C | α and M i in this paper are fixed constants. If you want to achieve near-most probable performance, you must decide | C | α and M i based on the worst channel conditions. However, according to this decision | C | α and M i are usually not small. Therefore, the degree of reduction in computational complexity will be very limited.
因此,本發明之目的即在提供一種多輸入多輸出偵測方法,可以與多種調變技術配合,且其計算複雜度低。Therefore, the object of the present invention is to provide a multi-input and multi-output detection method, which can be combined with various modulation techniques, and has low computational complexity.
於是,本發明多輸入多輸出偵測方法包含適用於在一利用QR分解的多輸入多輸出系統中進行樹狀搜尋,該多輸 入多輸出系統包括一多輸入多輸出偵測器,該多輸入多輸出偵測器包括一通道估測器、一QR分解單元、一轉換單元及一偵測單元,該通道估測器根據一接收信號向量進行通道估測,以得到一通道矩陣,該QR分解單元對該通道矩陣進行通道分解,以得到一單一矩陣及一上三角矩陣,該轉換單元根據該單一矩陣,將該單一矩陣的共軛複數轉置矩陣乘以該接收信號向量,以得到一經處理的接收信號向量,該多輸入多輸出偵測方法由該偵測單元執行,且包含以下步驟:(A)根據該上三角矩陣,對於到達一目前階層的每一路徑,進行以下子步驟:(A1)對於該目前階層,根據該經處理的接收信號向量中相對應的接收信號,計算一經移除前面階層干擾的去干擾接收信號;及(A2)對於由一星座圖分割成的一第一目標數目之子集合中的每一個進行:找出該子集合中距離該去干擾接收信號最近的一星座點,並從該路徑延伸一代表該星座點的分枝到下一階層,且計算該分枝的分枝長及一相對應的路徑之路徑長。Therefore, the MIMO detection method of the present invention comprises a tree search for multi-input and multi-output systems using QR decomposition, the multi-transmission The multi-input multi-output detector includes a channel estimator, a QR decomposition unit, a conversion unit and a detection unit, and the channel estimator is based on a Receiving a signal vector for channel estimation to obtain a channel matrix, the QR decomposition unit performing channel decomposition on the channel matrix to obtain a single matrix and an upper triangular matrix, the conversion unit according to the single matrix, the single matrix The conjugate complex transposed matrix is multiplied by the received signal vector to obtain a processed received signal vector, and the MIMO detection method is performed by the detecting unit, and includes the following steps: (A) according to the upper triangular matrix For each path arriving at a current level, the following sub-steps are performed: (A1) for the current level, based on the corresponding received signal in the processed received signal vector, a de-interference reception with the removal of the previous level interference is calculated. a signal; and (A2) for each of a subset of a first target number segmented by a constellation: finding the distance in the subset Scrambling nearest constellation point receives a signal, and a representative of the path extending from the branching point in the constellation to the next hierarchy, and calculates the path length of the branch, and a branching path corresponding long.
而本發明之另一目的即在提供一種多輸入多輸出偵測器,可以與多種調變技術配合,且其計算複雜度低。Another object of the present invention is to provide a MIMO multi-output detector that can be combined with a variety of modulation techniques and has a low computational complexity.
於是,本發明多輸入多輸出偵測器適用於在一利用QR分解的多輸入多輸出系統中進行樹狀搜尋,且包含一通道估測器、一QR分解單元、一轉換單元及一偵測單元。該通 道估測器根據一接收信號向量進行通道估測,以得到一通道矩陣。該QR分解單元對該通道矩陣進行通道分解,以得到一單一矩陣及一上三角矩陣。該轉換單元根據該單一矩陣,將該單一矩陣的共軛複數轉置矩陣乘以該接收信號向量,以得到一經處理的接收信號向量。該偵測單元根據該上三角矩陣,對於到達一目前階層的每一路徑,進行以下動作:對於該目前階層,根據該經處理的接收信號向量中相對應的接收信號,計算一經移除前面階層干擾的去干擾接收信號;及對於由一星座圖分割成的一第一目標數目之子集合中的每一個進行:找出該子集合中距離該去干擾接收信號最近的一星座點,並從該路徑延伸一代表該星座點的分枝到下一階層,且計算該分枝的分枝長及一相對應的路徑之路徑長。Therefore, the multiple input multiple output detector of the present invention is suitable for tree search in a multiple input multiple output system using QR decomposition, and includes a channel estimator, a QR decomposition unit, a conversion unit and a detection. unit. The pass The channel estimator performs channel estimation based on a received signal vector to obtain a channel matrix. The QR decomposition unit performs channel decomposition on the channel matrix to obtain a single matrix and an upper triangular matrix. The conversion unit multiplies the conjugate complex transposed matrix of the single matrix by the received signal vector according to the single matrix to obtain a processed received signal vector. The detecting unit performs, according to the upper triangular matrix, for each path that reaches a current level, for the current level, calculating the removed front layer according to the corresponding received signal in the processed received signal vector. Disturbing the interference to receive the signal; and performing, for each of a subset of the first target number divided by a constellation: finding a constellation point in the subset that is closest to the de-interfering received signal, and from the The path extension 1 represents the branch of the constellation point to the next level, and calculates the branch length of the branch and the path length of a corresponding path.
有關本發明之前述及其他技術內容、特點與功效,在以下配合參考圖式之一個較佳實施例的詳細說明中,將可清楚地呈現。The foregoing and other technical aspects, features and advantages of the present invention will be apparent from the following description of the preferred embodiments.
參閱圖2,本發明多輸入多輸出偵測器之較佳實施例適用於在一基於QR分解的多輸入多輸出系統中進行樹狀搜尋,且透過Nr 個接收天線25接收來自N t 個傳送天線(圖未示)的信號,以得到一接收信號向量y 。Referring to FIG. 2, a preferred embodiment of the multiple input multiple output detector of the present invention is suitable for performing tree search in a QR input based multiple input multiple output system, and receiving N t via N r receiving antennas 25. A signal of an antenna (not shown) is transmitted to obtain a received signal vector y .
本實施例多輸入多輸出偵測器包含一通道估測器21、 一QR分解單元22、一轉換單元23及一偵測單元24。通道估測器21根據接收信號向量y 進行通道估測,以得到一通道矩陣H 。QR分解單元22對通道矩陣H 進行QR分解,以得到一單一矩陣Q 及一上三角矩陣R ,且H =QR 。轉換單元23根據單一矩陣Q ,將單一矩陣的共軛複數轉置矩陣Q H 乘以接收信號向量y ,以得到一經處理的接收信號向量z ,因此,z =Q H y ,或詳述為式(2)。The multi-input multi-output detector of the embodiment comprises a channel estimator 21, a QR decomposition unit 22, a conversion unit 23 and a detection unit 24. The channel estimator 21 performs channel estimation based on the received signal vector y to obtain a channel matrix H. The QR decomposition unit 22 performs QR decomposition on the channel matrix H to obtain a single matrix Q and an upper triangular matrix R , and H = QR . The converting unit 23 multiplies the conjugate complex transposed matrix Q H of the single matrix by the received signal vector y according to the single matrix Q to obtain a processed received signal vector z , and therefore, z = Q H y , or is detailed as (2).
參閱圖3與圖4,偵測單元24所使用的多輸入多輸出偵測方法包含以下步驟:步驟31是對於第0階層,根據相對應的通道條件決定一包括|C |個星座點之星座圖分割成的子集合之一第一目標數目S 1 (1 S 1 |C |),且根據第一目標數目S 1 分割星座圖(詳細決定方式及分割方式留待整個方法介紹完再說明)。Referring to FIG. 3 and FIG. 4, the multiple input multiple output detection method used by the detecting unit 24 includes the following steps: Step 31 is to determine, for the 0th layer, a constellation including | C | constellation points according to corresponding channel conditions. One of the subsets into which the graph is divided into the first target number S 1 (1 S 1 | C |), and the constellation map is divided according to the first target number S 1 (the detailed decision mode and the split mode are left to be explained after the entire method is introduced).
步驟32是根據上三角矩陣R ,對於位在第0階層的樹根進行以下子步驟:子步驟321是對於在步驟31中分割成的S 1 個子集合中的每一個進行以下子步驟:子步驟3211是找出子集合中距離接收信號最近的一星座點(詳細尋找方式留待整個方法介紹完再說明)。Step 32 is based on the upper triangular matrix R , and performs the following substeps for the root of the tree at the 0th level: substep 321 is to perform the following substeps for each of the S 1 subsets divided in step 31: substep 3211 is to find the distance received signal in the subset The nearest constellation point (The detailed search method is left to be explained after the whole method is introduced).
子步驟3212是從樹根延伸一代表星座點的分枝到第1階層,且計算分枝的分枝長及一相對應的路徑(代表一傳送字元組)之路徑長,計算方式如下所示:
步驟33是對於第0階層,根據相對應的通道條件及路徑長,決定在步驟32中延伸到第1階層的S 1 條路徑中要保留下來的路徑之一第二目標數目M 1 (1 M 1 S 1 )。Step 33 is to determine, for the 0th level, one of the paths to be retained in the S1 path extending to the first level in step 32 according to the corresponding channel condition and path length, and the second target number M 1 (1) M 1 S 1 ).
步驟34是對於在步驟32中延伸到第1階層的S 1 條路徑,保留M 1 條最短路徑而刪除其餘路徑。Step 34 is to delete the remaining paths by retaining M 1 shortest paths for the S 1 paths extending to the first level in step 32.
在步驟33及步驟34中,可以利用現有的各種適應性M演算法來決定第二目標數目M 1 及保留M 1 條最短路徑,此處將不多加說明。In step 33 and step 34, the existing plurality of adaptive M algorithms can be used to determine the second target number M 1 and retain the M 1 shortest path, which will not be described here.
步驟41是設定i =2。Step 41 is to set i = 2.
步驟42是對於第i -1階層(即目前階層),根據相對應的通道條件決定星座圖分割成的子集合之第一目標數目S i (1 S i |C |),且根據第一目標數目S i 分割星座圖(詳細決定方式及分割方式留待整個方法介紹完再說明)。Step 42 is to determine, for the i - th level (ie, the current level), the first target number S i (1) of the subset into which the constellation is divided according to the corresponding channel condition. S i | C |), and the constellation map is divided according to the first target number S i (the detailed decision mode and the split mode are left to be explained after the entire method is introduced).
步驟43是對於到達第i
-1階層的M i
-1
條路徑中的每一個(代表一傳送字元組)進行以下子步驟:子步驟431是對於第i
-1階層,根據經處理的接收信號向量z
中相對應的一者,計算一經移除前面階層干擾的去干擾接收信號,計算方式如下所示:
子步驟432是對於在步驟42中分割成的S i 個子集合中的每一個進行以下子步驟:子步驟4321是找出子集合中距離去干擾接收信號最近的一星座點(詳細尋找方式留待整個方法介紹完再說明)。Sub-step 432 is to perform the following sub-steps for each of the S i subsets segmented in step 42: sub-step 4321 is to find the distance de-interference received signal in the subset The nearest constellation point (The detailed search method is left to be explained after the whole method is introduced).
子步驟4322是從路徑延伸一代表星座點的分枝到第i
階層(即下一階層),且計算分枝的分枝長及一相對應的路徑(代表一傳送字元組)之路徑長,計算方式如下所示:
步驟44是對於第i -1階層,根據相對應的通道條件及路徑長,決定在步驟43中延伸到第i 階層的M i -1 S i 條路徑中要保留下來的路徑之第二目標數目M i (1 M i M i -1 S i )。Step 44 is to determine, for the i - th level, the second target number of paths to be retained in the M i -1 S i path extending to the i-th level in step 43 according to the corresponding channel condition and path length. M i (1 M i M i -1 S i ).
步驟45是對於在步驟43中延伸到第i 階層的M i -1 S i 條路徑,保留M i 條最短路徑而刪除其餘路徑。Step 45 is to delete the remaining paths by retaining the M i shortest paths for the M i -1 S i paths extending to the i-th level in step 43.
在步驟44及步驟45中,可以利用現有的各種適應性M演算法來決定第二目標數目M i 及保留M i 條最短路徑,此處將不多加說明。In step 44 and step 45, the existing various adaptive M algorithms can be used to determine the second target number M i and the reserved M i shortest path, which will not be described here.
步驟46是判斷i 是否等於N t (即下一階層是否是一最終階層),如果否,跳到步驟47,如果是,跳到步驟48。Step 46 is to determine whether i is equal to N t (ie, whether the next level is a final level), if not, skip to step 47, and if yes, go to step 48.
步驟47是將i 加1,並跳到步驟42。Step 47 is to increment i by 1, and skip to step 42.
步驟48是從到達第N t 階層的條路徑中選取一條最短路徑,此路徑所代表的傳送字元組即是偵測出的傳送字元向量。Step 48 from reaching the first class N t Select a shortest path from the path, and the transfer character group represented by the path is the detected transfer character vector. .
由於在步驟32中只需計算S 1 條分枝之分枝長,在步驟43中只需計算M i -1 S i (i =2,…,N t )條分枝之分枝長,因此, 當S 1 ~中的至少一者小於|C |時,可以減少QRD-M演算法所需計算的分枝長。而且,S 1 ~及M 1 ~根據通道條件被適當地調整,在大幅降低計算複雜度的同時,仍達到接近最大概似偵測的效能。Since it is only necessary to calculate the branch length of the S 1 branch in step 32, it is only necessary to calculate the branch length of the branch of M i -1 S i ( i = 2, ..., N t ) in step 43, therefore, S 1 ~ When at least one of them is less than | C |, the branch length required for the QRD-M algorithm can be reduced. Moreover, S 1 ~ And M 1 ~ Appropriate adjustments based on channel conditions, while significantly reducing computational complexity, still achieve near-most probable detection performance.
星座圖的分割Segmentation of constellation
在步驟31及步驟42中,是利用溫格柏的集合分割(Ungerboeck’s set partitioning)將星座圖分割成S i 個子集合(第一目標數目S i 必須為2的冪次方)。例如:參閱圖5,16-QAM星座圖可以分割成包括十六個星座點的一個子集合A0 、各包括八個星座點且相斥的二個子集合B0 及B1 、各包括四個星座點且相斥的四個子集合C0 ~C3 、各包括二個星座點且相斥的八個子集合D0 ~D7 ,或各包括一個星座點且相斥的十六個子集合(如圖5中的E0 ~E15 所示);參閱圖6,8-PSK星座圖可以分割成包括八個星座點的一個子集合F0 、各包括四個星座點且相斥的二個子集合G0 及G1 、各包括二個星座點且相斥的四個子集合H0 ~H3 ,或各包括一個星座點且相斥的八個子集合I0 ~I7 。溫格柏的集合分割使子集合的內距(intraset distance)在所有分割中是最大的,這可以減少錯誤蔓延(error propagation)。In steps 31 and 42, the constellation map is segmented into S i sub-sets using Ungerboeck's set partitioning (the first target number S i must be a power of 2). For example, referring to FIG. 5, the 16-QAM constellation diagram can be divided into a subset A 0 including sixteen constellation points, two sub-sets B 0 and B 1 each including eight constellation points, and each of which includes four Four sub-sets C 0 ~ C 3 of constellation points and repulsive, eight sub-sets D 0 ~ D 7 each including two constellation points and repulsive, or sixteen sub-sets each including one constellation point and repelling (eg E 0 in FIG. 5 ~ E 15 shown); see FIGS. 6,8-PSK constellation may be divided into eight comprise a subset of the constellation point F 0, and each comprise four constellation points of two subsets repulsive G 0 and G 1 , four sub-sets H 0 to H 3 each including two constellation points and being repulsive, or eight sub-sets I 0 to I 7 each including one constellation point and being repulsive. Wenger's set partitioning makes the intraset distance of the subsets the largest among all the partitions, which can reduce error propagation.
最近星座點的尋找Recent search for constellation points
在子步驟3211及子步驟4321中,當S i <|C |時(即子集合所包括的星座點之數目大於1),是利用至少一臨界值TH在子集合中切割出多數分別涵蓋星座點的決策區間,並判斷接收信號及去干擾接收信號(以下統稱信號z )是 位在哪個決策區間,來找出距離信號z 最近的星座點。In sub-step 3211 and sub-step 4321, when S i <| C | (ie, the number of constellation points included in the subset is greater than 1), at least one threshold TH is used to cut the majority in the subset to respectively cover the constellation Point decision interval and judge the received signal And de-interference receiving signals (Where collectively referred to as signal z ) is the decision interval in which to locate the constellation point closest to the distance signal z .
參閱圖5,舉一個例子說明。當S i
=4時,16-QAM星座圖可以分割成各包括四個星座點的四個子集合C0
~C3
,如表1所示:
各子集合C0
~C3
的臨界值TH如表2所示:
其中,,是接收到的星座圖的星座點之間的最小間距,d min
是傳送的星座圖的星座點之間的最小間距。每一臨界值TH在相對應的子集合C0
~C3
中切割出四個決策區間,其中,每一決策區間涵蓋一星座點。判斷法則如表3所示:表3
信號z 如圖5中的×所示。由於在子集合C0 中,信號z 滿足z >Re(TH),也滿足z >Im(TH),因此找出的星座點是c 2 ;由於在子集合C1 中,信號z 不滿足z >Re(TH),但滿足z >Im(TH),因此找出的星座點是c 10 ;由於在子集合C2 中,信號z 不滿足z >Re(TH),但滿足z >Im(TH),因此找出的星座點是c 11 ;由於在子集合C3 中,信號z 滿足z >Re(TH),也滿足z >Im(TH),因此找出的星座點是c 3 。The signal z is as shown by × in FIG. Since in the subset C 0 , the signal z satisfies z >Re(TH) and satisfies z >Im(TH), the constellation point found is c 2 ; since in the subset C 1 , the signal z does not satisfy z >Re(TH), but satisfies z >Im(TH), so the constellation point found is c 10 ; since in the sub-set C 2 , the signal z does not satisfy z >Re(TH), but satisfies z >Im ( TH), so the constellation point found is c 11 ; since the signal z satisfies z >Re(TH) and satisfies z >Im(TH) in the subset C 3 , the constellation point found is c 3 .
參閱圖6,舉另一個例子說明。當S i =2時,8-PSK星座圖可以分割成各包括四個星座點的二個子集合G0 、G1 ,其中,子集合G0 可以很容易地用一臨界值TH從中找出距離信號z 最近的星座點,而子集合G1 經旋轉45°後,也可以很容易地用一臨界值TH從中找出距離信號z 最近的星座點。Referring to Figure 6, another example is illustrated. When S i = 2, the 8-PSK constellation can be divided into two subsets G 0 , G 1 each including four constellation points, wherein the subset G 0 can easily find the distance from a threshold TH The nearest constellation point of the signal z , and after the sub-set G 1 is rotated by 45°, it is also possible to easily find the constellation point closest to the distance signal z with a critical value TH.
值得注意的是,本實施例也可以與其它QAM調變技術、其它PSK調變技術及其它調變技術配合,不以16-QAM及8-PSK為限。It should be noted that this embodiment can also be combined with other QAM modulation techniques, other PSK modulation techniques, and other modulation techniques, not limited to 16-QAM and 8-PSK.
第一目標數目S First target number S ii 的決定decision
假設在選取分枝的過程中,正確的路徑(代表正確的傳送字元向量X true
)沒有被刪除。當此正確路徑要從第i
-1階層(i
=1,…,N t
)向下一階層延伸時,信號z
如下所示:
其中,是正確的傳送字元,是雜訊,且是一複數高斯函數。among them, Is the correct transfer character, It is a noise and is a complex Gaussian function.
參閱圖7,在雜訊功率固定的情況下(如圖7中的圓圈所示),如果通道衰減較嚴重的話(即較小時),接收到的星座圖的星座點(如圖7中的圓形點所示)之間的間距會變小,雜訊可能導致信號點越過數個星座點而偏移到信號z (如圖7中的菱形點所示),因此,需要採用較大的第一目標數目S i ,以使所找出的距離信號z 最近的S i 個星座點能涵蓋信號點。如圖7(a)所示,如果通道衰減較嚴重的話,圓圈涵蓋較多的星座點(即 第一目標數目S i 較大),如圖7(b)所示,如果通道衰減較輕微的話,圓圈涵蓋較少的星座點(即第一目標數目S i 較小)。由上可知,第一目標數目S i 和通道條件(即通道衰減及雜訊功率)有關。在樹狀搜尋中,對於第i -1階層(i =1,…,N t ),應當根據相對應的通道條件決定適當的第一目標數目S i 。Referring to Figure 7, in the case where the noise power is fixed (as shown by the circle in Figure 7), if the channel attenuation is severe (ie When it is small, the distance between the constellation points of the received constellation (shown by the circular points in Figure 7) will become smaller, and the noise will be small. May cause signal points Crossing a few constellation points and shifting to the signal z (as indicated by the diamond dots in Fig. 7), therefore, it is necessary to adopt a larger first target number S i so that the found distance signal z is the closest S i Constellation points can cover signal points . As shown in Fig. 7(a), if the channel attenuation is more serious, the circle covers more constellation points (that is, the first target number S i is larger), as shown in Fig. 7(b), if the channel attenuation is slight, The circle covers fewer constellation points (ie, the first target number S i is smaller). As can be seen from the above, the first target number S i is related to the channel conditions (ie, channel attenuation and noise power). In the tree search, for the i - th level ( i = 1, ..., N t ), the appropriate first target number S i should be determined according to the corresponding channel condition.
在向第i 階層延伸時,通常希望能決定一個適當的第一目標數目S i ,使得正確的分枝被刪除的機率P miss (S i )小於一目標機率P target 。顯然,第一目標數目S i 愈大,P miss (S i )愈小,但計算複雜度愈高。因此,必須找到能滿足以上條件的最小第一目標數目S i ,以降低計算複雜度。When extending to the ith level, it is generally desirable to determine an appropriate first target number S i such that the probability that the correct branch is deleted P miss ( S i ) is less than a target probability P target . Obviously, the larger the first target number S i , the smaller the P miss ( S i ), but the higher the computational complexity. Therefore, it is necessary to find a minimum first target number S i that satisfies the above conditions to reduce computational complexity.
P miss (S i )等同於事件E 的機率:正確傳送字元的分枝長不在S i 條最短的分枝長之內。由於根據事件E 的機率來求得P miss (S i )<P target 的解答之計算過程非常複雜,必須計算|C |個分枝長才能求得,本實施例採用以下方式來求出近似解,以降低計算複雜度。 P miss ( S i ) is equivalent to the probability of event E : the branch length of the correctly transmitted character is not within the shortest branch length of the S i . Since the calculation process of finding the solution of P miss ( S i )< P target according to the probability of the event E is very complicated, it is necessary to calculate | C | branch lengths to be obtained. In this embodiment, the approximate solution is obtained by the following method. To reduce the computational complexity.
參閱圖8,在星座圖中,以信號z
為中心,定義一個涵蓋S i
個星座點的正方形。事件E
可以近似成事件A
:正確傳送字元落在正方形之外。根據Forney的連續近似(continuous approximation),正方形的邊長可以近似成。根據式(12)及~CN(0,),正確的分枝被刪除的機率P miss
(S i
)如下所示:
其中,。解P miss
(S i
)<P target
可得一期望數目:
其中,Q -1 (.)是Q (.)的反函數,S max 是軟硬體可容許的最大第一目標數目S i 。如果S max 不受軟硬體限制的話,S max 可設為星座圖所包括的星座點之數目|C |,例如:對於16-QAM星座圖,S max 可設為16。Where Q -1 (.) is the inverse of Q (.), and S max is the maximum number of first targets S i that the hardware and software can tolerate. If S max is not limited by software and hardware, S max can be set to the number of constellation points included in the constellation | C |, for example, for a 16-QAM constellation, S max can be set to 16.
為了能利用溫格柏的集合分割,第一目標數目S i 必須為2的冪次方,所以,,其中,是最接近但不小於x 之2的冪次方。In order to be able to utilize Wenger's set partitioning, the first target number S i must be a power of 2, so ,among them, Is the nearest power but not less than the power of 2 of x .
綜上所述,本實施例在S 1 ~中的至少一者小於|C |時,可以減少QRD-M演算法所需計算的分枝長,且本實施例可以與QAM、PSK等多種調變技術配合,故確實能達到本發明之目的。In summary, this embodiment is in S 1 ~ When at least one of them is less than | C |, the branch length calculated by the QRD-M algorithm can be reduced, and the embodiment can cooperate with various modulation techniques such as QAM and PSK, so that the object of the present invention can be achieved.
惟以上所述者,僅為本發明之較佳實施例而已,當不 能以此限定本發明實施之範圍,即大凡依本發明申請專利範圍及發明說明內容所作之簡單的等效變化與修飾,皆仍屬本發明專利涵蓋之範圍內。However, the above is only the preferred embodiment of the present invention, when not The scope of the invention is to be construed as being limited by the scope of the invention and the scope of the invention.
21‧‧‧通道估測器21‧‧‧channel estimator
22‧‧‧QR分解單元22‧‧‧QR decomposition unit
23‧‧‧轉換單元23‧‧‧Transition unit
24‧‧‧偵測單元24‧‧‧Detection unit
25‧‧‧接收天線25‧‧‧ receiving antenna
31~48‧‧‧步驟31~48‧‧‧Steps
圖1是一樹狀圖,說明多輸入多輸出系統中的樹狀搜尋;圖2是一方塊圖,說明本發明多輸入多輸出偵測器之較佳實施例;圖3和圖4是流程圖,說明較佳實施例所使用的偵測方法;圖5是一示意圖,說明溫格柏的集合分割如何應用在16-QAM星座圖;圖6是一示意圖,說明溫格柏的集合分割如何應用在8-PSK星座圖;圖7是一示意圖,說明所需的星座點數目和通道條件之間的關係;及圖8是一示意圖,說明本實施例如何決定所需的星座點數目。1 is a tree diagram illustrating a tree search in a multiple input multiple output system; FIG. 2 is a block diagram illustrating a preferred embodiment of the multiple input multiple output detector of the present invention; FIGS. 3 and 4 are flow charts The detection method used in the preferred embodiment is illustrated; FIG. 5 is a schematic diagram showing how the set partitioning of Wengebo is applied to the 16-QAM constellation diagram; FIG. 6 is a schematic diagram showing how the Wengebo collection segmentation is applied. In the 8-PSK constellation diagram; Fig. 7 is a schematic diagram showing the relationship between the number of constellation points required and the channel conditions; and Fig. 8 is a schematic diagram showing how the number of constellation points required in this embodiment is determined.
41~48‧‧‧步驟41~48‧‧‧Steps
Claims (19)
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US20080187066A1 (en) * | 2007-02-06 | 2008-08-07 | Nokia Corporation | Detection method and apparatus for a multi-stream MIMO |
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