1363514 九、發明說明： 【發明所屬之技術領域】 .树财輯減的軸⑽）减祕理，技舰 -涉及一種在接收器内處理訊號的方法和系統。 【先前技術】 通訊改變了人們通訊的方式，行動電話也從一 •們日常生活的基本域部分。行_話的制取決於社會情 叉地點和技術的限制。當前，語音連接已經滿足了日 要，行動語音連接正不斷溶人日常生活的方方面面，而行動 '的下—步將是機網際網路。行_際網路將註定成為日常㈣齡 -要來源，在這以後，更加便利的通用行動資料接入將_而至。 為滿足對未來行動網際網路的上述要求，特別設計了 蜂窩網路。隨著這Jib服務的庫用p L % ” —翻更加普及’網路容量的最優性價比和 服務質1 (⑽等因素對於蜂窩電話運營商來說，將變得更為重要。 0可以通過仔細的網路規劃和運作以及傳輸方法和接收器技術的 實現上朝素。在這裏’運營商觀術來增加下行輸出量，缺 後提供更加出色的QOS性能和傳輪速率，來同使用魏調制解調制哭 ‘和DSL方式提供服務的運營商展開競爭。在這點上，建設基於寬 .CDMA (WCDMA)技術的娜，可以為今天的無線運營商提供向: ·端用戶傳輸資料更加可行的選擇。 * .，目U所示為現有的WCDMA規範為增加下行輪出量進行的技術 發展的時間軸示意圖。圖1a中示出了各種無線技術所能提供的資料 1363514 率’這些技術包括通用分組無線業務（GPRS) 100、GSM (全球行動 通訊系統）的增強資料率技術(EDGE ) 102、通用行動通訊系統(觀丁8 ) 104以及高速下行分組接入（HSDPA) 106。 • GPRS和EDGE技術可以用於提高當前的第二代系統如GSM的資 料輸出量。GSM技術可以支援高達I4.4kb/s的資料率，而2001年提 出的GPRS技術允許使用每個分時多重存取（TDMA)訊框中多達8 個的時隙傳送資料’從而可以支援高達155Kb/s的資料率。相比之下， C GSM技術只允許使用TDMA訊框中的1個時隙傳送資料。2〇〇3年提 出的EDGE技術，可以支援的高達384Kb/s的資料率。EDGE技術使 用八進制移相鍵控（8-psk)調制來提供比GPUS更高的資料率。GPRS 和EDGE技術通常認為是“2.5”代技術。 2003年提出的UMTS技術，理論資料率可高達2Mb/s，是一種在 GSM基礎上改進的WCDMA3G系統'UTMS技術之所以能提供如此 尚的傳輸速率，其一個原因是它使用了 5MHz的WCDMA通道帶寬， G而GSM使用的是200KHZ的通道帶寬。HSDPA是一種基於網際協定 (ip)的服務技術，用於資料通訊領域’採用WCDMA來支援1〇Mb/s 的資料傳輸速率。經過第三代行動通訊合作項目（3Gpp)組的進一步 發展’励PA技術現在可錢舒種方絲提供更高的資料傳輸速 率。例如’許多傳輸蚊可以在基地台級別上作出，對此在行動交換 中心（局）作出’其更靠近用戶設備。這些決定包括決定要傳輸的資 料的調度，資料什麼時候發送，以及對傳輸通道的質量進行評估。 HSDPA馳還相伽可魏解。HSDPA技術射以在高速下行 6 1363514 . 系統，由於其大小、複雜度和雜的増加而引起成本增加使得盆應 .用範圍受到限制。必須為每個發射和接收天唆八〜 ㈣一々 職天線早獨提供-個射頻鏈直 ' 夕天線系統成本的增加。每條射親通常包括-個低雜訊放 大$ (低雜訊放大器），-_、波器，—個下變轉換器和—個類比/ 數位轉換器（A/D)。在某些現有的單天線無線接收機中，所需的單個 射頻鏈占了接收器總成本的3G%以上。因此，㈣顯，隨著發射和接 ‘收天線數量的增加’祕複雜度、功耗和總成本也隨之增加。這為行 • c動系統的設計和應用造成了很多問題。 通過與本申凊後續部分結合附圖介紹的本發明提出的系統相比 較’現有的和傳朗方法的局雖和缺騎於本領域的普通技術人員 來說是很明顯的。 【發明内容】 本發明要解決的技術問題在於，針對現有技術的上述缺陷，槔出 一種在接收器内處理訊號的方法和系統，用於實現單權重（sw)單通 G道（sc)多進多出（MIM0)系統。 根據本發明的一個方面’提出一種在接收器内處理訊號的方法， 所述方法包括： 生成至少一個控制訊號，用於控制至少複數個接收訊號中的第一 . 訊號； 通過所述生成的至少一個控制訊號調整所述複數個接收訊號的第 一訊號的相位以使所述複數個接收訊號的第一訊號的相位等於所述複 數個接收訊號的至少第二訊號的相位，其中，所述第一訊號的相位在 1363514 用於參理所述複數個接收訊號的第一訊號的處理通路内進行調整。 優選地，所述方法進一步包括通過所述生成的至少一個控制訊號 - 調整所述複數個接收訊號的第一訊號的振幅以使所述複數個接收訊號 •的第一訊號的振幅等於所述複數個接收訊號的至少第二訊號的振幅， 其中’所述第一訊號的振幅在用於處理所述複數個接收訊號的第一訊 號的處理通路内進行調整。 優選地’所述生成的至少一個控制訊號包括一個單權重訊號。 C 優選地，所述複數個接收訊號的第一訊號的所述相位被連續調整。 優選地’所述複數個接收訊號的第一訊號的所述相位以不連續的 時間間隔進行調整。 優選地’所述方法進一步包括放大所述複數個接收訊號的第一訊 號’以使所述複數個接收訊號的第一訊號的增益等於所述複數個接收 訊號的至少第二訊號的增益。 優選地’所述方法進一步包括合併所述複數個接收訊號的相位調 C整後第-峨與所述複數個減喊的至少第二訊號以生成一個合併 接收訊號。1363514 IX. Description of the invention: [Technical field to which the invention belongs] The axis of the tree reduction (10) is reduced by the secret, the technical ship - relates to a method and system for processing signals in the receiver. [Prior Art] Communication has changed the way people communicate, and mobile phones are also part of the basic domain of their daily lives. The system of lines depends on the location of the social situation and the limitations of technology. Currently, voice connections have been met, and voice connections are constantly evolving in every aspect of everyday life, and the next step in action is the Internet. The line_internet will be destined to become a daily (four) age - source, and after that, more convenient general action data access will be. In order to meet the above requirements for the future mobile Internet, a cellular network has been specially designed. As the library of this Jib service uses p L % — “more popular”, the optimal price/performance ratio of network capacity and quality of service 1 ((10) and other factors will become more important for cellular phone operators. 0 can pass Careful network planning and operation, as well as the implementation of the transmission method and receiver technology. Here, the 'operator view to increase the downlink output, the lack of better QOS performance and transmission rate, to use Wei Debugging and demodulating crying and DSL-based services provide competition for operators. At this point, building a wide-bandwidth CDMA (WCDMA)-based technology can provide today's wireless carriers with: • More efficient transmission of data to end users The choice is shown in Fig. 1a, which is a timeline diagram of the technical development of the existing WCDMA specification for increasing the number of round-trips. Figure 1a shows the data available for various wireless technologies. General Packet Radio Service (GPRS) 100, GSM (Global System for Mobile Communications) Enhanced Data Rate Technology (EDGE) 102, Universal Mobile Telecommunications System (Dawn 8) 104, and High Speed Downlink Packet Connection (HSDPA) 106. • GPRS and EDGE technologies can be used to increase the current data output of second-generation systems such as GSM. GSM technology can support data rates up to I4.4kb/s, while the GPRS technology proposed in 2001 allows Up to 8 time slots in each time-sharing multiple access (TDMA) frame transmit data' to support data rates up to 155Kb/s. In contrast, C GSM technology only allows the use of TDMA frames. Data transmission in 1 time slot. EDGE technology proposed in 2〇〇3 years can support data rates up to 384Kb/s. EDGE technology uses octal phase shift keying (8-psk) modulation to provide higher data than GPUS. Rate. GPRS and EDGE technologies are generally considered to be "2.5" generation technologies. The UMTS technology proposed in 2003, the theoretical data rate can be as high as 2Mb / s, is a WCDMA3G system improved on the basis of GSM 'UTMS technology can provide such a One of the reasons for the transmission rate is that it uses 5MHz WCDMA channel bandwidth, while G uses GSM channel bandwidth of 200KHZ. HSDPA is an Internet Protocol (IP)-based service technology for data communication field using WCDMA. Support 1 Mb/s data transfer rate. After the third generation of mobile communication cooperation project (3Gpp) group further development 'excited PA technology can now provide higher data transmission rate. For example, 'many transmission mosquitoes can be at the base At the station level, this is done at the Mobile Switching Center (the Bureau), which is closer to the user equipment. These decisions include determining the schedule of the data to be transmitted, when the data is sent, and evaluating the quality of the transmission channel. HSDPA is still in sync with the gamma. HSDPA technology is shot at high speed down 6 1363514. The system, due to its size, complexity and miscellaneous additions, increases the cost of the basin. Must be provided for each transmitting and receiving 唆 〜 ~ (d) 々 天线 天线 天线 早 早 早 早 早 早 早 早 早 早 射频 射频 射频 射频 射频 射频 射频 射频 射频 射频 射频 射频 射频Each shot is usually included with a low noise amplification $ (low noise amplifier), -_, wave, - down converter and - analog / digital converter (A / D). In some existing single-antenna wireless receivers, the required single RF chain accounts for more than 3G% of the total cost of the receiver. Therefore, (4), as the number of transmitting and receiving antennas increases, the complexity, power consumption, and total cost also increase. This creates a lot of problems for the design and application of the c-system. It will be apparent to those skilled in the art that the prior art and the method of the present invention can be compared to those of the prior art described in conjunction with the drawings. SUMMARY OF THE INVENTION The technical problem to be solved by the present invention is to provide a method and system for processing signals in a receiver for implementing the above-mentioned defects of the prior art, which are used to implement a single weight (sw) single pass G channel (sc) Into the extra (MIM0) system. According to an aspect of the present invention, a method for processing a signal in a receiver is provided, the method comprising: generating at least one control signal for controlling a first one of at least a plurality of received signals; a control signal adjusts a phase of the first signal of the plurality of received signals such that a phase of the first signal of the plurality of received signals is equal to a phase of at least a second signal of the plurality of received signals, wherein the The phase of a signal is adjusted within the processing path of the first signal for the plurality of received signals at 1363514. Preferably, the method further comprises: adjusting, by the generated at least one control signal, an amplitude of the first signal of the plurality of received signals such that an amplitude of the first signal of the plurality of received signals is equal to the complex number The amplitude of at least the second signal of the received signal, wherein 'the amplitude of the first signal is adjusted within a processing path for processing the first signal of the plurality of received signals. Preferably, said generated at least one control signal comprises a single weight signal. C Preferably, the phase of the plurality of first signals receiving the signal is continuously adjusted. Preferably, said phases of said plurality of received signals of said plurality of received signals are adjusted at discrete time intervals. Preferably, the method further comprises amplifying the first signal of the plurality of received signals ′ such that a gain of the first signal of the plurality of received signals is equal to a gain of at least a second signal of the plurality of received signals. Preferably, the method further comprises combining the phase-modulation of the plurality of received signals with at least a second signal of the plurality of screams to generate a combined received signal.
I 、’所述方法進一步包括為至少所述複數個接收訊號的第一 訊號生成時變脈衝響應的至少—個通道估計值。 所述方法進一步包括使用所述生成的時變脈衝回應的至 ‘少一個=道估計值生成所述至少一健制訊號。 -優^也所述方法進—步包括使用至少一個最優化演算法生成所 、乂 y㈤控制机號，其中所述最優化演算法包括至少一個最大訊號 12 1363514 雜訊比（SNR)演算法，—個最大訊號干擾雜訊比（s臟）演算法和 一個最小誤碼率（BER)演算法。 • 根據本發明的—個方面’提出-種機ϋ可讀記憶體，其内存儲有 -電腦程式’包括至少-個在触射處理職的代碼部分，所述至 少一個代碼部分由一機器執行以使所述機器執行如下步驟： 生成至少一個控制訊號，用於控制至少複數個接收訊號中的第— d訊號； 通過所述生成的至少一個控制訊號調整所述複數個接收訊號的第 一訊號的相位以使所述複數個接收訊號的第一訊號的相位等於所述複 數個接收訊號的至少第二訊號的相位，其中，所述第一訊號的相位在 用於處理所述複數個接收訊號的第一訊號的處理通路内進行調整。 優選地，所述機器可讀記憶體進一步包括有用於通過所述生成的 至少一個控制訊號調整所述複數個接收訊號的第一訊號的振幅以使所 G述複數個接收訊號的第一訊號的振幅等於所述複數個接收訊號的至少 第二訊號的振幅的代碼，其中，所述第一訊號的振幅在用於處理所述 複數個接收訊號的第一訊號的處理通路内進行調整。 優選地’所述生成的至少一個控制訊號包括一個單權重訊號。 優選地，所述複數個接收訊號的第一訊號的所述相位被連續調整。 優選地’所述複數個接收訊號的第一訊號的所述相位以不連續的 時間間隔進行調整。 優選地’所述機器可讀記憶體進一步包括有用於放大所述複數個 13 1363514 接收訊號的弟一訊號以使所述複數個接收訊號的第一訊號的增益等於 所述複數個接收訊號的至少第二訊號的代碼。 優選地，所述機器可讀記憶體進一步包括有用於合併所述複數個 接收訊號的相位調整後第一訊號與所述複數個接收訊號的至少第二訊 號以生成一個合併接收訊號的代碼。 優選地，所述機器可讀記憶體進一步包括有為至少所述複數個接 收訊號的第一訊號生成時變脈衝響應的至少一個通道估計值的代碼。 優選地，所述機器可讀記憶體進一步包括有使用所述生成的時變 脈衝回應的至少一個通道估計值生成所述至少一個控制訊號的代碼。 優選地，所述機器可讀記憶體進一步包括有使用至少一個最優化 演算法生成所述至少一個控制訊號的代碼，其中所述最優化演算法包 括至少一個最大訊號雜訊比（SNR)演算法，一個最大訊號干擾雜訊 比（SINR)演算法和一個最小誤碼率（ber)演算法。 根據本發明的一個方面，提出一種在接收器内處理訊號的系統， 所述系統包括： 控制訊號生成器，生成至少一個用於控制至少複數個接收訊號中 的第一訊號的控制訊號； 至少一個處理器，通過所述生成的至少一個控制訊號調整所述複 數個接收訊號的第一訊號的相位以使所述複數個接收訊號的第一訊號 的相位等於所述複數個接收訊號的至少第二訊號的相位，其中，所述 第一訊號的相位在用於處理所述複數個接收訊號的第一訊號的處理通 14 1363514 路内進行調整。 優選地’所述至少一個處理器通過所述生成的至少一個控制訊號 調整所述複數個接敗訊號的第一訊號的振幅以使所述複數個接收訊號 -的第一訊號的振幅等於所述複數個接收訊號的至少第二訊號的振幅， 其中’所述第一訊號的振幅在用於處理所述複數個接收訊號的第一訊 號的處理通路内進行調整。 優選地’所述生成的至少一個控制訊號包括一個單權重訊號。 C 優選地’所述複數個接收訊號的第一訊號的所述相位被連續調整。 優選地’所述複數個接收訊號的第一訊號的所述相位以不連續的 時間間隔進行調整。 優選地’所述系統進一步包括一個放大器，放大所述複數個接收 訊號的第一訊號，以使所述複數個接收訊號的第一訊號的增益等於所 述複數個接收訊號的至少第二訊號的增益。 優選地’所述系統進一步包括一個合併器，合併所述複數個接收 (一訊號的相位調整後第一訊號與所述複數個接收訊號的至少第二訊號以 生成一個合併接收訊號。 優選地，所述系統進一步包括一個通道估算器，為至少所述複數 個接收訊號的第一訊號生成時變脈衝響應的至少一個通道估計值。 • 優選地’所述控制訊號生成器使用所述生成的時變脈衝響應的至 少一個通道估計值生成所述至少一個控制訊號。 優選地，所述控制訊號生成器使用至少一個最優化演算法生成所 述至少一個控制訊號，其中所述最優化演算法包括至少一個最大訊號 15 1363514 雜訊比（SNR)演算法，一個最大訊號干擾雜訊比（SINR)演算法和 一個最小誤碼率（BER)演算法。The method of claim 1, further comprising generating at least one channel estimate of the time varying impulse response for at least the first plurality of received signals. The method further includes generating the at least one health signal using the generated one of the time varying impulse responses to 'one less = track estimate. The method further includes generating, by using at least one optimization algorithm, a 乂 y (five) control number, wherein the optimization algorithm includes at least one maximum signal 12 1363514 noise ratio (SNR) algorithm, A maximum signal interference noise ratio (s dirty) algorithm and a minimum bit error rate (BER) algorithm. • According to one aspect of the present invention, a machine-readable memory having a computer program included therein includes at least one code portion in a touch processing job, the at least one code portion being executed by a machine The apparatus performs the following steps: generating at least one control signal for controlling a first-d signal in the at least one of the plurality of received signals; and adjusting, by the generated at least one control signal, the first signal of the plurality of received signals a phase such that a phase of the first signal of the plurality of received signals is equal to a phase of at least a second signal of the plurality of received signals, wherein a phase of the first signal is used to process the plurality of received signals The first signal is adjusted within the processing path. Preferably, the machine readable memory further includes an amplitude for adjusting the amplitude of the first signal of the plurality of received signals by the generated at least one control signal to cause the first signal of the plurality of received signals to be described And a code having an amplitude equal to an amplitude of the at least second signal of the plurality of received signals, wherein an amplitude of the first signal is adjusted within a processing path of the first signal for processing the plurality of received signals. Preferably, said generated at least one control signal comprises a single weight signal. Preferably, the phases of the plurality of first signals receiving signals are continuously adjusted. Preferably, said phases of said plurality of received signals of said plurality of received signals are adjusted at discrete time intervals. Preferably, the machine readable memory further includes a brother signal for amplifying the plurality of 13 1363514 receiving signals such that a gain of the first signal of the plurality of received signals is equal to at least the plurality of received signals The code for the second signal. Preferably, the machine readable memory further comprises code for combining the phase adjusted first signal of the plurality of received signals with the at least second signals of the plurality of received signals to generate a combined received signal. Advantageously, said machine readable memory further comprises code for generating at least one channel estimate of the time varying impulse response for at least said first of said plurality of received signals. Advantageously, said machine readable memory further comprises code for generating said at least one control signal using at least one channel estimate of said generated time varying impulse response. Advantageously, said machine readable memory further comprises code for generating said at least one control signal using at least one optimization algorithm, wherein said optimization algorithm comprises at least one maximum signal to noise ratio (SNR) algorithm , a maximum signal interference noise ratio (SINR) algorithm and a minimum bit error rate (BER) algorithm. According to an aspect of the present invention, a system for processing a signal in a receiver is provided, the system comprising: a control signal generator, generating at least one control signal for controlling a first one of the plurality of received signals; at least one The processor adjusts, by the generated at least one control signal, a phase of the first signal of the plurality of received signals such that a phase of the first signal of the plurality of received signals is equal to at least a second of the plurality of received signals The phase of the signal, wherein the phase of the first signal is adjusted in a processing pass 14 1363514 for processing the first signal of the plurality of received signals. Preferably, the at least one processor adjusts an amplitude of the first signal of the plurality of received signals by the generated at least one control signal such that an amplitude of the first signal of the plurality of received signals is equal to the A plurality of amplitudes of at least a second signal receiving the signal, wherein 'the amplitude of the first signal is adjusted within a processing path for processing the first signal of the plurality of received signals. Preferably, said generated at least one control signal comprises a single weight signal. Preferably, said phase of said first plurality of received signals is continuously adjusted. Preferably, said phases of said plurality of received signals of said plurality of received signals are adjusted at discrete time intervals. Preferably, the system further includes an amplifier that amplifies the first signals of the plurality of received signals such that a gain of the first signal of the plurality of received signals is equal to at least a second signal of the plurality of received signals Gain. Preferably, the system further includes a combiner that combines the plurality of received (a phase-adjusted first signal of a signal with at least a second signal of the plurality of received signals to generate a combined received signal. Preferably, The system further includes a channel estimator that generates at least one channel estimate of the time varying impulse response for at least the first plurality of received signals. • Preferably the 'control signal generator uses the generated time The at least one channel estimate of the variable impulse response generates the at least one control signal. Preferably, the control signal generator generates the at least one control signal using at least one optimization algorithm, wherein the optimization algorithm includes at least A maximum signal 15 1363514 noise ratio (SNR) algorithm, a maximum signal interference noise ratio (SINR) algorithm and a minimum bit error rate (BER) algorithm.
X . 本發明的各種優點、目的和創新特徵以及具體實施例的細節，將 •在以下的說明書和附圖中進行詳細介紹。 【實施方式】 本發明提出一種用於實現單權重（SingleWeight)單通道（singleThe various advantages, objects, and features of the present invention, as well as the details of the specific embodiments, will be described in detail in the following description and drawings. [Embodiment] The present invention provides a single channel for achieving single weight (single)
Channel)的多入多出（MIM0)系統的方法和系統。根據本發明的目 C.的，一個單權重生成器可與一接收訊號的第一部分一起用在mjM〇接 收态第一訊號處理路徑中。所述單權重生成器可用于生成一個控制訊 號，或一個單權重訊號，以用於控制所述接收訊號的所述第一部分。 更具體地，所魅f彳訊號’或所述單權重誠，可用在所述第一訊號 處理路徑中調整所述接收訊號的所述第—部分的相位和/或振幅，以使 其相位和/或振幅等於所述接收訊號的第二部分的相位和/或振巾^所述 訊號權重生成器可在MMO接收器接收到一個新訊號後對所述控制訊 G號進行更新。 圖lb是根據本發明一個實施例的實現低延遲鏈路自適應的 HSDPA (高速下行分組接人）分散式結構的示意圖。圖化中示出了 終端110和112以及-個基地台（BS) 114。㈣伙建立在分散式結 構基礎上，通過在基地台114中設置關鍵性處理來實現低延遲鍵路自 適應’並因此更靠近空令介面，如圖所示。励pA調整在現有的 SM/EDGEb準内建立的方法，包括快速物理層⑴）重傳合併和鏈 路自適應技術’來實現行動終端11〇 ' m與基地台m之間分組資料 1363514 輸出罝的顯著提高。 —HSDPA技術採用了幾種重要的新技術改進，包括基地⑼4中下 .行分組諸操作_度，高_制，自適應調制和編瑪，混合自動重 .發請求（HARQ)，暫態通道狀態的物理層反饋和允許幾_戶丘用空 甲介面通道的-種新的傳輸通道類型，被稱為高速下行共用通道 (hs-DSCH>進行配置後，咖pA可以與現有的㈣退和Channel) method and system for multiple input and multiple output (MIM0) systems. In accordance with the teachings of the present invention, a single weight generator can be used in conjunction with a first portion of a received signal in the mjM spliced first signal processing path. The single weight generator can be used to generate a control signal, or a single weight signal, for controlling the first portion of the received signal. More specifically, the ambiguous signal or the single weight may be used to adjust the phase and/or amplitude of the first portion of the received signal in the first signal processing path to make its phase and / or amplitude equal to the phase of the second portion of the received signal and / or the vibration wiper ^ The signal weight generator can update the control signal G number after the MMO receiver receives a new signal. Figure lb is a schematic diagram of a HSDPA (High Speed Downlink Packet Access) decentralized architecture implementing low latency link adaptation, in accordance with one embodiment of the present invention. Terminals 110 and 112 and a base station (BS) 114 are shown in the figure. (4) The buddy is built on a decentralized structure, by setting critical processing in the base station 114 to achieve low-latency key adaptation ‘and thus closer to the null interface, as shown. Excitation pA adjusts the method established in the existing SM/EDGEb quasi, including fast physical layer (1) retransmission combining and link adaptation technology to achieve packet data 1363514 output between mobile terminal 11〇m and base station m罝Significant improvement. - HSDPA technology employs several important new technology improvements, including base (9) 4 in the middle and lower rows of operations _ degrees, high _ system, adaptive modulation and programming, hybrid automatic repeat request (HARQ), transient channel The physical layer feedback of the state and the new type of transmission channel that allows the use of the air interface interface, which is called the high-speed downlink shared channel (hs-DSCH>, after configuration, the coffee pA can be reconciled with the existing (four)
UMTS .服務共存悄—触巾，允許運營商向現杨WCDMA網路中引入更 G大的容量和更高的資料傳輸速率。通過自適應_和編碼、擴展多重 碼操作和快速高效重傳策略，Η_替換了 Wcdma的許多基本特 徵，例如，可變擴頻因數和快速功率控制。 在财的WCDMA網路巾，下行鏈路的功雜觸態顧大約是 \ 。WCDMA下行鏈 路的功率控制動態特性受限於並行碼通道上的用戶間崎在干擾以及 。优DMA基地台實現的本質特徵。對於靠近基地台的動隐用戶 。而言，功率控制並不能最佳的降低功率，將功率降低到超過如犯後 僅對容量產生較小的影響。例如，HSDpA利用高級鏈路自適應以及自 適應調制編碼（AMC)來保證所有用戶享受到可能達到的最高資料 率。因此，AMC根據適當的無線鏈路的質量自適應的選擇調制編碼方 法。 圖lc是根據本發明一個實施例的用來删除無線網路控制器中有 關重傳調度和存儲的内容的設置在基地台中的第· 意圖》圖^和了混合自動重發請求（職Q)操作，=：；= 17 1363514 計用於__骑錄高重傳鱗。帛—層HARQa_ ι 控制位於節點B或基地台（BS) 122中，從而刪除無線網路控制器 .⑽C) 120中有關網路重傳調度和存儲的内容。這種HARQ方法避 .免了集線器延遲，並在-定程度上降低了最終的重傳延遲。 例h，當鏈路誤碼出現時，由於訊號干擾或其他原因，行動終端 m可請求對資料分組進行重傳。當前的WCDMA網路通過無線網路 控制器12〇處理這類重傳請求，而HSDPA重傳請求在基地台⑵中 C管理。此外’接收到的分組資料只有在成功解碼後才能在物理層進行 合併和.恢復。如歸碼失敗，重傳的資料將朗道解碼祕資料進行 合併。HSDPA方法允許先前發送軌框（解碼失敗的訊框）與重傳的 訊框進行合併。錯策略最小簡外鱗請求需要關時提供更 好的解碼效率和分集增益。 雖然擴頻因數可以是固定的，編碼率可在1/4和3/4之間變化，且 HSDPA規範支援多達10種多重碼的使用。更強的編碼、快速以叫 G.和多重碼操作使得不再需要可變擴頻因數，並允許使用比在大多數 CDMA系統中使用的傳統耙式接收器更高級的接收器結構如等化 器。這種方法還可以·戶接收到最佳的可用資料率，無論是具有較 好訊號質量或較高編碼率的用戶，還是處於蜂窩網邊緣較遠處具有較 低編碼率的用戶。 « • 通過將資料通訊調度移至基地台122處理，從而更加靠近空中介 面’並通過使用有關通道質量、終端性能、Q〇S和功率/編碼可用性^ 面的資訊，HSDPA可以實現更加高效的資料分組傳輸調度。通過將這 1363514 些智慧型網路操作移至基地台122處理，允許系統充分利用短期變化 的優勢’從而加快和簡化關鍵的傳輸調度過程。例如，HSDPA方法可 .以管理調度安排來跟_戶訊號的快速衰減，並且在條件允許的情況 -下，在一個較短的時間段内將大部分蜂窩容量分配給單獨一個用戶使 用。在基地台122處，HSDPA收集並使用每個活躍用戶的通道質量的 估計值，。這種反饋提供了大範圍内的通道物理層狀況的當前資訊包 括功率控制、ACK/NACK比、QoS和HSDPA特殊用戶反饋。 C 雖然wCDMARdease 99或WCDMA Rdease 4支援下行通道 (DCH)或下行共用通道（DSCH) ’而由WCDMARel_5提供的 HSDPA操作可在高速下行制通道（HS-DSCH)上實現。同10、2〇、 40或80笔秒的DSCH訊框長相比，這種高速方法使用2毫秒間隔的 訊框長（也稱為傳送時間間隔）。DHCP使用4到256位（chips)的可 變擴頻因數，而HS-DSCH使用最多具有個代· 16位固定擴頻 因數。HS_DSCH可以支援16位正交娜（16_QAM)，鏈路自適應， C .以及在物理層使用haRq對重傳訊號進行合併。HSDpA還調整高速 共用控制通道（HS-SCCH)來傳送所需的調制和重傳資訊。一條上行 高速專用物理控制通道（HS_DPCCH)在上行鏈路上傳送arq應答订 下行鏈路質量反饋和其他必要的控制資訊。 圖Μ是根據本發明一個實施例的基於HSDpA的巨集單元和微單 70系統的平均傳輸載荷的柱狀示意圖。如圖Id中的圖表13〇所示，在 實際配置中，與WCDMA Release 99相比，HSDPA提供了大於2俨的 最高用戶位元率峰值。使用可以與DSL數據機速率相嫂美的位元率， 19 1363514 HS-DSCH在大的巨集單元環境中可以提供給用戶超過1Mbit/s的位元 率，在較小微單元環境中可以提供高達5Mbit/s的位元率。HSDpA方 -法既支持非即QoS類，也支持帶有保證位元率的即時_^ (^oS 類。 跟WCDMARelease99相比’定義為通過單個蜂窩每秒發送給用 戶的位元總量的蜂窩輸出量，在使用HSDPA的情況下增長1〇〇〇/〇。這 是因為HSDPA使用HARQ將分組資料重傳與前一傳輸進行合併因 C此沒有浪費任何傳輸。同WCDMARdease99中只使用PQSK調制相 比，高階調制方法如16-QAM能提供更高的位元率，甚至是在兩個系 統中使用相同正交碼的情況下。在低路徑間干擾和低磁區間干擾的狀 態下，可以獲得最高輸出量。在微單元設計中，例如，hs_dsch可以 支援高達每磁區每載波5Mbit/s或lbit/s/Hz/cell的資料傳輸速率。 圖2是根據本發明一個實施例的用於WCDMA的單權重單通道系 統200的方框圖。圖2示出了發射器部分2〇〇a和接收器部分2〇肋。 G發射器部分200a包括混頻器2〇1和天線2〇3。資料登錄以和代碼ci 輸入給混頻器.2(Π。接收器部分2〇〇b包括天線2〇5和2〇7、帶通濾波 器（BPF) 202和206、低雜訊放大器（LNA) 2〇4、相移器/低雜訊放 大器（ps低雜訊放大器）模組208、直接轉換無線電（dcr)模組、 •類比數位（A/D)轉換器2丨4'基帶處理器216和單權重生成器（SWG) 218。 。〇 在發射器-側’混頻器2〇1用於將資料登錄χ1與代碼^混頻。 每個基地台的通道的實際畴脈衝回應由Μσ &表示。每個基地台的 20 1363514 通道實際時變脈衝回應齡計值由G和心表示。 在接收器-側，帶通遽波器202和施可包括適當的邏輯、電路 •和/或代碼’並甩於分別從天線205和2〇7接收射頻訊號作為輸入。隨 -後帶通滤波旨202和206將訊號的頻率限制到一個預先設定的頻帶 上，並且向低雜訊放大器204和相劍/低雜訊放大器模組·輸出該 頻帶。低雜訊放大器204和相移器/低雜訊放大器模組2〇8可包括適當 的邏輯、電路和/或代碼，並且用於接收一個訊號作為輸入，隨後將該 C訊號放大’並只引入了很少的額外雜訊。此外，相移器/低雜訊放大器 模組208中的低雜訊放大器可接收一放大訊號作為輪入對該訊號進 行相移，並輸出最後生成的相移訊號。 在本發明的一個方面中，相移器/低雜訊放大器模組2〇s可以用來 對天線207接收到的訊號進行相移，以使其與天線2〇5接收到的訊號 同相。例如’相移器/低雜訊放大器模組2〇8可以接收一個單權重（sw) 控制訊號220，該訊號可以由單權重生成器（SWG) 218生成。隨後， G相移器/低雜訊放大器模組208可以依據接收的8臀控制訊號22〇對天 線207接收到的訊號進行相移。在這點上，分別由天線2〇5和2〇7接 收到的兩個sfl號可以在點210處同相。此外，相移器/低雜訊放大器模 組208中的低雜訊放大器和低雜訊放大器2〇4可對分別從天線2〇7和 205接收到的訊號進行放大，從而在點21〇處實現兩個訊號的平衡增 益。 直接轉換無線電模組212可包含適當的邏輯、電路和/或代碼，用 於放大並轉換接收到的類比射頻訊號為基帶訊號。例如，直接轉換無 1363514 線電模組212可以使用一組用低雜訊放大器實現的放大器、一個複雜 同相正交訊號元件混頻器和一個低通訊道濾波器。Α/〇轉換器214可 .包括適當的邏輯、電路和/或代碼，用於從直接轉換無線電模組212接 收類比訊號，並生成相應的輸出數位訊號，該訊號將傳送給基帶處理 器216。該數位訊號將以一個預先設定的採樣率對類比訊號進行採樣。 基帶處理器216可包括適當的邏輯、電路和/或代碼，用於處理數 位訊號並生成語音輸出訊號222和資料輸出訊號224。此外，基帶處 (Γ理器216可以用於生成一供單權重生成器使用的輸出訊號.。單權重生 成器模組218使用該輸出訊號生成單權重22〇，用於控制相移器/低雜 訊放大器模組208中的相移。語音輸出訊號222進一步被語音處理單 元和/或數位顯示處理器分別處理。 單權重生成器模組218可包括適當的邏輯、電路和/或代碼，例如， 用於處理從基帶處理器216接收到的通道函數估計值和射頻訊號計時 資訊，並生成單權重（SW) 220。相移器/低雜訊放大器模組2〇8可以 C使用單權重220對從天線207接收到_頻訊號進行相移，並生成與 從天線205接收到的訊號同相的射頻訊號。 在操作過程巾’發射H侧2GGa可用於將輸人資料訊號χ1與代碼 訊號cH昆頻，隨後通過天線2〇3向空中發射該訊號。纽號被發射到 空t後’由於反射的原目，其可能會橫貫複數個不同的路徑或多路徑。 該訊號所橫貫的每個基地台的通道的實際時變脈衝回應表示為^和 h2。該通道實際變脈衝回應的估計值表示為。發射的訊號可 通過各種路徑接收，其中每個基地台的通道實際時變脈衝回應由^和 22 1363514. ib表示。帶通濾波器202和206分別對天線205和207接收到的訊號 進行帶通濾波。此外，相移器/低雜訊放大器模組208可以從單權重生 -成态模組218接收單權重控制訊號220，並基於單權重220調整從天 線207接收到的訊號的相位。因此天線2〇7接收到的訊號將與天線2〇5 接收到的訊號同相。此外，從天線205和207接收到的兩個訊號的增 益將被調整，以使接收器側200b中的點210處可以實現增益平衡。 然後射頻訊號由直接轉換無線電模組212進行處理，隨後進一步 • C放大’並與個VCO §fl號進行混頻，和/或進行低通遽波。直接轉換 無線電模組處理的射頻類比訊號可以由A/D轉換器214轉換為數位訊 號。A/D轉換器214的數位輸出作為輸入傳送給基帶處理器216。基 帶處理器216對輪入訊號進行進一步處理，生成語音訊號222和資料 訊號224。語音訊號222可由例如語音處理系統進行進一步處理，資 料訊號224可由例如顯示處理器進行進一步處理。此外，基帶處理器 216還可生成一訊號，單權重生成器使用該訊號生成訊號單權重22〇。 G 雖然發射器侧中只使用了一個天線2〇3，但是本發明並不僅 限於此，本發明還可以使用複數個發射天線。同樣的，也可以在接收 器侧iOOb中使用複數個接收天線。此外，雖然對一個或複數個訊號使 用單權重進行相位調整的技術是在接收器侧2〇〇b中實現的，但是本發 •明並不僅限於此，該相位調整也可以在發射器側2〇〇a中實現。 圖3是根據本發明一個實施例的直接轉換無線電模組的方框圖。 在圖3中，直接轉換無線電模組3〇〇可包括適當的邏輯、電路和/或代 碼，用於放大並轉換接收的類比射頻訊號為基帶訊號。一個具體實施 23 1363514 例中’直接轉換無線電模組300可以包括一個低雜訊放大器3〇4，一 個電壓控制振盪器（VCO) 308，一個混頻器306和一個低通濾波器 (LPF)312。 低雜放大器304接收射頻訊號302，並基於預先設定的增益級 對其進行放大。電壓控制振盪器308可包括適當的邏輯、電路和/或代 碼，用於輸出一個特定頻率的訊號310，該特定頻率可以預先確定或 由輸入電塵控制振盪器的電壓訊號進行控制。混頻器3〇6將電屋控制 C振盪器訊號與從低雜訊放大器304接收的放大訊號混頻。低通濾波器 312可包括適當的邏輯、電路和/或代碼，用於接收混頻器3〇6輸出的 混頻訊號，將混頻訊號的頻率限定在以某個特定頻率為上限的預先設 定的頻帶内，然後將該頻帶作為基帶訊號314輸出。 圖4是根據本發明一個實施例的可用於ΜΜ〇系統中的基帶處理 器的方框圖。如圖4所示，基帶處理器400包括群集路徑處理器（cpp ) 模組432、最大比合併（MRC)模組424、解擴頻模組426、分集處理 C器428、巨集單元合併器模組、卷積編碼器模組极和渦輪㈤⑻ 解碼器模組440。 2005年6月30日申請的美國專利f請號為11/173,854的美國專 利申請“快速多路徑採集，，提供了對訊號群集的詳細描述，該申 此全文引用。 月 群集路徑處黯模組432可包括複數個群集處理n，用於接收和 ，理來自類比數位轉換器⑽）的輸入訊號穀。在基帶接收器處理 态400中’群集路徑處理器模組极中的群集路徑處理器极&，... 24 1363514 地台的兩個或複數個不同天線中接收的獨立衰減路雜取的長期對數 正感訊號。該宏齡集方法可以用於合併兩個或複數個通過從同—個 -接收地點的兩個或複數個不同天線中接收的獨立衰減路徑獲取的短期 .瑞利（Rayleigh)訊號。 卷積編碼器438可包括適當的邏輯、電路和/或代碼，用於依據 3GPP規範’處珊卷積編解•卷義的輸出可以是數位訊 號，包括適於岭音驗模組處理的語音資訊。渦輪解· _可包 〇括適當的邏輯、電路和/或代碼，用於依據3Gpp規範，處理對渦輪代 碼的解碼。解的輸出可岐數位峨，包括適合視頻顯示處 理器使用的資料資訊。 一參看圖2和圖4 ’在操作過程中，發射器側2〇加可以用來將輸入 資料訊號XI與代碼訊號cl混頻，並生成輸出訊號，通過天線加在 空中的不同路徑上傳送。每個空中路徑或通道包含一個相應的時變脈 衝響應函數ΜΑ。通道估計值&和心提供了傳送接收訊號的通道的 〇實際時«衝回應估計值。天線2〇5和2〇7接收到的訊號分別通過帶 通遽波器202和206進行帶通濾波，並分別通過低雜訊放大器2〇4和 相移器/低雜訊放大器模組施放大。此外，相移器/低雜訊放大器模組 208可從單權重生成器模組218接收單權重控制訊號22〇，並基於單權 重〃周整從天線207接收到訊號的相位。這樣的話，從天線207接 收到的訊號可以和從天線2〇5接收到的訊號同相。此外，還對從天終 205和207接收到的兩訊號的增益進行調整，使得接收器側2〇此點21〇 處實現增益平衡。 27 1363514 射頻訊號隨後由直接轉換無線電模組212進行處理，並進一步放 大’與一個VCO訊號進行混頻，和/或進行低通濾波。直接轉換無線 •電模組處理的射頻類比訊號可由A/D轉換器214轉換為數位訊號。a/j) 、轉換器214的數位輸出將作為輸入傳送給基帶處理器216。基帶處理 器216對輸入訊號做進一步處理，生成語音訊號222和數位訊號224。 語音訊號222可以進一步由語音處理系統或設備進行處理，資料訊號 224可以進一步由顯示處理器進行處理。此外，基帶處理器216還可 G生成一訊號，單權重生成器218使用該訊號生成訊號單權重22〇。 A/D轉換器模組的數位訊號輸出可以作為輸入訊號*犯傳送 給群集路徑處理器模組432。群集路徑處理||模組松隨後生成每個 基地台的通道實際時變脈衝回應的通道估計值，以及每個基地 台的計時資訊T。每個基地㈣通道實際時變脈衝回應的通道估計值 心和心和/或每個基地台的計時資訊m後傳遞給最大比合併模組似 進行處理。最大比合併模組424使用每個基地台的估計似批和計 G時資訊τ來生成傳送的資料的估計值。 解擴麵組426對每個基地台的估計訊號進行解觸，從而生成 原始訊號。分集處理器模組428提供分集處理，巨集單元合併器模組 實現宏觀分集。卷積編碼_43_集單元合併器模組· 生成軌號的語音部分執行卷積解碼，並生成語音輸出訊號442。渦 對從巨集單元合併器模組43〇的輪出中生成的訊號 的貝枓Μ執行卷積解碼，並生成資料輸出訊號444。 圖5是根據綱—峨·她㈣職的步驟的流 28 1363514 程圖。如圖5所示’步驟502中，複數個通訊訊號由一個mmo接收. 器接收。步驟504中生成一個控制訊號，用於控制該接收訊號的第一 .部分。在步驟506，使用所述控制訊號調整所述第一訊號部分的相位 '和/或振幅’以使第一 訊號部分的相位和/或振幅與所述接收訊號的第二 部分相等。 在步驟508，所述接收訊號的相位和/或振幅調整後的第一部分與 所述接受訊號的第二部分進行合併，生成合併接收訊號。在步驟51〇， v對該合併接收訊號進行處理以生成所述接收訊號的第一和/或第二部 分的時變脈衝回應的通道估計值。在步驟512，單權重生成器使用所 述接收訊號的第一和/或第二部分的時變脈衝回應的通道估計值生成 控制訊號。 本發_上述實施例介紹了-_於在接收器巾處理訊號的方法 和系統。所述方法包括生成至少一個控制訊號，用於控制第一接收訊 號。所述第-接收訊號的相位可以通過生成的控制訊號進行調整，使 G得所述第一接收訊號的相位等於第二接收訊號的相位。所述第一接收 訊號的相位在一個用於處理第一接收訊號的處理路徑中進行調整。所 述第一接收訊號的振幅可以通過生成的控制訊號進行調整，使得所述 第一接收訊號的振幅等於第二接收訊號的振幅，其中，所述第一接收 訊號的振幅在一個用於處理第一接收訊號的處理路徑中進行調整。 所述生成的控制賴；包括一個單權重訊號。所述第—接收訊號的 相位可連續調整和/或材連續㈣關隔進行調整。可以對所述第一 接收訊號進行放大，使得所述第—接魏號的增鱗於第二接心號 29 1363514 的增益。相位調整後的第一接收訊號和第二接收訊號進行合併，從而 生成一個合併接收訊號。生成第一接收訊號的時變脈衝回應的通道估 -計值’並且利用該時變脈衝響應的通道估計值生成一個控制訊號。該 •控制訊號可以使用一個或複數個最優化演算法來生成，如最大訊號雜 訊比（SNR)演算法、最大訊號干擾雜訊比（SINR)演算法和最小誤 碼率（BEH)演算法。 本發明的另一個實施例提供了一種機器可讀記憶體，其内存儲的 G電腦程式包括至少一個可以被機器執行的代碼部分，從而使得所述機 器執行上述步驟以在接收機中處理訊號。 本發明的所述系統包括使用控制訊號生成器生成一個控制訊號， 其中該控制訊號可以用於控制至少第一接收訊號。處理器通過生成的 控制訊號對第一接收訊號的相位和/或振幅進行調整，使得第一接收訊 號的相位和/或振幅等於第二接收訊號的相位和/或振幅，其中，第一接 收訊號的相位/振幅是在一個用於處理第一接收訊號的處理路徑中進 -行調整的。生成的控制訊號包括一個單權重訊號。第一接收訊號的相 位可連續調整和/或在不連續的時間間隔進行調整。一放大器對第一接 收訊號進行放大，使得第一接收訊號的增益等於第二接收訊號的增益。 η併器將相位調整後的第一接收訊號與第二接收訊號進行合 併生成一個合併接收訊號。通道估算器生成第一接收訊號的時變脈 衝回應的通道估計值。控制訊號生成器使用時變脈衝回應的通道估計 值生成控制訊號。控制訊號生成器可使用一個或複數個最優化演算 法'生成該蝴職，如最纽_減（驗）法、最大訊號干 30 丄剛514 擾雜訊比（s職）演算法和最小誤碼率（BER)演算法。 因此’本發明可以通過硬體、軟體或硬體和軟體的結合來。 树明可由至少-個電腦系統_集中模式來實現，也可由不同元件 2在幾個互連的電職統中的分顏式來實現。任何—種能夠實現 本申請中介紹的枝㈣㈣統錢其他設備較可翻的。 Ο 型的硬體和軟體的結合是帶有電腦程式的朝電腦系統，該電腦喊 被裝載和執行時能控㈣⑽:統實現本申請所述的方法。 ， 本發明還可嵌人包括有能夠實縣方法的各種特徵的電腦程式產 。口中’當該程式载人到電腦系統中時能夠實縣申請所述的方法。本 文中所述的電腦程式是指，例如，以任何語言、代碼或符號表示的一 組指令’能魅接使具有龍處理能力的祕執行蚊魏或者姐 過以下-種或各種處理後使具有資訊處理能力料統執行特定功能： a)轉換成另—種語言、代碼或符號；b)以不_材料複製。 本申請已結合—定的實_對本剌進行了描述，本領域的普通 」技術人員可知’可以對本發明進行各種改變或等同替換而不脫離本發 明的範圍。此外，根據本發明的指導進行的各種修改以適應特定的環 境或材料也並未脫離本發明的範圍。因此，本發明並不限於公開的那 些具體實施例，本發明包括落人中請專利範_的所有實施例。 【圖式簡單說明】 圖 W現有的WCDMA規範為增加下行輸出量進躺技術發展的時 間軸示意圖； 31 1363514 · 圖lb是根據本發明一個實施例的實現低延遲鏈路自適應的HSDpA* 散式結構的示意圖； 圖lc是根據本發明—個實施例的用來刪除無線網路控制器中有關重 傳調度和存儲的内容的設置在基地台中的第一層控制的示 園， 圖Id是根據本發明一個實施例的基於HSDPA的巨集單元和微單元系 統的平均傳輸載荷的柱狀示意圖； C圖2是根據本發明一個實施例的用於WCDMA的單權重單通道系統的 方框圖； ^ 圖3是根據本發明一個實施例的直接轉換無線模組的方框圖； 圖4是根據本發明—個實細的可祕純巾的絲處理 方框圖； 4 圖5是根據本發明—個實施例的在接收器中處理訊號的步驟的 圖。UMTS. The service coexistence—the headset—allows operators to introduce more large capacity and higher data transfer rates into the existing Yang WCDMA network. By adaptive _ and encoding, extended multiple code operations, and fast and efficient retransmission strategies, Η_ replaces many of the basic features of Wcdma, such as variable spreading factor and fast power control. In the WCDMA network towel of the money, the downlink touch is about \. The power control dynamics of the WCDMA downlink are limited by the interference between users on the parallel code channel. The essential features of the DMA base station implementation. For users who are close to the base station. In this case, power control does not optimally reduce power, reducing power to less than just having a small impact on capacity. For example, HSDpA utilizes advanced link adaptation and adaptive modulation coding (AMC) to ensure that all users enjoy the highest possible data rate. Therefore, the AMC adaptively selects the modulation coding method according to the quality of the appropriate radio link. Figure lc is a diagram of a set of intentions in a base station for deleting content related to retransmission scheduling and storage in a wireless network controller according to an embodiment of the present invention, and a hybrid automatic repeat request (job Q) Operation, =:; = 17 1363514 is used for __ riding high-heavy scales. The H-layer HARQa_ ι control is located in Node B or Base Station (BS) 122, thereby deleting the radio network controller. (10) C) 120 about network retransmission scheduling and storage. This HARQ approach avoids hub delays and reduces the final retransmission delay to a certain extent. For example, when a link error occurs, the mobile terminal m may request retransmission of the data packet due to signal interference or other reasons. The current WCDMA network handles such retransmission requests through the radio network controller 12, and the HSDPA retransmission request is managed in the base station (2). In addition, the received packet data can only be merged and restored at the physical layer after successful decoding. If the code return fails, the retransmitted data will be combined with the Landau decoding secret data. The HSDPA method allows the previous transmit track frame (the frame where the decoding failed) to be merged with the retransmitted frame. The wrong strategy minimum simple scale request requires better decoding efficiency and diversity gain when it is off. Although the spreading factor can be fixed, the coding rate can vary between 1/4 and 3/4, and the HSDPA specification supports the use of up to 10 multiple codes. Stronger coding, fast G. and multiple code operations eliminate the need for variable spreading factor and allow for more advanced receiver structures such as equalization than traditional rake receivers used in most CDMA systems. Device. This method also allows the user to receive the best available data rate, whether it is a user with better signal quality or higher coding rate, or a user with a lower coding rate at a farther edge of the cellular network. « • HSDPA enables more efficient data by moving data communication schedules to base station 122 for closer proximity to the empty mediation plane and by using information about channel quality, terminal performance, Q〇S and power/code availability. Packet transmission scheduling. By moving these 1363514 smart network operations to the base station 122 for processing, the system is allowed to take full advantage of the short-term changes' to accelerate and simplify the critical transmission scheduling process. For example, the HSDPA method can allocate a large amount of cellular capacity to a single user for a short period of time by managing scheduling arrangements to quickly decay with the _ household signal and, if conditions permit. At base station 122, HSDPA collects and uses an estimate of the channel quality for each active user. This feedback provides current information on the physical state of the channel over a wide range including power control, ACK/NACK ratio, QoS, and HSDPA special user feedback. C Although wCDMARdease 99 or WCDMA Rdease 4 supports Downlink Channel (DCH) or Downlink Shared Channel (DSCH)', HSDPA operation provided by WCDMARel_5 can be implemented on High Speed Downlink Channel (HS-DSCH). This high speed method uses a frame length of 2 milliseconds (also known as a transmission time interval) compared to a DSCH frame length of 10, 2, 40, or 80 seconds. DHCP uses a variable spreading factor of 4 to 256 chips, while the HS-DSCH uses a maximum of 16 bits of fixed spreading factor. HS_DSCH can support 16-bit orthogonal (16_QAM), link adaptation, C. and use haRq to merge retransmission signals at the physical layer. HSDpA also adjusts the High Speed Shared Control Channel (HS-SCCH) to transmit the required modulation and retransmission information. An upstream high-speed dedicated physical control channel (HS_DPCCH) transmits the arq response to the downlink quality feedback and other necessary control information on the uplink. Figure 2 is a bar graph of the average transmission load of the HSDpA-based macrocell and the micro-single 70 system in accordance with one embodiment of the present invention. As shown in Figure 13 of Figure Id, in the actual configuration, HSDPA provides a peak of the highest user bit rate greater than 2俨 compared to WCDMA Release 99. Using a bit rate comparable to that of a DSL modem, 19 1363514 HS-DSCH can provide users with bit rates in excess of 1 Mbit/s in large macrocell environments, providing up to 1Mbit/s in smaller microcell environments Bit rate of 5 Mbit/s. The HSDpA side-method supports both non-QoS classes and instant _^ with guaranteed bit rate (^oS class. Compared to WCDMA Release 99, the cell defined as the total number of bits sent to the user per second through a single cell. The output is increased by 1〇〇〇/〇 when using HSDPA. This is because HSDPA uses HARQ to combine packet data retransmission with the previous transmission because C does not waste any transmission. Only PQSK modulation phase is used in WCDMARdease99. Higher-order modulation methods such as 16-QAM can provide higher bit rates, even in the case where the same orthogonal code is used in both systems. In the case of low path interference and low magnetic interval interference, Maximum output. In the microcell design, for example, hs_dsch can support data transmission rates up to 5 Mbit/s or 1 bit/s/Hz/cell per carrier. Figure 2 is a diagram for WCDMA in accordance with one embodiment of the present invention. A block diagram of a single-weight single-channel system 200. Figure 2 shows a transmitter section 2a and a receiver section 2 ribs. The G-transmitter section 200a includes a mixer 2〇1 and an antenna 2〇3. Enter with the code ci Mixer .2 (Π. Receiver section 2〇〇b includes antennas 2〇5 and 2〇7, bandpass filters (BPF) 202 and 206, low noise amplifier (LNA) 2〇4, phase shifter /low noise amplifier (ps low noise amplifier) module 208, direct conversion radio (dcr) module, analog-to-digital (A/D) converter 2丨4' baseband processor 216 and single weight generator (SWG) 218. 发射 In the transmitter-side 'mixer 2〇1 is used to register the data χ1 and code^. The actual domain impulse response of each base station channel is represented by Μσ & The 20 1363514 channel actual time-varying impulse response age value is represented by G and the heart. At the receiver-side, the bandpass chopper 202 and the stipulation include appropriate logic, circuitry, and/or code's and Antennas 205 and 2〇7 receive RF signals as inputs. The follow-up bandpass filters 202 and 206 limit the frequency of the signal to a predetermined frequency band and to the low noise amplifier 204 and the phase/low noise amplifier. Module · Output the frequency band. Low noise amplifier 204 and phase shifter / low noise amplifier module 2〇8 may include appropriate Logic, circuitry, and/or code, and for receiving a signal as an input, then amplifying the C signal' and introducing only a small amount of additional noise. Further, in the phase shifter/low noise amplifier module 208 The low noise amplifier can receive an amplified signal as a wheel to phase shift the signal and output the last phase shift signal. In one aspect of the invention, the phase shifter/low noise amplifier module 2〇s can It is used to phase shift the signal received by the antenna 207 so as to be in phase with the signal received by the antenna 2〇5. For example, the phase shifter/low noise amplifier module 2〇8 can receive a single weight (sw) control signal 220, which can be generated by a single weight generator (SWG) 218. Subsequently, the G phase shifter/low noise amplifier module 208 can phase shift the signal received by the antenna 207 according to the received 8-hip control signal 22〇. At this point, the two sfl numbers received by antennas 2〇5 and 2〇7, respectively, can be in phase at point 210. In addition, the low noise amplifier and the low noise amplifier 2〇4 in the phase shifter/low noise amplifier module 208 can amplify the signals received from the antennas 2〇7 and 205, respectively, at point 21〇. Achieve balanced gain of the two signals. The direct conversion radio module 212 can include suitable logic, circuitry, and/or code for amplifying and converting the received analog RF signal to a baseband signal. For example, direct conversion without the 1363514 line module 212 can use a set of amplifiers implemented with low noise amplifiers, a complex in-phase orthogonal signal component mixer, and a low channel filter. The Α/〇 converter 214 can include appropriate logic, circuitry, and/or code for receiving analog signals from the direct conversion radio module 212 and generating corresponding output digital signals that are transmitted to the baseband processor 216. The digital signal will sample the analog signal at a pre-set sampling rate. Baseband processor 216 may include suitable logic, circuitry, and/or code for processing digital signals and generating voice output signals 222 and data output signals 224. In addition, the baseband (the processor 216 can be used to generate an output signal for use by the single weight generator. The single weight generator module 218 uses the output signal to generate a single weight 22〇 for controlling the phase shifter/low The phase shift in the noise amplifier module 208. The voice output signal 222 is further processed by a speech processing unit and/or a digital display processor, respectively. The single weight generator module 218 can include appropriate logic, circuitry, and/or code, such as And for processing the channel function estimation value and the radio frequency signal timing information received from the baseband processor 216, and generating a single weight (SW) 220. The phase shifter/low noise amplifier module 2〇8 can use a single weight 220 The phase signal is received from the antenna 207, and the RF signal is generated in phase with the signal received from the antenna 205. In the operation process, the transmitting H side 2GGa can be used to input the data signal χ1 and the code signal cH. The frequency is then transmitted to the air through the antenna 2〇3. After the button is transmitted to the space t, it may traverse a plurality of different paths or multipaths due to the original of the reflection. The actual time-varying impulse response of each base station's channel is denoted as ^ and h2. The estimated value of the actual pulse response of the channel is expressed as . The transmitted signal can be received through various paths, where the channel of each base station actually changes. The impulse response is represented by ^ and 22 1363514. ib. Bandpass filters 202 and 206 bandpass filter the signals received by antennas 205 and 207, respectively. Additionally, phase shifter/low noise amplifier module 208 can be single weighted. The raw-state module 218 receives the single weight control signal 220 and adjusts the phase of the signal received from the antenna 207 based on the single weight 220. Therefore, the signal received by the antenna 2〇7 will be in phase with the signal received by the antenna 2〇5. In addition, the gain of the two signals received from antennas 205 and 207 will be adjusted to achieve gain balancing at point 210 in receiver side 200b. The RF signal is then processed by direct conversion radio module 212, followed by Further • C amplifies 'and mixes with a VCO §fl number, and/or performs low-pass chopping. The RF analog signal processed by the direct conversion radio module can be converted by the A/D converter 214. The digital signal is transmitted as an input to the baseband processor 216. The baseband processor 216 further processes the round-robin signal to generate a voice signal 222 and a data signal 224. The voice signal 222 can be, for example, a voice processing system. For further processing, the data signal 224 can be further processed by, for example, a display processor. In addition, the baseband processor 216 can also generate a signal that the single weight generator uses to generate a signal weight of 22 〇 G. Although only used in the transmitter side An antenna 2〇3 is used, but the present invention is not limited thereto, and a plurality of transmitting antennas may be used in the present invention. Similarly, a plurality of receiving antennas may be used in the receiver side iOOb. In addition, although the technique of phase adjustment using one weight for one or a plurality of signals is implemented in the receiver side 2〇〇b, the present invention is not limited thereto, and the phase adjustment can also be performed on the transmitter side 2 Implemented in 〇〇a. 3 is a block diagram of a direct conversion radio module in accordance with one embodiment of the present invention. In Figure 3, the direct conversion radio module 3A may include appropriate logic, circuitry, and/or code for amplifying and converting the received analog RF signal to a baseband signal. A specific implementation 23 1363514 In the example, the direct conversion radio module 300 can include a low noise amplifier 3〇4, a voltage controlled oscillator (VCO) 308, a mixer 306 and a low pass filter (LPF) 312. . The low noise amplifier 304 receives the RF signal 302 and amplifies it based on a pre-set gain stage. Voltage controlled oscillator 308 may include suitable logic, circuitry, and/or code for outputting a signal 310 of a particular frequency that may be predetermined or controlled by a voltage signal input to the dust control oscillator. The mixer 3〇6 mixes the house control C oscillator signal with the amplified signal received from the low noise amplifier 304. The low pass filter 312 can include appropriate logic, circuitry and/or code for receiving the mixing signal output by the mixer 3〇6, limiting the frequency of the mixing signal to a predetermined upper limit at a particular frequency. Within the frequency band, the frequency band is then output as baseband signal 314. 4 is a block diagram of a baseband processor that can be used in a system in accordance with one embodiment of the present invention. As shown in FIG. 4, the baseband processor 400 includes a cluster path processor (cpp) module 432, a maximum ratio combining (MRC) module 424, a despreading module 426, a diversity processing C 428, and a macro unit combiner. Module, convolutional encoder module pole and turbine (5) (8) decoder module 440. U.S. Patent Application Serial No. 11/173,854, entitled "Fast Multi-Path Acquisition," which provides a detailed description of the signal cluster, which is incorporated by reference in its entirety. 432 can include a plurality of clustering processes n for receiving and receiving input signal valleys from the analog digital converter (10). In the baseband receiver processing state 400, the cluster path processor in the cluster path processor module &,... 24 1363514 Long-term logarithmic positive signal received by two or more different antennas in the ground, independent of the attenuation path. The macro age set method can be used to merge two or multiple passes through the same A short-term Rayleigh signal obtained from an independent attenuation path received in two or a plurality of different antennas at a receiving location. Convolutional encoder 438 may include appropriate logic, circuitry, and/or code for The output of the 3GPP specification's convolutional solution can be a digital signal, including speech information suitable for the processing of the ridge sound module. The turbo solution _ can include appropriate logic, circuits and/or generations. The code is used to process the decoding of the turbo code according to the 3Gpp specification. The output of the solution can be digitally encoded, including information suitable for use by the video display processor. See Figure 2 and Figure 4, during operation, the transmitter side 2〇 can be used to mix the input data signal XI with the code signal cl and generate an output signal, which is transmitted through different paths in the air by the antenna. Each air path or channel contains a corresponding time-varying impulse response functionΜΑ The channel estimates & and heart provide the actual time of the channel transmitting the received signal «the impulse response estimate. The signals received by antennas 2〇5 and 2〇7 are bandpassed by bandpass choppers 202 and 206, respectively. Filtering and amplifying by a low noise amplifier 2〇4 and a phase shifter/low noise amplifier module, respectively. Further, the phase shifter/low noise amplifier module 208 can receive a single from the single weight generator module 218. The weight control signal 22 is received and the phase of the signal is received from the antenna 207 based on the single weight. In this case, the signal received from the antenna 207 can be in phase with the signal received from the antenna 2〇5. In addition, the gains of the two signals received from the ends 205 and 207 are adjusted such that the receiver side 2 achieves gain balancing at 21 points. 27 1363514 The RF signal is then processed by the direct conversion radio module 212. And further amplifying 'mixing with a VCO signal, and/or performing low-pass filtering. The direct conversion radio frequency analog signal processed by the radio/electric module can be converted into a digital signal by the A/D converter 214. a/j), conversion The digital output of the device 214 is transmitted as an input to the baseband processor 216. The baseband processor 216 further processes the input signal to generate a voice signal 222 and a digital signal 224. The voice signal 222 can be further processed by a voice processing system or device. Signal 224 can be further processed by the display processor. In addition, the baseband processor 216 can also generate a signal, and the single weight generator 218 uses the signal to generate a signal weight 22 〇. The digital signal output of the A/D converter module can be transmitted to the cluster path processor module 432 as an input signal. Cluster Path Processing || Modules then generate channel estimates for the actual time-varying impulse responses for each base station's channel, as well as timing information T for each base station. The estimated channel value of the actual time-varying impulse response of each base (four) channel is calculated by the heart and heart and/or the timing information of each base station is passed to the maximum ratio merging module. The maximum ratio combining module 424 uses the estimated batch-to-batch information τ of each base station to generate an estimate of the transmitted data. The despreading group 426 decouples the estimated signals of each base station to generate an original signal. The diversity processor module 428 provides diversity processing and the macro unit combiner module implements macro diversity. The convolutional code_43_set unit combiner module performs a convolutional decoding of the speech portion of the generated track number and generates a speech output signal 442. The vortex performs convolutional decoding on the signal of the signal generated from the rounding of the macro unit combiner module 43, and generates a data output signal 444. Figure 5 is a flow diagram of the flow according to the steps of the outline-峨·she (four). As shown in Fig. 5, in step 502, a plurality of communication signals are received by an MMO receiver. A control signal is generated in step 504 for controlling the first portion of the received signal. In step 506, the phase 'and/or amplitude' of the first signal portion is adjusted using the control signal such that the phase and/or amplitude of the first signal portion is equal to the second portion of the received signal. In step 508, the phase and/or amplitude adjusted first portion of the received signal is combined with the second portion of the received signal to generate a combined received signal. In step 51, v, the combined received signal is processed to generate a channel estimate of the time varying impulse response of the first and/or second portion of the received signal. At step 512, the single weight generator generates a control signal using the channel estimate of the first and/or second portion of the received signal that is time-varying. The above embodiment describes a method and system for processing signals in a receiver towel. The method includes generating at least one control signal for controlling the first received signal. The phase of the first received signal can be adjusted by using the generated control signal, so that the phase of the first received signal is equal to the phase of the second received signal. The phase of the first received signal is adjusted in a processing path for processing the first received signal. The amplitude of the first received signal may be adjusted by the generated control signal, such that the amplitude of the first received signal is equal to the amplitude of the second received signal, wherein the amplitude of the first received signal is used for processing The adjustment is performed in the processing path of the received signal. The generated control depends on a single weight signal. The phase of the first received signal can be continuously adjusted and/or continuously (four) separated to adjust. The first received signal may be amplified such that the first-order Wei number is scaled to the gain of the second core number 29 1363514. The phase-adjusted first received signal and the second received signal are combined to generate a combined received signal. A channel estimate of the time varying impulse response of the first received signal is generated and a control signal is generated using the channel estimate of the time varying impulse response. The control signal can be generated using one or a plurality of optimization algorithms, such as a maximum signal to noise ratio (SNR) algorithm, a maximum signal to interference noise ratio (SINR) algorithm, and a minimum bit error rate (BEH) algorithm. . Another embodiment of the present invention provides a machine readable memory having stored therein a computer program including at least one portion of code executable by a machine such that the machine performs the steps described above to process signals in the receiver. The system of the present invention includes generating a control signal using a control signal generator, wherein the control signal can be used to control at least a first received signal. The processor adjusts the phase and/or amplitude of the first received signal by using the generated control signal, such that the phase and/or amplitude of the first received signal is equal to the phase and/or amplitude of the second received signal, where the first received signal The phase/amplitude is adjusted in a row for processing the first received signal. The generated control signal includes a single weight signal. The phase of the first received signal can be continuously adjusted and/or adjusted at discrete time intervals. An amplifier amplifies the first received signal such that the gain of the first received signal is equal to the gain of the second received signal. The η parallel combines the phase-adjusted first received signal with the second received signal to generate a combined received signal. The channel estimator generates a channel estimate of the time varying pulse response of the first received signal. The control signal generator generates a control signal using the channel estimate of the time varying impulse response. The control signal generator can use one or a plurality of optimization algorithms to generate the game, such as the most recent _ subtraction (test) method, the maximum signal dry 30 丄 514 disturbance noise ratio (s) algorithm and the smallest error Rate (BER) algorithm. Thus, the invention may be by hardware, software or a combination of hardware and software. The tree can be implemented by at least one computer system _ centralized mode, or by different component 2 in several interconnected electrical functions. Any kind of equipment that can realize the branches (4) and (4) introduced in this application can be turned over. The combination of hardware and software of the Ο type is a computer-oriented computer-oriented system that can be controlled when loaded and executed (4) (10): The method described in this application is implemented. The present invention can also be embedded in a computer program including various features capable of implementing the method of the county. In the mouth, when the program is loaded into a computer system, it can apply for the method described in the county. The computer program described herein refers to, for example, a set of instructions expressed in any language, code, or symbol that can be enchanted to enable a dragon with the ability to handle dragons or a sister to have the following types or various treatments to have Information processing capabilities perform specific functions: a) conversion to another language, code or symbol; b) copying without material. The present application has been described in connection with the present invention, and it is to be understood by those of ordinary skill in the art that various changes or equivalents may be made without departing from the scope of the invention. In addition, various modifications may be made to adapt a particular environment or material to the invention without departing from the scope of the invention. Therefore, the present invention is not limited to the specific embodiments disclosed, and the present invention includes all embodiments of the invention. BRIEF DESCRIPTION OF THE DRAWINGS Figure W is a time-axis diagram of the existing WCDMA specification for increasing the development of the downlink output. 31 1363514 · Figure lb is an HSDpA* dispersion for implementing low-latency link adaptation in accordance with one embodiment of the present invention. Schematic diagram of a structure; FIG. 1c is a display of a first layer control set in a base station for deleting content related to retransmission scheduling and storage in a radio network controller according to an embodiment of the present invention, FIG. A bar graph of the average transmission load of a HSDPA-based macrocell and microcell system according to an embodiment of the present invention; FIG. 2 is a block diagram of a single-weight single-channel system for WCDMA according to an embodiment of the present invention; 3 is a block diagram of a direct conversion wireless module in accordance with one embodiment of the present invention; FIG. 4 is a block diagram of a silk processing of a solid secretable tissue in accordance with the present invention; FIG. 5 is a block diagram of an embodiment of the present invention. A diagram of the steps of processing a signal in a receiver.
【主要元件符號說明】 通用分組無線業務 1〇〇 通用行動通訊系統 1〇4 終端 110、112 無線網路控制器 12〇 行動終端 124 \ 接收器部分 200b GSM的增強資料率技術 高速下行分組接入 基地台 基地台 發射器部分 混頻器 102 106 114 122. 200a 201 32[Main component symbol description] General packet radio service 1〇〇Universal mobile communication system 1〇4 Terminal 110, 112 Wireless network controller 12〇Mobile terminal 124 \ Receiver part 200b GSM enhanced data rate technology High-speed downlink packet access Base station base station transmitter partial mixer 102 106 114 122. 200a 201 32