九、發明說明： 【發明所屬之技術領域】 本發明係有關於一種電源轉換系統，更詳而言之，係 =關於:種應用於電容性負載並使輸出電流之電流值、頻 。及波形X控於輸入電壓之電源轉換系統。 【先前技術】 夕带ί’如第1圖所示包括有負載電容Cl與負載電阻Rl 電谷性負載（如具有臭氧產生器結構特性、電聚產生器 喷嘴結構特性等負載），盆 者 貝戰）八靜態電谷效應不易量測，因此， 、、電谷Cl的電極放電時，整個動態特性變化更為複 雜而導致不易被推斷或量測 般& _ 呵又里/則，且右負載電容Cl的兩極被 而：路％，易使得切換級電力元件損壞。此外，又因 ★載電4 &的電極係持續地反覆進行充放電，故而使得 电路的輸出電流不易被控制。 有鏗於此，目前業界中為了克服上述問題，較常見的 係如第2圖所示’在電路中的電容性負載前端增加一 9n/7 °。 L(其詳細的技術内容請參考美國專利號第 ▲ /0108040) ’然，此電路之輸出電流仍會因負載電容 ，應的動態變化而使得輸出電流不易被控制，如第^至 下圖所不’其係為在負载電阻之電阻值為10ΚΩ之情況 負載電各之電容值分別為以及⑽ 、先連接电路的輸出電流波形示意圖。由圖中可知，對 :輪出負載電容匕之電容值10nF、lOOnF以及l〇〇〇nF之 3出電流的峰值變化係由大約5A至大約繼再至大約 5 110611 1352887 5A ’亦即輪出電流之電流值差異甚大，此外，輸出電流之 頻率與波形亦有相當大的差異。 、，職是，如何提供一種可使輸出電流之電流值、頻率及 波2不致因負載電容之電容值的變化而產生較大的差異 之毛源轉換系統’以避免負载電容的兩極被擊穿而造成短 路進而使得㈣級電力元件損壞，實為此產業中亟待解決 之問題。 、 【發明内容】 鑒於上述|知技術之缺失，本發明之主要目的在於提 供一種使輪出電流之電流值受控於輪入電壓，而不致因電 各性負載之負載電容之電容值的變化而產生較大的差異 =:源轉換系統，以避免電容性負載之負載電容的兩極被 牙而造成短路進而使得切換級電力元件損壞。 ，達上述之目的，本發明之電源轉換系統，係應用於 署:負載’該電源轉換系統包括：電壓調節裝置，係接 用以供調節輸入電壓；電源轉換裝置，係與該電 置電性連接，用以將該㈣調節I置調節過之輸 進行電源轉換程序，並輸出轉換電壓；以及負载調 ^裝置，係料f源㈣裝置以及該電隸負載電性連 :轉該電源轉換裝置所輸出之轉換㈣，並依據 電容性 Ί 調整輸出電流，且輸出該輸出電流至該 可依 110611 6 1352887 輸出電流之負載調節裝置，以使輸出電流之電流值 及波形受控於輪入電壓，而不致因該電容性負载之恭命 谷之電容值的變化而使輸出電流之電流值、 、念电 生，大的差異，俾可避免該電容性負載之負载電容的兩^ 被擊穿而造成短路進而使得切換級電力元 到上述目的。 、呀、错以建 【實施方式】 以下係藉由特定的具體實例說明本發明之每 ，’熟悉此技藝之人士可由本說明 :: 瞭解本發明之其他優點與功效。本發明亦可==易地 的具體實例加以施行戋庫用，太％ aB + 錯由八他不同 基於不同觀點與應用在;項， 修飾與變更。 不障離本發明之精神下進行各種 請參閲第4圖，其係為本發明 例的系統架構干音岡兮； ％原轉換糸統之實施 _= = ==容性 *負載電容。州電阻心：電至= 中所^ 結構特性、電衆產生！^嘴 如為具有臭氧產生器 為限。 構純等負載，但並非以此 如圖所示，本發明之電源棘 裝置10、電源轉換裝置u、負戴财”、1係包括電壓調節 置】3。以下即分別針對本發:置】2以及控制裝 明： 上揭各物件進行詳細說 110611 7 1352887 …該電厘調節裝置10，係接置電源，用以調節輸入電 £，於本貝％例中’該電壓調節裝置！ 〇以及該電源轉換 裝置11分別具有正負兩端。 、 該電源轉換裝置]1，# 直u係與該電壓調節裝置10電性連 接，用以將該電壓調節奘罢1Λ 月即裒置10調節過之輸入電壓進行電 源轉換程序，並輸出轉換電壓；於本實施例中，該電源轉 換裝置11/刀別具有正負兩端，該電源轉換裝置U係可實 施為全橋（fu11 bridge)電源轉換裝置11、半橋（half ^idge)電源轉換裝置η'推挽式（pushpu⑴電源轉換 、置11或具有切換疋件之切換式電源轉換裝置U等且 :，該切換元件係選自金屬氧化層半導體場效電晶體 (曰OSFETs)、雙極性接面電晶體⑻Ts)以及絕緣閘雙極電 晶體（IGBT )之其中一者。 …該控制裝置13,係與該電㈣節裝置1()、該負 :裝置12以，該電容性負載2電性連接，用以接收該電 丨並依據該反饋訊 二^ 的6又定，相應地控制該電壓調節裝置1 〇，以 調節該輪入電壓，俾相應地控制該輸出電流。 該負载調節裝置12,係與該電源轉換裝置u以及該 輸2電性連接，用以接收該電源轉換裝置11所x 土 鈐換電壓，並依據該轉換電壓相應地調整輸出電 Li輸出該輸出電流至該電容性負载2;另請同時參閱 =所示，於本實施例中，該負載調節裝置12包括電 时C、第一電感器L丨以及第二電感器L2,該第一電感器 110611 8 1352887 L!與該第二電咸哭丨 包為L2—端以及該電容器c 一端共同 連接於一點，該電容考Λ ^ 置11負端以及該電容 * 包令性負載2負端，該第一電感器L】另 U連接於該電源轉換裝置u正端，該第 L:另：端電性連接於該電容性負載2正端，其中，該第： :感盗L,與該第二電感器L2之電感值相等，且該負載 節裝置12之共振頻率係為1/，LC，而該電源轉換裝置u 之輸出頻率亦與該負載調節裝置12之共振頻率相等，其 中’L係為該第一電感器匕】或該第二電感器^之電感值， C係為該電容器C之電容值。 ^ 於本發明之另一實施例，該負載調節裝置12包括電 感器以及具有雜散電容與雜散電感之變壓器，該電感哭一 端電性連接於該電源轉換裝置u正端，該電感器另一端 ^生連接於該變麗器一次側正端，以與該變壓器之雜散電 各一端以及雜散電感一端共同電性連接於一點，該變屢器 :次側負端電性連接於該電源轉換裝置u負端以及該; 容性負载2負端，以使該雜散電容另一端電性連接於該電 源轉換裝置11負端以及該電容性負载2負端該變壓哭 二次侧正端電性連接於該電容性負載2正端，以使該雜散 電感另一端電性連接於該電容性負載2正端其中，該電 :器與該變麼器之雜散電感之電感值相等，該負載調;;裝. 置12之共振頻率係為i/ZLC，而該電源轉換裝置u之 輸出頻率亦與該負載調節裝置12之共振頻率相等，其 中，L係為該電感器或該變壓器之雜散電感之電感值，匸 110611 9 丄/ 係為該變壓器之雜散電容之電容值。 右坪：本ί明之再一實施例，該負載調節裴置12包括具 锉Φ電合與雜散電感之變壓器以及電感器’該電感器-拔11連接於錢容性負載2正端，該電感器另—端電性 “於該變壓器二次侧正端，以與該變壓器之雜散電容一 ^以及雜散電感-端共同電性連接於—點，該變屋器_次 電性連接於該電源轉換裝置11正端，以使該雜散 m感另一端電性連接於該電源轉換裝置u正端，該變壓 #二次侧貞端電性連接於該電源轉換裝置11貞端以及該 電合性負載2負端，以使該雜散電容另一端電性連接於該 •電源轉換褒置11負端以及該電容性負載2負端，其中， 電感器與該㈣器之雜散電感之電感值相等，該負載調 節裝置12之共振頻率係為！ //LC，而該電源轉換裝置u 之輸出頻率亦與該負載調節裝置12之共振頻率相等，其 中，L係為該電感器或該變壓器之雜散電感之電感值，c 籲係為該變壓器之雜散電容之電容值。 需予以說明的是，於本發明之另一實施例中的電感器 以及變壓器之雜散電容與雜散電感係分別等效於如第5 圖之實施例中之第一電感L】、電容器c以及第二電感L2，· 而於本發明之再一實施例中的變壓器之雜散電容與雜散 %感以及電感器係分別等效於如第5圖之實施例中之電 各C第一電感Li以及弟二電感L2’因此未另透過圖式 予以呈現本發明之另一實施例以及再一實施例中之詳細 電路結構。 110611 10 +而為了說明本發明之負載調節裒置12是如何依據該 电源轉換裝置11戶斤輸出之轉換電壓（由該該電源轉換襄 置將該電壓調節I置1G調節過之輸人電壓進行電源轉 換=序所得者）相應地調整輸出電流，以下係透過基本電 路刀析及第5圖之符號說明輸入電壓與輸出電流之關係: V^jmLi^-L·^) -----------------------IX. INSTRUCTIONS OF THE INVENTION: TECHNICAL FIELD The present invention relates to a power conversion system, and more particularly, to a current value and frequency applied to a capacitive load and an output current. And the power conversion system with the waveform X being controlled by the input voltage. [Prior Art] As shown in Figure 1, there is a load capacitance Cl and a load resistance Rl. The electric grain load (such as the structure characteristic of the ozone generator, the structural characteristics of the electropolymer generator nozzle), etc. The eight static electric valley effect is difficult to measure. Therefore, when the electrode of the electric valley Cl is discharged, the whole dynamic characteristic change is more complicated, which makes it difficult to be inferred or measured like & _ 呵又里/则, and right The two poles of the load capacitor C1 are: the road %, which is easy to damage the switching stage power component. In addition, since the electrodes of the carrier 4 & continue to be charged and discharged repeatedly, the output current of the circuit is not easily controlled. In view of this, in order to overcome the above problems in the industry, the more common one is as shown in Fig. 2, which increases the front end of the capacitive load in the circuit by 9n/7 °. L (for detailed technical content, please refer to US Patent No. ▲ /0108040). However, the output current of this circuit will still be difficult to be controlled due to the dynamic change of load capacitance and capacitance, as shown in the figure below to the following figure. It is not a case where the resistance value of the load resistance is 10 Ω, and the capacitance values of the load power are respectively (10), and the waveform of the output current of the first connected circuit is shown. As can be seen from the figure, the peak value of the three currents of the capacitors 10nF, 100nF and l〇〇〇nF of the load capacitance 轮 is from about 5A to about 5 110611 1352887 5A ' The current values of the current vary greatly. In addition, the frequency and waveform of the output current are quite different. ,, is, how to provide a hair source conversion system that can make the current value, frequency and wave 2 of the output current not cause a large difference due to the change of the capacitance value of the load capacitance to avoid the breakdown of the two poles of the load capacitance The short circuit which causes the damage of the (four)-level power components is an urgent problem to be solved in this industry. SUMMARY OF THE INVENTION In view of the above-mentioned shortcomings of the prior art, the main object of the present invention is to provide a method for controlling the current value of the wheel current to be controlled by the wheel-in voltage without changing the capacitance value of the load capacitance of the electric load. A large difference is generated = the source conversion system to avoid the short circuit of the load capacitance of the capacitive load caused by the teeth and damage of the switching stage power component. For the above purpose, the power conversion system of the present invention is applied to a load: the power conversion system includes: a voltage regulating device connected to adjust an input voltage; a power conversion device, and the electrical power supply a connection for performing the power conversion program for outputting the (four) adjustment I, and outputting a conversion voltage; and a load adjustment device, the device f source (four) device, and the electric load electrical connection: the power conversion device The output is converted (4), and the output current is adjusted according to the capacitive Ί, and the output current is output to the load regulating device capable of outputting current according to 110611 6 1352887, so that the current value and waveform of the output current are controlled by the wheel-in voltage. Without causing a change in the capacitance value of the capacitive load, the current value of the output current, and the difference in the output current, the two capacitors of the capacitive load can be prevented from being broken down. The short circuit is caused to cause the switching stage power element to achieve the above purpose. DETAILED DESCRIPTION OF THE INVENTION [Embodiment] The present invention is described by way of specific specific examples, and those skilled in the art can understand the other advantages and effects of the present invention. The present invention can also be used for the implementation of the = 易 = = = 太 太 太 太 太 太 太 太 太 太 太 太 太 太 易 易 易 易 易 易 易 易 易 易 易 易 易 易 易 易 易Various embodiments are made without departing from the spirit of the present invention. Please refer to FIG. 4, which is a system architecture of the present invention. The implementation of the % original conversion system _= = == capacitive * load capacitance. State resistance: electricity to = medium ^ structural characteristics, electricity generation! ^ mouth is limited to have an ozone generator. The load is pure and the like, but not as shown in the figure, the power supply ratchet device 10, the power conversion device u, the negative wear", and the 1 system include the voltage adjustment device 3. The following are respectively for the present invention: 2 and the control device: The above-mentioned items are detailed. 110611 7 1352887 ... The electro-optic adjustment device 10 is connected to a power supply for adjusting the input power. In the example of this case, the voltage adjustment device! The power conversion device 11 has positive and negative terminals, respectively. The power conversion device 1 and # are directly connected to the voltage adjustment device 10 for adjusting the voltage, and the device 10 is adjusted. The input voltage is subjected to a power conversion process, and the converted voltage is output. In the embodiment, the power conversion device 11/knife has both positive and negative ends, and the power conversion device U can be implemented as a full-bridge (fu11 bridge) power conversion device 11 , half bridge (half ^idge) power conversion device η 'push-pull type (pushpu (1) power conversion, set 11 or switching power converter U with switching components, etc. and: the switching element is selected from the metal oxide semiconductor field effect One of a crystal (曰 OSFETs), a bipolar junction transistor (8) Ts), and an insulated gate bipolar transistor (IGBT). The control device 13 is connected to the electric (four) device 1 (), the negative device 12, the capacitive load 2 is electrically connected to receive the power and according to the feedback signal, the voltage regulating device 1 相应 is controlled accordingly to adjust the wheeling voltage, correspondingly Controlling the output current. The load adjusting device 12 is electrically connected to the power conversion device u and the power transmission 2 for receiving the voltage exchange voltage of the power conversion device 11 and adjusting the output according to the conversion voltage. The electric current Li outputs the output current to the capacitive load 2; as shown in FIG. 2, in the embodiment, the load adjusting device 12 includes an electric time C, a first inductor L丨, and a second inductor L2. The first inductor 110611 8 1352887 L! and the second electric salty packet are connected to the L2 terminal and the capacitor c end are connected to one point, and the capacitance is set to 11 negative terminal and the capacitor * package load 2 negative terminal, the first inductor L] another U is connected to the electricity a positive end of the conversion device u, the L: another terminal is electrically connected to the positive end of the capacitive load 2, wherein: the:: the thief L, the inductance value of the second inductor L2 is equal, and the load The resonant frequency of the node device 12 is 1/, LC, and the output frequency of the power conversion device u is also equal to the resonant frequency of the load adjusting device 12, where 'L is the first inductor 匕 】 or the second The inductance value of the inductor ^, C is the capacitance value of the capacitor C. ^ In another embodiment of the invention, the load regulation device 12 includes an inductor and a transformer having stray capacitance and stray inductance, the inductor crying One end is electrically connected to the positive end of the power conversion device u, and the other end of the inductor is connected to the positive side of the primary side of the transformer to be electrically connected to one end of the stray electric current of the transformer and one end of the stray inductance In one point, the secondary side is electrically connected to the negative end of the power conversion device u and the negative end of the capacitive load 2, so that the other end of the stray capacitance is electrically connected to the power conversion device 11 Negative end and the negative end of the capacitive load 2 The positive terminal is electrically connected to the positive end of the capacitive load 2, so that the other end of the stray inductance is electrically connected to the positive end of the capacitive load 2, and the stray inductance of the electric device and the variable device The inductance value is equal, the load is adjusted; the resonance frequency of the device 12 is i/ZLC, and the output frequency of the power conversion device u is also equal to the resonance frequency of the load adjustment device 12, wherein L is the inductance The inductance value of the stray inductance of the transformer or the transformer, 匸110611 9 丄 / is the capacitance value of the stray capacitance of the transformer. Right ping: In another embodiment of the present invention, the load regulating device 12 includes a transformer having 锉Φ electrical and stray inductance and an inductor connected to the positive end of the capacitive capacitive load 2 The other end of the inductor is “on the positive side of the secondary side of the transformer, and is electrically connected to the stray capacitance of the transformer and the stray inductance-end. The variator is connected to the sub-electrical connection. The positive end of the power conversion device 11 is electrically connected to the other end of the power conversion device u, and the secondary side of the power conversion device is electrically connected to the power conversion device 11 And the negative end of the electrical coupling load 2, such that the other end of the stray capacitance is electrically connected to the negative end of the power conversion device 11 and the negative end of the capacitive load 2, wherein the inductor is mixed with the (four) device The inductance of the distributed inductance is equal, the resonant frequency of the load adjusting device 12 is @ //LC, and the output frequency of the power conversion device u is also equal to the resonant frequency of the load adjusting device 12, wherein L is the inductance The inductance value of the stray inductance of the transformer or the transformer, c is called the transformer The capacitance value of the stray capacitance of the device. It should be noted that the stray capacitance and the stray inductance of the inductor and the transformer in another embodiment of the present invention are equivalent to those in the embodiment as shown in FIG. 5, respectively. The first inductance L], the capacitor c and the second inductance L2, and the stray capacitance and the spurious % inductance of the transformer in another embodiment of the present invention and the inductor system are respectively equivalent to those in FIG. In the embodiment, the first inductor Li and the second inductor L2' are respectively shown in another embodiment of the present invention and the detailed circuit configuration in still another embodiment. 110611 10 + The load regulating device 12 of the invention is based on the conversion voltage of the power conversion device 11 (the power conversion device is used to convert the voltage adjustment I to 1G to adjust the input voltage for power conversion = order) Adjust the output current accordingly. The following describes the relationship between the input voltage and the output current through the basic circuit analysis and the symbol in Figure 5: V^jmLi^-L·^) ------------- ----------
~]^(h~h)= J^Li2+V2 (2) 由方程式（2)分解可得： 如灿2 ★沁 LCi2 +i2 + /crt：K2 +JmC^ κ 將方程式（3)代入方程式（1)可得：~]^(h~h)= J^Li2+V2 (2) Decomposed by equation (2): 灿2 ★沁LCi2 +i2 + /crt:K2 +JmC^ κ Substituting equation (3) into the equation (1) Available:
心>2+赠2]+忐卜㈣2 + w]_^ jwn4-rtc乂+“坤2+逆2____________。 若操作頻率與LC共振頻率相等則(me)二〇 因此’由方程式（3)及（4)可得： 0 JtuL jtsiC 〇 κ -l2. Ο JZm .1 Λ JT 0 ν2 λ. (5) ζ. 其中 由上述之推導可知本發明之電源轉換系統丨係可利 110611 11 丄JJZOO/ 用輸入電壓v】來控制輸出電流“。 再如第6A至6D圖户斤+ #〆、、 ^ έ ,、’，、糸为別為藉由本發明之電 —，且輸入電屋為不同4，丄？容之電容值為 流波形示意圖。如“An 4值之方波訊號時的輸出電 圖所不，輸入電壓係為400V的方 / :广輪出電流峰值約為81A，如第6β圖所 入電壓係為300V的方波雷厭 一 /皮電壓，其輸出電流峰值約為6Α， 雷，所7F ’輸入電壓係為2_的方波電壓，其輸出 峰值f為4. 1A ’如第⑽圖所示’輪人電壓係為聊 的方波電壓’其輸出電流峰值約為2 ia，藉此可得知， 輸出電流係受控於輸人電壓，錄出電流之電流值係與輸 入電壓之電壓值成正比。 又請參閲第7A至7C圖，其係分別為藉由本發明之電 源轉換系統應用於電容性負載之負載電阻之電阻值為 10ΚΩ之情況下，負載電容之電容值分別為ι〇ηρ、ι〇〇π 以及lOOOnF的輸出電流波形示意圖。由圖中可知，對應 電容性負載2之負載電容之電容值1〇nF、i〇〇nF以及 lOOOnF之輪出電流的波形皆近似為弦波，且電流之頻 率、峰值變化彳艮小。 、 綜上所述’本發明之電源轉換系統主要係透過可依據 該電壓調節裝置調節過後之輸入電壓相應地調節輸出電 流之負載調節裝置，以使輸出電流之電流值、頻率及波形 受控於輸入電壓，相較於習知技術，係可避免習知技術中 因電容性負載之負載電容之電容值的變化而使輪出電流 110611 12 1352887 之電流值、頻率及波形產生較大的差異，俾 之負㈣容的兩極被擊穿而造成短路 ^ '裁 力元件損壞。 叨便评切換級電 #用=*實施例僅㈣性說明本發明之原理及|功效’而 =限制本發明。任何熟習此項技藝之人士均可二： 背本發明之精神及範轉 在不延 變。因此，太心 述貫施例進行修飾與改 ^因此本發明之權利保護範圍，應 範圍所列。 <〈τ明專利 【圖式簡單說明】 f 1圖係為習知技術之電容性負載示意圖； 弟2圖係為習知技術為了克服電容性負载所產生之 問題所揭示的電路結構之示意圖； 、兄下第/^%圖係為在負载電阻之電阻值為刪之情 容之電容值分別為1〇，咖以及_ 傳:先連接電路的輸出電流波形示意圖； 牟槿第人圖係為本發明之電源轉換系統之實施例的系統 架構不意圖； f 5圖係為本發明之電源轉換系統中的負載調節裝 置之貫施例的電路架構示意圖； 弟6A至6D圖係分別氣訪丄 刀別為藉由本發明之電源轉換系統應 =電容性負載之負載電容之電容值為i〇〇nF，且輸入電 -為不同電[值之方波訊號時的輸出電流波形示意圖；以 及 第7A至7C圖係分別為藉由本發明之電源轉換系統應 110611 13 1352887 用於電容性負載之負載電阻之電阻值為1 OK Ω之情況 下，負載電容之電容值分別為10nF、100nF以及lOOOnF 的輸出電流波形示意圖。 【主要元件符號說明】 1 電源轉換系統 10 電壓調節裝置 11 電源轉換裝置 12 負載調節裝置 • 13 控制裝置 2 電容性負載 14 110611Heart >2+2]+忐(4)2 + w]_^ jwn4-rtc乂+"Kun 2+ inverse 2____________. If the operating frequency is equal to the LC resonance frequency, then (me) 〇 〇 ' 'by equation (3) And (4) available: 0 JtuL jtsiC 〇κ -l2. Ο JZm .1 Λ JT 0 ν2 λ. (5) ζ. Which is derived from the above derivation, the power conversion system of the present invention is available, 110611 11 丄JJZOO / Use the input voltage v] to control the output current ". For example, in Figures 6A to 6D, the figures are + #〆, , ^ έ , , ', 糸, which is the electricity of the present invention, and the input electricity house is different 4, 丄? The capacitance value of the capacitor is a schematic diagram of the flow waveform. For example, the output voltage of the square wave signal of the An 4 value is not, the input voltage is 400V / the peak of the wide current is about 81A, and the voltage of the 6th figure is 300V. A / skin voltage, the output current peak value is about 6 Α, Ray, 7F 'input voltage is 2 _ square wave voltage, the output peak f is 4. 1A 'as shown in Figure (10) 'wheel voltage is The square wave voltage of the chat 'the output current peak is about 2 ia. It can be known that the output current is controlled by the input voltage, and the current value of the recorded current is proportional to the voltage value of the input voltage. Referring to Figures 7A to 7C, respectively, the resistance values of the load resistors applied to the capacitive load by the power conversion system of the present invention are 10 Κ Ω, and the capacitance values of the load capacitors are ι 〇 ρ, ι π, respectively. And the output current waveform diagram of lOOOnF. As can be seen from the figure, the waveforms of the capacitance values of the load capacitances corresponding to the capacitive load 2, 1〇nF, i〇〇nF, and lOOOnF are approximated as sine waves, and the frequency of the current The peak change is small. The power conversion system mainly controls the load current adjusting device according to the input voltage adjusted by the voltage regulating device, so that the current value, frequency and waveform of the output current are controlled by the input voltage, compared with the conventional one. The technology can avoid the variation of the capacitance value of the load capacitance of the capacitive load due to the change of the capacitance value of the load capacitance of the capacitive load in the prior art, and the difference between the current value, the frequency and the waveform of the wheel current 110611 12 1352887 is large, and the negative poles of the negative (four) capacitance are Breakdown causes a short circuit ^ 'The trimming element is damaged. 叨 评 切换 级 电 # 用 * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * * Yes 2: The spirit and scope of the invention are not extended. Therefore, the modification of the invention is modified and modified. Therefore, the scope of protection of the present invention should be listed in the scope of the invention. Brief description of the formula] The f 1 diagram is a schematic diagram of the capacitive load of the prior art; the second diagram is a schematic diagram of the circuit structure disclosed by the prior art in order to overcome the problem caused by the capacitive load. Intention; Brother, the /^% diagram is the capacitance value of the load resistance is deleted, the capacitance value is 1〇, coffee and _ transmission: the output current waveform diagram of the first connected circuit; The system architecture of the power conversion system of the present invention is not intended; f 5 is a schematic diagram of the circuit architecture of the load regulation device in the power conversion system of the present invention; the brothers 6A to 6D are separately gas The access tool is a power conversion system according to the present invention. The capacitance value of the load capacitance of the capacitive load is i〇〇nF, and the input power is a schematic diagram of the output current waveform when the square wave signal of different values is used; 7A to 7C are respectively the power supply conversion system of the present invention, 110611 13 1352887, and the load resistance of the load resistor for the capacitive load is 1 OK Ω, and the capacitance values of the load capacitance are 10 nF, 100 nF, and 100 OnF, respectively. Schematic diagram of the output current waveform. [Main component symbol description] 1 Power conversion system 10 Voltage regulation device 11 Power conversion device 12 Load adjustment device • 13 Control device 2 Capacitive load 14 110611