1325681 調變不同VP f d c輸出電麼之功能，故仍存有進—步改良之空間。 斗古^於’,第三圖所示者，係為f用昇㈣功率因數校正器輪出電塵之設 雷^，當輸入電壓Vi a C由9〇Va C變化至2 6 4Va c時，輸出 P f d C 一般都固定在某—電麼（3 6 Q v〜3 8 0 V)，因此在輸 電壓之範圍如此寬廣之情況下，較高輸入龍即可獲致較佳之效率，而 固ίΐΐΤί低電壓狀況(例如9 0V3 C)時，需將其電壓昇至較高之 壓（3 6 0 V〜3 8 〇 V)，而其之間的電㈣絲大，電源整體效 率自然而然就會偏低。 【發明内容】 本發明「具功率隨調整之電源供齡統」，係為—種結合雜型功率 校正H的高效率電_換電触構，藉由機控㈣M型功率因數校 之輸出電壓的動作，可以達成電源供應器整體效率之提高，並克服丁 電1之問題’使其更適合顧於較大功率之輸出與較寬廣之輸入 【實施方式】 ^能使貴審查委員清楚本發明之電路架構組成，以 式，兹配合圖式說明如下： 構组「具功率因數調整之電源供應系統」，其電源供應係統之電路架 四圖所示，乃係由謂1驗器1 0、整流與舰電路2 〇、 Γ因數校正器3 〇與非對稱半橋轉換器5 ◦所組成；其中，直流 於，換器電路即係採用非對稱半橋轉換器5 0之電路架構為主；至 功率因數校正器3 Q之電路内部餘有功率因數校正控制器3 in;授控制電路32 ’並且加入調變控制vp f d。輸出電壓 ㈣n 一制即藉由此電路與輸出電壓迴授控制電路3 2結合來予以 =制功率因數校正控制器3 i之功週u 達到調變不同Vpf dc之輸出電壓。 Kie)使其 轉換1=:2半橋轉換器5 〇,電路架構係可以為非對稱半橋順向式 效率可i以提高飞返驰式轉換器之電路架構，如此搭配電源供應器整體 6 1325681 如第五圖至第七圖所示，係為本發明中非對稱半橋順向式轉換器之各 實施方式之電路架構示意圖，整個非對稱半橋順向式轉換器之電路架構係 在單一變壓器τ1 (第五、六圖之實施例所示）或串聯之變壓器τ1、τ 2 (第七圖之實施例所示）之輸入一次側與由PWM控制電路I C1、驅 動控制電路I C 2所構成之控制電路之間設有主開關元件q1以及副開關 元件Q 2，主開關元件(3丄之兩接點之間係配設有第一寄生二極體D工與 第寄生電谷C1’其副開關元件Q2之兩接點之間係配設有第二寄生二 極體D 2與第二寄生電容c 2 ’並且分別在主開關元件Q1以及副開關元 件Q2其中一接點之通路處設有第一飽和電感L丄與第二飽和電感匕2， 而其變壓HT1、T2之控制電路則係藉由PWM控制電路Ic1與驅動 控制電路I C 2來相實現；另外，於變壓器τ丨、T2與控制電路之間 外加一f皆振電感L3與一阻隔電容c3。 俾由谐振電感L 3用以達成諧振功能，以令變壓器τ1、τ 2之漏咸 以及第一寄生電容c i與第二寄生電^ 2，在開關之間的J == d time)產生共振，以分別達到主開關元件Q1與副開關元件口已的 零電壓切換。又，阻隔電容c3(bl〇cking㈡…… r )，由於其值足夠大，跨於其上之電壓可視為定值。 至於，變壓器Τ1、T2之輸出二次側則係由變壓器τ丄、T2之次 級繞組加上第—整流二極體D3與第二整流二極體D4，或是採用第一同 步整流開關Q 3與第二同步整流關Q4，以及由第—驗電容C4、第 ;慮波電谷C 5與遽波電感L 4所組成之整流濾波電路所逹成。 在此電路架構中’主開關元件…與副開關元件Q2之工作週期㈠ 二|y C Υ c 1 e)不相同，而為互補之情況，因此稱之為非對稱之架 拖哭另1 卜⑧如第人圖至第十—騎示，係為本發财非對稱半橋返馳式轉 換器之各實施方式之電路架構示_，整個非對稱半橋返驰式轉換器 器”、下丄第圖之實施例所示）或串並聯之變壓 、"Ί實齡!解）之輸人—:欠顺&PWM控 制電路1 C1、驅動控制電路1 C 2所構狀控制電路之間設有主開關元 1325681 件Q1以及副開關元件Q2，而其所謂串並聯之變壓器T1、τ2乃係在 變壓器Τ1、丁2之一次側繞組係為串聯方式，而變摩器τ1、Τ2之二 -人側變壓器繞組則為並聯方式，使其功率可以平均分攤於其上。 其中，主開關元件q1之兩接點之間係配設有第一寄生二極體D1與 第一寄生電容C1，其副開關元件Q2之兩接點之間係配設有第二寄生二 極體D 2與第二寄生電容c 2，並且分別在主開關元件(3丄以及副開關元 件Q2其中一接點之通路處設有第一飽和電感L1與第二飽和電感L2， 而其變壓器T1與變壓器τ 2之控制電路則係藉由PWM控制電路I C1 •與驅動控制電路I C2來予以實現；另外，於變壓器τΐ、T2與控制電 φ 路10之間外加一諧振電感L 3與一阻隔電容C 3。 俾由諧振電感L3用以達成諧振功能，以令變壓器τ1、T2之漏感 乂及第寄生電谷C1與第一寄生電容C 2 ’在開關之間的盲時（d e a d t ime)產生共振，以分別達到主開關元件qi與副開關元件的 零電壓切換。又，阻隔電容c3(blocking capacit〇 r )，由於其值足夠大，跨於其上之電壓可視為定值。 至於’變壓器Τ1、丁2之輸出二次側則係由變壓器Τ1、T2之次 級繞組加上配合變壓器τ^、丁2所附加之整流二極體（圖式中以第一整 流二極體D 3與第二整流二極體D4加以區分），以及由第一濾波電容C 鲁 4、第二遽波電容c 5與濾波電感l 4所組成之整流濾波電路2 〇所達 成，又’變壓器Τ1、T 2之輸出二次侧配合變壓器丁1、τ 2所外加整 流二極體亦可以由同步整流開關（圖式中係以第一同步整流開關Q 3與第 一同步整流開關Q4加以區分）所替代。在此電路架構中，主開關元件Q 1與副開關元件Q2之工作週期（d u t y c y c 1 e)不相同，而為 互補之情況，因此稱之為非對稱之架構。 前述之非對稱半橋轉換器不論是屬於非對稱半橋順向式轉換器或非對 稱半橋返馳式轉換器之電路架構，皆可達成開關的零電壓導通，使其切換 損失能予以降低，並且在多重變壓器疊家使用兩顆變壓器時可以將此磁性 元件予以薄型化’並將其所消耗之功率適度分散在兩顆變壓器上，不致於 造成變壓器過熱之問題產生。 1325681 調變控制VD f d Ίφ〔在^型功率因數校正器3 0之電路内部加入 源供應=路3 3 ’用來補償低電壓輸人情況下，電 工作週期nr 罐迴授控制電路互相結合，用來控制其 dc之目的。y c y c 1 e )，達到調變昇壓型電路輸出電壓f =要調變V p f d c輸出電壓在策略上設計發明各種不同之方式 升’例如第十二圖所提出之第—種策略方法就是將h f 電壓範圍q ^成―段¥ P f d C 1與V P f d C 2 ’也就是說在低輸入 電壓細9 〇 Va C〜V i以1之間，.P f d c僅昇壓至Vp f d cl^^t^®Vical^2 64Vca^^.mVpfd c幵壓至較高之Vp f d c 2。 如第十二圖所提出的策略方法就是將當輸人電壓在9 〇 V a c〜v 土 a c 1之間改變時，Vp f d c之輸出電壓會隨著輸人電壓之變化而線性 調變’而輸入電壓在V i a c 1〜2 6 4 V a c之間，輸出電壓則維持在 固定Vp f d c 2。 在第十四圖所提出的策略方法就是將當輸入電壓在9 〇v a c〜v 土 a c 1之間改變時，輸出電壓則維持在固定Vp f d c丄，而輸入電壓在 V1 a c 1〜V1 a c 2之間，Vp f d c之輸出電壓會隨著輸入電壓之 變化而線性調變，而至於輸入電壓在v iac2〜264Vac之間，輸 出電壓則維持在固定Vp f d c 2。 在第十五圖所提出的策略方法就是將當輸入電壓在9 〇 v a c〜2 6 4V a c之間改變時，v p f d c之輸出電壓會隨著輸入電壓之變化而線 性調變。 在第十六圖所提出的策略方法就是將當輸入電壓在9 〇Va c〜V i a c 1之間改變時’輸出電壓則維持在固定vp f d c 1，而輸入電壓在 Viacl〜264Vac之間，V p f d c之輸出電壓會隨著輸入電壓 之變化而線性調變。 最後在第十七圖所提出的策略方法就是將當輸入電壓在9 〇v a c〜 V1 a c 1之間改變時，輸出電壓則維持 viacl〜Viac2之間，輸出小而輸入電 c2，而至於輸入電麼在Vi acl〜264v、.^P_Vpfd 持在固定vp f d c 3。 a c之間，輪出電壓則維 藉由以上所提之策略方法，其電路之實現 =電==之非對稱半橋順向式 此登體之電源即可獲至較好之效率；當然後級之 电岭如 馳式路定猶Γ驰式、順向式或半橋式之可结為構變頻返 轉換電路架構，不但ΐ提器的高效率電源 m m的問題，更可經由效率之提高而達到使其產 植柄小之目的，爰依法提呈發明專利之中請；惟，以上之實施說 明及圖式所示，係、本發曝佳實施例之-者 β5 舉凡與本發明之構造、裝置 μ匕·本發月’疋以’ 設目的及巾請專利顧^置。特鮮独或相制者，均麟本發明之創 【圖式簡單說明】 =-圖係為㈣具有型辨隨校正_電_肺電路方塊圖。 之==有昇壓型功率因數校正器的電源轉換器應用在咖 第三圖係為習用昇壓型功率因數校正器輸出龍之策略設計圖。 第四圖係為本㈣之基本電路架構示意圖。 第五圖係為本發明中非對稱半橋順向式轉換器第一實施例之電路架構示意 圖0 意 第八圖係為本發明中非對辭橋順向式轉換器第二實施例之電路架構示 圖。 示意 第七圖係為本發明中非對稱半橋順向式轉換器第三實施例之電路架構 圖。 第圖係為本發曰月中非對稱半橋返馳式轉換器第一實施例之電路架構示意 ΐ九圖係為本發日种_辭橋返驰式轉換器第二實施例之電路架構示意 ^Η係為本發明t非對稱半橋返馳式轉換器第三實施例之電路架構示意 係為本發財雜鮮橋返赋轉難第四實酬之電路架構示 輸出電壓之策略設計之一 輸出電壓之策略設計之二 輸出電壓之策略設計之三 輸出電壓之策略設計之三 輸出電壓之策略設計之四 輸出電壓之策略設計之五 c ，十—圖係為本發明中用以調變V p亡d c 第十二圖係為本發明中肋調變Vp f d c f十四圖係為本發明中用以調變Vp f d c 第十五圖係為本發明中用以調變Vp f d c 第十，、圖係為本發明中用以調變Vp f d 第十七圖係為本發明中用以調變Vp f d •第一寄生電容 •第二寄生電容 •阻隔電容 •第一濾波電容 •第二濾波電容 •第一寄生二極體 •第二寄生二極體 .第一整流二極體 .第二整流二極體 .PWM控制電路 •驅動控制電路 .第一飽和電感 .第二飽和電感 •諧振電感 【主要元件符號說明】 c 1 · ·......... C2 . . . ·.. 參 ♦參 ♦秦 C3 ·.......... C4 ·.......... C5 ·.......... D1 ........... D2 · .......: · · D3 ·.......:. D4 . ·......: . · I C1.......' .. I C2 .......... L 1 -.......... L2 ·.......... L 3 ..... 1325681 L 4............濾波電感 Q 1............主開關元件 Q2............副開關元件 Q 3............第一同步整流開關 Q4............第二同步整流開關 T 1............變壓器 T 2............變壓器 ' 10............EMI濾波器 2 0............整流與濾波電路 ^ 3 0............昇壓型功率因數校正器 3 1............功率因數校正控制器 3 2............輸出電壓回授控制電路 3 3..........昇壓型電路輸出電壓Vp f d c調變控制電路 4 0............脈波寬度調變直流對直流轉換器 5 0............非對稱半橋轉換器 121325681 Modulates the function of different VP f d c output power, so there is still room for further improvement.斗古^于', as shown in the third figure, is the settling of the electric dust by the volt (four) power factor corrector, when the input voltage Vi a C changes from 9〇Va C to 2 6 4Va c The output P fd C is generally fixed at a certain voltage (3 6 Q v~3 8 0 V), so in the case where the range of the transmission voltage is so wide, the higher input dragon can obtain better efficiency, and the solid ίΐΐΤί When low voltage conditions (such as 90 V3 C), the voltage needs to be raised to a higher voltage (3 60 V~3 8 〇V), and the power between them is large, and the overall efficiency of the power supply will naturally Low. SUMMARY OF THE INVENTION The present invention is a high-efficiency electric-electrical contact structure with a hybrid power correction H, which is a machine-controlled (four) M-type power factor output voltage. The action can achieve the improvement of the overall efficiency of the power supply, and overcome the problem of Dingdian 1 'making it more suitable for the output of larger power and wider input [embodiment] ^ can make the review committee clear the invention The circuit structure is composed of the following formula: The following is a description of the following: The construction of a power supply system with power factor adjustment, the circuit diagram of the power supply system shown in Figure 4, is the first detector 100. The rectifying and ship circuit 2 〇, the Γ factor corrector 3 〇 and the asymmetric half bridge converter 5 ; are formed; wherein, the DC converter circuit is mainly composed of an asymmetric half bridge converter 50 circuit structure; The power factor correction controller 3 in is left inside the circuit to the power factor corrector 3 Q; the control circuit 32' is taught and the modulation control vp fd is added. The output voltage (4) n system is combined with the output voltage feedback control circuit 32 to make the power cycle of the power factor correction controller 3 i to reach the output voltage of the different Vpf dc. Kie) makes it convert 1=:2 half-bridge converter 5 〇, the circuit architecture can be asymmetric half-bridge forward efficiency can improve the circuit structure of the flyback converter, so with the power supply overall 6 1325681 is a schematic diagram of the circuit architecture of the embodiments of the asymmetric half-bridge forward converter in the present invention, as shown in the fifth to seventh embodiments. The circuit architecture of the entire asymmetric half-bridge forward converter is The input primary side of the single transformer τ1 (shown in the fifth and sixth embodiments) or the series connected transformers τ1, τ 2 (shown in the seventh embodiment) and the PWM control circuit I C1 and the drive control circuit IC 2 A main switching element q1 and a sub-switching element Q 2 are disposed between the control circuits, and the main switching element (the first parasitic diode D and the parasitic electric valley C1 are disposed between the two contacts) 'The second parasitic diode D 2 and the second parasitic capacitance c 2 ' are disposed between the two contacts of the sub-switching element Q2 and are respectively connected to one of the main switching element Q1 and the sub-switching element Q2. Where the first saturation inductance L丄 and the second saturation inductance 匕2 are The control circuit of the transformer HT1 and T2 is realized by the PWM control circuit Ic1 and the drive control circuit IC 2; in addition, an inductor F3 and a blocking capacitor are applied between the transformers τ丨, T2 and the control circuit. C3. 谐振 The resonant inductor L 3 is used to achieve the resonance function, so that the leakage of the transformers τ1 and τ 2 and the first parasitic capacitance ci and the second parasitic capacitance 2, J == d time between the switches are generated. Resonance to switch to the zero voltage of the main switching element Q1 and the sub-switching element port respectively. Also, the blocking capacitor c3 (bl〇cking(b)...r), since its value is sufficiently large, the voltage across it can be regarded as a constant value. As for the secondary side of the output of the transformers Τ1 and T2, the secondary windings of the transformers τ丄 and T2 are added with the first-rectifying diode D3 and the second rectifying diode D4, or the first synchronous rectifying switch Q is used. 3 and the second synchronous rectification off Q4, and the rectification filter circuit composed of the first verification capacitor C4, the first wave capacitance C 5 and the chopper inductor L 4 . In this circuit architecture, the 'main switching element...' and the sub-switching element Q2 have different duty cycles (1), 2|y C Υ c 1 e), and are complementary. Therefore, it is called an asymmetric frame. 8 such as the first person to the tenth - riding, is the circuit architecture of the various embodiments of the asymmetric half-bridge flyback converter of the fortune _, the entire asymmetric half-bridge flyback converter", under所示 之 之 之 之 或 或 或 或 或 或 或 或 或 或 或 丄 丄 实施 丄 实施 — — — — — : : : : : : : : : : : : PWM PWM PWM PWM PWM PWM PWM PWM PWM PWM PWM PWM PWM PWM There are a main switch element 13256681 piece Q1 and a sub-switch element Q2, and the so-called series-parallel transformers T1 and τ2 are connected in series in the primary winding of the transformer Τ1, D2, and the variator τ1, Τ2 The second-human-side transformer winding is in parallel mode, so that its power can be evenly distributed on it. Among them, the first parasitic diode D1 and the first parasitic capacitance are arranged between the two contacts of the main switching element q1. C1, the second parasitic diode D 2 and the second are disposed between the two contacts of the sub-switching element Q2 The parasitic capacitance c 2 and the first saturation inductor L1 and the second saturation inductor L2 are respectively disposed at the path of one of the main switching elements (3丄 and the sub-switching element Q2), and the control of the transformer T1 and the transformer τ 2 The circuit is realized by the PWM control circuit I C1 • and the drive control circuit I C2 ; in addition, a resonant inductor L 3 and a blocking capacitor C 3 are applied between the transformers τ ΐ, T2 and the control φ path 10 . The resonant inductor L3 is used to achieve a resonance function to resonate the leakage inductance of the transformers τ1 and T2 and the dead time between the parasitic electric valley C1 and the first parasitic capacitance C 2 ′ in the switch, respectively. The zero voltage switching of the main switching element qi and the sub-switching element is reached. Further, the blocking capacitor c3 (blocking capacit〇r), because its value is sufficiently large, the voltage across it can be regarded as a fixed value. As for 'transformer Τ1, Ding 2 The secondary side of the output is the secondary winding of the transformer Τ1, T2 plus the rectifying diode attached to the transformer τ^, D2 (in the figure, the first rectifying diode D 3 and the second rectifying diode 2) Polar body D4 is distinguished), and by A filter capacitor C Lu 4, a second chopper capacitor c 5 and a filter inductor 14 composed of a rectifying and filtering circuit 2 达成 are achieved, and the 'transformer Τ1, T 2 output secondary side is matched with the transformer D1, τ 2 The external rectifying diode can also be replaced by a synchronous rectification switch (in the figure, the first synchronous rectification switch Q 3 is distinguished from the first synchronous rectification switch Q4). In this circuit architecture, the main switching element Q 1 and the vice The duty cycle (dutycyc 1 e) of the switching element Q2 is different, and is complementary, so it is called an asymmetric structure. The aforementioned asymmetric half-bridge converter, whether it is an asymmetric half-bridge forward converter or an asymmetric half-bridge flyback converter, can achieve zero-voltage conduction of the switch, so that the switching loss can be reduced. And when the two transformers use two transformers, the magnetic components can be thinned' and the power consumed by them is moderately dispersed on the two transformers, so that the problem of overheating of the transformer is not caused. 1325681 Modulation control VD fd Ίφ [in the ^ power factor corrector 3 0 circuit inside the source supply = road 3 3 ' used to compensate for low voltage input, the electric duty cycle nr tank feedback control circuit combined with each other, Used to control the purpose of its dc. Ycyc 1 e ), reaching the output voltage of the modulation boost circuit f = to modulate the V pfdc output voltage is strategically designed in a variety of different ways. For example, the first strategy proposed in the twelfth figure is to hf The voltage range q ^ becomes - segment ¥ P fd C 1 and VP fd C 2 'that is, at a low input voltage, 9 〇Va C~V i is between 1, and .P fdc is only boosted to Vp fd cl^^ t^®Vical^2 64Vca^^.mVpfd c is pressed to a higher Vp fdc 2 . The strategy proposed in Figure 12 is to change the output voltage of Vp fdc linearly with the change of the input voltage when the input voltage is changed between 9 〇V ac~v soil ac 1 ' The input voltage is between V iac 1 and 2 6 4 V ac and the output voltage is maintained at a fixed Vp fdc 2 . The strategy proposed in Figure 14 is to maintain the output voltage at a fixed Vp fdc丄 and the input voltage at V1 ac 1~V1 ac 2 when the input voltage is varied between 9 〇 vac and v ac 1 . Between, the output voltage of Vp fdc is linearly changed with the input voltage, and the output voltage is maintained at a fixed Vp fdc 2 as the input voltage is between v iac2 and 264Vac. The strategy proposed in the fifteenth figure is that when the input voltage is changed between 9 〇 v a c~2 6 4V a c , the output voltage of v p f d c is linearly modulated as the input voltage changes. The strategy proposed in Figure 16 is to keep the output voltage at a fixed vp fdc 1 and the input voltage between Viacl and 264Vac when the input voltage is changed between 9 〇Va c and V iac 1 . The output voltage of pfdc is linearly modulated as the input voltage changes. Finally, the strategy proposed in Figure 17 is to change the output voltage between 9 〇 vac and V1 ac 1 while maintaining the output voltage between viacl and Viac2. The output is small and the input power is c2. In Vi acl~264v, .^P_Vpfd is held in fixed vp fdc 3. Between ac, the voltage of the turn-off is achieved by the above-mentioned strategy method, the realization of the circuit = electric == asymmetric half-bridge forward, the power of the board can obtain better efficiency; The level of the electric ridge is like a chirp type, the forward type or the half bridge type can be combined into a variable frequency return conversion circuit structure, which not only raises the high efficiency power supply of the extractor, but also improves the efficiency. In order to achieve the purpose of making the plant handle small, the invention patent is required to be submitted according to law; however, as shown in the above description and drawings, the method of the present invention is the same as that of the present invention. Structure, device μ匕·本发月'疋's purpose and towel, please take care of the patent. Special fresh or phased, Jun Lin's invention [Simplified illustration] =- The system is (4) Having the type discrimination correction _ electricity _ lung circuit block diagram. == Power converter with boost power factor corrector is used in the third diagram is the strategic design of the output of the conventional boost factor power factor corrector. The fourth figure is a schematic diagram of the basic circuit architecture of (4). The fifth figure is a schematic diagram of the circuit architecture of the first embodiment of the asymmetric half-bridge forward converter of the present invention. The eighth figure is the circuit of the second embodiment of the non-symmetric bridge forward converter of the present invention. Schematic diagram. BRIEF DESCRIPTION OF THE DRAWINGS Figure 7 is a circuit diagram of a third embodiment of an asymmetric half-bridge forward converter of the present invention. The figure is a schematic diagram of the circuit architecture of the first embodiment of the asymmetric half-bridge flyback converter in the present month. The circuit diagram of the second embodiment of the present invention is the circuit architecture of the second embodiment. The schematic diagram of the circuit structure of the third embodiment of the t-symmetric half-bridge flyback converter of the present invention is a strategic design of the output voltage of the circuit structure of the fourth real remuneration. The strategy of designing an output voltage, the design of the output voltage, the design of the output voltage, the design of the output voltage, the design of the output voltage, the design of the output voltage, the c, the ten-graph is used to modulate the invention. V p dc The twelfth figure is the rib modulation Vp fdcf of the present invention is used to modulate Vp fdc in the present invention. The fifteenth figure is used to modulate Vp fdc in the present invention. The figure is used to modulate Vp fd in the present invention. The seventeenth figure is used to modulate Vp fd in the present invention. • First parasitic capacitance • Second parasitic capacitance • Barrier capacitance • First filter capacitor • Second filter Capacitor • First Parasitic Dipole • Second Parasitic Dipole First rectifying diode, second rectifying diode, PWM control circuit, drive control circuit, first saturation inductor, second saturation inductor, resonant inductor [main component symbol description] c 1 · ·..... .... C2 . . . ·.. Participate in ♦ ♦ Qin C3 ·.......... C4 ·.......... C5 ·........ .. D1 ........... D2 · .......: · · D3 ·.......:. D4 . ·......: . C1.......' . . I C2 .......... L 1 -........ L2 ·.......... L 3 ..... 1325681 L 4............Filtering inductance Q 1............Main switching element Q2.......... .. sub-switching element Q 3 .........the first synchronous rectifying switch Q4 .........the second synchronous rectifying switch T 1 ... ...transformer T 2............transformer '10............EMI filter 2 0......... ...rectification and filter circuit ^ 3 0............Boost type power factor corrector 3 1............power factor correction controller 3 2 ............output voltage feedback control circuit 3 3.......... boost type circuit output voltage Vp fdc modulation control circuit 4 0... ... pulse width modulation DC to DC converter 5 0............ asymmetric half Converter 12