TWI323112B - Ofdm receiver and co-channel interference detecting method - Google Patents

Description

1323112 IX. Description of the Invention: [Technical Field] The present invention relates to an orthogonal frequency division multiplexing (OFDM) receiver, and more particularly to a terrestrial television terrestrial broadcast ( Digita丨Video Broadcasting—Terrestria DVB-T) Orthogonal Frequency Division Multiplexer Receiver. [Prior Art] In the field of digital communication, modulation and modulation techniques for orthogonal frequency division multiplexing are widely used in various applications. Fig. 1 is a diagram showing a digital television terrestrial broadcasting system 10 generally applied to Digital Terrestrial Transmission (DTT). The digital television terrestrial broadcasting system includes an OFDM transmission system 11 and an orthogonal frequency division multiplexing receiver 12. During digital terrestrial broadcasting system 1 地面 during terrestrial transmission, multi-path fading and co-channel interference (CCI) often occur, resulting in the transmission of the patriarchal transmission system. Distortion of the signal (emittecl signai) s(t). For example, please refer to Figure 2A. When an analog TV signal (TV signal) and a quadrature frequency division multiplexing signal s(t) coexist in the same frequency band, the two signals may interfere with each other. The co-channel interference waveform that causes distortion appears, as shown in Figure 2B. Since the co-channel interference is a typical narrow-band interference, it is set up in the orthogonal frequency division multiplexing receiver 12-time fn, time-domain notch filter 121 To eliminate the gate frequency rejection interference of τ 收 μ + Τ in the time domain. However, the orthogonal frequency division multiple reception benefit 12 in the time domain | Zheng Chengyou, , to accurately predict the time of the same channel interference '.』, and identify the frequency of the co-channel duty, but very Difficulties, on the other hand, positive; 〇: eight

Mr ^ Knife, Xigong Transmission System 11 may also transmit u s() to a channel with multiple path attenuation. Therefore, to design an appropriate time domain oil trap, the difficulty and complexity of the virtual ice skin/wave wave β 1 2 1 is quite high' and thus will lead to an increase in production cost 1 to the Lecco domain notch filter Eliminating co-channel interference will make it difficult to improve the reception quality of the digital television terrestrial broadcasting system 10. SUMMARY OF THE INVENTION Therefore, the object of the present invention is to provide an orthogonal frequency division capacity for digital television terrestrial broadcasting, 丨A 33; It can eliminate the problem of co-channel interference. One embodiment of the present invention provides an orthogonal frequency division multiplexing receiver. The orthogonal frequency division multiplexing receiver includes a co-channel interference detect 〇r' CCI detect 〇r and a frequency-domain notch filter. The co-channel interference detector is configured to receive a frequency-domain signal and generate an estimated error value (esUmated error). Wherein, the frequency domain signal comprises a plurality of sub-carriers located in the frequency domain, and the sub-carriers of the g-sub-carriers comprise a plurality of scattered pilots. The estimated error value is calculated using a first dispersion pilot signal and a second dispersion pilot signal separated by a predetermined time. The post-3112 'co-channel interference detector' compares the estimated error value with a pre-set threshold to produce a comparison result. The frequency domain notch filter is configured to receive the frequency domain signal and generate a notch frequency domain signal based on the comparison result. The notch frequency domain signal has a plurality of subcarriers ' and the parent one subcarrier contains a notch frequency domain tribute. When the estimated error value is greater than the preset threshold, the frequency domain notch filter reduces the second load of the selected first and second scattered pilot signals.

The magnitude of the weight coefficient of the wave, and/or the magnitude of the weighting coefficient of the secondary carrier adjacent to the secondary carrier; relatively 'when the estimated error value is less than the predetermined threshold value, the frequency domain notch filter is increased by the selected number The weight coefficient size of the secondary carrier where the first and second dispersed pilot signals are located, and/or the weighting factor size of the secondary carrier adjacent to the secondary carrier, or the first and the first of the frequency domain notch choppers to be selected The weight coefficient of the secondary carrier where the second distributed pilot signal is located, and/or the weight coefficient of the secondary carrier adjacent to the secondary carrier is set to 1. The co-channel interference detector of the orthogonal frequency division multiplexing receiver according to an embodiment of the present invention can effectively detect whether co-channel interference exists in any of the sub-carriers, and can be caused by co-channel interference. The problem of the prior art is solved by the effect of the distorted subcarrier (channel), and/or the distorted subcarrier (channel) adjacent to the weight of the subcarrier (channel) that may be distorted. Furthermore, an embodiment of the present invention provides a method for detecting a co-channel dry sample, the method comprising the steps of: first, receiving a frequency domain signal including a plurality of carrier waves. Next, an estimated error value is calculated from the flute v-dispersion pilot signal and a second dispersion pilot signal separated by a predetermined time. Finally, the weight coefficients of the secondary carriers in which the selected first and second dispersions, the 1323112 signal is located, and/or the weight coefficients of the secondary carriers adjacent to the secondary carrier are adjusted according to the estimated error value. [Embodiment] FIG. 3C is a diagram showing a digital television terrestrial broadcast receiver (DVB-T receiver) 32 according to an embodiment of the present invention. The 3A diagram shows a conventional digital terrestrial broadcast transmitter (DVB_t transmiUer). A digital television terrestrial broadcast system typically includes a digital television terrestrial broadcast receiver 32 and a digital television terrestrial broadcast transmitter, both of which operate in an orthogonal frequency division multiplexing (OFDM) manner. The mode of operation includes an inner conventional code, an outer Reed-Solomon (RS code), and different modulation constellation choices. The modulated astrological map can be Quadrature Phase Shift Keying (QPSK), 16 Quadrature Amplitude Modulation (16QAM), or 64-ary Quadrature Amplitude Modulation (64)

Quadrature Amplitude Modulation, 64QAM). Referring to FIG. 3A, the digital television terrestrial broadcast transmitter 丨丨 includes a pilot insert unit 11 2. an inverse discrete Fourier Transform circuit (IDFT circuital 13 and a guard interval (Guard) Interval, GI) insertion unit 114, a digital to analog converter (DAC) 115, a radio frequency modulator (RF modulator) 116. The pilot signal insertion unit 112 receives the encoded data CDA' And insert a continuous icon such as 112 in the encoded data CDA according to a preset manner.

A pilot signal (continuous PilOt) or a scattered pilot signal (scauered) is used to generate a transmission symbol C(n, k). Next, the pilot signal \insertion unit 1丨2 outputs the transmission symbol c(n, k) to the Fourier inverse conversion power 3 to perform Fourier inverse conversion processing. Thereby, the frequency domain data signal will be converted into a time domain data signal. Next, the guard interval inserting unit 11 4 inserts the guard interval to the output of the Fourier inverse conversion circuit 丨13, thereby increasing the resistance of the signal to the multipath fading. Thereafter, the digital/analog converter U5 digitally-to-analog-converts the processed data signal, and then modulates the converted data signal through the RF modulator 丨16 to generate a transmitted signal s(t). Finally, the transmitted signal s(t) is transmitted by the antenna. The transmitted signal s(t) is an orthogonal frequency division multiplexing signal containing a plurality of separately modulated sub-carriers. These sub-carriers can be 々G [foot min ’ "^max ]. Referring to the 3B diagram, for example, the value of the κ' is set to 〇, and the value of the Kmax is equal to W04 in the 2k mode (_heart) and equal to 6816 in the 8k mode. Furthermore, the dedicated synchronization symbol (dedicated synchronization symb 〇 1) p(n, k) is also embedded into the orthogonal multiplexed data stream (transmitted signal s(t)). The scattered pilot signals in the figure are in a string of symbols to form a periodic pattern pattern). The arrangement of the symbols of the 'scattered pilot signal is arranged every other time interval Dt=4 (for example, between S1 and S2 in the figure), and every other frequency interval Df=12 (for example, in the figure) Between S1 and S3). Both the continuous pilot signal and the dispersion pilot signal are transmitted at a boosted P〇wer level, and the corresponding modulation value E{p(n, k)} = ±4/3. 1323112 Furthermore, the transmitted signal S(t) is expressed by the following equation: κ„ <〇= Re =0 ^herei^nk(t) 如〒{卜匕~nTs, eu nTs <t<(n + \) Ts else where k is the number of the subcarrier (number); n is the number of the orthogonal frequency division, and Ts is the period of the pay unit (durati〇n); Tu is the reverse interval of the subcarrier spacing ( Inverse of subcarrier spacing) ; A is the period of the guard interval; fc is the intermediate frequency of the RF signal; k' is the subcarrier index and is positively correlated with the center frequency (k'=k-(Kmax) +Kmin)/2); Cn,k is a transmission symbol. Next, please refer to FIG. 3C. This figure shows a digital television broadcast receiver 32 according to an embodiment of the present invention. The digital television broadcast receiver 32 includes a RF demodulator (RF demodulat〇r) 32 1. Analog to Digital Converter (ADC) 322, an orthogonal frequency division multiplexing receiver 3a, and a match filter 327, a channel estimator 328, a soft bit reverse mapper (s〇ft demapper) 329, A Viterbi decoder (Viterbi dec〇der) 33〇, and a RSS decoder 3 3 1. The orthogonal frequency division multiplexing receiver 3a includes a Fourier transform circuit (Discrete Fourier Transform circuit) 'DFT circuit' 323, a guard interval removal unit (GI removal unit) 324, a frequency-domain notch filter 325, and a co-channel interference detector 1323112

Tester (CCI detect〇r) 326. The co-channel interference detector (CCI detector) 326 includes a calculator (caicuiat) 326a and a co-channel interference comparison unit (CCI comparing unit) 326b. The RF demodulator (RF dem〇dUlat〇r) 321 receives the transmitted signal s(t) transmitted by the digital television terrestrial broadcast transmitter through the antenna, and outputs the analogy to the analog/digital converter 322 after demodulation. Digital conversion to generate an input signal In(t). Where the input signal In(t) is included in the time domain

Several subcarriers. Next, the operation mode of the orthogonal frequency division multiplexing receiver 3a will be described in detail. First, the Fourier transform circuit 323 receives the input signal ln(t) to generate a frequency domain signal Y(f) containing a plurality of subcarriers. The frequency domain data of each carrier in the frequency domain signal Y(f) can be represented by Y(n, k) (7) and k are positive integers). The data in the frequency domain data Y(n, k) may include a preset plurality of consecutive pilot signals 'for example, Kmin = Q % frequency domain data Y (n, 〇) in FIG. 3B; or frequency domain data Y (n) , k)* data may not contain any pilot signal 'for example, the frequency domain data γ(η, 5) of k=5 in FIG. 3B; or the data in the frequency domain data Y(n, k) may include preset A plurality of scattered pilot signals, such as the frequency domain data γ(n, 12) of k=12 in Fig. 3B. Of course, the above-mentioned arrangement of the signal and the dispersion guide signal can be arbitrarily adjusted according to the design requirements. The frequency domain data Y(n,k) can be expressed by the following equation table 2. 'Expressing the nth orthogonal frequency division multiplex symbol, and the kth subcarrier...(1) ^ where, //(«, illusion For the channel parameters in the frequency domain, the transmission A m ^ ^ 7 («^) 1J23112 guard interval removal unit 324 is used to remove the guard interval of the input signal In(t) in the time domain. Stomach and co-channel interference detection The 326 detects the energy of the co-channel interference in the dispersion V = 唬 of the frequency domain signal Y(f). In the embodiment, the co-channel interference detector 326 receives the frequency domain signal Y(f), and The two decentralized pilot signals are subjected to an operation to be described later to generate an -estimation error value, wherein the two decentralized pilot signals are in the same subcarrier (S) and S2' S1 and S2 are located on the same carrier (channel) as in FIG. 3B. And spaced apart by a predetermined time interval Dt. Thereafter, the co-channel interference detector 326 compares the estimated error value with a predetermined threshold (thresh〇ld) TH to generate a comparison result, and wherein the 'estimation error The value (10) is obtained by subtracting the two f-domain data Y(n, k) from Y(n-Dt, k) via the calculator 326a and then taking the absolute value. And the frequency domain data Y(n, k) and Y(n_Dt, k) respectively contain the two different scattered pilot signals (for example, S1#S2). Furthermore, for two identical-undercarriers For the decentralized pilot signal, the data carried by it will be the same as the transmission C(n, k) will be equal to C(n-Dt, k;), so "Y(n,k) "Y( After n-Dt,k) subtracts and then takes the absolute value squared, it will be approximately equal to "subtract 1(4) and Kn-D^k) and then take the absolute squared". Therefore, the equation 'of the estimated error value ^ can be expressed as follows: • (10) 'eight hearts-print-W}, if = c (four) magic x E{\Kn,k)~I(n-Dt,k)\2} ...( 2) ^ In addition, in order to obtain a more accurate estimation error value < (phantom, the invention - the calculation of the y column y can also be on the same subcarrier for other = scatter u number) The estimated error value is calculated by the scattered pilot signals of the preset time Dt, and finally, in the calculated majority of the estimated error values of 13 1323112 <(4), the average is estimated, θ is measured out + mean, and k is the same The accuracy of the channel interference detection. Next, in the embodiment of the present invention, the co-channel interference comparing unit 326b compares the obtained estimated error value (10) with 1 by the threshold & th & to generate a - comparison result CR Of course, in another embodiment, the same channel interference comparison unit 326b may also use the obtained average estimated error value ί(4) to compare with a predetermined threshold TH to generate a comparison result. The frequency domain filter is 3 2 5 A single _ tap filter set for each carrier (one taP out 4 〇. According to the above comparison result CR, the The frequency-domain notch filter state 3 2 5 is when the estimated error value $(8) is greater than the predetermined threshold TH (which indicates that the subcarrier and/or its adjacent subcarriers are distorted by co-channel interference), Reducing the weight of the secondary carrier where the scattered pilot signal is located and/or its adjacent secondary carrier; and when the estimated error value #(9) is less than the threshold TH, the secondary carrier where the distributed pilot signal is located and/or its neighbors - The weight of the secondary carrier is set to 1 (or the weight of the secondary carrier and/or its adjacent secondary carrier wave is increased). By this, the 'frequency domain notch filter 325 can eliminate the co-channel _ interference for the digital television broadcast receiver. For example, the weight coefficient of the frequency domain notch filter 325 is M(k). The frequency domain notch filter 325 can operate according to the following equation: \〇<M(k)<\ If ξ^) > ΤΗ 1 M(k) = \ if ξ{Κ)<ΤΗ (3) According to equation (3), assuming that the estimated error value is greater than the preset threshold τη, the kth time Carrier distortion, so the frequency domain notch filter 3 2 5 must set its weight coefficient M(k) to be greater than or equal to 0 to less than 1 The value of the k-th subcarrier can be reduced. On the other hand, if the estimated error value is less than the threshold TH, it means that the kth subcarrier has no distortion, and the 14 1323112 is a frequency domain notch filter. 325 sets its weighting factor M(k) to 1, so that the kth secondary carrier will not be affected by the frequency domain notch filter 325. Furthermore, if the k'th subcarrier adjacent to the kth subcarrier of the frequency domain notch filter 325 is to be processed, the weight coefficient M(k,) of the kth subcarrier can be expressed as follows: {Q<M{k')<\ if ξ^) > ΤΗ 1 M(k') = \ if ξ{^<ΤΗ (4) According to equation (4), assume the estimation of the kth subcarrier When the error value f(9) is greater than _ the predetermined threshold TH, the frequency domain trapper 325 sets its weight system 'number M(k') to a value greater than or equal to 〇~ less than 1, and can reduce the number ' The weight of k' subcarriers; if the estimated error value of the kth subcarrier is less than the threshold TH, the frequency domain notch filter 325 sets its weight coefficient M(k') to 1, The k'th subcarrier will not be affected by the frequency domain notch filter 325. It should be noted that when the above weighting factor]^(1〇 and M(k,) are set to a value greater than or equal to 〇~ less than 1, the setting can be performed by waveform A as shown in the 4th φ diagram. In contrast, when the weight coefficient ^4 (|^ and M(k,) is set to 1, this setting can be performed by using waveform B as shown in FIG. 4B to represent 0 after the 'frequency domain notch filter 325 output. A notch frequency domain signal 'Y, (1)' and the notch frequency domain signal Y, (1), the notch frequency domain data γ, (ηΛ) or Y, (n, k,) of each subcarrier Use the following equation Y\n,k) = M(k)Y(n,k) (5) · Y\n,k') = M{k')Y{n,k') So, when frequency domain data The frequency domain notch filter 325 can utilize the adjustment weight coefficient M(k) or M(k' when the subcarrier at the Y(n,k) or Y(nk,w test &A also) position is distorted 1323112. In a way, the weight of the distorted frequency domain data Y(n, k) 4 Y(nk,) is reduced. Therefore, the subsequent circuit will not receive the frequency domain data Y(n,k) or Y(n,k,) affected by the co-channel interference, but only the processed notch frequency domain data Y, ( n, k) or Y, (n, k,). In summary, the orthogonal frequency division multiplexing receiver 3a of the present invention can use the co-channel interference detector 326 to effectively detect whether co-channel interference exists in any one subcarrier, and can achieve interference due to co-channel. The problem of the prior art is solved by the effect of reducing the weight of the subcarrier (channel) which may cause distortion, and the effect of the weight reduction of the subcarrier (channel) which may cause distortion. Next, the operation of the subsequent circuits of the orthogonal frequency division multiplexing receiver 3a will be discussed, and will be discussed only in the notch frequency domain data for the sake of simplicity. Referring to FIG. 3C, first, the channel estimator 328 receives the notch frequency domain data r («, and, according to the notch frequency domain data r〇?, a plurality of scattered pilot signals in the phantom to estimate a channel parameter // , („,々). The channel parameter phantom is expressed as follows: H'(n, k) = V'(n, k) / C(n, k) * k) (7) After the channel The estimator 328 interpolates all channel parameters in the frequency domain using its built-in interpolator and outputs the processed channel parameter //((α) to the matched filter 327. In order to improve the reception performance of the digital television terrestrial broadcast receiver 32, it is necessary to obtain a highly reliable soft-decision metric result from the demodulation data and feed the result into the Viterbi decoder. 1323112 According to an embodiment of the present invention, the processed channel parameter (1) is output to the matched filter 327. The matched filter 327 receives the notch frequency domain data r(", 〇, and according to the processed channel The parameter factory generates a matching output signal (matched 〇utput signa丨) from the illusion The matching output signal //''οαγοα) can be expressed as: H (n^)-M2(k)ilH(n,k)\2 C(n,k) + H\n,k)I(n, k)) (8) The π two L bit inverse mapper 329 receives the matched output signal and performs symbol inverse mapping on the matched output signal f(10) heart to generate an output signal 〇. Since the matching output signal already has channel reliabiHty, the bit decision metric of the kth-ower#, & ke ii k-person carrier can be obtained from the soft inverse mapper 329 Value = drrnmetdCValUe) "° after 'Viterbi decoder 33. The horse exits the signal 〇' to generate an output data 〇D. Finally, Rhodes can get - no co-channel interference is detected. The decoder 33 1 decodes the round-out data 〇D, and the decoded data DDA affected by the same channel interference. Figure 5 is a flow chart showing a method of an embodiment of the present invention. The method includes the following steps: Step S502: Start. Step S504: receiving the frequency domain signal, and the subcarrier frequency "in the frequency domain" includes a plurality of steps consisting of being located in the same line wave and spaced apart from each other - the preset scattered pilot signal and the second scattered pilot signal 2 — Value. T-out—estimation error step S508: judging whether the estimated error value is a large top 3 boundary value, if 1323112 is 'skip to the next step; if no, skip to step S5 1 2. Step S5 1 0: lowering The weight coefficient of the secondary carrier where the selected first and second distributed pilot signals are located, and/or the weight coefficient of the secondary carrier adjacent to the secondary carrier. Step S512: where the selected first and second scattered pilot signals are located The weight coefficient size of the secondary carrier 'and/or the weight coefficient of the secondary carrier adjacent to the secondary carrier is set to 1.

Step S514·· ends. It should be noted that the weight coefficient of the secondary carrier where the selected first and second distributed pilot signals are located in step S51, and/or the weight coefficient of the secondary carrier adjacent to the secondary carrier may be set to be greater than or equal to 〇~ Less than between 1. Furthermore, the estimated error value can be an average estimated error value. The average estimated error value is calculated by the same subcarrier for other scattered pilot signals, that is, the calculation error value of the other arbitrary number of scattered pilot signals separated by the preset time, and finally using the calculated majority Estimate the average of the error values. Furthermore, the above embodiment uses the first and first knife-instruction k numbers on the same carrier for processing, but the present invention is not limited thereto; in another embodiment, after some improvements, it is too invented. The technique of 尽R尽& Ming can also be processed using the first and second scattered pilot signals located on different subcarriers. The scope of the present invention is described by the embodiments of the present invention as set forth in the appended claims. However, the present invention is not limited thereto, and the industry can perform various kinds of 1323112. [Simplified description of the drawings] Fig. 1 shows a schematic diagram of a conventional digital television terrestrial broadcasting system. Figure 2A shows a waveform diagram of a conventional analog broadcast television signal and an orthogonal frequency division multiplex signal. Figure 2B shows a waveform diagram of conventional co-channel interference. Figure 3A shows a schematic diagram of a conventional digital television terrestrial broadcast transmitter. Figure 3B shows the frame structure of conventional digital television terrestrial broadcast data transmission. Fig. 3C is a view showing a digital television terrestrial broadcast receiver according to an embodiment of the present invention. Fig. 4A is a waveform diagram showing a method of setting a weight coefficient according to an embodiment of the present invention. Fig. 4B is a waveform diagram showing the manner of setting the weight coefficient in an embodiment of the present invention. Figure 5 is a flow chart showing a method of detecting co-channel interference according to an embodiment of the present invention. / [Main component symbol description] 10 digital TV terrestrial broadcasting system 11 positive father crossover multiplex transmission system (digital TV terrestrial broadcast transmission 12 orthogonal frequency division multiplexing receiver,). ) 121 time domain notch filter 112 pilot signal insertion unit 113 FFT inverse conversion circuit 114 guard interval insertion unit 115 digital/analog converter

Claims (1)

凊 凊 凊 凊 · 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交And comparing the estimated 5 Wu difference with a predetermined threshold to generate a comparison result, wherein each carrier includes a plurality of scattered pilot signals, and the estimated error values are first guided by a predetermined time interval The signal and the second dispersion guide signal are calculated and processed; and the frequency domain notch filter receives the frequency domain signal, and generates a notch frequency domain signal according to the comparison result, where the notch frequency domain signal includes a plurality of subcarriers, and each carrier includes notch frequency domain data; wherein 'when the estimated error value is greater than the preset threshold value, the frequency domain notch filter reduces the subcarrier of the scattered pilot signal and/or The weight coefficient of the secondary carrier or its neighboring carrier; and ^. When the error value of the estimated juice is less than the predetermined threshold, the frequency domain notch has a weight of 1 for the secondary carrier where the distributed pilot signal is located and/or its adjacent secondary carrier. The orthogonal frequency division multiplexing receiver according to claim 1, further comprising a Fourier transform circuit, wherein the Fourier transform circuit receives an input signal including a plurality of subcarriers in a time domain, and generates the foregoing Frequency domain signal. The orthogonal frequency division multiplexing receiver according to claim 1, wherein when the estimated error value is greater than the predetermined threshold, the frequency 丄丄丄z domain notch data filter uses the foregoing scattered pilot signal The weight coefficient of the secondary carrier where it is located is set to be greater than or equal to 0 to less than 1. 4. For application: the orthogonal frequency division multiplexing receiver according to item i of the patent scope, wherein the co-channel interference detector comprises: a calculator for calculating the estimated error value; The interference comparison unit is configured to compare the estimated error value /, the predetermined threshold value to generate the foregoing comparison result.士申°月月辜 辜 帛 帛 帛 项 帛 户 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交 正交After subtracting the frequency domain data from the second frequency domain data, the value of the square of the absolute value is taken. 6_ The orthogonal frequency division multiplexing receiver according to claim 1, wherein the estimated error value is an average estimated error value, and the average estimated error value is determined by using a selected distributed pilot signal. Most of the subcarriers # are separated from the aforementioned prediction history time (four), and the scattered pilot signals are calculated and averaged. A 7. The orthogonal frequency division multiplexing receiver according to claim i, further comprising a channel estimator, the channel estimator receiving the aforementioned notch frequency domain data 'and according to the inclusion in the notch frequency domain The decentralized pilot signal in the data is used to generate a processed channel parameter. 8. The orthogonal frequency division multiplexing receiver according to claim 7, further comprising a matched filter, wherein the matched filter receives the notch frequency domain data, and according to the processed channel parameter A matching output signal is generated. 22 9. If the orthogonal component described in item 8 of the patent application scope further comprises a rescue ten-party receiver, the device receives the aforementioned matching 衿^ Λ position 兀 reverse mapping W” and executes the matching round-out signal The reverse mapping is performed to generate an output signal. The nickname is 10. If the patent application scope is the ninth item, the current Yada, and the positive scallop multiplex receiver is used to decode the aforementioned soft bit. The Viterbi decoder with the inverse of the element. (4) The output k Ήΐ " The orthogonal frequency division multiplexing receiver described in the item: 3, to decode the output nickname of the soft bit reverse mapper The Rod Solomon decoder. ° 12. The application of the Orthogonal Frequency Division Multiplexed Receiver described in the patent scope, ', the first and second distributed pilot signals are located in different symbols, and / or located on the same carrier. U. The orthogonal frequency division h receiver described in the scope of the patent application is applied to a digital television terrestrial broadcasting system. An orthogonal frequency division multiplexing receiver includes: a co-channel interference detector, which receives a frequency domain 包含 including a plurality of subcarriers, and is separated by a preset time by a first dispersed pilot signal and a second dispersion guiding signal to calculate an estimated error value; and a frequency domain wave filter, wherein the weighting coefficient of the secondary carrier in which the selected first and second dispersed guiding signals are located is adjusted according to the estimated error value, and / or adjust the weight coefficient of the secondary carrier adjacent to the secondary carrier. The invention relates to an orthogonal frequency division multiplexing receiver according to claim 14, wherein when the estimated error value is greater than a preset threshold, the frequency domain notch filter reduces the scattered pilot signal. The weight coefficient of the subcarrier and/or its adjacent subcarriers; and when the estimated error value is at a predetermined threshold value, the frequency domain notch filter sets the subcarrier of the decentralized pilot signal and / The weight coefficient of the secondary carrier or its neighbor is set to 1. 16. The orthogonal frequency division multiplexing receiver according to claim 14, wherein the frequency domain notch filter has the foregoing scattered pilot signal when the estimated error value is greater than a predetermined threshold. The weight coefficient of the secondary carrier and/or its adjacent secondary carrier is set to be greater than or equal to 〇~ less than 1. 17. The orthogonal frequency division multiplexing receiver according to item 4 of claim 4, wherein the estimated error value is an average estimated error value, and the average estimated error value is obtained by using a selected scattered pilot signal. The other plurality of carriers are calculated by calculating the average of the scattered pilot signals of the preset time and averaging them. 18. The orthogonal frequency division multiplexing receiver according to claim w, wherein the first and second distributed pilot signals are located in different symbols, and/or are located on the same subcarrier. A method for detecting co-channel interference in a debt, comprising: receiving a frequency domain signal including a plurality of subcarriers; calculating an estimation error from a first dispersion pilot signal and a second dispersion pilot signal separated by a preset time And the value of the weighting coefficient of the secondary carrier where the selected first and second distributed pilot signals are located, and/or the weighting coefficient of the secondary carrier adjacent to the secondary carrier are adjusted according to the foregoing estimated error value. 20. The method of detecting co-channel interference as described in claim 19, wherein the first and second scattered pilot signals are located at different symbols' and/or on the same secondary carrier. 21. The method for detecting co-channel interference according to claim 19, wherein when the estimated error value is greater than a predetermined threshold, the secondary carrier where the scattered pilot signal is located and/or its adjacent secondary carrier The weight coefficient of the signal will be reduced; and when the estimated error value is less than the predetermined threshold, the weight coefficient of the secondary carrier where the distributed pilot signal is located and/or its adjacent secondary carrier will be set to 1. 22. The method for detecting co-channel interference according to claim 19, wherein when the estimated error value is greater than a predetermined threshold, the secondary carrier where the scattered pilot signal is located and/or its adjacent secondary carrier The weight coefficient size will be set to be greater than or equal to 0 to less than 1. 2 3. If the method of inter-channel co-channel interference described in claim 19 of the patent application scope, the φ, 4, and , and the estimated error error value are an average estimated error value 'the flat # ..", The value is obtained by calculating and averaging the scattered tigers in the battle wave in which the selected scattered pilot signal is located. 25