TWI301705B - Sigma-delta modulator, d/a conversion system and dynamic element matching method - Google Patents
Sigma-delta modulator, d/a conversion system and dynamic element matching method Download PDFInfo
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1301705 - 九、發明說明: . 【發明所屬之技術領域】 本發明係有關於一種資料轉換系統;尤指一種使用動 態元件匹配邏輯之積分三角調變器、資料轉換系統及其方 法。 【先前技術】 會 資料轉換技術已存在多年,且用途極其廣泛。於—般 • 的家庭裡,可以在通訊系統、消費及專業音訊系統以及精 準測量裝置等應用中發現轉換器,如一數位/類比(D/A)轉 換器或者是類比/數位(A/D)轉換器。 積分三角調變器(Sigma-delta modulator,SDM)係一 種超取樣(oversampling)類比/數位轉換器,具為高度動態 範圍(dynamic range)以及高解析度。積分三角調變器已成 功地使用於通訊以及其他資料處理領域中。1位元積分三 Φ 角調變器因本身具有的線性度(linear ity),於過去被廣泛 地使用。然而’為了不增加超取樣率(oversamp 1 ing rat io) 而達到較高之解析度以及較寬之頻寬,則需使用可降低量 化雜訊功率的多位元積分三角調變器。但在多位元積分三 角調變器中裡’其回饋(feedback)多位元數位/類比轉換器 裡的數位/類比元件(D/A elements)存在匹配誤差 (mismatching) ’因而影響線性度。第la圖係表示一傳統 的N位元積分三角調變器1〇,其中N為一大於1之整數。 0697-A40463TWF 6 曰修正替換頁 1301705 • N位元積分三角調變器10包括一加法器12、一迴路濾波器 -(Loop Filter)14、一 N 位元量化器(Quantizer)16 以及一 N位元數位/類比轉換器18。加法器12接收一類比輸入訊 號Vin,且減去一傳送自N位元數位/類比轉換器18之一類 1 比回饋訊號VFB。迴路濾波器14耦接至加法器12,且接收 • 加法器12的輸出。迴路濾波器14包括複數串連的類比積 分器(integrators),用以產生一濾波類比輸出至N位元量 ® 化器16。N位元量化器16接著將迴路濾波器14的類比輸 出量化,以產生一數位碼至N位元數位/類比轉換器18。N 位元數位/類比轉換器18包括複數數位/類比(D/A)元件, 用以將數位碼轉換為類比回饋訊號Vfb,且將其輸入至加法 器12。N位元數位/類比轉換器18中之數位/類比(D/A)元 件,如電容器、電阻器或電流源,可能因製造變異、使用 有瑕疫之材料、溫度變動、濕度以及劣化(degradation) ® 等原因引起匹配性問題,此種元件間之匹配誤差會影響回 饋路徑的線性度,且於輸出產生失真(distortion)以及雜 訊0 動態元件匹配平均法(Dynamic element matching, DEM)可以解決多位元數位/類比轉換器的線性度問題。第 lb圖係表示使用動態元件匹配平均法之一傳統N位元積分 三角調變器20。第lb圖與第la圖極為類似,除了在第lb 0697-A40463TWF 7 1301705 時正替換頁 圖中包括-耦接於N位元 換器18間之動態元件匹配及n位元數位/類比轉 會觼機選取iY位讀位/類&」d元件匹配邏輯22 件,以將非線性誤差分佈 轉換器丨8中之數位/類比元 平均法中之一種為資 外’動態元件匹配 、丁加權平约、 average,DWA)。第 2 圖所示係使=去(data weighted 元件的N位元數位/類比轉換器使用了具有8個數位/類比 資料加權平均法的動態元件 肖^兄明第lb ®中使用 ^配邏輯9 9 β , 中,γ轴係表示每一時間槽的輪讀原理。其 方塊以及數字則係表示選取的_ 馬,而X軸之灰色 加權平均法會根據數位輸入石馬疋二及選取的次序。資料 選取數位/類比元件。例如,在預定順序,一個個 為5,則資料加權平均法會按照财位=碼 一個時間槽財,數位輸入 取C1至C5。而在下 先選取-接續前次最後觀元件G5’㈣料加權平均法會 C7。數位/類比元件的選取順序之疋件C6,接著選取 ta 貝序如前碩所示。資料加權平均 法_平均每-數位/類比元件被選取的機率,因此將數位/ 類比轉換II的匹配性誤差移至—較高頻帶,且其較易實 施,並具有一階雜訊重整(first order noise shaping) 效果 然而,由於資料加權平均法與輸入數位碼的大小振幅 0697-A40463TWF 8 1301705 正替換頁j •相關,因此,當輸入數位碼很小時,頻域内(in-band)會產 - 生大量突波(tones),因而嚴重影響積分積分三角調變器的 信號雜訊失真比(signa卜to-noise plus distortion ratio)以及無突波動態比(spur free dynamic range, SFDR)。第3a及3b圖係一具有第1圖中3位元數位/類比 轉換器之三階積分三角調變器,在使用資料加權平均法時1301705 - IX. Description of the invention: 1. Field of the Invention The present invention relates to a data conversion system; and more particularly to an integral triangular modulator, a data conversion system and a method thereof using dynamic component matching logic. [Prior Art] Data conversion technology has existed for many years and is extremely versatile. In general-purpose homes, converters can be found in applications such as communication systems, consumer and professional audio systems, and precision measurement devices, such as a digital/analog ratio (D/A) converter or analog/digital (A/D). converter. The Sigma-delta modulator (SDM) is an oversampling analog/digital converter with a high dynamic range and high resolution. The integral delta modulator has been successfully used in communications and other data processing areas. 1-bit integral three Φ An angle modulator has been widely used in the past due to its linearity. However, in order to achieve higher resolution and wider bandwidth without increasing the oversampling rate, a multi-bit integral delta modulator that reduces the amount of noise power is used. However, in a multi-bit integral triangular modulator, there is a mismatching of the digital/analog elements in the multi-bit digital/analog converter, which affects linearity. The first diagram shows a conventional N-bit integral triangular modulator 1〇, where N is an integer greater than one. 0697-A40463TWF 6 曰Replacement Replacement Page 1301705 • The N-bit integration delta modulator 10 includes an adder 12, a loop filter 14, a N-bit quantizer 16 and an N-bit. A meta-bit/analog converter 18. The adder 12 receives an analog input signal Vin and subtracts a class 1 ratio feedback signal VFB transmitted from the N bit digital/analog converter 18. The loop filter 14 is coupled to the adder 12 and receives the output of the adder 12. The loop filter 14 includes a plurality of series of analog integrators for generating a filter analog output to the N bit quantity converter 16. The N-bit quantizer 16 then quantizes the analog output of the loop filter 14 to produce a digital code to N-bit digital/analog converter 18. The N-bit digit/analog converter 18 includes a complex digital/analog ratio (D/A) element for converting the digital code into an analog feedback signal Vfb and inputting it to the adder 12. Digital/analog ratio (D/A) components in N-bit digital/analog converters 18, such as capacitors, resistors, or current sources, may be subject to manufacturing variations, use of plague materials, temperature variations, humidity, and degradation (degradation) ) ® causes a matching problem. The matching error between the components affects the linearity of the feedback path, and the distortion occurs in the output and the noise element dynamic material matching (DM) can be solved. The linearity problem of multi-bit digital/analog converters. Figure lb shows a conventional N-bit integral delta modulator 20 using a dynamic component matching averaging method. The lb diagram is very similar to the first diagram, except that in the lb 0697-A40463TWF 7 1301705, the replacement page includes dynamic component matching and n-bit digit/analog transfer coupled between the N-bit converters 18. The downtime selects the iY bit read/class &"d element matching logic 22 pieces to take one of the digital/analog element averaging methods in the nonlinear error distribution converter 丨8 as the extra-component 'dynamic component matching, d-weighting Ping, average, DWA). Figure 2 shows the == (N-bit digit/analog converter of the data weighted component uses a dynamic component with a weighted averaging method of 8 digits/analog data. The 9 β, medium, and γ-axis systems represent the principle of the round-robin of each time slot. The squares and numbers represent the selected _ horse, and the gray-weighted average method of the X-axis is based on the number of digits input and the order of selection. The data is selected as a digit/analog component. For example, in the predetermined order, one is 5, then the data weighted average method will be based on the financial position = code for a time slot, and the digit input for C1 to C5. Finally, the component G5'(4) material weighted average method will be C7. The order of the digit/analog component is selected as C6, and then the ta shell order is selected as shown in the previous figure. The data weighted average method _ average per-digit/analog component is selected. The probability of shifting the matching error of the digital/analog conversion II to the higher frequency band, and it is easier to implement, and has a first order noise shaping effect. However, due to the data weighted average method and lose Digital code size amplitude 0697-A40463TWF 8 1301705 Positive replacement page j • Correlation, therefore, when the input digit code is small, in-band will produce a large number of tones, thus seriously affecting the integral integration triangle The signal to noise distortion ratio of the modulator (signa to-noise plus distortion ratio) and the spur free dynamic range (SFDR). The 3a and 3b diagrams have the 3-bit digit in the first figure. Third-order integral delta modulator of analog/analog converter, when using data weighted averaging
之輸出頻譜,其輸入訊號分別為-2(dB)以及-45(dB)。比較 第3a及3b圖可以發現在第3b圖中產生了大量的突波,這 是因為在輸入訊號很小時’積分三角調變器會產生週期性 的回饋訊號,其中數位/類比元件間的匹配誤差亦會被週期 性化,此週期性誤差和輸入訊號產生折頻現象 (a 1 iasing),因而在頻域内產生突波。因此,需要一種可 以在輸入訊號很小時,消減頻域内突波之資料加權平均法。 【發明内容】 本發明揭露一種積分三角調變器(Sigma_delta modulator),包括一加法器,接收一類比輪入訊號以及一 回饋(feedback)訊號’用以根據該類比輪入訊號以及該回 饋訊號間之差值’產生-誤差訊號;—迴路據波器(L〇〇pThe output spectrum has input signals of -2 (dB) and -45 (dB). Comparing Figures 3a and 3b, we can see that a large number of glitch are generated in Figure 3b because the input triangle is very small when the input signal is small. The integral triangle modulator generates periodic feedback signals, where the digital/analog components match. The error is also periodically periodicized, and this periodic error and the input signal produce a frequency shift (a 1 iasing), thus generating a glitch in the frequency domain. Therefore, there is a need for a data weighted average method that can reduce the glitch in the frequency domain when the input signal is small. SUMMARY OF THE INVENTION The present invention discloses an integrated delta modulator (Sigma_delta modulator), including an adder that receives an analog wheel signal and a feedback signal 'for rounding between the analog signal and the feedback signal. The difference 'generating-error signal'; the loop data device (L〇〇p
Filter),與該加法器耦接,且接收該誤差邙 、没汛唬以產生一濾 波訊號;一量化器(Quantizer),與該迴肷、、会 、略濾波器耦接,用 以將該濾波訊號轉換成一量化輪出訊號;—叙 歎位/類比轉換 0697-A40463TWF 9 13咖 L 嶋 __一 态,與該加法為、孝禺接,包括複數數位/類比元件,用以以該 '等數位/類比元件,產生相當於該量化輸出訊號之該回饋訊 號至遠加法裔,以及一動態元件匹配邏輯(dynamic element matching l〇gic),耦接於該量化器以及該數位/ , 類比轉換器之間,且接收該量化輸出訊號,用以選取該數 • 位/類比轉換器之該等數位/類比元件,其中該動態元件匹 配邏輯將該等數位/類比元件分為複數群組,且該等群組之 ® 數量與該等數位/類比元件之數量互質,並根據該量化輸出 訊號以及前次選取之該等群組以及該等數位/類比元件,以 選取該等群組以及該等數位/類比元件。 本發明另外揭露一種數位/類比轉換系統,包括一數位 /類比轉換裔,包括複數數位/類比元件,用以產生相當於 一數位輸入訊號之一類比輸出訊號;以及一動態元件匹配 邏輯(dynamic element matching logic),耦接至數位/ 類比轉換為,且接收該數位輸入訊號,用以選取該數位/ 類比轉換器之該等數位/類比元件,其中該動態元件匹配邏 輯將該等數位/類比元件分為複數群組,且該等群組之數量 與該等數位/類比元件之數量互質,並根據該數位輸入訊號 以及前次選取之該等群組以及該等數位/類比元件,以選取 該等群組以及該等數位/類比元件。 本發明另外揭露一種根據一數位輪入碼選取數位/類 0697-A40463TWF 10 1301705Filtering, coupled to the adder, and receiving the error 汛唬, no 汛唬 to generate a filtered signal; a quantizer (Quantizer) coupled to the 肷, 会, 略 filter to The filtered signal is converted into a quantized round-out signal; - the sigh/analog conversion 0697-A40463TWF 9 13 coffee L 嶋 __ one state, and the addition, filial piety, including a plurality of digits / analog components for the ' An equal-bit/analog component that generates the feedback signal corresponding to the quantized output signal to a far-reaching French, and a dynamic element matching l〇gic coupled to the quantizer and the digital/analog conversion Between the devices, and receiving the quantized output signal for selecting the digit/analog components of the digital/analog converter, wherein the dynamic component matching logic divides the digital/analog components into a plurality of groups, and The number of ® of the groups is contiguous with the number of the digits/analog components, and the groups are selected based on the quantized output signals and the previously selected groups and the digits/analog components These digits/analog components. The present invention further discloses a digital/analog conversion system including a digital/analog conversion, including a complex digital/analog component for generating an analog output signal equivalent to a digital input signal; and a dynamic element matching logic (dynamic element) Matching logic, coupled to the digital/analog conversion, and receiving the digital input signal for selecting the digital/analog components of the digital/analog converter, wherein the dynamic component matching logic is the digital/analog component Divided into a plurality of groups, and the number of the groups is relatively prime with the number of the digits/analog components, and is selected according to the digit input signal and the previously selected group and the digit/analog components The groups and the digit/analog components. The invention further discloses a method for selecting a digit/class according to a digital wheel code. 0697-A40463TWF 10 1301705
τιΤι
- 比元件之方法,包括將複數數位/類比元件分為複數群組, - 其中,該等群組之數量與該等數位/類比元件之數量互質; 根據該數位輸入碼以及前次選取之該等群組以及該等數位 /類比元件,選取該等群組以及該等數位/類比元件。 , 【實施方式】 _ 為使本發明之上述目的、特徵和優點能更明顯易懂, 下文特舉一較佳實施例,並配合所附圖式,作詳細說明如 藝ητ。 第4圖係表示本發明一實施例之一多位元積分三角調 變器40。積分三角調變器40包括一加法器12、一迴路濾 波器(Loop Filter)14、一 Ν 位元量化器(Quantizer)16、 一 N位元數位/類比轉換器18以及一先進動態元件匹配邏 輯42。第4圖與第la及lb圖類似,除了耦接於N位元量 化器(Quantizer)16及N位元數位/類比轉換器18間之先 ^ 進動態元件匹配邏輯42。在第4圖與第la圖中使用相同 數字標示之元件,具有相同的功能,因此在此不再說明。 先進動態元件匹配邏輯42的操作說明如下。 假設N位元數位/類比轉換器18包括8個數位/類比 元件C1〜C8。先進動態元件匹配邏輯42將數位/類比元件 分為數個群組,且群組的數量與數位/類比元件的數量互 質。例如,當N位元數位/類比轉換器18中有8個數位/ 0697-A40463TWF 11 月日修正替換黃 1301705 類比元件時,則先淮氣Μ - 勒悲70件匹配邏輯42可將Cl〜C8分成 3、5或7個群組。第R R^ ^ 米ΰ圖係於具有8個數位/類比元件之 數位/類比轉換器18巾 ^ 〒之本發明一實施例之先進動態元件 匹*配邏輯42的一拇作無γ丨 木作只例,其中先進動態元件匹配邏輯 42將數位/類比元件公 一 刀马3個群組。在第5圖中,Υ軸係表 示母一時間槽的輪入數位 Βί ^ 1瑪’而X軸之灰色方塊以及數字 則係表示選取的元件以及 久焉破選取的次序。先進動態元件 匹配邏輯42將C1〜(:8分為h 刀馬3個群組,其中ci〜C3為第一群 組,C4〜C5為第二群組,rR r。 旦 · 、 C6〜C8則為第三群組。當自N位元 器(Quantizer)l6收到數位輪人碼時,先進動態元件 匹配邏輯42會根據數位輸人碼以及前次選取之群組以及 數位/類比元件’選取群組以及其中之數位·比元件,且 其總共選取的數位/類比元件數量相當於數位輸入碼。例 如,在時間槽tl時,數位輪入石篆 馬為5,則先進動態元件匹 ^輯42會按照箭頭的順序,依:欠於第一群組選取C1, 群組選取C4’第三群組觀.第—馳選取C2, Μ及第二群組選取C5。而在t2時’數位輸入碼為2,則先 進動態元件匹配邏輯42會自前*最㈣取群_卩第二群 組)的下一個群組(即第三群组)中, 璉取元件。且其會自前 次最後選取之數位/類比元件(亦即第二群組之曰 個數位/類比元件(亦即C7)開始選你 ^ 的下 、取。所以進動態元件匹 0697-A40463TWF 12- a method of comparing components, comprising dividing a plurality of digits/analog components into a plurality of groups, - wherein the number of the groups is equal to the number of the digits/analog components; inputting the code according to the digits and selecting the previous one The groups and the digit/analog components select the groups and the digit/analog components. BRIEF DESCRIPTION OF THE DRAWINGS In order to make the above objects, features and advantages of the present invention more comprehensible, a preferred embodiment of the invention will be described in detail with reference to the accompanying drawings. Fig. 4 is a view showing a multi-bit integral triangular modulator 40 according to an embodiment of the present invention. The integrating delta modulator 40 includes an adder 12, a loop filter 14, a Quantizer 16, an N-bit digit/analog converter 18, and an advanced dynamic component matching logic. 42. Figure 4 is similar to the first and third and lb diagrams except that the dynamic component matching logic 42 is coupled between the N-bit quantizer 16 and the N-bit digit/analog converter 18. Elements labeled with the same numerals in Figures 4 and 1 have the same function and will not be described here. The operation of the advanced dynamic component matching logic 42 is explained below. It is assumed that the N-bit digit/analog converter 18 includes eight digit/analog components C1 to C8. The advanced dynamic component matching logic 42 divides the digital/analog components into groups, and the number of groups is mutually prime with the number of digital/analog components. For example, when there are 8 digits in the N-bit digit/analog converter 18 / 0697-A40463TWF 11th day correction replaces the yellow 1301705 analog component, then the first qi Μ - 勒 70 70 matching logic 42 can be Cl ~ C8 Divided into 3, 5 or 7 groups. The RR^^ meter diagram is based on a digital/analog converter with eight digit/analog elements. The advanced dynamic component of the embodiment of the present invention For example, the advanced dynamic component matching logic 42 divides the digital/analog components into three groups. In Fig. 5, the x-axis indicates the wheel-in digit of the parent-time slot Βί ^ 1 玛' and the gray squares and numbers on the X-axis indicate the selected components and the order in which the selection is long. The advanced dynamic component matching logic 42 divides C1~(:8 into three groups of h-knife, wherein ci~C3 are the first group, C4~C5 are the second group, rR r. Dan, C6~C8 Then, it is the third group. When the digitizer code is received from the N-bitizer (Quantizer) l6, the advanced dynamic component matching logic 42 will select the group according to the digit and the previously selected group and the digit/analog component. Select the group and its digits and ratio components, and the total number of digits/analog components selected is equivalent to the digit input code. For example, when the time slot is tl, the digits are rounded to 5, and the advanced dynamic components are ^ Series 42 will follow the order of the arrows, according to: the C1 is selected for the first group, the C4' third group view is selected for the group, the C2 is selected for the first, the C5 is selected for the second group, and the C5 is selected for the second group. The digital input code is 2, and the advanced dynamic component matching logic 42 will extract the components from the next group (ie, the third group) of the first *most (four) group _ 卩 second group). And it will start from the last selected digit/analog component (that is, the second digit/analog component (ie C7) of the second group). So the dynamic component is 0697-A40463TWF 12
λ 正替換頁 1301705 • 配邏輯42首先選取第三群組的C7,接著是下一個群組中 - 之接續前次最後選取數位/類比元件之數位/類比元件,亦 即第一群組之C3。 本發明之動態元件匹配邏輯可以有效地移除頻域内 . 突波,因而提高了積分三角調變器在頻域内之效能。第6 . 圖係表第4圖之本發明一實施例之積分三角調變器的輸出 頻譜,且其輸入訊號為-45(dB),其中元件間存在0. 1%〜0. 2% ® 的匹配誤差,且先進動態元件匹配邏輯42將數位/類比元 件分為三個群組。比較第3b及6圖,可以發現頻域内突波 已被移除,因此提高了積分三角調變器在頻域内之效能。 , 第7圖係表示使用傳統的資料加權平均法(DWA)(o)以及本 發明之動態元件匹配邏輯(X)之信號雜訊失真比(SNDR)。可 以發現於相較使用傳統資料加權平均法之積分三角調變 器,使用本發明之先進動態元件匹配邏輯的積分三角調變 ® 器具有較佳之信號雜訊失真比線性度。 第8圖係表示本發明一實施例之一種根據一數位輸入 碼選取數位/類比元件之方法80。首先,將複數數位/類比 元件分為複數群組,其中,群組之數量與數位/類比元件之 數量互質(步驟82)。接著根據數位輸入碼以及前次選取 之群組以及數位/類比元件,選取群組以及數位/類比元件 (步驟84),其中選取群組以及該等數位/類比元件係按照 0697-A40463TWF 13λ positive replacement page 1301705 • The matching logic 42 first selects the C7 of the third group, followed by the digit/analog component of the last last selected digit/analog component in the next group, ie the C3 of the first group . The dynamic component matching logic of the present invention can effectively remove the glitch in the frequency domain, thereby improving the performance of the integral triangular modulator in the frequency domain. Figure 2 is a diagram showing the output spectrum of the integrating delta modulator according to an embodiment of the present invention, and the input signal is -45 (dB), wherein there is 0.1% to 0. 2% ® The matching error, and the advanced dynamic component matching logic 42 divides the digital/analog components into three groups. Comparing Figures 3b and 6, it can be seen that the glitch in the frequency domain has been removed, thus improving the performance of the integral delta modulator in the frequency domain. Fig. 7 shows the signal noise distortion ratio (SNDR) using the conventional data weighted average method (DWA) (o) and the dynamic element matching logic (X) of the present invention. It can be found that the integral delta modulator using the advanced dynamic component matching logic of the present invention has better signal noise distortion than linearity compared to the integral delta modulator using the conventional data weighted average method. Figure 8 is a diagram showing a method 80 for selecting a digital/analog component based on a digital input code in accordance with an embodiment of the present invention. First, the complex digital/analog components are divided into complex groups, wherein the number of groups is relatively prime to the number of digital/analog components (step 82). Then, based on the digit input code and the previously selected group and digital/analog components, the group and the digit/analog component are selected (step 84), wherein the selected group and the digit/analog components are in accordance with 0697-A40463TWF.
1JU1/UJ 一預定财進行。在_—數 驟84。此外,在步驟84中,首取^ ’會重複進行步 群组之群組,且觀此接續料最後=前次最後選取 接續前次料觀數朗㈣元件之數=組之群組中, 在一下個群組裡,選取此下個群接著 數位/類比元件之數位舰元件,朗核後選取 類比元件數量相當於數位輪人碼。〜、選取到之數位/ 本發ΓΓΓ魄佳實施_露如上,㈣麟用以限定 r圍rt此項技藝者’在不脫離本發明之精神和 圍内’ *可做些許的更動與潤飾,因此本發明之保護範 圍當視後附之申請專利範圍所界定者為準。 【圖式簡單說明】 第la圖為-傳統N位元積分三角調變器之方塊圖。 第lb圖為-使用DEM技巧之傳统N位元積分三角調 變器之方塊圖。 苐2圖為於一具有8個元件之N位元類比/數位轉換 器中,使用傳統DWA技巧之示意圖。 第3a及3b圖表示第2圖之具有8個元件之3位元類 比/數位轉換器,經由三階64倍超取樣率之積分三角調變 1§ ’分別在輸入訊號為-2(dB)以及-45(dB)時,以傳統的 DWA技巧選取元件之輸出頻譜圖。 0697-A40463TWF 14 13〇17〇5 ---||a i_ % 第4圖為根據本發明一實施例所述 -角調變器。 之N位喊分三 哭第5圖為於-具有8個元件之N位元類比績位轉換 器中,使用本發明之先進動態元件匹配邏輯之示意圖。 ^ 第6圖係表第4圖之本發明一實施例之積分三角調變 在輪入訊號為—45(dB)時之輸出頻譜示意圖。 ϋ 第7圖係表一使用傳統的資料加權平均法(DWA)(〇) 乂及本發明之動態元件匹配邏輯(X)之積分三角調變器 | ’其輪入振幅對信號雜訊失真比(SNDR)之示意圖。 第8圖為根據本發明一實施例所示之一種根據一數 位輪入碼選取數位/類比元件之方法。 【主要元件符號說明】 1G ' 20、40〜積分三角調變器 B 12〜壓法器 14〜迴路濾波器 16〜N位元量化器 18〜N位元數位/類比轉換器 22〜動態元件匹配邏輯 42〜先進動態元件匹配邏輯 C1〜C8〜數位/類比元件1JU1/UJ is scheduled to be carried out. At _ - number 84. In addition, in step 84, the first take ^ ' will repeat the group of the step group, and the last batch of the last selection = the last time before the last selection of the number of elements (four) of the number of components = group, In the next group, select the digital ship component of the next group followed by the digital/analog component. After the core is selected, the number of analog components is equivalent to the digital wheel human code. ~, select the number of digits / the hairpin 实施 good implementation _ dew as above, (four) lin to limit r rt this artist 'without the spirit and scope of the invention' * can make some changes and refinements, Therefore, the scope of the invention is defined by the scope of the appended claims. [Simple description of the figure] The first picture is a block diagram of a conventional N-bit integral triangular modulator. Figure lb shows a block diagram of a conventional N-bit integral delta modulator using DEM techniques. The 苐2 diagram is a schematic diagram of a conventional DWA technique used in an N-bit analog/digital converter with 8 components. Figures 3a and 3b show the 3-bit analog/digital converter with 8 components in Figure 2, which is converted by the third-order 64-times oversampling rate. 1§ 'In the input signal is -2 (dB) And -45 (dB), the output spectrum of the component is selected by the traditional DWA technique. 0697-A40463TWF 14 13〇17〇5 ---||a i_ % FIG. 4 is an angle modulator according to an embodiment of the invention. N-bit shouting three crying Figure 5 is a schematic diagram of the advanced dynamic component matching logic of the present invention in an N-bit analog-to-performance converter having eight components. ^ Fig. 6 is a diagram showing the output spectrum of an embodiment of the present invention in the fourth embodiment of the present invention when the round-in signal is -45 (dB). ϋ Figure 7 shows the use of the traditional data weighted average method (DWA) (〇) 乂 and the dynamic component matching logic (X) of the present invention, the integral triangular modulator | 'the round-in amplitude versus signal noise distortion ratio Schematic diagram of (SNDR). Figure 8 is a diagram showing a method of selecting a digital/analog component based on a digital wheel-in code according to an embodiment of the invention. [Description of main component symbols] 1G '20, 40~ Integral triangular modulator B 12~Volume 14 to loop filter 16 to N bit quantizer 18 to N bit digit/analog converter 22 to dynamic component matching Logic 42 ~ advanced dynamic component matching logic C1 ~ C8 ~ digital / analog components
0697-A40463TWF 150697-A40463TWF 15
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