546991 五、發明說明（1 ) 枝術領域 本發明揭示可調光鎭流器系統。 - 發明背景 在提供螢光燈可調整照明位準之電源的現有鎭流器電路 中，使用許多不同方法來調光控制。用於調光控制之一種 普通方法使用相位控制裝置，諸如向（交流觸發）三極體 (t I* i a c )。相位控制裝置使用來修改交流（AC )電源信號之 點火相位角（firing phase angle)。同樣地，調光鎭流器 電路根據點火相位角使得螢光燈可控制地調光。 用於調光控制之另一普遍方法是相據直流（DC)輸入，諸 如0至1 0伏特DC輸入，而不同於AC電源信號。本方法中， 反相器電路根據DC輸入之大小（magni etude)可控制地使 得螢光燈調光。 附圖之簡蜇說明 本發明特定地揭示在申請專利範圍。然而，本發明其他 特徵參照本文下述詳細說明書伴以附圖，將變得更顯而易 見，其中： 第1圖是雙重控制調光鎭流器裝置之實施例方塊圖； 第2圖是第1圖配置中電壓-對-PWM轉換器、點火角-對 一PWM轉換器、光耦合器及濾波器之較佳實施例槪略圖示； 第3圖是第1圖配置中PFC/反相器之較佳實施例槪略圖 示； 第4圖是用於控制燈之雙重控制調光鎭流器裝置替代實 546991 五、發明說明（2) 施例方塊圖； 第〜5圖是第4圖配置中點火角-對- 轉換器、光耦合 器及濾波器之較佳實施例槪略圖示； 第6圖表示第5圖實施例中大致全導通情況之實例波形； 及 第7圖表示第5圖實施例中大致90Q導通情況之實例波 形。 較佳實施例之詳細說明 本發明實施例提供一種雙重控制調光鎭流器裝置。雙重 控制調光鎭流器裝置之實施例能接受及提供兩種調光控制； 電源線上調光控制及非電源線上調光控制。電源線上調光 控制響應雙向三極體所產生.截相AC電源信號較佳。非電 源線上調光控制響應DC控制信號較佳。本發明實施例優 點在於提供一種可和多種調光控制方法共用之鎭流器，而 且其可使用於多燈應用。 如本專利申請案中所使用，用語”燈”通常包括放電燈。 其不僅包括螢光燈，也包括其他型式放電燈之諸如高壓放 電（ΗID )燈。 第1圖是用於控制燈20之雙重控制調光鎭流器裝置實 施例的方塊圖。裝置接收來自AC電源線22及24之主電 源。AC電源線22及24分別可稱爲，，活線，，及，，中性線，，，或 分別爲”電源線”及”共用線”。 截相雙向二極體26可耦接到AC電源線22來提供燈20 -4- 546991 五、發明說明（3) 調光之電源型式控制。截相雙向三極體26變動截相電源 信號之點火角來使得其調光控制信號編碼化。雙重控制調 光鎭流器裝置可根據點火角來使得燈20調光。 非電源線上調光控制信號可經輸入30及32來接收。較 佳地，非電源線上調光控制信號包含跨接在輸入30及32 之DC電壓。DC電壓可在請如0VDC至10VDC之範圍內變 動。DC電壓較佳地具有大小小於AC電源信號者。雙重控 制調光鎭流器裝置進一步可根據DC電壓來使得燈20調 光。 EMI(電磁干擾）濾波器34耦接到雙向三極體26AC電源 線24及接地線36之輸出。EMI濾波器34提供AC信號到 其所耦接之整流器38。整流器38整流AC信號來施加到其 所耦接之功率因數修正（PFC)/反相器電路40。PFC/反相器 電路40根據自整流器38所接收之電力及自調光位準輸入 42所接數之調光位準指令信號來控制及供給電源到燈 20 ° 點火角-對-PWM(脈寬調變）轉換器44耦接到整流器38 之輸出。點火角-對-PWM轉換器44產生根據整流器38輸 出之點火角來調變脈寬的脈衝信號。 濾波器46之諸如低通濾波器響應點火角-對-PWM轉器 44。濾波器46產生信號，具有和點火角-對-PWM轉換器44 之脈寬相關的DC電壓位準。來自濾波器46之信號施加到 調光位準輸入42來提供調光位準指令信號。PFC/反相器 五、發明說明（4) 電路40根據在調光位準輸入42之調光位準指令信號來使 -得燈20調光。因此，點火角-對-PWM轉換器44、濾波器46 及PFC/反相器電路40根據截相雙向三極體26所產生點火 角來共同使提燈20調光。 電壓-對-PWM轉換器50響應輸入30及32。電壓-對-PWM轉換器50產生脈衝信號，其脈寬根據輸入30和32間 之電壓來調變。 光耦合器52耦接電壓-對-PWM轉換器50到濾波器46。 光耦合器52使得電壓·對- PWM轉換器50及輸入30及32 光隔離點火角-對-PWM濾波器44。 濾波器46產生信號，具有和來自電壓-對-PWM轉換器50 之脈寬相關的DC電壓位準。來自濾波器46之信號施加到 調光位準輸入42來提供調光位準指令信號。PFC/反相器 電路40根據調光位準指令信號來使得燈20調光。因此， 電壓-對- PWM轉換器50、光耦合器52、濾波器46及PFC/ 反相器電路40根據輸入30及32來共同作業使得燈20調 光。 第2圖是第1圖雙重控制調光鎭流器裝置實施例之槪略 圖示。點火角-對-PWM轉換器44包含微控制器60。微控 制器60具有輸入62,經電阻器64來耦接到第1圖之整流 器38。稽納二極體70耦接在輸入端62及鎭流器接地兩者 之間。微控制器60程式規畫來轉換在輸入端62處所接收 點火角信號成爲在輸出端72處所提供之脈寬調變信號。 546991 五、發明說明（5) 電路45接收來自點火角對PMW轉換器44之輸出端72。 電路45包含電晶體74、電阻器75、稽納二極體76及電 阻器80。來自點火角-對-PWM轉換器44之輸出端72經電 阻器75來耦接到電晶體74之基極。電晶體74具有射極 耦接到鎭流器接地，而集極以串聯組合稽納二極體76及電 阻器80來耦接到電源線VCC。電晶體74之集極耦接到濾 波器46的輸入端。 電壓-對-PWM轉換器50包含電容器82,耦接在輸入端30 及輸入32之間。二極體具有陰極耦接到輸入端30,陽極耦 接到電晶體86之基極。電晶體86具有集極耦接到電源線 VCC，而基極經串聯組合電阻器90及92來耦接到電源線 VCC。稽納二極體94耦接在控制接地及電阻器90及92之 接點兩者間；如在本文中所使用”控制接地”當然在區別及 分別”鎭流器接地”，因爲該兩個接地事實上對大地接地是 在非常不同電位。電晶體96具有閘極耦接到輸入端32，源 極耦接到控制接地。電晶體86具有射極經串聯組合之電 阻器1 00及1 02來耦接到控制接地。 電阻器100及102之接點耦接到PWM控制電路之空檔時 間控制（DTC)輸入端104,諸如具有零件號碼TL494。在電 壓-對- PWM轉換器50中上述組件作用在根據電阻器100及 102之値，來使得輸入端30及32間的電壓分壓而施加到 DTC輸入端1 04。上述組件進一步作用在限制所施加到DTC 輸入端104之最大及最小電壓。 546991 五、發明說明（6) PWM控制電路106具有以定時電阻器110及定時電容器 112所控制之晶片上振盪器（〇n-chip osci 1 lator)。PWM 控制電路106也具有晶片上之第一誤差放大器及第二誤差 放大器。第一誤差放大器之非反相輸入11 3及第二誤差放 大器之非反相輸入端1 1 4各耦接到接地。第一誤差放大器 之反相輸入端1 1 5及第二誤差放大器之反相輸入端11 6耦 接到晶片上參考調整器（reference regulator)之參考端 117° PWM控制電路106具有晶片上之輸出電晶體，可由集極端 1 1 8及射極端1 1 9來接達。集極端1 1 8耦接到電源線 VCC。射極端119經電阻器120來耦接到光耦合器52之輸 入端。 在上述架構中，PWM控制電路106在射極端119處產生具 有視DTC輸入端104處之電壓而定來調變脈寬的脈衝信 號。 光耦合器52具有射極射輸出端耦接到鎭流器接地，而集 極輸出端經由串聯組合之稽納二極體76及電阻器80來耦 接到電源線VCC。光耦合器52之集極輸出端及電晶體74 之集極兩者耦接到濾波器46之輸入端。 濾波器46包含其形成低通濾波器之電阻器140及電容 器142。濾波器146輸出信號，具有根據以點火角-對-PWM 轉換器44所產生信號或電壓-對- PWM轉換器50所產生信 號之脈寬的DC位準。546991 V. Description of the invention (1) Field of branch surgery The present invention discloses a dimmable ballast system. -BACKGROUND OF THE INVENTION In existing ballast circuits that provide power for fluorescent lamps with adjustable lighting levels, many different methods are used for dimming control. A common method for dimming control uses a phase control device such as a triac (t I * i a c). The phase control device is used to modify the firing phase angle of an alternating current (AC) power signal. Similarly, the dimming ballast circuit allows the fluorescent lamp to be dimmed controllably based on the ignition phase angle. Another common method for dimming control is based on a direct current (DC) input, such as a 0 to 10 volt DC input, rather than an AC power signal. In this method, the inverter circuit can control the dimming of the fluorescent lamp according to the size of the DC input (magni etude). Brief description of the drawings The present invention is specifically disclosed in the scope of patent application. However, other features of the present invention will become more apparent with reference to the following detailed description herein accompanied by the accompanying drawings, in which: FIG. 1 is a block diagram of an embodiment of a dual control dimming ballast device; FIG. 2 is FIG. 1 The configuration of the voltage-to-PWM converter, ignition angle-to-to-PWM converter, optocoupler, and filter in the configuration is not shown in the diagram; Figure 3 is a diagram of the PFC / inverter in the configuration of Figure 1. The preferred embodiment is schematically shown; Figure 4 is a dual control dimming ballast device used to control the lamp instead of 546991. 5. Description of the invention (2) Example block diagram; Figures 5 to 5 are the configuration of Figure 4 The preferred embodiment of the intermediate firing angle-to-converter, optocoupler, and filter is not shown in the diagram; FIG. 6 shows an example waveform of approximately full conduction in the embodiment of FIG. 5; and FIG. 7 shows the fifth embodiment. An example waveform of approximately 90Q conduction in the embodiment of the figure. Detailed description of the preferred embodiment An embodiment of the present invention provides a dual-control dimming ballast device. The embodiment of the dual-control dimming ballast device can accept and provide two kinds of dimming control; dimming control on the power line and dimming control on the non-power line. Power line dimming control response is generated by bidirectional triode. Phase-cut AC power signal is better. The non-power line dimming control responds better to the DC control signal. An advantage of embodiments of the present invention is to provide a ballast which can be shared with multiple dimming control methods, and which can be used in multi-lamp applications. As used in this patent application, the term "lamp" generally includes a discharge lamp. It includes not only fluorescent lamps, but also other types of discharge lamps such as high-voltage discharge (ΗID) lamps. FIG. 1 is a block diagram of an embodiment of a dual control dimming ballast device for controlling a lamp 20. As shown in FIG. The device receives main power from AC power lines 22 and 24. The AC power lines 22 and 24 may be called, live lines, and, neutral lines, or, respectively, "power lines" and "common lines". The phase-cut bidirectional diode 26 can be coupled to the AC power line 22 to provide the lamp 20 -4- 546991. V. Description of the invention (3) Dimming power supply type control. The phase-cut bidirectional transistor 26 changes the ignition angle of the phase-cut power signal to encode its dimming control signal. The dual control dimming ballast device can dim the lamp 20 according to the ignition angle. Dimming control signals on non-power lines can be received via inputs 30 and 32. Preferably, the dimming control signals on non-power lines include DC voltages across inputs 30 and 32. The DC voltage can be changed within the range of 0VDC to 10VDC. The DC voltage preferably has a magnitude smaller than the AC power signal. The dual control dimming ballast device can further dim the lamp 20 based on the DC voltage. An EMI (electromagnetic interference) filter 34 is coupled to the output of the bidirectional triode 26AC power line 24 and the ground line 36. The EMI filter 34 provides an AC signal to a rectifier 38 to which it is coupled. Rectifier 38 rectifies the AC signal to apply to a power factor correction (PFC) / inverter circuit 40 to which it is coupled. The PFC / inverter circuit 40 controls and supplies power to the lamp 20 ° according to the power received from the rectifier 38 and the dimming level command signal received from the self-dimming level input 42. Ignition angle-pair-PWM (pulse A wide modulation converter 44 is coupled to the output of the rectifier 38. The ignition angle-to-PWM converter 44 generates a pulse signal that adjusts the pulse width according to the ignition angle output from the rectifier 38. The filter 46, such as a low-pass filter, responds to the ignition angle-to-PWM converter 44. The filter 46 generates a signal having a DC voltage level related to the pulse width of the ignition angle-to-PWM converter 44. A signal from the filter 46 is applied to the dimming level input 42 to provide a dimming level command signal. PFC / Inverter V. Description of the Invention (4) The circuit 40 causes the lamp 20 to be dimmed according to the dimming level command signal of the dimming level input 42. Therefore, the ignition angle-to-PWM converter 44, the filter 46, and the PFC / inverter circuit 40 collectively dim the lantern 20 based on the ignition angle generated by the phase-cut bidirectional triode 26. The voltage-to-PWM converter 50 responds to inputs 30 and 32. The voltage-to-PWM converter 50 generates a pulse signal whose pulse width is adjusted according to a voltage between inputs 30 and 32. The opto-coupler 52 couples the voltage-to-PWM converter 50 to the filter 46. The optocoupler 52 optically isolates the voltage-to-PWM converter 50 and the inputs 30 and 32 from the ignition angle-to-PWM filter 44. The filter 46 generates a signal having a DC voltage level related to the pulse width from the voltage-to-PWM converter 50. A signal from the filter 46 is applied to the dimming level input 42 to provide a dimming level command signal. The PFC / inverter circuit 40 dims the lamp 20 according to the dimming level command signal. Therefore, the voltage-to-PWM converter 50, the photocoupler 52, the filter 46, and the PFC / inverter circuit 40 work together according to the inputs 30 and 32 so that the lamp 20 is dimmed. Fig. 2 is a schematic diagram of the embodiment of the dual control dimming ballast device of Fig. 1. The ignition angle-to-PWM converter 44 includes a microcontroller 60. The microcontroller 60 has an input 62 and is coupled to a rectifier 38 in Fig. 1 via a resistor 64. The zener diode 70 is coupled between the input terminal 62 and the ballast ground. The microcontroller 60 is programmed to convert the ignition angle signal received at the input terminal 62 into a pulse width modulation signal provided at the output terminal 72. 546991 V. Description of the invention (5) The circuit 45 receives the output terminal 72 from the ignition angle to PMW converter 44. The circuit 45 includes a transistor 74, a resistor 75, an audit diode 76, and a resistor 80. The output terminal 72 from the ignition angle-to-PWM converter 44 is coupled to the base of the transistor 74 via a resistor 75. Transistor 74 has an emitter coupled to the ground of the inverter, and a collector coupled to the power supply line VCC in series with an integrated diode 76 and a resistor 80. The collector of the transistor 74 is coupled to the input of the filter 46. The voltage-to-PWM converter 50 includes a capacitor 82, which is coupled between the input terminal 30 and the input 32. The diode has a cathode coupled to the input terminal 30 and an anode coupled to the base of the transistor 86. Transistor 86 has a collector coupled to the power line VCC, and a base coupled to the power line VCC via a series combination of resistors 90 and 92. The zener diode 94 is coupled between the control ground and the contacts of the resistors 90 and 92; as used in this article, "control ground" is of course different and separate from "ballast ground" because the two Grounding is in fact a very different potential to ground. The transistor 96 has a gate coupled to the input terminal 32 and a source coupled to the control ground. Transistor 86 has an emitter coupled to a control ground via resistors 100 and 102 combined in series. The contacts of the resistors 100 and 102 are coupled to a neutral time control (DTC) input 104 of the PWM control circuit, such as having a part number TL494. In the voltage-to-PWM converter 50, the above-mentioned components act to divide the voltage between the input terminals 30 and 32 to be applied to the DTC input terminal 104 according to the resistor 100 and 102. The above components further limit the maximum and minimum voltages applied to the DTC input 104. 546991 V. Description of the invention (6) The PWM control circuit 106 has an on-chip oscillator (On-chip osci 1 lator) controlled by a timing resistor 110 and a timing capacitor 112. The PWM control circuit 106 also has a first error amplifier and a second error amplifier on the chip. The non-inverting input 11 3 of the first error amplifier and the non-inverting input 1 1 4 of the second error amplifier are each coupled to ground. The inverting input terminal 1 1 5 of the first error amplifier and the inverting input terminal 11 6 of the second error amplifier are coupled to the reference terminal 117 ° of the reference regulator on the chip. The PWM control circuit 106 has an output on the chip. The transistor can be accessed by the collector terminal 1 1 8 and the emitter terminal 1 1 9. The collector terminal 1 1 8 is coupled to the power line VCC. The emitter terminal 119 is coupled to the input terminal of the opto-coupler 52 via a resistor 120. In the above-mentioned architecture, the PWM control circuit 106 generates a pulse signal at the emitter terminal 119 having a pulse width which is adjusted according to the voltage at the DTC input terminal 104. The photocoupler 52 has an emitter output terminal coupled to the ground of the current source, and a collector output terminal coupled to the power line VCC via a series-combined zener diode 76 and a resistor 80. Both the collector output of the photocoupler 52 and the collector of the transistor 74 are coupled to the input of the filter 46. The filter 46 includes a resistor 140 and a capacitor 142 which form a low-pass filter. The output signal of the filter 146 has a DC level based on the pulse width of the signal generated by the ignition angle-to-PWM converter 44 or the voltage generated from the voltage-to-PWM converter 50.
546991 五、發明說明（7) 較佳零件號碼及組件値如表1所示。然而，當然替代性 實施例具有替代性零件號碼及/或組件.値也是在本發明範 圍內。 表1 組 件 零件號碼/組件値 光 耦 合 器52 5IL00401 微 控 制 器60 PIC12C508 電 阻 器 64 200V歐姆 稽 納 極體70 4.7伏特 電 晶 體 74 2Ν3904 電 阻 器 75 2 . 3Κ歐姆 稽 納 極體76 3 . 3伏特 電 阻 器 80 10Κ歐姆 電 容 器 82 6800PF，600 伏特 二 極 體 84 RGP10J 電 晶 體 86 2N3904 電 阻 器 90 10K歐姆 電 阻 器 92 10K歐姆 稽 納 二 極體94 48L01162S20，15 伏特 電 晶 體 96 48L001 186,600 伏特， 電 阻 器 100 6 . 8K歐姆 電 阻 器 102 3.6K歐姆 PWM 控制電路106 TL494 546991 五、發明說明（8) 電阻器11 0 電容器112 10K歐姆 0 . 1 2微法拉 電阻器120 3.6K歐姆 電阻器140 10K歐姆 電容器142 1 0微法拉 如第3圖所示，PFC/反相器電路40可以實施爲啓動轉換 器500組合半橋式反相器600及串接諧振輸出電路700。 啓動轉換器500包含電感器510、電晶體520、啓動控 制電路530、整流器540及能量儲存電容器550。啓動轉 換器500接受在整流器38輸出端處之全波整流（但大致未 濾波）電壓（第1圖），且提供跨接在電容器5 50之大致濾波 DC電壓。跨接電容器550之DC電壓具有大於在整流器38 輸出端處全波整流電壓之降値。此外，當適當地設計及控 制，啓動轉換器500提供高程度功率因素修正，使得自AC 主電源所取得電流大致和AC主電壓同相位。啓動轉換器 500也確保自AC主電源所取得電流具有大致和AC主電壓 相同之波形。 反相器600包含第一電晶體610,第二電晶體620、驅動 器電路640及比較器電路660。驅動器電路640使得電晶 體610及620以大致互補形式地導通及不導通，諸如當電 晶體610導通時，電晶體620不導通，反之亦然。驅動器電 路640交換電晶體610及620之頻率可以響應外部調光輸 入來變動，因而提供燈之可調整照明位準。 -10- 546991 五、發明說明（9) 諧振輸出電路700包含變壓器、第一電容器720、第二 電容器730及燈電流感測電路740。變壓器具有一次繞組 712作用爲電感器。一次繞組712及第一電容器720 —起 作用爲串接諧振電路，其提供雙重功能爲（i )供給高電壓使 得燈點火；及（i i )在燈點火後限制所供給到燈之電流。二 次繞組7 1 4、7 1 6提供加熱燈之陰極的電力。第二電容器 730作用爲DC阻斷電容器，確保所提供到燈之電流大致是 AC(即，具有小或無DC分量）。燈電流感測電路740包含二 極體742、744及電阻器746。跨接電阻器746所產生電壓 和燈電流之値成比例。二極體 742、744作用來”導 引”（“ s t e e r ”）燈電流之正半週經過電阻器746，同時允許燈 電流之負半週旁通過電阻器746。因爲僅燈電流之正半週 需要流經電阻器746,以便允許監測燈電流，二極體742、 744之導引功能因而避免在電阻器746內不需要之額外電 力消耗。 驅動器電路640包含具有頻率控制輸入端644之驅動器 積體電路（1C) 642。例如，驅動器IC642可使用工業零件號 碼IR2 155來獲得。驅動器1C以輸入端644及鎭流器接地 兩者間顯現之有效電阻所決定頻率來提供反相器電晶體的 互補交換。在輸入端644及鎭流器接地間顯現之有效電阻 視電阻器646、648之値及在比較器電路660之輸出端處 所提供信號而定。 比較器電路660包含具有輸入端6 64、666及輸出端668 -11- 546991 五、發明說明（1〇) 之運算放大器IC662。例如，運算放大器IC662可以工業零 件號碼LM2 9 04來獲得。在第3圖中，IC662之腳端1，2及 3對應1C內部運算放大器（op-amp)之輸出端及輸入端；更 明確地，腳端1內部連接到〇 p - in a p之輸出端，腳端2運接 到op - amp之反相（一）輸入端，而腳端3連接到op - amp之 非反相（十）輸入端。 比較器電路660比較兩種信號：（i )來自燈電流感測電路 740之燈電流反饋信號；及（ii)在濾波器46之輸出端42處 所提供調光位準指令信號（第1圖中）。比較器電路660響 應任何兩個數値間之差異而在腳端1所提供適當輸出。同 樣地，在腳端1處之輸出控制反相器驅動器IC642之輸入 端64.4及鎭流器接地間所顯現的有效電阻，其同樣地決定 驅動器IC642交換反相器電晶體之頻率。 和驅動器電路640及比較器電路660大致相同之電路詳 細作業詳細說明在美國專利第5,457,360號，其中公開說 明倂在本文中參考。 第4圖是用於控制燈220之雙重控制鎭流器裝置替代性 實施例的方塊圖。裝置接收來自AC電源線222及224之 主電源。AC電源線222及224可以分別地稱爲”活線”及，， 中性線”，或分別爲”電源線”及”共用線”。 截相雙向三極體226可以耦接到AC電源線222來提供 用於燈220調光之電源線型式控制。截相雙向三極體226 變動截相電源信號之點火角來使得其調光控制信編碼。雙 -12- 五、發明說明（11) 重控制調光鎭流器裝置可根據點火角來使得燈220調光。 非電源線調光控制信號可-經輸入端230及23 2來接收。 較佳地非電源線調光控制信號包含DC電壓施加跨接在輸 入端230及23 2。DC電壓可在諸如0VDC至10VDC範圍內 變動。較佳地，DC電壓具有大小小於AC電力信號者。雙重 控制調光鎭流器裝置可進一步根據DC電壓來使得燈220 調光。 EMI濾波器23 4耦接到雙向三極體226AC電源線224及 大地接地線236之輸出端。EMI濾波器234提供AC信號到 其所耦接之整流器238。整流器238整流濾波AC信號來施 加到其所耦接之PFC/反相器電路240。PFC/反相器電路 240根據來自整流器23 8所接收電力及來自輸入端.242所 接收頻率控制信號來控制及供給電源給燈220。 點火角-對-PWM轉換器244耦接到整流器23 8之輸出 端。點火角-對- PWM轉換器244產生根據整流器238輸出 之點火角來調變脈寬之脈衝信號。 光耦合器245耦接點火角-對-PWM轉換器244到濾波器 246諸如低通濾波器。濾波器246產生信號，具有和點火角 -對-PWM轉換器244之脈寬相關的DC電壓位準。來自濾波 器246之信號施加到輸入端230。光耦合器245使得輸入 端230及2 3 2光隔離點火角-對- PWM轉換器244及其他鎭 流器電路。 調光調整電路248響應輸入端230及232至濾波器246 -13- 546991 五、發明說明（12) 之輸出端及自電源線249之感測燈電流信號。調光調整電 路248根據所感測燈電流及所施加到輸入端230及23 2之 DC電壓信號來產生頻率控制信號。調光調整電路248以光 耦合器250來耦接到輸入端242。PFC/反相器電路240根 據自光耦合器250所接收頻率控制信號來使得燈220調 光。 點火角-對-PWM轉換器244、光耦合器245、濾波器 246、調光調整電路248、光耦合器250及PFC/反相器電 路240根據截相雙向三極體226所產生相位角來共同使得 燈2 20調光。調光調整電路248、光耦合器2 50及PFC/反 相器電路240根據輸入端230及232間之電壓來共同使得 燈220調光。 第5圖是第4圖之點火角-對- PWM轉換器244、光耦合 器245、濾波器246的實施例槪略圖示。點火角-對-PWM 轉換器244包含微控制器260。微控制器260具有輸入端 26 2,以電阻器264來耦接到第4圖之整流器238。輸入端 262經稽納二極體270來耦接到接地。微控制器260程式 規畫來轉換在輸入端262處所接收點火角成爲在輸出端 272處所提供脈寬調變信號。輸出端272以電阻器292來 耦接到光耦合器245。 光耦合器245具有射極輸出端耦接到鎭流器接地，及集 極輸出端經電阻器294來耦到10伏特電源線。電容器296 使得光耦合器245之集極輸出端耦接到鎭流器接地。電阻 -14- 546991 五、發明說明（13) 器300使得光耦合器24 5之集極輸出端耦接到電晶體302 之基極。電晶體302—之射極連接到鎭流器接地。電晶體 3 02之集極以電阻器304來耦接到10伏特電源線。 電晶體302之集極以串聯組合電阻器306及二極體310 及312來耦接到輸入端230。二極體310及312之接點處 以電容器3 1 4耦接到鎭流器接地。 上述點火角-對-PWM轉換器244之實施例在輸出端272 處產生責務循環（duty cycle)響應來自整流器所整流截相 電壓而變動的PWM信號。第6及7圖表示當截相調光器使 用來串接鎭流器時所整流電壓之實例。第6圖表示大致全 導通情況之整流電壓波形320。在本情形中，燈電流大約是 1 80毫安培。第7圖表示大約900導通情況之整流電壓波 形3 22。在本情形中，燈電流約是80毫安培。 第6圖進一步圖示根據整流電壓波形320在輸出端272 處所產生脈衝波形。第7圖進一步圖示根據整流電壓波形 322在輸出端272處所產生脈衝波形324。光耦合器245 及包括電晶體302之電路共同隔離及重新產生在輸出端 272處所產生之波形。在電晶體302之集極處所顯現重新 產生波形具有約1 0伏特之大小。跨接電容器3 1 4之電壓 具有根據重新產生波形之脈寬的DC位準。DC位準自約 10VDC(第6圖中之波形330 )至約10VDC(第7圖中之波形 332 )來變動，因而使得調光鎭流器所控制0至10VDC之先 輸出調光。 -15- 546991 五、發明說明（14) 表π表示較佳零件號碼及組件値。然而，當然具有替代 性零件號碼及/或替代性組件値之替代性實施例也在本發 明之範圍內。 表Π 組 件 零件號碼/組件値 微 控 制 器260 PIC12C509 電 阻 器 264 200K歐姆 稽 納 二 極體270 4 . 7伏特 電 容 器 288 0 . 1微法拉 電 阻 器 292 5K歐姆 電 阻 器 294 20K歐姆 電 容 器 296 1000PF 電 阻 器 300 200K歐姆 電 阻 器 304 10K歐姆 電 阻 器 306 200歐姆 二 極 體 310 1N4148 二 極 體 312 1N4148 電 容 器 314 22微法拉 因而，本文中已說明包括雙重控制調光鎭流器之較佳實 施例的數個實施例。 顯然地對擅於本技術者可以許多方式來修改本發明所說 明，且可實施不同於上述及所明確地發表較佳方式的許多 實施例。例如，在替代性實施例中，一些組件對如以較佳形 -16- 546991 五、發明說明（15) 式可間接地耦接而不直接地耦接。進一步，替代性相位控 制調光器可替代本文所發表截相雙向三極體。 因而，申請專利範圍係涵蓋本發明之全部修改例，其在本 發明之真精神及範圍內。 符號說明 20,220 燈 22,222 線交流電源線 24,224 中性線交流電源線 26,226 截相雙向三極體 30,32,62,230,232 輸入端 34,234 電磁干擾濾波器 36,236 接地線 38,238 整流器 40,240 功率因數修正（pFC ) /反相器電路 42,242 調光位準輸入 44,244 點火角-對- PWM轉換器 45 電路 46，146，246 濾波器 50 電壓-對-PWM轉換器 52,245 光親合器 60,260 微控制器 62,262 輸入細 64,75,80,90,92,ΐω,102,120, 140,264,292,294,300,304,306 電阻器 -17- 546991 五、發明說明（16) 70，76 稽納二極體 72 ,272 輸出端 〜 74,86,96,302,520,610 電晶體 82，142，296，314 電容器 104 空檔時間控制輸入端 106 PWM控制電路 110 定時電阻器 112 定時電容器 1 13 〜1 16 反相器輸入端 117 參考端 118 集極端 119 射極端 310,312 二極體 320,302 整流電壓波形 500 啓動轉換器 510 電感器 520 電晶體 530 啓動控制電路 540 整流器 550 電容器 600 半橋式反相器 610 第一電晶體 620 第二電晶體 -18- 546991 五、發明說明（17) 640 驅動器電路 642 — s 驅動器1C 644 輸入端 646,648 電阻器 660 比較器 662 放大器1C 664,666 輸入端 700 串接諧振輸出電路 712 一次繞組 714,716 二次繞組 730 第二電容器 740 電流感測電路 742,744 二極體 746 電阻器 248 調光調整電路 249 電源線 250 光親合器 -19-546991 V. Description of the invention (7) The preferred part numbers and components are shown in Table 1. However, of course alternative embodiments have alternative part numbers and / or components. It is also within the scope of the invention. Table 1 Component Part Numbers / Components 値 Optocoupler 52 5IL00401 Microcontroller 60 PIC12C508 Resistor 64 200V Ohm Zona Polar Body 70 4.7 Volt Transistor 74 2N3904 Resistor 75 2. 3K Ohm Zona Polar Body 76 3 .3 Volt Resistor 80 10K ohm capacitor 82 6800PF, 600 volt diode 84 RGP10J transistor 86 2N3904 resistor 90 10K ohm resistor 92 10K ohm audit diode 94 48L01162S20, 15 volt transistor 96 48L001 186,600 volt, resistor 100 6. 8K ohm resistor 102 3.6K ohm PWM control circuit 106 TL494 546991 5. Description of the invention (8) Resistor 11 0 capacitor 112 10K ohm 0.1 .2 microfarad resistor 120 3.6K ohm resistor 140 10K ohm capacitor 142 As shown in FIG. 3, the 10 microfarad can be implemented as a start-up converter 500 combining a half-bridge inverter 600 and a series resonant output circuit 700. The startup converter 500 includes an inductor 510, a transistor 520, a startup control circuit 530, a rectifier 540, and an energy storage capacitor 550. The start-up converter 500 accepts a full-wave rectified (but substantially unfiltered) voltage at the output of the rectifier 38 (FIG. 1), and provides a substantially filtered DC voltage across the capacitor 5050. The DC voltage of the jumper capacitor 550 has a drop greater than the full-wave rectified voltage at the output of the rectifier 38. In addition, when properly designed and controlled, the start-up converter 500 provides a high degree of power factor correction so that the current obtained from the AC main power source is approximately in phase with the AC main voltage. Starting the converter 500 also ensures that the current obtained from the AC main power source has a waveform that is approximately the same as the AC main voltage. The inverter 600 includes a first transistor 610, a second transistor 620, a driver circuit 640, and a comparator circuit 660. The driver circuit 640 makes the transistors 610 and 620 conductive and non-conductive in a substantially complementary form, such as when the transistor 610 is on, the transistor 620 is not on, and vice versa. The frequency of the driver circuit 640 switching transistors 610 and 620 can be changed in response to the external dimming input, thus providing an adjustable lighting level of the lamp. -10- 546991 V. Description of the Invention (9) The resonant output circuit 700 includes a transformer, a first capacitor 720, a second capacitor 730, and a lamp current sensing circuit 740. The transformer has a primary winding 712 that functions as an inductor. The primary winding 712 and the first capacitor 720 function as a series resonant circuit, which provides a dual function of (i) supplying a high voltage to ignite the lamp; and (i i) limiting the current supplied to the lamp after the lamp is ignited. The secondary windings 7 1 4 and 7 1 6 provide power to the cathode of the heating lamp. The second capacitor 730 functions as a DC blocking capacitor, ensuring that the current provided to the lamp is approximately AC (ie, has a small or no DC component). The lamp current sensing circuit 740 includes diodes 742 and 744 and a resistor 746. The voltage generated across the resistor 746 is proportional to the magnitude of the lamp current. The diodes 742 and 744 act to “guide” (“s t e e r”) the positive half cycle of the lamp current through the resistor 746, while allowing the negative half cycle of the lamp current to pass through the resistor 746. Because only the positive half cycle of the lamp current needs to flow through the resistor 746 in order to allow the lamp current to be monitored, the guidance function of the diodes 742, 744 thus avoids extra power consumption that is not needed in the resistor 746. The driver circuit 640 includes a driver integrated circuit (1C) 642 having a frequency control input terminal 644. For example, the driver IC 642 can be obtained using the industrial part number IR2 155. The driver 1C provides complementary switching of the inverter transistor at a frequency determined by the effective resistance appearing between the input terminal 644 and the inverter ground. The effective resistance appearing between the input terminal 644 and the ground of the inverter depends on the signal provided at the output terminal of the comparator circuit 660 among the resistors 646 and 648. The comparator circuit 660 includes an operational amplifier IC662 having an input terminal 6 64, 666 and an output terminal 668 -11-546991. V. Invention Description (10). For example, the operational amplifier IC662 is available under the industrial part number LM2 9 04. In Figure 3, the pins 1, 2 and 3 of IC662 correspond to the output and input of the 1C internal op-amp; more specifically, pin 1 is internally connected to the output of oop-in ap , Pin 2 is connected to the inverting (a) input of op-amp, and pin 3 is connected to the non-inverting (ten) input of op-amp. The comparator circuit 660 compares two types of signals: (i) a lamp current feedback signal from the lamp current sensing circuit 740; and (ii) a dimming level command signal provided at the output terminal 42 of the filter 46 (FIG. 1) ). The comparator circuit 660 provides the appropriate output at pin 1 in response to the difference between any two numbers. Similarly, the output at pin 1 controls the effective resistance appearing between the input terminal 64.4 of the inverter driver IC642 and the ground of the inverter, which also determines the frequency at which the driver IC642 exchanges the inverter transistor. Circuit details that are substantially the same as the driver circuit 640 and the comparator circuit 660 are detailed in U.S. Patent No. 5,457,360, the disclosure of which is incorporated herein by reference. Figure 4 is a block diagram of an alternative embodiment of a dual control ballast device for controlling the lamp 220. The device receives main power from AC power lines 222 and 224. The AC power lines 222 and 224 may be referred to as “live lines” and “neutral lines”, respectively, or “power lines” and “shared lines”. The phase-cut bidirectional triode 226 may be coupled to the AC power line. 222 to provide the power line type control for the dimming of the lamp 220. The phase-cut bidirectional triode 226 changes the ignition angle of the phase-cut power signal to make its dimming control signal code. Double-12- V. Description of the invention (11) The re-control dimming ballast device can dimm the lamp 220 according to the ignition angle. The non-power line dimming control signal can be received through the input terminals 230 and 23 2. Preferably, the non-power line dimming control signal includes DC The voltage is applied across the input terminals 230 and 23 2. The DC voltage can be varied in a range such as 0VDC to 10VDC. Preferably, the DC voltage has a size smaller than the AC power signal. The dual-control dimming ballast device can further be based on DC The voltage is used to dim the lamp 220. The EMI filter 23 4 is coupled to the output of the bidirectional triode 226AC power line 224 and the earth ground line 236. The EMI filter 234 provides an AC signal to the rectifier 238 to which it is coupled. 238 rectified filtered AC signal to apply to it The coupled PFC / inverter circuit 240. The PFC / inverter circuit 240 controls and supplies power to the lamp 220 according to the power received from the rectifier 23 8 and the frequency control signal received from the input terminal .242. Ignition angle-pair -PWM converter 244 is coupled to the output of rectifier 23 8. Ignition angle-yes-PWM converter 244 generates a pulse signal that adjusts the pulse width according to the ignition angle output by rectifier 238. Optocoupler 245 is coupled to the ignition angle- The pair-PWM converter 244 to a filter 246 such as a low-pass filter. The filter 246 generates a signal having a DC voltage level related to the pulse width of the ignition angle-pair-PWM converter 244. The signal from the filter 246 is applied To the input 230. The optical coupler 245 makes the input 230 and 2 3 2 optically isolate the ignition angle-to-PWM converter 244 and other ballast circuits. The dimming adjustment circuit 248 responds to the input 230 and 232 to the filter 246 -13- 546991 V. Description of the invention (12) output terminal and the sensing lamp current signal from the power line 249. The dimming adjustment circuit 248 is based on the sensed lamp current and the DC voltage signals applied to the input terminals 230 and 23 2 To generate a frequency control signal. The adjustment circuit 248 is coupled to the input terminal 242 with a photocoupler 250. The PFC / inverter circuit 240 makes the light 220 dimmed according to the frequency control signal received from the photocoupler 250. Ignition angle-to-PWM converter 244 , The photocoupler 245, the filter 246, the dimming adjustment circuit 248, the photocoupler 250 and the PFC / inverter circuit 240 make the lamps 2 and 20 dimm together according to the phase angle generated by the phase-cut bidirectional triode 226. The dimming adjustment circuit 248, the photo coupler 250 and the PFC / inverter circuit 240 collectively make the lamp 220 dimmed according to the voltage between the input terminals 230 and 232. Fig. 5 is a schematic illustration of the embodiment of the ignition angle-to-PWM converter 244, the optical coupler 245, and the filter 246 of Fig. 4. The firing angle-to-PWM converter 244 includes a microcontroller 260. The microcontroller 260 has an input terminal 262, and a resistor 264 is coupled to the rectifier 238 of FIG. The input terminal 262 is coupled to the ground via the audit diode 270. The microcontroller 260 is programmed to convert the ignition angle received at the input terminal 262 into a pulse width modulation signal provided at the output terminal 272. The output terminal 272 is coupled to the opto-coupler 245 with a resistor 292. The opto-coupler 245 has an emitter output terminal coupled to the ground of the ballast, and a collector output terminal coupled to the 10-volt power line via a resistor 294. The capacitor 296 couples the collector output of the photocoupler 245 to the ballast ground. Resistance -14- 546991 V. Description of the invention (13) The device 300 enables the collector output terminal of the photocoupler 24 5 to be coupled to the base of the transistor 302. The emitter of transistor 302- is connected to the ballast ground. The collector of the transistor 302 is coupled to the 10 volt power line with a resistor 304. The collector of the transistor 302 is coupled to the input terminal 230 by a series combination resistor 306 and diodes 310 and 312. The junctions of the diodes 310 and 312 are coupled to the ballast ground by a capacitor 3 1 4. The above embodiment of the ignition angle-to-PWM converter 244 generates a duty cycle at the output terminal 272 in response to a PWM signal that varies from the rectified phase-cut voltage from the rectifier. Figures 6 and 7 show examples of rectified voltages when a phase-cut dimmer is used in series with a ballast. Fig. 6 shows a rectified voltage waveform 320 in a substantially fully on condition. In this case, the lamp current is approximately 180 mA. Figure 7 shows a rectified voltage waveform 3 22 of about 900 on-states. In this case, the lamp current is about 80 milliamps. FIG. 6 further illustrates a pulse waveform generated at the output terminal 272 according to the rectified voltage waveform 320. FIG. 7 further illustrates the pulse waveform 324 generated at the output terminal 272 according to the rectified voltage waveform 322. The optocoupler 245 and the circuit including the transistor 302 isolate and regenerate the waveform generated at the output terminal 272. The reproduced waveform appearing at the collector of the transistor 302 has a size of about 10 volts. The voltage across the capacitor 3 1 4 has a DC level according to the pulse width of the reproduced waveform. The DC level varies from about 10 VDC (waveform 330 in Figure 6) to about 10 VDC (waveform 332 in Figure 7), so that the output dimming controlled by the dimming current converter from 0 to 10 VDC first. -15- 546991 V. Description of the invention (14) Table π indicates the preferred part numbers and components 値. However, of course alternative embodiments with alternative part numbers and / or alternative components are also within the scope of the invention. Table Π Component part number / component 値 Microcontroller 260 PIC12C509 resistor 264 200K ohm zener diode 270 4 .7 volt capacitor 288 0. 1 microfarad resistor 292 5K ohm resistor 294 20K ohm capacitor 296 1000PF resistor 300 200K Ohm Resistor 304 10K Ohm Resistor 306 200 Ohm Diode 310 1N4148 Diode 312 1N4148 Capacitor 314 22 MicroFarads Thus, a number of preferred embodiments including a dual control dimming ballast have been described herein Examples. Obviously for those skilled in the art, the description of the present invention can be modified in many ways, and many embodiments other than the above and explicitly published preferred modes can be implemented. For example, in alternative embodiments, some component pairs may be indirectly coupled instead of directly coupled in a preferred form. Furthermore, alternative phase-controlled dimmers can replace the phase-cut bidirectional triodes published in this paper. Therefore, the scope of patent application covers all modifications of the present invention, which is within the true spirit and scope of the present invention. Symbol description 20,220 Lamp 22,222 Line AC power line 24,224 Neutral line AC power line 26,226 Phase-cut bidirectional triode 30, 32, 62, 230, 232 Input 34, 234 EMI filter 36, 236 Ground wire 38, 238 Rectifier 40, 240 Power factor correction (pFC) / Inverted Circuit 42,242 dimming level input 44,244 ignition angle-to-PWM converter 45 circuit 46,146,246 filter 50 voltage-to-PWM converter 52,245 photocoupler 60,260 microcontroller 62,262 input 64,75, 80, 90, 92, ΐω, 102, 120, 140, 264, 292, 294, 300, 304, 306 resistors -17- 546991 V. Description of the invention (16) 70, 76 Zona diode 72, 272 Output ~ 74, 86, 96, 302, 520, 610 Transistor 82, 142, 296 314 capacitor 104 neutral time control input 106 PWM control circuit 110 timing resistor 112 timing capacitor 1 13 ~ 1 16 inverter input 117 reference terminal 118 set terminal 119 emitter terminal 310,312 diode 320,302 rectified voltage waveform 500 start Converter 510 Inductor 520 Transistor 530 Start-up control circuit 540 Rectifier 550 Capacitor 600 half Bridge inverter 610 First transistor 620 Second transistor -18- 546991 V. Description of the invention (17) 640 Driver circuit 642 — s Driver 1C 644 Input terminal 646,648 Resistor 660 Comparator 662 Amplifier 1C 664,666 Input terminal 700 Series resonant output circuit 712 Primary winding 714,716 Secondary winding 730 Second capacitor 740 Current sensing circuit 742,744 Diode 746 Resistor 248 Dimming adjustment circuit 249 Power line 250 Photocoupler-19-