497325 五、發明說明（i) 【發明領域】 有關本發明申請之一主要動機，乃是申請人有鑑於目前國家正大力推動智慧財產權之觀 念’且國內業界亦受到國外極大之壓迫，因此，特別將所硏究之一些成果，於發表至國際上 學術期刊之則，先行提出申請，俾有助於建立本土化技術。 本發明係關於一種三相直接鏈型交/交流之轉換器之控制器，特別係關於僅需使用單級 轉換器即可獲得高效率之三相交/交流之轉換器之控制器，尤指同時兼具備單位功率因數且 兼具輸出源爲可變電壓可變頻率轉換器之控制器。 【先前技術】 近年來’由於局功率筒切換頻率的功率半導體元件(power semiconductor devices)(例如金 氧半場效電晶體(MOSFET)，雙極性電晶體（bipolar transistor )和絕緣閘雙極性電晶體（IGBT ) 等)的快速發展，使得脈寬調變（pulse width modulation，PWM)技術更得以輕易地使用於交 / 父流轉換器（AC/AC converter )以得到可變電壓可變頻率(variable voltage variable frequency, VVVF)之電源並兼具改善輸入電流波形品質及功因之功能。基本上，交/交流轉換器（AC/ AC converter)依其電力轉換架構上的連結方式而言，大致可以分成交流鏈型轉換器（AC-link converter)、直流鏈型轉換器（DC-link converter)及直接鏈型轉換器（direct-link converter) 等三大類。交流鏈型的架構，雖然在近年來有所發展但卻未達到一個較成熟完善的境界;而 直流鏈型乃由交/直流轉換器（AC/ DC converter)及直/交流轉換器（DC/AC converter)串 接(cascade)而成。由於該二項技術已經相當成熟，因此此類轉換器可說是現今最常用也最普 遍的一種架構。圖1所示即爲一直接鏈型之m相變η相交/交流轉換器。由於其開關元件以 矩陣之方式連接輸出與輸入，因此此種直接鏈型之交/交流轉換器亦稱爲矩陣轉換器(matrix converter)。由圖1可知相對於其它二種架構而言，直接鏈型轉換器少了中間連結之儲能元 件，因此轉換器之體積可以大大地減小。此外，此類轉換.器亦允許雙向的電力潮流，所以近 年來吸引許多硏究學者的興趣，其中又以三相交/交流轉換器最廣受注目。然而由於直接鏈 liii 第4頁 497325 五、發明說明（2) 型之交/交流轉換器無緩衝電感與電容等儲能元件，因此其所使用的雙向開關架構上，在開 關切換時無法像交/直流轉換器或直/交流轉換器所使用之單向開關中有反向的背接二極體 (body diode)可供給負載電流迴路，因而甚易造成電壓及電流突波，進而損毀開關元件。 雖然應用柔性切換技術或抑制突波的方法來達成可解決上述之開關切換突波問題，然其在控 制及硬體實現上仍過於複雜且/或使用了過多的元件，影響轉換器體積及效率。此外，就控 制器而言’目前之相關文獻所提出之方法在硬體實作上仍然十分複雜。 另就控制型式而言，直接鏈型之交/交流轉換器可分爲電壓控制型之直接鏈型交/交流轉 換器與電流控制型之直接鏈型交/交流轉換器兩大類型。一般來說，電壓控制型之直接鏈型 交/交流轉換器具改善輸入電流波形品質之功能，然而其動態響應差且轉換器之性能甚易受 到輸入電源波形之影響；電流控制型之直接鏈型交/交流轉換器雖具甚佳之動態響應與穩定 性’然輸入電流波形含高成份之低次諧波且功因較低爲其主要之缺點。此外，在兼具考慮開 關元件間之換向問題與控制機制，直接鏈型之交/交流轉換器之實體製作甚爲複雜。 【發明目的】 本發明之目的係提出一在硬體實作上十分簡易之控制器，以達到能將一種三相直 接鏈型交/交流轉換器輸入之三相交流電源轉換成可變電壓可變頻率之輸出源，並 同時兼具快速動態響應、改善輸入電流波形品質與功因等功能，且可以減少 三相直接鏈型交/交流轉換器開關元件之切換次數及消除不理想輸入電源對輸 出源之影響與開關元件切換時所產生之電壓與電流突波。 【技術內容】 1、三相直接鏈型交/交流轉換器之系統架構說明： 基本上，本發明裝置(14)與欲控制三相直接鏈型交/交流轉換器(11)(由9個雙向開關元497325 V. Description of the invention (i) [Field of invention] One of the main motivations for the application of the present invention is that the applicant has the idea that the country is vigorously promoting the intellectual property right and that the domestic industry is also greatly oppressed by foreign countries. Therefore, In particular, some of the research results will be applied to the international academic journals before they are submitted, which will help establish local technology. The present invention relates to a controller for a three-phase direct-chain AC / AC converter, in particular to a controller for a three-phase AC / AC converter that can obtain high efficiency by using only a single-stage converter, especially at the same time Controller with unit power factor and output source as variable voltage variable frequency converter. [Prior art] In recent years, power semiconductor devices (such as metal-oxide-semiconductor field-effect transistors (MOSFETs), bipolar transistors, and insulated gate bipolar transistors (eg, MOSFETs) The rapid development of IGBT, etc.) makes pulse width modulation (PWM) technology more easily used in AC / AC converters to obtain variable voltage and variable frequency. variable frequency (VVVF) power supply also has the function of improving the input current waveform quality and power factor. Basically, AC / AC converters can be roughly divided into AC-link converters and DC-links according to the connection method of their power conversion architecture. converter) and direct-link converter. The structure of the AC chain type, although it has developed in recent years, has not reached a relatively mature and perfect state; while the DC chain type consists of AC / DC converters and DC / AC converters (DC / AC converter) is cascaded. Since the two technologies are quite mature, this type of converter is arguably the most commonly used and most popular architecture today. Figure 1 shows a m-phase transition η-phase / AC converter of a direct chain type. Because its switching elements are connected to the output and input in a matrix manner, this direct-chain AC / AC converter is also called a matrix converter. It can be seen from Figure 1 that compared with the other two architectures, the direct-chain converter has fewer intermediate energy storage components, so the size of the converter can be greatly reduced. In addition, this type of converter also allows two-way power flow, so in recent years has attracted the interest of many research scholars, of which the three-phase AC / AC converter has attracted the most attention. However, because of direct chain liii, page 4 497325 V. Invention description (2) The AC / AC converter has no energy storage elements such as snubber inductors and capacitors. Therefore, the bidirectional switch architecture used by it does not behave like AC power when switching. The one-way switch used by the DC / DC converter or the DC / AC converter has a reverse body diode that can supply the load current loop, so it is easy to cause voltage and current surges and damage the switching element. . Although the flexible switching technology or the method of suppressing the surge is used to achieve the above-mentioned problem of switching surges, its control and hardware implementation is still too complicated and / or uses too many components, which affects the size and efficiency of the converter. . In addition, as far as the controller is concerned, the methods proposed in the related literature are still very complicated in terms of hardware implementation. In terms of control types, direct-chain AC / AC converters can be divided into voltage-controlled direct-chain AC / AC converters and current-controlled direct-chain AC / AC converters. Generally speaking, voltage-controlled direct-chain AC / AC converters have the function of improving the quality of the input current waveform. However, their dynamic response is poor and the performance of the converter is easily affected by the input power waveform. Current-controlled direct-chain type Although the AC / AC converter has very good dynamic response and stability, the input current waveform contains high-order low-order harmonics and the low power factor is its main disadvantage. In addition, taking into account the commutation problem and control mechanism between the switching elements, the physical production of the direct-chain AC / AC converter is very complicated. [Objective of the Invention] The purpose of the present invention is to propose a controller that is very simple in hardware implementation, so as to achieve the conversion of a three-phase AC power input from a three-phase direct-chain AC / AC converter into a variable voltage. Variable frequency output source, which also has fast dynamic response, improved input current waveform quality and power factor, and can reduce the number of switching times of three-phase direct-chain AC / AC converter switching elements and eliminate undesired input power pairs. The influence of the output source and the voltage and current surge generated when the switching element is switched. [Technical content] 1. Description of the system architecture of the three-phase direct-chain AC / AC converter: Basically, the device (14) of the present invention and the three-phase direct-chain AC / AC converter (11) to be controlled (by 9 Bidirectional switch element
IBS 第5頁 497325 五、發明說明（3) 件乂= 1，2，_·，9所組成)之系統架構’可經由圖2加以說明。因現今的功率半導體元件均爲單 向開關兀件’因此大致可由圖3所不的三種架搆加以合成。然而爲了配合本發明裝置(14)， 採用由圖3(c)所示之正向與反向開關組合而成之雙向開關之架構。雖然九個雙向開關元件有 512( = 29)種不同的組合，但扣除導致三相輸入電源間有短路且/或三相輸出電流間有開路之 情形後’僅只27種組態可茲應用。爲了方便說明起見，將此27可能的狀態列於表1並將其 分類成I、Π-ab、Π-bc、Π-ca與ΠΙ等五種類型。I類是表示三相輸出端(A，B，c份別接 在不同的三相輸入之各種組合，如（a，b，〇等；n-ab類則表示三相輸出只接在輸入端a 相及b相的各種組合狀態如（a，b，b)等。同理Π-bc類和Π-ca類是表示只接在輸入端b 相及c相和c相及a相的各種組合狀態。而m類則表示三相輸出端皆連接至同一電源端，如 (a ’ a ’ a)等，此亦即一般所謂的零電壓空間向量(zero voltage space vect〇r滕法。此外，於 輸入電源與電力電路間加入一輸入濾、波器（input filter )以消除因開關元件切換時造成輸入電 流之高頻諧波。有關本發明裝置(14)之詳細功能方塊圖則如圖4所示。首先三相輸入電壓經 冋步柄5虎產生器(13)得到6個位兀之電壓问步控制訊號，以便將一週期的輸入電壓訊號分成 12個不同之區間。此外’因本發明裝置(14)所欲控制三相直接鏈型交/交流_專換器(11)亦需兼 具功因之改善及高轉換效率之功能，所以必須考慮其輸入電流的流向是否與電壓源之極性一 致並盡量減少開關元件之切換次數。而且爲了提升轉換器之動態響應性能，必需將不理想電 源對輸出源所造成的影響排除。爲得到上述等性能，本發明裝置(14)將前述所得6個位元之 電壓同步控制訊號配合一磁滯控制器(hysteresis controller)(l5)與半頻器(16)所得到6個位元 控制訊號，以決定三相直接鏈型交/交流轉換器(11)上18個單向開關元件之切換狀態，進而 達到所欲得到之性能。至於本發明裝置(14)之工作原理，於『控制器工作原理說明』中將有 更詳盡之說明。 2、控制器工作原理說明 首先考慮如圖5所示之理想三相電壓波形。申請人將其區分成12個區間且 mm 第6頁 497325 五、發明說明（4) ’ 在每一區間裏必有其中一相電壓是在最大絕對値且在此區間都不變號，而其 餘兩相電壓不僅必不相等外並與前者相反且振幅較小。爲便利往後之分析與 說明起見，申請人定義如下所示之區間偵測信號。 表1 三相直接鏈型交/交流轉換器之切換組合表 類型 編號 A B C Swl Sw2 Sw3 Sw4 Svv5 Sw6 Sw7 Sw8 Sw9 1 A b c 1 0 0 0 1 0 0 0 1 2 A c b 1 0 0 0 0 1 0 1 0 I 3 B a c 0 1 0 1 0 0 0 0 1 4 B c a 0 1 0 0 0 1 1 0 0 5 C a b 0 0 1 1 0 0 0 1 0 6 C b a 0 0 1 0 1 0 1 0 0 7 A b b 1 0 0 0 1 0 0 1 0 8 B a a 0 1 0 1 0 0 1 0 0 Il-ab 9 A b a 1 0 0 0 1 0 1 0 0 10 B a b 0 1 0 1 0 0 0 1 0 11 A a b 1 0 0 1 0 0 0 1 0 12 B b a 0 1 0 0 1 0 1 0 0 13 B c c 0 1 0 0 0 1 0 0 1 14 C b b 0 0 1 0 1 0 0 1 0 II-be 15 B c b 0 1 0 0 0 1 0 1 0 16 C b c 0 0 1 0 1 0 0 0 1 17 B b c 0 1 0 0 1 0 0 0 1 18 C c b 0 0 1 0 0 1 0 1 0 19 C a a 0 0 1 1 0 0 1 0 0 20 A c c 1 0 0 0 0 1 0 0 1 Π-ca 21 C a c 0 0 1 1 0 0 0 0 1 22 A c a 1 0 0 0 0 1 1 0 0 23 C c a 0 0 1 0 0 1 1 0 0 24 A a c 1 0 0 1 0 0 0 0 1 25 A a a 1 0 0 1 0 0 1 0 0 III 26 B b b 0 1 0 0 1 , 0 0 1 0 27 C c c 0 0 1 0 0 1 0 0 1 497325 五、發明說明（5) G4 = 1，「/12 >〇 0 ，F/12 二匕―厂/2 <0 (2) 1 ^/23 ==^/2-^3 >〇0 ，HK3<〇 (3) (4) 此外，本發明裝置(14)將控制三相直接鏈型交/交流轉換器(u)使其之輸入具有單位功 因之性能，即三相輸入之線電流與其相對應之相電壓同相(in phase)。由於三相具有對稱性， 這裡僅以區間1作爲例子加以說明，其餘區間將同理可得。於區間1中，第2相電壓爲負値 且最大而第1相與第3相則爲正値且第3相電壓之絕對値大於第1相電壓之絕對値。換言之， 輸入電壓源有高中低三個電壓可茲選擇。由磁滯控制器之基本工作原裡申請人可知於區1間 時，若要使三相直接鏈型交/交流轉換器(Π)之輸出電流/〜，=1，2,3上升則必須選用。或 Κ/3之正電壓;反之，若要使輸出電流下降則必須選擇負電壓。 再來說明本發明裝置(14)是如何來達成目標。圖4所不爲本發明裝置(14)之系統功能圖。 其中 1 ，當4碰到後 〇 ，當4碰到後 k = 15253 (5) Δ5爲磁滯電流控制信號之寬度，而控制信號圮乃由&除頻得之。至於巧與G相對於實際 輸出電流和參考電流値的關係如圖6所示。由圖6可知PWM的切換週期可由與仄的信號 分成四個區間加以編碼。又由G，Α: = 1，2，·.·，6編碼可得輸入電壓源於不同區間裏三相電壓之 間的大小關係及極性(例如當（G，G2，G3，G4，G，G6 >=( 1，〇, 1，1，〇, 1)時即表示輸入電壓 第8頁 497325 五、發明說明（6) 源在區間1之狀態下）。因此，申請人便可在每個區間的每次PWM的切換週期裏適當選擇施 加之三相電源，而使每相電流在每一切換週期均分擔部份負載電流。另外，爲了使各相電流 平均分配，本發明的作法是在（//*，尽）二（1,1) ((〇,〇))的部份中，因其電流誤差量絕對 値較大，所以選擇該區間絕對値最大的正(負)電壓，而在（仄，巧）二（1,0) ((0，1))時選 擇該區間中間大小的電壓源以降低開關切換的頻率。茲進一步以實例加以說明如下。當輸入 電壓源於區間1時，此區間有^及κ/3兩個正電壓源，一個負電壓源ί//2。在二正一負的情況 下，可將切換週期分成4段。第二段h ,〖2 ]((圮，仄）=(1，1))輸出電流爲上升趨勢， 遂將開關切換至正電壓源，因爲此段爲輸出電流經過較大的誤差量（4 + Δ5 )，若欲加速誤 差量之減少必須施加最大正電壓源K/3。至於第四段U3，G ]輸出電流亦爲上升趨勢，若欲減 少誤差量之增加，則選擇另一正電壓源匕。而在第一段[〖。4 ]與第三段u2，/3 ]輸出電流爲 下降趨勢，爲減少誤差量，因只有一個負電壓源可用，所以必須切換至唯一的負電壓源厂/2。 因此’在此PWM的切換週期裏，區間1的三相電壓源都分配到與其電壓同極性的輸入電流供 給至負載。特別是在區段[]時，由於施加的電壓較在區段[(1，^ ]來得小’所以在電流 上升趨勢的斜率比第一段小，如此便可使第一段與第四段導通時間相近，進而降低開關切換 的頻率。値得一提的是雖然由/^與巧所產生64個不同的訊號狀態皆包含表一裏所有27種 不同的開關切換狀態，但事實上在本區間內表一中第Π -ca的開關組合將會造成輸入電流//2 此時將會成爲正値，即與負電壓的62極性相反，不符合功因控制目標’因此此類的切換狀 態則必須要去除。其解決的方法是將開關切換組合修改成零電壓空間向量中的（a ’ a ’ a)， (b，b，b)或（c，c，c)接法代替。經逐一檢各種開關連接狀態得知僅有如表2中所示 之12種需更改成零電壓空間向量接法，其餘均屬正確。其他11個區間之開關切換表同理亦 可得之。最後，將G，札與仄作爲輸入信號並送入信號選擇器(17)以決定三相直接鏈型交/ 交流轉換器(11)中各開關之切換狀態。 1·· 第9頁 497325 五、發明說明（7) 表 在圖5之區間1時所使甩之零電壓空間向量接法 同步信號檢測器之 輸出信號 磁滯電流控制器之 輸出信號 開關狀態 備註 G2 g3 G4 G5 G6 F' Fi H2 f3 心1 心3 ^w4 ^w5 心8 ^w9 1 0 1 1 0 1 0 0 0 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 0 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 0 1 1 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 0 1 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 1 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 1 1 0 1 0 1 0 0 1 0 0 1 0 * 1 0 1 1 0 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 1 0 1 0 1 1 0 0 1 0 0 1 0 0 1 0 1 1 0 1 0 1 0 1 1 1 1 0 0 1 0 0 1 0 0 氺 1 0 1 1 0 1 0 1 1 1 0 1 1 0 0 1 0 0 1 0 0 氺 1 0 1 1 0 1 0 1 1 1 1 0 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 1 1 1 1 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 0 0 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 0 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 1 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 1 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 1 0 1 0 1 1 0 0 1 0 0 1 0 0 * 1 0 1 1 0 1 1 1 0 1 1 0 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 1 1 0 1 1 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 1 1 0 0 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 1 1 1 1 0 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 1 1 1 1 1 0 0 1 0 0 1 0 0 1 :需改為零電壓空間向量接法 開關突波之抑制原理說明= 理論上，開關在切換時要同時，而且要在瞬間改換切換狀態，才不會造成損失及突波IBS Page 5 497325 V. Description of the invention (3) System structure consisting of 乂 = 1, 2, _, and 9) can be explained by referring to FIG. 2. Since today's power semiconductor components are unidirectional switching elements, they can be synthesized roughly from the three architectures shown in FIG. However, in order to cooperate with the device (14) of the present invention, the structure of a bidirectional switch composed of the forward and reverse switches shown in FIG. 3 (c) is used. Although there are 512 (= 29) different combinations of the nine bidirectional switching elements, only 27 configurations can be applied after deducting the conditions that cause a short circuit between the three-phase input power sources and / or an open circuit between the three-phase output currents. For the convenience of explanation, this 27 possible states are listed in Table 1 and classified into five types such as I, Π-ab, Π-bc, Π-ca, and ΠI. Type I is a three-phase output terminal (A, B, and c are connected to various combinations of different three-phase inputs, such as (a, b, 0, etc .; n-ab type indicates that the three-phase output is only connected to the input terminal. Various combinations of phase a and phase b, such as (a, b, b), etc. Similarly, Π-bc and Π-ca are all types that are connected only to the input terminals b-phase, c-phase, c-phase, and a-phase. The combination state. And the m type indicates that the three-phase output terminals are all connected to the same power terminal, such as (a'a'a), etc., which is also commonly known as the zero voltage space vector method. In addition, An input filter and an input filter are added between the input power source and the power circuit to eliminate the high-frequency harmonics of the input current caused by the switching element. The detailed functional block diagram of the device (14) of the present invention is shown in the figure As shown in Fig. 4. First, the three-phase input voltage is obtained by the 6-step voltage step control signal through the 5 step generator (13), so as to divide the input voltage signal of a cycle into 12 different intervals. The device (14) of the present invention intends to control three-phase direct-chain AC / AC _ special converter (11) also needs to improve both the power factor and the high speed. The function of conversion efficiency, so it must be considered whether the direction of the input current is consistent with the polarity of the voltage source and minimize the number of switching times of the switching element. In addition, in order to improve the dynamic response performance of the converter, it must be caused by the undesired power supply to the output source Elimination of influence. In order to obtain the above-mentioned performance, the device (14) of the present invention obtains 6 obtained by synchronizing the 6-bit voltage synchronization control signal with a hysteresis controller (15) and a half-frequency (16). Single bit control signal to determine the switching state of the 18 unidirectional switching elements on the three-phase direct-chain AC / AC converter (11), thereby achieving the desired performance. As for the working principle of the device (14) of the present invention There will be a more detailed explanation in the "Explanation of the working principle of the controller". 2. The description of the working principle of the controller first considers the ideal three-phase voltage waveform as shown in Figure 5. The applicant divided it into 12 sections and mm Page 6 497325 V. Description of the invention (4) 'In each section, there must be one phase voltage at the maximum absolute value and the number is unchanged in this section, and the other two phase voltages are not only Outside and opposite to the former, the amplitude is small. In order to facilitate future analysis and explanation, the applicant defines the interval detection signal as shown below. Table 1 Switching combination table of three-phase direct-chain AC / AC converter Type number ABC Swl Sw2 Sw3 Sw4 Svv5 Sw6 Sw7 Sw8 Sw9 1 A bc 1 0 0 0 1 0 0 0 1 2 A cb 1 0 0 0 0 1 1 B ca 0 1 0 0 0 1 1 0 0 5 C ab 0 0 1 1 0 0 0 1 0 6 C ba 0 0 1 0 1 0 1 0 0 7 A bb 1 0 0 0 1 0 0 1 0 8 B aa 0 1 0 1 0 0 1 0 0 Il-ab 9 A ba 1 0 0 0 1 0 1 0 0 10 B ab 0 1 0 1 0 0 0 1 0 11 A ab 1 0 0 1 0 0 0 1 0 12 B ba 0 1 0 0 1 0 1 0 0 13 B cc 0 1 0 0 1 1 0 0 1 14 C bb 0 0 1 0 1 0 0 1 0 II-be 15 B cb 0 1 0 0 0 1 0 1 0 16 C bc 0 0 1 0 1 0 0 0 1 17 B bc 0 1 0 0 1 0 0 0 1 18 C cb 0 0 1 0 0 1 0 1 0 19 C aa 0 0 1 1 0 0 1 0 0 20 A cc 1 0 0 0 0 1 0 0 1 Π-ca 21 C ac 0 0 1 1 0 0 0 0 1 22 A ca 1 0 0 0 0 1 1 0 0 23 C ca 0 0 1 0 0 1 1 0 0 24 A ac 1 0 0 1 0 0 0 0 1 25 A aa 1 0 0 1 0 0 1 0 0 III 26 B b b 0 1 0 0 1, 0 0 1 0 27 C cc 0 0 1 0 0 1 0 0 1 497325 V. Description of the invention (5) G4 = 1, "/ 12 > 〇0, F / 12 two daggers-factory / 2 < 0 (2) 1 ^ / 23 == ^ / 2- ^ 3 > 〇0, HK3 < 〇 (3) (4) In addition, the device (14) of the present invention will control three-phase direct-chain type The AC / AC converter (u) makes its input have the performance of unit power factor, that is, the line current of the three-phase input is in phase with its corresponding phase voltage. Due to the symmetry of the three phases, only section 1 is used as an example for illustration, and the remaining sections will be obtained in the same way. In interval 1, the voltage of the second phase is negative and maximum, and the voltage of the first and third phases is positive and the absolute voltage of the third phase voltage is greater than the absolute voltage of the first phase voltage. In other words, the input voltage source has three voltages: high, medium, and low. From the basic work of the hysteresis controller, the applicant can know that if the area 1 is to be increased, the output current of the three-phase direct-chain AC / AC converter (Π) must be increased by 1,2,3. Optional. Or K / 3 positive voltage; conversely, if you want to reduce the output current, you must choose a negative voltage. Let us explain how the device (14) of the present invention achieves the goal. FIG. 4 is not a system function diagram of the device (14) of the present invention. Among them 1, when 4 meets 〇, when 4 meets k = 15253 (5) Δ5 is the width of the hysteresis current control signal, and the control signal 圮 is obtained by dividing by & As for the relationship between Q and G with respect to the actual output current and reference current 如图, see Figure 6. It can be seen from Fig. 6 that the PWM switching period can be coded by dividing the signal with 仄 into four sections. By G, Α: = 1, 2, ···, 6 encoding, the input voltage is derived from the magnitude relationship and polarity between the three-phase voltages in different sections (for example, when (G, G2, G3, G4, G, G6 > = (1, 〇, 1,1, 〇, 1) means the input voltage. Page 8 497325 V. Description of the invention (6) The source is in the range 1.) Therefore, the applicant can The three-phase power to be applied is appropriately selected in each PWM switching cycle of each section, so that each phase current shares part of the load current in each switching cycle. In addition, in order to evenly distribute the current of each phase, the method of the present invention is In the part of (// *, exhaustion) two (1,1) ((〇, 〇)), because the amount of current error is relatively large, the absolute positive (negative) voltage in this interval is selected to be the largest, In (仄, 巧) two (1,0) ((0,1)), a voltage source of the middle size of the interval is selected to reduce the frequency of switching. Here is an example to explain it as follows. When the input voltage originates from the interval At 1, this interval has two positive voltage sources, ^ and κ / 3, and one negative voltage source, / 2. In the case of two positive and one negative, the switching period can be divided into 4 segments. The second segment h, [2] ((圮, 仄) = (1, 1)) the output current is increasing, so the switch is switched to a positive voltage source, because this segment is the output current after a large amount of error (4 + Δ5), if you want to accelerate the reduction of the error amount, you must apply the maximum positive voltage source K / 3. As for the fourth stage U3, G] the output current is also rising. If you want to reduce the increase of the error amount, choose another positive voltage In the first section [〖.4] and the third section u2, / 3], the output current shows a downward trend. In order to reduce the amount of error, because there is only one negative voltage source available, it must be switched to the only negative voltage source. Factory / 2. Therefore, in this PWM switching cycle, the three-phase voltage sources in section 1 are all assigned to the input current of the same polarity as the voltage supplied to the load. Especially in section [], because the applied voltage is The section [(1, ^] comes small ', so the slope of the current rising trend is smaller than that of the first section, so that the on time of the first section and the fourth section are similar, thereby reducing the frequency of switching.) The reason is that although 64 different signal states generated by / ^ and Qiao are included in Table 1 There are 27 different switching states, but in fact the switch combination of Π-ca in Table 1 in this section will cause the input current // 2 to become positive 此时 at this time, which is opposite to the polarity of 62 of the negative voltage. , Does not meet the power factor control objective, so this type of switching state must be removed. The solution is to modify the switch combination to (a 'a' a), (b, b, b ) Or (c, c, c) connection instead. After checking the connection status of each switch one by one, it is learned that only 12 types shown in Table 2 need to be changed to zero voltage space vector connection, and the rest are correct. The other 11 The switch table of the interval can be obtained by the same principle. Finally, G, Zar and 仄 are used as input signals and sent to a signal selector (17) to determine the switching state of each switch in the three-phase direct-chain AC / AC converter (11). 1 ·· Page 9 497325 V. Description of the invention (7) Table 0 shows the zero voltage space vector connected to the output signal of the synchronous signal detector during the interval 1 in Figure 5. Switching state of the output signal of the hysteresis current controller G2 g3 G4 G5 G6 F 'Fi H2 f3 Heart 1 Heart 3 ^ w4 ^ w5 Heart 8 ^ w9 1 0 1 1 0 1 0 0 0 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 0 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 0 1 1 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 0 1 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 1 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 0 0 1 1 0 1 0 1 0 0 1 0 0 1 0 * 1 0 1 1 0 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 1 0 1 0 1 1 0 0 1 0 0 1 0 0 1 0 1 1 0 1 0 1 0 1 1 1 1 0 0 1 0 0 1 0 0 氺 1 0 1 1 0 1 0 1 1 1 0 1 1 0 0 1 0 0 1 0 0 氺 1 0 1 1 0 1 0 1 1 1 1 0 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 0 1 1 1 1 1 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 0 0 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 0 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 1 0 0 0 0 1 0 0 1 0 0 1 0 1 0 1 1 0 1 1 0 1 0 1 0 0 1 0 0 1 0 0 1 0 1 0 1 1 1 0 1 1 1 0 1 0 1 1 0 0 1 0 0 1 0 0 * 1 0 1 1 0 1 1 1 0 1 1 0 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 1 1 0 1 1 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 1 1 0 0 1 0 1 0 0 1 0 0 1 0 氺 1 0 1 1 0 1 1 1 1 1 0 1 0 0 1 0 0 1 0 0 1 氺 1 0 1 1 0 1 1 1 1 1 1 1 0 1 At the same time, and change the switching state in an instant, so as not to cause losses and surges
第10頁 497325 五、發明說明（8) 可是在實際上，驅動電路及開關本身之動作均有些時間延遲（time del ay)因而造成切換損失 及突波現象。在此，申請人以開關由4切換至心爲例說明之。若&在尙未截止的情況下，& 就導通的話，將會造成^與K/2將經&、&形成一短暫的迴路而造成短路電流突波。如果此 突波過大的話還可能將本發明裝置（14)所控制之三相直接鏈型交/交流轉換器(丨1)之功率半 導體開關元件擊穿而燒毀。另外，若於A截止後而&尙未導通，則因無法形成一迴路供給 電感性負載，在電流急速變化之情況下，負載端電壓將形成一突波，若此突波超過開關的電 壓應力時，亦將損壞開關。爲解決前述之問題，申請人首先將開關的控制訊號減去一小部分， 使開關在切換時之控制訊號不會重疊而使形成短路迴路，而造成電流突波。然在解決電流突 波的問題時，因增加了開關切換時的間隔時間，相對的會增加電感性負載開路的時間，而造 成電壓突波的變大，申請人可依電壓源區間及電壓絕對値大小而預先導通不影響控制器的單 向開關，以便可提供一迴路給電感性負載，使其不會造成電壓突波。爲淸楚分析與說明起見， 申請人將三相直接鏈型交/交流轉換器(11)之雙向開關開關元件以圖3(c)所示之實際架構表 之。舉例圖5之區間4且第1，2,3相輸出電流分別爲負，正，正時爲例。在此區間a相是最高 電壓，因此所連接之雙向開關控制主要由= 〇，1,2主導，所以導通\+3/> , / = 0，1，2不 會和其他相的電源形成迴路，而且並不會對前述之控制器產生影響；相對的，對於c相輸入 電源的部份，由於c相電壓最負，因此，y = 〇,1，2的導通並不會和其他相的電源形成迴 路也不會影響控制。圖7所示爲負載開路時流通負載電流迴路之等效電路。至於當第1，2,3 相輸出電流分別爲正，負，負時’反向開關4α, 之反向的背接二極體在負載開路時正 好可提供一如圖8所示之迴路流通負載電流。換言之，在任何時間負載電流皆有通路，電感 性負載電流不會驟降’因此得以解決電壓突波的問題。値得一提的是，申請人若在此區間同 時導通這六個開關（’除可提供於此區間在開關切換時造成的負載開路的情 況之迴路流通負載電流外’其開關切換次數亦僅約一般控制策的三分之二進而用以提升轉換 器之效率。 第11頁 497325 五、發明說明（9) 【實例驗證】 申請人實體製作一雛形電路以爲驗證本發明裝置之可行性與正確性。首先圖9所示爲開 關、，1，2,3之控制訊號波形圖。由此圖可看出於任何時間皆僅有一開關導通且^分別在 匕相輸入電壓爲最大負値的120。中導通，其與本發明裝置(14)之工作原理一致。接著圖10 示爲三相直接鏈型交/交流轉換器(11)在穩態下之未經高頻濾波之輸入電流與輸出電流波 形。由圖10看出其輸入之位移因數爲1.0且於正負半週期內的電壓源，都有切滿180°同極性 之輸入電流。此外，輸出電流爲相當良好之正弦波。最後，圖11示爲三相直接鏈型交/交流 轉換器(11)之動態響應波形圖。由圖11知即使步階(step)變化輸出電流命令之振幅或頻率’ 本發明裝置(14)皆可使三相直接鏈型交/交流轉換器(11)得到相當快速的響應。圖12與圖13 所示爲輸入電源在有諧波或不平衡輸入電源情況下之輸出入波形圖。由圖12與圖13可知本 發明裝置〇4)即使在不平衡或含有高成份之低次諧波成份之輸入電源下，仍可使三相直接鏈 型交/交流轉換器(11)之每相輸入電壓與電流之位移因數（displacement factor)除仍可保持1.0 外，於正負半週期內的電壓源，都有切滿180°同極性之輸入電流；此外，三相直接鏈型交/交 流轉換器(11)之三相輸出電流亦爲平衡且良好之正弦波。 【特點及功效】 一般就控制型式而言，三相直接鏈型交/交流轉換器可分爲電壓控制型之三相直接鏈 型交/交流轉換器與電流控制型之三相直接鏈型交/交流轉換器兩大類型。電壓控制型之 三相直接鏈型交/交流轉換器雖具改善輸入電流波形品質之功能’然而其動態響應差且轉 換器之性能甚易受到輸入電源波形之影響；電流控制型之三相直接鏈型交/交流轉換器雖 具甚佳之動態響應與穩定性’然其主要之缺點爲輸入電流波形含高成份之低次諧波且功因較 低。因此.，本發明裝置提出一在硬體實作上十分簡易以同時兼具上述之優點，並可以減少 IBB ^ 第12頁 497325 五、發明說明（ίο) 三相直接鏈型交/交流轉換器中之半導體開關元件切換次數與抑制與切換時所產生之電壓 與電流突波，且不會犧牲三相直接鏈型交/交流轉換器本質之功能。由模擬與實驗結果 得以驗證本發明裝置確實可使三相直接鏈型交/交流轉換器兼具改善輸入電流波形品質及 功因與快速之動態響應與穩定性等功能’此些特性乃一般之電壓控制型或電流控制型三相 直接鏈型交/交流轉換器所無法同時達成的。 縱上所述，本案不但在技術思想上屬創新且能較習用方法增進功效，爰依法提出申請， 懇請貴局核准本件發明專利申請案，以勵發明，至感德便。 第13頁 497325 圖式簡單說明 【圖示簡單說明】 圖1 m相變η相直接鏈型交/交流轉換器架構圖。 圖2本發明裝置與欲控制之三相直接鏈型交/交流轉換器系統架構圖。 圖3(a)橋式型之雙向開關架構圖。 圖3(b)並聯型之雙向開關架構圖。 圖3(c)串聯型之雙向開關架構圖。 圖4 本發明裝置之詳細系統功能方塊圖。 圖5 理想三相電壓波形示意圖。 圖6 控制信號相對於實際輸出電流和參考電流値之關係圖。 圖7在圖5之區間4且第1相(第2,3相)輸出電流爲負(正)時負載開路之迴路。 圖8在圖5之區間4且第1相(第2,3相)輸出電流爲正(負)時負載開路之迴路。 圖9(a) \，之控制訊號巨觀實測波形圖。 圖9(b) 5V,之控制訊號微觀實測波形圖。 圖10穩態下三相直接鏈型交/交流轉換器之未經高頻濾波之輸入電流與輸出電流波形。 圖11(a)轉換器步階變化輸出電流命令之頻率動態響應實測波形圖。 圖11(b)轉換器步階變化輸出電流命令之振幅動態響應實測波形圖。 圖12(a)三相輸入電源在含3次諧波時之第1相濾波前輸入電流與第1相輸入電壓波形圖。 圖12(b)三相輸入電源在含3次諧波時之三相輸出電流波形圖。 圖13(a)三相輸入電源不平衡之第1相濾波前輸入電流與第1相輸入電壓波形圖。 圖13(b)三相輸入電源不平衡之三相輸出電流波形圖。 表1 三相直接鏈型交/交流轉換器之切換組合表’。 1111 第14頁 497325 圖式簡單說明 表2 在圖5之區間1時所使用之零電壓空間.向量接法。 【元件符號說明】 e〇k 三相負載反電勢 Fk 第A個磁滯電流控制器輸出信號 Gk 第々個三相電源區間偵測信號 Hk 巧除頻後信號 iIk 三相輸入電流 hk 第々相輸出電流 L〇 三相負載電感 R〇 三相負載電阻 S, 第/個雙向半導體開關元件 Sia 第/個順向半導體開關元件 Slb 第/個逆向半導體開關元件 Sm 第/個雙向半導體開關元件導通狀態 Vlk 第A相輸入電壓 V0k 第々相輸出電壓 AB 磁滯電流控制信號寬度Page 10 497325 V. Description of the invention (8) However, in fact, the drive circuit and the switch itself have some time delay (time del ay), which causes switching loss and surge phenomenon. Here, the applicant takes the switch from 4 to heart as an example to explain. If & is on when 尙 is not cut off, it will cause ^ and K / 2 to form a short circuit through &, & and cause a short-circuit current surge. If the surge is too large, the power semiconductor switching elements of the three-phase direct-chain AC / AC converter (丨 1) controlled by the device (14) of the present invention may be broken down and burned. In addition, if & 尙 does not turn on after A is turned off, because a loop cannot be used to supply an inductive load, under the condition of rapid changes in current, the load terminal voltage will form a surge. If this surge exceeds the voltage of the switch Stress will also damage the switch. In order to solve the aforementioned problem, the applicant first subtracts a small portion of the control signal of the switch, so that the control signal of the switch during the switching will not overlap and cause a short circuit, which will cause a current surge. However, when solving the problem of the current surge, the increase of the interval time during the switching of the switch will increase the open time of the inductive load and cause the voltage surge to increase. The applicant can rely on the voltage source interval and the absolute voltage.値 The size of the unidirectional switch does not affect the controller in advance, so that it can provide a loop to the inductive load so that it will not cause a voltage surge. For the sake of thorough analysis and explanation, the applicant has listed the bidirectional switching elements of the three-phase direct-chain AC / AC converter (11) as shown in FIG. 3 (c). For example, interval 4 in FIG. 5 and the output currents of phases 1, 2, and 3 are respectively negative, positive, and positive. Phase a is the highest voltage in this interval, so the connected bidirectional switch control is mainly dominated by = 〇, 1,2, so the conduction \ + 3 / >, / = 0,1,2 will not form with the power of other phases Circuit, and it will not affect the aforementioned controller. In contrast, for the part of the c-phase input power, because the c-phase voltage is the most negative, the conduction of y = 〇, 1,2 will not be connected to other phases. The power supply loop will not affect the control. Figure 7 shows the equivalent circuit of the load current loop when the load is open. As for the 1st, 2nd and 3rd phase output currents, which are positive, negative and negative, respectively, the 'reverse switch 4α, the reverse back-connected diode can provide a circuit circulation as shown in Figure 8 when the load is open. Load current. In other words, there is a path for the load current at any time, and the inductive load current does not drop sharply, so the problem of voltage surge can be solved. It is worth mentioning that if the applicant turns on the six switches at the same time in this interval ('except for the load current flowing in the loop, which can provide the load open circuit caused by the switch during this interval', its number of switchovers is only About two-thirds of the general control strategy is used to improve the efficiency of the converter. Page 11 497325 V. Description of the invention (9) [Example verification] The applicant entity made a prototype circuit to verify the feasibility and correctness of the device of the present invention. First, Figure 9 shows the control signal waveforms of switches, 1, 2, 3. From this figure, it can be seen that only one switch is turned on at any time, and the input voltage at the phase of the dagger phase is 120, which is the maximum negative voltage. .Continuous conduction, which is consistent with the working principle of the device (14) of the present invention. Next, FIG. 10 shows the input current and output of the three-phase direct-chain AC / AC converter (11) without high-frequency filtering in the steady state. Current waveform. It can be seen from Figure 10 that the input source has a displacement factor of 1.0 and the voltage source in the positive and negative half cycles has an input current of 180 ° with the same polarity. In addition, the output current is a fairly good sine wave. Finally, Figure 11 Shown is the dynamic response waveform diagram of the three-phase direct-chain AC / AC converter (11). From FIG. 11, the amplitude or frequency of the output current command can be known even if the step changes. Phase direct-chain AC / AC converter (11) gets a fairly fast response. Figures 12 and 13 show the input and output waveforms of the input power in the case of harmonic or unbalanced input power. From Figure 12 and Figure 13 It can be known that the device of the present invention 〇4) Even under the input power of unbalanced or containing high-order low-harmonic components, the input voltage and current of each phase of the three-phase direct-chain AC / AC converter (11) can still be made. In addition to maintaining the displacement factor of 1.0, the voltage source in the positive and negative half cycles has an input current of 180 ° with the same polarity; in addition, a three-phase direct-chain AC / AC converter (11) The three-phase output current is also a balanced and good sine wave. [Features and functions] Generally speaking, in terms of control types, three-phase direct-chain AC / AC converters can be divided into voltage-controlled three-phase direct-chain AC / AC converters and current-controlled three-phase direct-chain AC / AC converters. / AC converter two types. The voltage-controlled three-phase direct-chain AC / AC converter has the function of improving the quality of the input current waveform. However, its dynamic response is poor and the performance of the converter is easily affected by the input power waveform. Although the chain AC / AC converter has very good dynamic response and stability, its main disadvantage is that the input current waveform contains low-order harmonics with high components and low power factor. Therefore, the device of the present invention proposes a hardware implementation that is very simple to have the above advantages, and can reduce IBB ^ page 12 497325 V. Description of the invention (Three-phase direct-chain AC / AC converter) The switching times of the semiconductor switching elements and the voltage and current surges generated during suppression and switching, without sacrificing the essence of the three-phase direct-chain AC / AC converter. It is verified from the simulation and experimental results that the device of the present invention can indeed make the three-phase direct-chain AC / AC converter have the functions of improving the input current waveform quality, power factor, and fast dynamic response and stability. These characteristics are general Voltage-controlled or current-controlled three-phase direct-chain AC / AC converters cannot be achieved simultaneously. As mentioned above, this case is not only technically innovative and can improve efficacy over conventional methods. It has submitted an application in accordance with the law, and I implore your office to approve this invention patent application in order to encourage inventions and to benefit you. Page 13 497325 Simple description of the diagram [Simplified description of the diagram] Figure 1 m-phase change η-phase direct-chain AC / AC converter architecture. FIG. 2 is an architecture diagram of the device of the present invention and a three-phase direct-chain AC / AC converter to be controlled. Figure 3 (a) Bridge type bidirectional switch architecture diagram. FIG. 3 (b) is a parallel bidirectional switch architecture diagram. Fig. 3 (c) A bidirectional switch architecture diagram of a series type. Figure 4 is a detailed system functional block diagram of the device of the present invention. Figure 5 Schematic diagram of ideal three-phase voltage waveform. Figure 6 The relationship between the control signal relative to the actual output current and the reference current 値. FIG. 7 is a circuit in which the load is open when the output current of the first phase (second and third phase) is in the interval 4 of FIG. 5 and the output current is negative (positive). FIG. 8 is a circuit in which the load is opened when the output current of the first phase (second and third phases) is positive (negative) in the interval 4 in FIG. 5. Figure 9 (a) \, the measured waveform of the control signal macroscopic observation. Figure 9 (b) 5V, control signal micro-measured waveform. Figure 10 Input current and output current waveform of three-phase direct-chain AC / AC converter without high-frequency filtering under steady state. Fig. 11 (a) Measured waveform of the frequency dynamic response of the output current command of the converter step change. Fig. 11 (b) Measured waveform of the amplitude dynamic response of the converter step output current command. Figure 12 (a) Waveform diagram of the input current and the input voltage of the first phase before the first phase filtering when the three-phase input power supply contains the third harmonic. Figure 12 (b) Three-phase output current waveform diagram of the three-phase input power supply when it contains the third harmonic. FIG. 13 (a) is a waveform diagram of the input current before the first phase filtering and the input voltage of the first phase when the three-phase input power is unbalanced. Figure 13 (b) Three-phase output current waveform diagram of unbalanced three-phase input power. Table 1 Switching combination table of three-phase direct-chain AC / AC converter. 1111 Page 14 497325 Brief description of the diagram Table 2 Zero voltage space. Vector connection method used in interval 1 of Fig. 5. [Description of component symbols] e〇k Three-phase load back-EMF Fk A hysteresis current controller output signal Gk The third three-phase power interval detection signal Hk The signal iIk three-phase input current hk The third phase Output current L〇 Three-phase load inductance R〇 Three-phase load resistance S, S / th bidirectional semiconductor switching element Sia Sth / forward semiconductor switching element Slb Sth / reverse semiconductor switching element Sm S / th bidirectional semiconductor switching element ON state Vlk Phase A input voltage V0k Phase I output voltage AB Hysteresis current control signal width
ΙΙΙ·ΙΙΙΙ 第15頁 497325 圖式簡單說明 【圖號說明】 11 三相直接鏈型交/交流轉換器 12 電流迴授控制器 13 同步信號產生器 14 本發明裝置 15 磁滯控制器 16 半頻器 17 信號選擇器 第16頁ΙΙΙ · ΙΙΙΙ Page 15 497325 Brief description of drawings [Description of drawing number] 11 Three-phase direct-chain AC / AC converter 12 Current feedback controller 13 Synchronous signal generator 14 Device of the present invention 15 Hysteresis controller 16 Half frequency Selector 17 signal selector 第 16 页