TW202416627A - Power transfer system and methods - Google Patents

Abstract

A system and associated method transfer power between a DC source and a variable load. Two power signals are extracted from the DC source at an HF frequency via two self-synchronous radio frequency rectifiers/amplifiers switched by two corresponding HF switching signals having between them a phase difference controlled by a duty cycle and overlap controller. The two HF power signals are mixed in a wired, wireless, or bimodal wireless HF power link system to produce a transferred power signal based on the mixing and on manipulating the phase difference. An unfolded output power signal is created from the transferred power signal by means of a power signal conversion circuit in communication with the HF power link system. The system and method allow transfer to the load of at least one of an adjustable DC power signal and an AC power signal phase locked to an existing power signal in the load.

Description

Power transmission system and method

The present invention relates to a power transmitter, a receiver, and a system and method for power transmission.

In inductive power transfer (IPT), power is transferred between coils, usually by means of a magnetic field. An alternating current (AC) is driven through a transmitter coil to create an oscillating magnetic field. The magnetic field passes through a receiving coil, where it induces the AC in the receiving coil. The induced AC can drive a load directly, or be rectified to direct current (DC), which is applied to drive a load. To achieve high efficiency, the transmitter and receiver coils must be very close together. For example, typically the transmitter and receiver coils are separated by only a portion of the coil diameter (e.g., within a few centimeters), and the axes of the coils are closely aligned.

In some IPT systems, resonant inductive coupling is used. Resonant inductive coupling can improve the efficiency of IPT by using a resonant circuit. Resonant inductive coupling can achieve higher efficiency at longer distances than non-resonant inductive coupling. In resonant inductive coupling, power is transferred by the magnetic field between two resonant circuits, one in the transmitter and the other in the receiver. The two circuits are tuned to resonate at the same resonant frequency.

In some IPT systems, magnetic fields can induce eddy currents in nearby metal. This can lead to significant temperature rise and fire hazard. Ferromagnetic plates can be used to provide shielding and improve inductive coupling, but can add cost to such systems.

Capacitive power transfer (CPT) uses electric fields to transfer power between two electrodes (such as metal plates). Typically, four metal plates are used in a CPT system to form a capacitive coupler. Two metal plates act as power transmitters, while the other two act as power receivers, resulting in at least two coupled capacitors to provide a power flow loop. The transmitter applies an AC voltage to the transmitter plates. The oscillating electric field induces an AC potential on the receiver plates, which causes AC current to flow in the load circuit. Resonance can also be used with capacitive coupling to extend the power transfer range.

In a CPT system, eddy currents can be reduced, and the panels used are low cost and reduce system cost. However, a problem with many systems is that high voltages can be imposed on the panels. These high voltages can generate strong electric fields, which result in significant field emissions to the surrounding area.

There are also problems associated with capacitive or inductive compensation networks in CPT and IPT systems. Currently, both CPT and IPT systems require minimal spacing between the receiver and transmitter. This typically requires large capacitors and inductors in the compensation network on both the primary and secondary sides. It is difficult to produce these large components, and their parasitic resistance can significantly reduce system efficiency. Additionally, these compensation components are not directly involved in the power transfer process.

There is still a desire for wireless power transmitters and receivers with fewer components and/or reduced cost. There is still a desire for wireless power transmitters and receivers with reduced reliance on compensation networks. There is still a desire for wireless power transmitters and receivers with higher efficiency. There is still a desire for wireless power transmitters with more flexible requirements for alignment and spacing therebetween. There is still a need for power transmission systems capable of transmitting power in both forward and reverse directions between a load and a power source, including between a DC source and an AC grid.

The area of power delivery for consumer products is becoming increasingly important. In the automotive space, electrical wiring harnesses have become a critical and expensive subsystem of the vehicle. The market for automotive wiring harnesses is expected to exceed $77 billion this decade. In an age of concerns about gas mileage for internal combustion vehicles, the carbon emissions of such vehicles, and the range of electric vehicles, the cost, weight, and power delivery efficiency of such wiring harnesses have become major concerns in vehicle design. These concerns are understandable given that materials and components account for 57% of the cost of manufacturing a vehicle.

While battery technology is steadily improving to provide cells with higher energy density, consumer demand for more and more auxiliary user electronics and electric drive systems integrated into vehicles is also increasing. This places increasing demands on battery and vehicle weight, cost, and power delivery efficiency. In the 1990s, the automotive industry proposed higher voltage battery systems, partly due to the desire to reduce wiring harness weight.

There have been many efforts to reduce the amount of expensive copper used in wiring harnesses, and there is a move toward using cheaper aluminum. This trend is also driven by the desire to save about 40 pounds of weight in a typical car. This trend towards aluminum has its own problems, in part because the electrical resistivity of aluminum is 1.58 times that of copper. Aluminum also has a phenomenon called creep, which causes connections to loosen. In addition, aluminum will oxidize, so precautions must be taken with connections. Some aspects of wiring harnesses still require copper, and any connection between copper and aluminum will introduce problems with current potential.

Therefore, there is a clear need for an alternative approach for vehicle wiring harnesses that reduces the expensive copper content, provides flexibility in voltage, avoids the problems represented by aluminum, and reduces weight.

At the same time, the efficiency of power delivery technology needs to improve to keep pace with rapid advances in battery technology, which in turn is stimulated by developments in the electric vehicle sector.

For example, these requirements are not limited to the automotive sector, but also apply to the sector of solar power transmission and, with certain modifications, also to other household consumer devices such as computers and television displays. Power conditioning units are widely used today which optimally extract power from a power source with a varying voltage, but these are usually subject to a limited degree of control facilities. This in turn prevents optimization of the power transmission efficiency.

The above examples of related art and the limitations associated therewith are intended to be illustrative rather than exclusive. After reading this specification and studying the accompanying drawings, other limitations of the related art will become apparent to those with ordinary knowledge in the art.

In a first aspect, a dual-peak near-field resonant wireless power transfer system is provided, which is configured to simultaneously perform capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio at a resonant power signal oscillation frequency, and the system includes: a transmitter subsystem, including a transmitter antenna subsystem and a power signal tuner module, the tuner module is configured to adjust the transfer mode ratio by adjusting the power signal provided by the tuner module to the transmitter antenna subsystem; and a receiver subsystem, including a receiver antenna subsystem, the receiver antenna subsystem is configured to receive power from the transmitter antenna subsystem according to the transfer mode ratio.

The tuner module may be configured to adjust the power signal by adjusting a phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem. The transmitter subsystem may further include: a controller; and at least one sensor, wherein the controller is configured to receive sensor information from the at least one sensor and to automatically provide a tuning instruction to the tuner module based on the sensor information; and the tuner module is configured to adjust the phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem according to the tuning instruction.

The at least one sensor may be disposed on the transmitter subsystem. In other embodiments, the at least one sensor may be disposed on the receiver subsystem, and the controller may be configured to wirelessly receive the sensor information. The at least one sensor may be one of: a power load sensor, a transmit power sensor, a surrounding object detector, and a distance detector configured to monitor the distance between the transmitter antenna and the receiver antenna.

The resonant power signal oscillation frequency can be freely varied within a predetermined frequency band. The predetermined frequency band can be an industrial, scientific and medical (ISM) band. The system can be detuned to the extent that the resonant power signal oscillation frequency is allowed to vary within opposite limits of the predetermined frequency band.

In another aspect, a wireless method for transmitting power bimodally according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency is provided, the method comprising: providing a transmitter subsystem, the transmitter subsystem including a power signal tuner module and a transmitter antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a receiver subsystem, the receiver subsystem including a power signal tuner module and a transmitter antenna subsystem configured to resonate at the resonant power signal oscillation frequency; A method for transmitting a power signal to a transmitter antenna subsystem comprising: providing a receiver antenna subsystem resonant at a power signal oscillation frequency; providing a power signal from the tuner module to the transmitter antenna subsystem at the power signal oscillation resonance frequency; adjusting the transmit mode ratio by adjusting the power signal from the tuner module to the transmitter antenna subsystem; and receiving the transmitted power at the power signal oscillation resonance frequency through the receiver antenna subsystem at the transmit mode ratio in the receiver subsystem. Adjusting the transmit mode ratio may include adjusting a phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem.

Providing a transmitter subsystem may further include: providing a controller and at least one sensor, and the phase difference between the current and the voltage may be adjusted by the tuner module based on sensor information received by the controller from the at least one sensor through a command of the controller. The controller may automatically send the command of the controller to the tuner module when receiving the sensor information; and the tuner module may automatically execute the command from the controller to change the phase difference.

The method may further include: allowing the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific and medical (ISM) band. Providing a transmitter subsystem may include providing a transmitter subsystem that is detuned to a degree that allows the resonant power signal oscillation frequency to vary within opposite extremes of the predetermined frequency band.

In yet another aspect, a dual-peak near-field resonant wireless power transfer system is provided, the dual-peak near-field resonant wireless power transfer system being configured to simultaneously perform capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio of the capacitive power transfer and the inductive power transfer at a variable resonant power signal oscillation frequency, the system comprising: a transmitter subsystem including a transmitter antenna subsystem and a power signal tuner module, wherein the power signal tuner module adjusts the transfer mode ratio by adjusting a power signal provided by the power signal tuner module to the transmitter antenna subsystem; and a receiver subsystem including a receiver antenna subsystem that receives power from the transmitter antenna according to the transfer mode ratio.

The system transmits information between the transmitter antenna subsystem and the receiver antenna subsystem via the transmitter antenna and the receiver antenna of the receiver antenna subsystem. The system may further include a modulator for modulating information onto an information bearing signal and providing the information bearing signal to the transmitter antenna subsystem. The system may modulate information onto an information bearing signal and provide the information bearing signal to the transmitter antenna subsystem. The modulator may be arranged to modulate the information bearing signal to the transmitter antenna subsystem based on the information. The power signal tuner module may include the modulator.

The information bearing signal may have a frequency different from the frequency at which the variable resonant power signal oscillates. The modulator may modulate the information bearing signal by any of frequency modulation, amplitude modulation, and phase modulation. The information bearing signal may be modulated so that the variable power signal oscillates at a frequency that is a harmonic of the frequency of the information bearing signal. The information bearing signal may be modulated onto a harmonic of the power signal. The signal modulated and provided to the transmitter antenna subsystem may be the power signal.

The modulator may modulate a reflection characteristic of the receiver antenna and transmit the information from the receiver antenna subsystem to the transmitter antenna subsystem by modulating the reflection characteristic of the receiver antenna according to the information. The modulated reflection characteristic of the receiver antenna may be an impedance of the receiver antenna.

The system can transmit the information from the receiver subsystem to the transmitter subsystem by modulating the reflection of the signal from the transmitter subsystem by the receiver antenna. The receiver subsystem can modulate the reflection characteristics of the receiver antenna. The receiver subsystem can modulate the impedance of the receiver antenna.

A power load may be present at the output of the receiver subsystem; and the information may include one or more of the presence of the power load, the charge level of the power load, the power transfer efficiency, the charge rate of the power load, the status of the power load, the presence of voltage on the power load, the charge capacity of the power load, and a remaining time to charge the power load.

The system may transmit digital information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The system may transmit analog information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The receiver subsystem may be configured to transmit power to a subsequent receiver subsystem. The receiver may further include a rectifier including a phase shifter.

In yet another aspect, a dual-peak resonant near-field RF power transfer system is provided, comprising a plurality of power transmit-receive modules for simultaneously performing capacitive power transfer and inductive power transfer via a power signal at a power signal frequency according to an adjustable transfer mode ratio, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator configured to exchange power with at least another one of the plurality of power transmit-receive modules.

A first power transmit-receive module of the plurality of power transmit-receive modules may include a power signal tuner module that is adjustable by adjusting a power signal provided by the power signal tuner module to a transmitter-receiver resonator in wired communication with the first power transmit-receive module of the plurality of power transmit-receive modules for changing the transmit mode ratio. At least one of the plurality of power transmit-receive modules may include a modulator arranged to modulate information onto a radio frequency signal that is exchanged between an associated transmitter-receiver resonator in wired communication with the at least one of the plurality of power transmit-receive modules and a transmitter-receiver resonator in wired communication with any other of the plurality of power transmit-receive modules.

The modulator may be any one of an amplitude modulator, a frequency modulator, and a phase modulator. The information may include one or both of digital information and analog information. The radio frequency signal modulated by the modulator may be a power signal. The radio frequency signal modulated by the modulator may have a frequency different from a power signal frequency. The radio frequency signal modulated by the modulator may have a frequency that is a harmonic of the power signal frequency. The power signal frequency may be a harmonic of the frequency of the modulated signal.

The modulator may be arranged to modulate a reflection characteristic of an associated wire-connected transmitter-receiver resonator according to the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. The modulator may be arranged to modulate a signal provided to the associated transmitter-receiver resonator according to the information. The power signal tuner module of the first power transmit-receive module of the plurality of power transmit-receive modules may include the modulator. Each of the power transmit-receive modules may include a compensation network, and the compensation network may include the modulator. At least one of the power transmit-receive modules may include a radio frequency oscillator that provides a signal to the at least one power transmit-receive module at the power signal frequency, and the radio frequency oscillator may include the modulator.

Each of the plurality of power transmit-receive modules may be reconfigurable between a power transmitter mode and a power receiver mode. Each of the power transmit-receive modules may include a differential self-synchronous RF power amplifier/rectifier capable of reconfiguring between amplifier states and rectifier states corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively. The differential self-synchronous RF power amplifier/rectifier may be a differential switching mode self-synchronous RF power amplifier/rectifier. Each of the power transmit-receive modules may include a controller, and the reconfiguration may be controlled by the controller. Each DSRFPA/rectifier may include a phase shifter adjustable by the controller for reconfiguring the DSRFPA/rectifier between the amplifier state and the rectifier state.

When a power load is present at the output of one of the plurality of power transmit-receive modules in the receiver mode, the information may include one or more of the presence of the power load, the charge level of the power load, the power transfer efficiency, the charge rate of the power load, the status of the power load, the presence of voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

In yet another aspect, a near-field radio frequency method for transferring power via a power signal at a power signal frequency is provided, the method comprising: providing a double-peak resonant near-field radio frequency power transfer system comprising a plurality of power transmit-receive modules, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator configured to exchange power with at least one other of the plurality of power transmit-receive modules; and operating the power transfer system according to an adjustable transfer mode ratio for simultaneous capacitive power transfer and inductive power transfer.

A first power transmit-receive module of the plurality of power transmit-receive modules provided may include a power signal tuner module; and operating the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module. Providing the power transmission system may include providing at least one power transmit-receive module in the plurality of power transmit-receive modules that is in wired communication with an associated transmitter-receiver resonator and has a modulator, and operating the power transmission system may include exchanging radio frequency signals between the associated transmitter-receiver resonator and a transmitter-receiver resonator in wired communication with at least another one of the plurality of power transmit-receive modules; and modulating information onto the exchanged radio frequency signals. When a power load is present at the output of one of the plurality of power transmit-receive modules, the information may include, for example, without limitation, one or more of the presence of the power load, the charge level of the power load, the power transfer efficiency, the charge rate of the power load, the status of the power load, the presence of voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

The information may be modulated onto the exchanged RF signal by amplitude modulation, frequency modulation, or phase modulation. Modulating the information onto the exchanged RF signal may include modulating digital information or analog information onto the exchanged RF signal.

Modulating the information onto the exchanged radio frequency signal may include modulating the information onto the power signal. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

Modulating the information onto the exchanged RF signal may include modulating a reflection characteristic of the associated wire-connected transmitter-receiver resonator according to the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. Modulating the information onto the exchanged RF signal may include modulating a signal provided to the associated transmitter-receiver resonator according to the information.

The method may include operating the power signal tuner module of the first power transmit-receive module of the plurality of power transmit-receive modules to modulate the information onto the exchanged radio frequency signal. Each of the provided power transmit-receive modules may include a compensation network, and the compensation network may include the modulator, allowing the compensation network to be operated to modulate the information onto the exchanged radio frequency signal. At least one of the power transmit-receive modules may include an radio frequency oscillator that provides a signal to the at least one power transmit-receive module at the power signal frequency, and the radio frequency oscillator may include the modulator, allowing the information to be modulated into the oscillator onto the exchanged radio frequency signal.

Each of the plurality of power transmit-receive modules provided may be reconfigurable between a power transmitter mode and a power receiver mode; and the method may further include reconfiguring at least two of the plurality of power transmit-receive modules between the power transmitter mode and the power receiver mode to reverse the power transmission direction between the at least two transmit-receive modules. Each of the plurality of power transmit-receive modules provided may include a differential self-synchronous radio frequency power amplifier/rectifier capable of reconfiguring between amplifier states and rectifier states corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively; and the method may include reconfiguring the differential self-synchronous radio frequency power amplifier/rectifier of the at least two transmit-receive modules between the amplifier state and the rectifier state. Each differential self-synchronous RF power amplifier/rectifier may include a phase shifter that is adjustable for reconfiguring the differential self-synchronous RF power amplifier/rectifier between the amplifier state and the rectifier state; and the method may include adjusting the phase shifter of each of the differential self-synchronous RF power amplifier/rectifiers in the at least two transmit-receive modules.

In another aspect, a near-field resonant wireless power transmission system is provided, comprising: a transmitting subsystem, including a plurality of transmitter resonators that are substantially decoupled from each other, and a corresponding transmitter module that communicates power signals with each transmitter resonator, each transmitter module including a transmitting controller and a power signal source having a power signal oscillation frequency and a power signal phase, each power signal source being controlled by a corresponding transmitting controller; one or more receiver subsystems, each including a corresponding receiver resonator; a software query A lookup table having discrete allowed power signal oscillation frequencies for the power signal sources; and software that, when loaded into memory and executed by a controller of any of the transmitter modules, performs the following actions: measuring one of an input impedance of a corresponding transmitter resonator and a test signal power draw of the corresponding transmitter resonator; and selecting a frequency for the corresponding power signal source from the lookup table based on one of the input impedance of the corresponding transmitter resonator and the test signal power draw of the corresponding transmitter resonator. The software, when executed, may perform the following actions: measuring a power level delivered by the corresponding transmitter resonator while adjusting a phase of a power signal from the corresponding power signal source. The transmitter resonators may be substantially decoupled from each other by a grounded shielding mesh.

In yet another aspect, a wireless near-field method for transferring power from a multiple transmitter subsystem to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency is provided, the method comprising: providing the multiple transmitter subsystem comprising a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding electrically connected transmitter module being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common emitting surface; arranging a resonant receiver subsystem proximate to the common emitting surface, the resonant receiver subsystem comprising a resonant power signal oscillation ... a single receiver resonator stacked above; measuring the input impedance of each of the transmitter resonators and one of the powers drawn by each of the transmitter resonators from a test signal; setting the power signal to each of the plurality of independent transmitter resonators to one of an off state and an active state based on the corresponding measured resonator input impedance and one of the powers drawn by the corresponding transmitter resonator from the test signal; selecting a power signal oscillation frequency for each active transmitter resonator from the plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator; and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting a phase of a power signal applied to each corresponding transmitter resonator to a phase at which power transfer through the transmitter resonator is substantially maximum.

In another aspect, a wireless near-field method for transmitting power from a multi-transmitter subsystem to two or more receiver subsystems at a variable resonant power signal oscillation frequency is provided, the method comprising: providing the multi-transmitter subsystem including a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding transmitter module being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common emitting surface; arranging the two or more resonant receiver subsystems proximate to the common emitting surface, each resonant receiver subsystem including two or more of the transmitter resonators being coupled to the common emitting surface; a single receiver resonator stacked above; measuring the input impedance of each of the transmitter resonators and one of the powers drawn by each of the transmitter resonators from the test signal; setting the power signal to each of the plurality of independent transmitter resonators to one of an off state and an active state based on the corresponding measured resonator input impedance and one of the powers drawn by the corresponding transmitter resonators from the test signal; selecting a power signal oscillation frequency for each active transmitter resonator from the plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator; and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting a phase of a power signal applied to each corresponding transmitter resonator to a phase at which power transfer through the transmitter resonator is substantially maximum.

In another aspect, a near-field wireless system for transmitting power from a photovoltaic cell to a power load is provided, the system comprising: a transmitter module, which is in wired electrical communication with the photovoltaic cell, the transmitter module is configured to convert the power from the photovoltaic cell into an oscillating power signal having an oscillation frequency; a transmitter resonator, which is in wired electrical communication with the transmitter module and is configured to resonate at the oscillation frequency; a receiver resonator, which is configured to resonate at the oscillation frequency and is arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; and a receiver module, which is in wired electrical communication with the receiver resonator, the receiver module is configured to receive power from the receiver resonator and provide the received power to the power load in the form of direct current via wired electrical communication.

The transmitting module may include a power amplifier configured to modulate the power received from the photovoltaic cell at the oscillation frequency. The transmitting module may include an oscillator configured to provide the oscillation frequency to the power amplifier. The transmitting module may include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. The transmitting module may include a transmission tuning network configured to at least change the phase of the power provided by the transmitting module to the transmitter resonator based on second information from at least one of the one or more sensors under the control of the controller.

The system may include a power conditioning unit electrically connected between the photovoltaic cell and the transmitter module and configured to adapt power from the photovoltaic cell to a format compatible with the transmitter module. The transmitter module may include small signal electronic circuitry, and the power conditioning unit may be further configured to provide power to the small signal electronic circuitry. The emitter resonator may be disposed on a surface of the photovoltaic cell opposite an active solar radiation receiving surface of the cell. The emitter resonator has a surface area having an extension that is at least a major portion of the extension of the active solar radiation receiving surface of the cell.

The transmitter resonator may have a planar area that is smaller than a planar area of the receiver resonator. The receiver resonator may be arranged and configured to receive power from the other transmitter resonator via at least one of capacitive coupling and magnetic induction at the resonant frequency.

In yet another embodiment of a near-field wireless system for transmitting power from a photovoltaic cell array to a power load, the system includes: a first plurality of transmitter modules, each transmitter module in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillating frequency; a second plurality of transmitter resonators, each transmitter resonator in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules; The invention relates to a power supply module of the present invention, wherein the plurality of transmitter resonators are in wired electrical communication with each other and are configured to resonate at the oscillation frequency; a single receiver resonator configured to resonate at the oscillation frequency and arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a receiver module, which is in wired electrical communication with the receiver resonator, the receiver module being configured to receive power from the receiver resonator and provide the received power to a power load in the form of direct current via the wired electrical communication.

Each transmitting module from the first plurality of transmitting modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmitting module from the first plurality of transmitting modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmitting module from the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmitting module from the first plurality of transmitting modules may include a transmission tuning network configured to at least change the phase of power provided by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

The system may include a third plurality of power conditioning units, each power conditioning unit from the third plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell and a corresponding transmitter module and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitter module. Each transmitter module from the first plurality of transmitter modules may include a small signal electronic circuit, and the corresponding power conditioning unit may be further configured to provide power to the small signal electronic circuit. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of the corresponding photovoltaic cell opposite an active solar radiation receiving surface of the cell.

In yet another embodiment of a near-field wireless system for transmitting power from an array of photovoltaic cells to a power load, the system includes: a first plurality of transmitter modules, each transmitter module in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at the oscillation frequency; a third plurality of receiver resonators, The invention relates to a power supply module of the present invention, wherein the first plurality of receiver resonators is configured to resonate at the oscillation frequency, each receiver resonator from the third plurality of receiver resonators is configured to receive power from a corresponding transmitter resonator from the second plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each receiver module being in wired electrical communication with a corresponding receiver resonator from the third plurality of receiver resonators, the receiver module being configured to receive power from the corresponding receiver resonator and provide the received power to a power load in the form of direct current via wired electrical communication.

Each transmitting module from the first plurality of transmitting modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmitting module from the first plurality of transmitting modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmitting module from the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmitting module from the first plurality of transmitting modules may include a transmit tuning network configured to at least change the phase of power provided by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

The system may further include a fifth plurality of power conditioning units, each power conditioning unit from the fifth plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell from the solar cell array and a corresponding transmitting module from the first plurality of transmitting modules, and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitting module. Each transmitting module from the first plurality of transmitting modules may include a small signal electronic circuit, and the corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuit. Each emitter resonator from the second plurality of emitter resonators may be disposed on a surface of a corresponding photovoltaic cell from the photovoltaic cell array opposite an active solar radiation receiving surface of the cell.

In another embodiment, a near-field wireless system for transmitting power from a photovoltaic cell array to a power load is provided, the system comprising: a first plurality of transmitter modules, each transmitter module being in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module being configured to convert power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator being in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and being configured to resonate at the oscillation frequency; a third plurality of transmitter resonators being in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and being configured to resonate at the oscillation frequency; The invention further comprises a plurality of receiver resonators, each of which is configured to resonate at the oscillation frequency, each of which is configured to receive power from a portion of the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each of which is in wired electrical communication with a corresponding receiver resonator, the receiver modules being configured to receive power from the corresponding receiver resonator and provide the received power to a power load in the form of direct current via the wired electrical communication.

Each transmitting module from the first plurality of transmitting modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmitting module from the first plurality of transmitting modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmitting module from the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmitting module from the first plurality of transmitting modules may include a transmit tuning network configured to at least change the phase of power provided by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

The system may include a fifth plurality of power conditioning units, each of the fifth plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell from the photovoltaic cell array and a corresponding transmitting module from the first plurality of transmitting modules, and being configured to adapt power from the corresponding photovoltaic cell into a format compatible with the corresponding transmitting module.

Each transmitter module from the first plurality of transmitter modules may include small signal electronic circuitry, and a corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of a corresponding photovoltaic cell from the photovoltaic cell array opposite an active solar radiation receiving surface of the cell.

In yet another aspect, a method for transmitting power from a photovoltaic cell to an electrical load is provided, the method comprising: converting power from the photovoltaic cell into an oscillating electrical signal having an oscillation frequency in a transmitter module; transmitting the power to a transmitter resonator that is in wired electrical communication with the transmitter module and configured to resonate at the oscillation frequency; receiving the power in a receiver resonator that is configured to resonate at the oscillation frequency and is configured to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving the power in a receiver module that is in wired electrical communication with the receiver resonator; and providing the received power to the electrical load in the form of direct current via wired electrical communication.

In yet another embodiment of a method for delivering power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillating frequency in each of a first plurality of corresponding transmitter modules; delivering power from a corresponding transmitter resonator in each of the transmitter modules to a second plurality of transmitter resonators, the transmitter resonators The invention relates to a method for transmitting power to a power load in a power supply module of the present invention. The method comprises: receiving power in a receiver resonator, each of which is configured to resonate at the oscillation frequency; receiving power in a receiver resonator, the receiver resonator being configured to resonate at the oscillation frequency and being arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; receiving power in a receiver module in wired electrical communication with the receiver resonator; and providing the received power in the form of direct current to a power load via wired electrical communication.

In yet another embodiment of a method for transmitting power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitter modules; transmitting power from each of the transmission modules to a corresponding transmitter resonator from a second plurality of transmitter resonators, wherein each transmitter resonator is configured to resonate at the oscillation frequency; ; receiving power from each transmitter resonator in a corresponding receiver resonator configured to resonate at the oscillation frequency, wherein each receiver resonator is further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving power from each receiver resonator in a corresponding receiver module in wired electrical communication with the receiver resonator; and providing the received power to a power load in the form of direct current via wired electrical communication.

In yet another embodiment of a method for transmitting power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitter modules; transmitting power from each of the transmission modules to a transmitter resonator from a second plurality of transmitter resonators, wherein each transmitter resonator is configured to resonate at the oscillation frequency; and transmitting power from each of the transmission modules to any adjacent receiver resonator in a third plurality of receiver resonators. Receiving power from each transmitter resonator, the receiver resonators configured to resonate at an oscillation frequency, wherein each receiver resonator is further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; sharing the received power between the third plurality of receiver resonators; and providing the received power to a power load in direct current form via wired electrical communication, the received power coming from one or more of the third plurality of receiver resonators via corresponding one or more receiver modules. The method may further include converting the voltage and current of the power from each photovoltaic cell into a voltage and current suitable for the corresponding transmitter module before converting the power into the oscillating power signal.

A power transmission system for supplying power from a DC power source to a power load is provided, the system comprising: a radio frequency power amplifier in wired electrical communication with the power source and configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase radio frequency rectifier in wired electrical contact with the power load and in radio frequency communication with the power amplifier, the rectifier configured to receive power transmitted from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier. The rectifier may be a differential self-synchronous radio frequency rectifier.

The receiver controller may be configured to automatically adjust the current-voltage phase characteristic of the rectifier. The power transmission system may further include a load management system in wired communication with the load and disposed between the load and the rectifier in a power signaling manner, the load management system being configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier. The load management system may be configured to automatically adjust the current-voltage phase characteristic of the rectifier.

The power transmission system may further include a transmitter controller in communication with the amplifier, the transmitter controller configured to increase the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the amplifier. The transmitter controller may be configured to automatically adjust the current-voltage phase characteristic of the amplifier to increase the efficiency of the power transmission.

The power transmission system may further include an oscillator in communication with the amplifier and the transmitter controller. The transmitter controller may be configured to adjust an oscillation frequency via the oscillator.

The power amplifier may be in direct wired radio frequency communication with the adjustable phase radio frequency rectifier. The power amplifier may be in wireless near-field radio frequency communication with the adjustable phase radio frequency rectifier. The power transmission system may include: a transmitter resonator in wired radio frequency communication with the power amplifier; and a receiver resonator in wired radio frequency communication with the rectifier. The transmitter resonator and the receiver resonator may be in wireless near-field radio frequency communication with each other. The power amplifier may be in at least one of capacitive near-field radio frequency communication and inductive near-field radio frequency communication with the rectifier. The power amplifier may be in dual-peak near-field radio frequency communication with the rectifier.

The DC power source may include a rechargeable battery and the load may include an electric motor. The load may include a computer monitor. The resonant structure of the system may include at least one conductive mechanical load that carries the structural components of the system.

The system may further include a power conditioning unit electrically disposed between the power source and the power transmission system, the power conditioning unit being configured to regulate at least one of the current and the voltage from the power source to improve the efficiency of the power transmission.

Further provided is a method for transmitting power from a DC power source to an electrical load, the method comprising: providing a power transmission system in wired electrical communication with the power source, the power transmission system comprising an RF power amplifier in RF communication with an adjustable phase RF rectifier, the adjustable phase RF rectifier being in wired electrical contact with the electrical load; converting power from the DC power source into an RF oscillating power signal in the amplifier; converting the RF oscillating power signal into a DC power signal in the rectifier; and adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the rectifier. Providing the adjustable phase RF rectifier may include providing a differential self-synchronous RF rectifier.

The method may further include adjusting the efficiency of the power transmission by adjusting the DC equivalent input resistance of the amplifier. Providing the power transmission system may include providing a load management system in wired communication between the rectifier and the load. The adjusting the DC equivalent input resistance of the amplifier may include adjusting the input impedance of the rectifier by adjusting the load management system. Adjusting the load management system may include automatically adjusting the load management system.

The method may further include adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the power amplifier. Providing the power transmission system may include providing a transmitter controller in communication with the power amplifier to control the power amplifier. The adjusting the current-voltage phase characteristic of the power amplifier may be performed by the transmitter controller. The adjusting the current-voltage phase characteristic of the power amplifier may be performed automatically by the transmitter controller.

The method may further include adjusting the efficiency of power transfer by changing the oscillation frequency of the power amplifier.

Providing a power transmission system may include providing a receiver controller in communication with the rectifier to control the rectifier. The adjusting the current-voltage phase characteristic of the rectifier may be performed by the receiver controller. The adjusting the current-voltage phase characteristic of the rectifier may be performed automatically by the receiver controller.

Providing the power delivery system may include providing the power amplifier in direct wired radio frequency communication with the adjustable phase radio frequency rectifier. Providing the power delivery system may include providing the power amplifier in wireless near field radio frequency communication with the adjustable phase radio frequency rectifier.

Providing the power transfer system may include: a transmitter resonator that provides wired radio frequency communication with the power amplifier; and a receiver resonator that provides wired radio frequency communication with the radio frequency rectifier. The method may further include operating the transmitter resonator and the receiver resonator in wireless near-field radio frequency communication with each other. Providing the power transfer system may include providing the power amplifier in at least one of capacitive near-field wireless radio frequency communication and inductive near-field wireless radio frequency communication with the rectifier. Providing the power transfer system may include providing a receiver resonator and the power amplifier in bimodal wireless near-field communication with the rectifier.

The method may further include: providing a power conditioning unit electrically disposed between the power source and the power transmission system; and adjusting the power conditioning unit to adjust at least one of the current and voltage from the power source to improve the efficiency of the power transmission.

Further provided is a method for transmitting power from a DC power source to a power load, the method comprising: providing a power transmission system in wired communication with the power source, the power transmission system comprising: an oscillator capable of oscillating at an oscillation frequency; a power amplifier and a transmitter tuning network, both of which are under the control of a transmitter controller; and a receiver tuning network and a load management system, both of which are under the control of a receiver controller, the load management system in wired communication with the power load; in the power amplifier The invention relates to a method for transmitting the power from the power source into an oscillating power signal having an oscillation frequency; transmitting the power signal from the power amplifier to the load management system via the transmitter tuning network and the receiver tuning network under the control of the transmitter controller; adjusting at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier, the transmitter tuning network, the receiver tuning network and the load management system to change the rate of power transmission; and providing the power received by the load management system to the power load in the form of direct current via wired communication.

Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting power by wired communication. Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting power by wireless communication. Transmitting power by wireless communication may include transmitting power by near-field wireless communication. Transmitting power by near-field wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling.

Delivering power from a DC power source may include delivering power from at least one solar cell. Delivering power from a DC power source may include delivering power from at least one solar cell. Delivering power from a DC power source may include delivering power from a power source having a varying voltage.

In another embodiment, an electric system includes: a mechanical load carrying structure having a conductive first portion; a power load; and a power transfer system including at least one radio frequency resonator configured for near-field wireless power transfer, wherein the resonator at least partially includes the conductive first portion. The electric system may further include a rechargeable battery, and the power load may include an electric motor. The electric system may be an electric vehicle and the mechanical load carrying structure may include a chassis of the vehicle. The electric system may be a display monitor, and the mechanical load carrying structure may be at least one of a frame and a base of the monitor.

The electric power system may further include a power source. The power transmission system may include: a radio frequency power amplifier in wired electrical communication with the power source and configured to convert a direct current voltage from the power source into an alternating current voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier in wired electrical contact with the power load and in radio frequency communication with the power amplifier, the rectifier configured to receive power transmitted from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier.

In another embodiment, an apparatus includes: a mechanical load bearing structure having a conductive first portion; a power source; an electrical load; and a power transmission system including: an RF power amplifier in wired electrical communication with the power source and configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier in wired electrical communication with the electrical load and in communication with the power amplifier; a rectifier configured to receive power transmitted from the amplifier; and a receiver controller communicating with the rectifier, the receiver controller configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier; wherein the conductive first portion is configured to carry at least one of the RF signal from the amplifier and the RF signal to the rectifier.

The device may further include a load management system in wired communication with the load and disposed between the load and the rectifier in a power signal manner, the load management system being configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier. The device may further include a transmitter controller in communication with the amplifier, the transmitter controller being configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristic of the amplifier. The device may further include an oscillator in communication with the amplifier and the transmitter controller, wherein the transmitter controller is configured to adjust the oscillation frequency via the oscillator.

The power amplifier may be in direct wired RF communication with the rectifier via the conductive first portion. The power amplifier may be in wireless near-field RF communication with the rectifier. The power transmission system may include: a transmitter resonator in wired RF communication with the power amplifier; and a receiver resonator in wired RF communication with the rectifier, and one of the transmitter resonator and the receiver resonator may include the conductive first portion. The transmitter resonator and the receiver resonator may be in wireless near-field RF communication with each other. The power amplifier may be in at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier. The power amplifier may be in bimodal near-field wireless RF communication with the rectifier. The DC power source may include a rechargeable battery, and the load may include an electric motor.

In some embodiments, a sealed bidirectional power transmission circuit device includes a plurality of terminals, the plurality of terminals are configured to communicate electrically with a device outside the sealed device, the sealed device includes within the sealed interior: a multi-terminal power switching device having at least one DC terminal, at least one AC terminal, and at least one control terminal, the multi-terminal power switching device being adjustable between an amplification state and a rectification state, and being arranged to: bidirectionally transmit a DC voltage and a DC current via at least one DC terminal; and bidirectionally transmit a DC voltage and a DC current via at least one AC terminal. The terminal bidirectionally transmits a radio frequency power signal having amplitude, frequency and phase; in wired data communication with a controller, a phase, frequency and duty cycle adjustment circuit performs wired electrical communication with the power switching device via the at least one control terminal and is arranged to: establish a radio frequency oscillation signal having the frequency and phase of the radio frequency power signal at the at least one control terminal of the power switching device; and adjust the power switching device between an amplification state and a rectification state by adjusting the phase of the radio frequency oscillation signal under the command of the controller. In some embodiments, the controller can be disposed in a sealed interior of the sealed bidirectional power transmission circuit device. The plurality of terminals of the sealed power transfer circuit device may include terminals for data communication between the controller and devices outside the sealed interior.

The RF power signal may have a duty cycle, and the phase, frequency and duty cycle adjustment circuit may be further arranged to adjust the duty cycle of the RF power signal by adjusting the duty cycle of the RF oscillation signal. The phase, frequency and duty cycle adjustment circuit may include an RF oscillator for generating the RF oscillation signal under instructions from the controller.

The sealed power transmission circuit device may further include a tuning network in wired data communication with the controller inside the seal, the tuning network is in wired electrical communication with the power switching device via the at least one AC terminal, and the tuning network is arranged to adjust the radio frequency power signal to a tuned radio frequency power signal under instructions from the controller. The bidirectional power transmission circuit device may include a modulator configured to modulate information onto the radio frequency power signal. The modulator includes the tuning network. The modulator may be configured to modulate the radio frequency power signal using information provided by the controller. The tuning network may include a harmonic termination network circuit, which is arranged to suppress the harmonics of the RF oscillation signal in the RF power signal. The harmonic termination network may include one or more inductors and one or more of a first harmonic terminal, a second harmonic terminal, and a third harmonic terminal. The sealed power transmission circuit device may further include an amplitude/frequency/phase detector in the sealed interior for wired data communication with the controller, the amplitude/frequency/phase detector being set to perform wired electrical communication with the tuning network and arranged to determine the amplitude, frequency and phase of any RF power signal transmitted between the tuning network and an AC load/source outside the sealed device. The tuning network may further include one or more of a compensation network, a matching network, and a filter.

The phase, frequency and duty cycle adjustment circuit can be arranged to receive instructions from the controller based on the measurement data transmitted to the controller by the amplitude/frequency/phase detector. The phase, frequency and duty cycle adjustment circuit can be configured to adjust the RF oscillation signal based on the feedback signal received directly from the amplitude/frequency/phase detector. The tuning network can include a voltage-current tuner, which is used to adjust the phase difference between the voltage and current of the tuned RF power signal based on the measurement data from the amplitude/frequency/phase detector when the power switching device is in the amplification state.

The sealed power transmission circuit device may further include a power management circuit within the seal for wired communication between the power switching device and a DC power source/load outside the sealed device, the power management circuit being configured to impedance match the power switching device with the external DC power source/load and to adjust the DC power transmitted between the power switching device and the DC power source/load based on a feedback signal received directly from the amplitude/frequency/phase detector. In other embodiments, the sealed power transmission circuit device may further include a power management circuit inside the seal that performs wired data communication with the controller and performs wired electrical communication between the power switching device and a DC power source/load outside the sealed device, the power management circuit being configured to impedance match the power switching device with the external DC power source/load and to adjust the DC power transmitted between the power switching device and the DC power source/load based on the measurement data transmitted to the controller by the amplitude/frequency/phase detector.

The sealed power transmission circuit device may further include a voltage/current detector in wired data communication with the controller within the seal, the voltage/current detector being configured to determine the DC voltage and DC current transmitted between the power switching device and the power management circuit. The phase, frequency and duty cycle adjustment circuit may be configured to receive instructions from the controller based on measurement data transmitted to the controller by the voltage/current detector. In other embodiments, the phase, frequency and duty cycle adjustment circuit may be configured to adjust the RF oscillation signal based on feedback signals received directly from the voltage/current detector.

The sealed power transmission circuit device may further include a memory inside the seal for wired data communication with the controller, the amplitude/frequency/phase detector and the voltage/current detector, wherein the memory is configured to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

The sealed power transmission circuit device may further include a power management circuit within the seal for wired communication between the power switching device and the AC power source/load outside the sealed device, the power management circuit being configured to match the amplitude, frequency and phase of the power switching device with the external AC power source/load, and to adjust the AC power transmitted between the power switching device and the AC power source/load based on feedback signals received directly from the amplitude/frequency/phase detector.

The sealed power transmission circuit device may further include a power management circuit inside the seal that performs wired data communication with the controller and performs wired electrical communication between the power switching device and the AC power source/load outside the sealed device, the power management circuit being configured to match the amplitude, frequency and phase of the transmission power switching device with the external AC power source/load, and adjusting the DC power transmitted between the power switching device and the AC power source/load based on the measurement data transmitted by the amplitude/frequency/phase detector to the controller.

The sealed power transmission circuit device may further include a voltage/current detector within the seal for wired data communication with the controller, the voltage/current detector being configured to determine the DC voltage and DC current transmitted between the power switching device and the power measurement circuit.

In some embodiments, the phase, frequency and duty cycle adjustment circuit is arranged to receive instructions from the controller based on measurement data transmitted to the controller by the voltage/current detector. In some embodiments, the phase, frequency and duty cycle adjustment circuit is arranged to adjust the RF oscillation signal based on feedback signals received directly from the voltage/current detector.

The sealed power transmission circuit device may further include a memory inside the seal for wired data communication with the controller, the amplitude/frequency/phase detector and the voltage/current detector, wherein the memory is arranged to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

The sealed power transmission circuit device may further include at least one of a Bluetooth communication circuit, a WiFi communication circuit, a Zigbee communication circuit, and a cellular communication technology circuit in the sealed interior for transmitting information between the controller and a device external to the sealed power transmission circuit device. The communication circuit may perform two-way wired communication with at least one communication antenna, and the communication antenna is arranged to communicate with a device external to the sealed power transmission circuit device. The antenna for the communication circuit may be disposed within the sealed interior of the sealed device.

The bidirectional power transmission circuit device may include a modulator configured to modulate information onto at least one of the RF power signal and the DC voltage. The modulator may include the power switching device. The modulator may be configured to modulate at least one of the RF power signal and the DC voltage using information provided by the controller. The modulator may further include the phase, frequency and duty cycle adjustment circuit.

In some embodiments, all circuit elements of the bidirectional power transmission circuit device can be monolithically integrated in a silicon single crystal wafer. In some embodiments, at least a portion of the circuit elements of the device can be integrated by flip chip technology.

In one specific embodiment, the electronic circuitry of the sealed bidirectional power transmission circuit device can be implemented in conjunction with at least one photovoltaic cell used as a DC source/load in a single silicon single crystal wafer. In another embodiment, the electronic circuitry of the sealed bidirectional power transmission circuit device can be implemented in conjunction with at least one photovoltaic cell used as a DC source/load 700 and a resonator structure used as an AC load/source on a surface of the silicon single crystal wafer in a single silicon single crystal wafer. Antennas for Bluetooth, WiFi, Zigbee, and cellular technologies can also be integrated on the same single silicon single crystal wafer.

In another aspect, a power transmission system for transmitting power between a DC source and a variable load is provided. A first self-synchronous radio frequency rectifier/amplifier and a second self-synchronous radio frequency rectifier/amplifier are configured to extract a first high frequency (HF) power signal and a second high frequency (HF) power signal from the DC source at a first high frequency frequency and a second high frequency frequency, respectively. A high frequency power link system is configured to receive and mix the first high frequency power signal and the second high frequency power signal to generate a transmitted power signal. A power signal conversion circuit in communication with the high frequency power link system and the variable load is configured to generate an output power signal from the transmitted power signal and supply the output power signal to the variable load.

The power transmission system further includes: a high-frequency switching signal generator configured to supply a first switching signal and a second switching signal to the first rectifier/amplifier and the second rectifier/amplifier at respective first and second high-frequency frequencies, and to establish and control a mutual phase relationship between the first switching signal and the second switching signal.

The power signal conversion circuit includes: a switching mode rectifier, configured to receive the transmitted power signal from the high-frequency power link system and rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit, configured to receive the rectified power signal from the switching mode rectifier and expand the rectified power signal to generate the output power signal.

The first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier can be configured to operate in a rectification mode, and the switching mode rectifier can be configured to operate in a normally-on mode, thereby allowing power to be extracted from the variable load and transmitted to the DC source via the power signal conversion circuit and the high-frequency power link system.

The expansion circuit can be configured to receive a reference signal from the variable load to expand the rectified power signal in synchronization with the signal in the variable load. The power signal conversion circuit, the high frequency power link system and the plurality of pairs of self-synchronous radio frequency rectifier/amplifiers can be configured to transmit control information from the rest of the system to the high frequency switching signal generator. The system can further include one or more controllers that communicate data with a plurality of components of the system and are configured to control the plurality of components. The system can further include: an isolable load information circuit configured to transmit information about at least one of the DC level, frequency and phase of the power signal in the variable load to the high frequency switching signal generator. The load information circuit may include a phase-locked loop. The load information circuit may further include an isolator system, which may include an air gap. The high frequency power link system may include a wireless power link system, which may be a dual peak wireless high frequency power link system. The high frequency power link system may include a wired power link system.

In two phase difference based implementations, the first high frequency frequency and the second high frequency frequency are the same frequency; and the first switching signal and the second switching signal may have a mutual phase difference that can be adjusted by the high frequency switching signal generator. In the first phase difference based implementation, the high frequency switching signal generator is configured to adjust the mutual phase difference between the first switching signal and the second switching signal based on the DC level in the variable load, thereby generating the transmitted power signal from the high frequency power link system as a DC signal that is correspondingly adjusted in amplitude. In an implementation based on a second phase difference, the high-frequency switching signal generator is configured to modulate the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load, thereby generating the transmitted power signal from the high-frequency power link system as an AC power signal modulated at the frequency of the power signal in the variable load.

In a frequency difference based implementation, the first high frequency frequency and the second high frequency frequency differ by a difference frequency ∆f. In this implementation, the high frequency switching signal generator is configured to determine the first high frequency frequency and the second high frequency frequency, and set the difference frequency ∆f to double the frequency of the power signal in the variable load. The high frequency power link system is configured to generate the transmitted power signal at the difference frequency ∆f, and the power signal conversion circuit is configured to supply the output power signal to the variable load at the frequency of the power signal in the variable load.

In another aspect, a method for transmitting power between a DC source and a variable load is provided, the method comprising: extracting a corresponding first high frequency (HF) power signal and a second high frequency (HF) power signal from the DC source at a first high frequency and a second high frequency via a corresponding first self-synchronous RF rectifier/amplifier and a second self-synchronous RF rectifier/amplifier; receiving and mixing the first high frequency power signal and the second high frequency power signal in a high frequency power link system to generate a transmitted power signal; generating an output power signal from the transmitted power signal in a power signal conversion circuit that communicates with the high frequency power link system and the variable load; and supplying the output power signal to the variable load.

The method may further include: generating a first switching signal and a second switching signal in a high frequency switching signal generator, and transmitting the first switching signal and the second switching signal to the first rectifier/amplifier and the second rectifier/amplifier at respective first high frequency frequencies and second high frequency frequencies; and establishing and controlling a mutual phase relationship between the first switching signal and the second switching signal in the high frequency switching signal generator. The method may further include: receiving the transmitted power signal from the high frequency power link system and rectifying the transmitted power signal in a switching mode rectifier of the power signal conversion circuit; and receiving the rectified power signal from the switching mode rectifier and expanding the rectified power signal in an expansion circuit of the power signal conversion circuit. The method may further include: setting the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier to rectification mode; setting the switching mode rectifier to normally open mode; extracting power from the variable load; and transmitting the extracted power to the DC source via the power signal conversion circuit and the high-frequency power link system.

The method may further include: developing the rectified power signal synchronized with the signal in the variable load based on a reference signal from the variable load; transmitting control information from the rest of the system to the high frequency switching signal generator via the power signal conversion circuit, the high frequency power link system, and the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier; controlling the plurality of components of the system by means of one or more controllers in data communication with the plurality of components; and transmitting information about at least one of the DC level, frequency, and phase of the power signal in the variable load to the high frequency switching signal generator using an isolable load information circuit including a phase-locked loop and an optional isolator system. Transmitting the power signal in the high frequency power link system may include transmitting the power signal wirelessly, transmitting the power signal bimodally, or transmitting the power signal wiredly.

Two methods for delivering power from the DC source to the variable load exploit a phase difference between switching signals. In such embodiments, the first switching signal and the second switching signal may have the same frequency and a mutual phase difference that may be adjusted by the high frequency switching signal generator. The method for a first of these embodiments includes adjusting the mutual phase difference between the first switching signal and the second switching signal based on a DC level in the variable load to generate the delivered power signal from the high frequency power link system as a DC signal that is correspondingly adjusted in amplitude. The method for a second of these embodiments includes modulating a mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load to generate the transmitted power signal from the high frequency power link system as an AC power signal modulated at the frequency of the power signal in the variable load.

A method for a frequency difference based implementation includes: determining a first high frequency and a second high frequency of corresponding first switching signals and second switching signals; and setting the frequency difference equal to twice the frequency of a power signal in a variable load. The method further includes: generating a transmitted power signal from a high frequency power link system at the frequency difference; and supplying the output power signal to the variable load at the frequency of the power signal in the variable load.

Power delivery systems described herein utilize phase or frequency differences between switching signals supplied to a pair of self-synchronous radio frequency rectifier/amplifiers to deliver AC or DC power from a DC source to a variable load, which can be extended to deliver power from a single DC source to a single variable load via multiple pairs of rectifier/amplifiers, and to deliver power from multiple DC sources to a single variable load using multiple pairs of rectifier/amplifiers. Apparatus and methods for achieving these objectives are described. In certain embodiments, these apparatus and methods also allow for simultaneous delivery of DC power and AC power to a load.

In one embodiment, a solar panel system for generating electricity and transmitting the electricity to an AC load is provided, the system comprising: a planar transparent solar cover having a planar first solar cover surface and a second solar cover surface; at least one photovoltaic cell disposed on the first solar cover surface, the at least one photovoltaic cell having a planar photosensitive surface facing the solar cover; a high-frequency power module disposed on the first solar cover surface and corresponding to each photovoltaic cell, the high-frequency power module A printed circuit board is provided, which carries a high-frequency power circuit for wired communication with at least one corresponding photovoltaic cell on a planar surface of the printed circuit board facing away from the solar cover; a conformal encapsulation layer is bonded to a planar surface of the solar cover and covers the at least one photovoltaic cell and the corresponding high-frequency power module; and a frame carries a single aggregator for receiving power from the at least one high-frequency power circuit and for transmitting the power to the AC load at the AC load line frequency.

The high frequency power circuit may be disposed on a planar surface of the printed circuit board facing away from the solar cell. The at least one planar printed circuit board may be disposed close to the corresponding at least one photovoltaic cell. The at least one photovoltaic cell may be arranged in an array. All high frequency power circuits may be phase locked to each other. All high frequency power circuits may be phase locked to each other via a phase locked loop to an AC power signal in an AC load.

In certain embodiments, the aggregator may be configured to receive power from the at least one high frequency power circuit via wireless power transfer. The aggregator may be configured to receive power from the at least one high frequency power circuit via bimodal wireless power transfer. Each of the high frequency power circuits may include a transmitter resonator configured to receive power from the corresponding at least one photovoltaic cell. The system may include a receiver resonator configured to receive power from the transmitter resonator. The aggregator may include: a low frequency expansion circuit; a switching mode rectifier; and a receiver module configured to receive power from the receiver resonator via wired communication. The receiver resonator may be mounted in the frame. The aggregator may be mounted on the receiver resonator.

In some embodiments, the aggregator may be configured to receive power from the at least one high-frequency power circuit via wired power transfer at a low frequency. Each of the high-frequency power circuits may include: a transmitter module configured to receive power from a corresponding at least one photovoltaic cell; a receiver module in wired communication with the transmitter module to receive power from the transmitter module at a high frequency; and a switching mode rectifier providing a low frequency power signal. The aggregator may include an expanded circuit capable of receiving power from the high-frequency power circuit at the low frequency and delivering the power to the AC load at the AC load line frequency.

The first solar cap surface may include an optically transparent polymer layer. The system may include a dielectric protective cap over the high frequency power circuit. The protective cap may be disposed above or below the conformal encapsulation layer. The periphery of the protective cap may be disposed below the conformal encapsulation layer and sealed to the conformal encapsulation layer.

A method for manufacturing a solar panel is provided, the method comprising: arranging at least one photovoltaic cell and a high-frequency power module on a planar surface of a transparent solar cover, the at least one photovoltaic cell having a photosensitive surface facing a surface of the transparent solar cover, the high-frequency power module including a high-frequency power circuit on a printed circuit board that performs wired communication with the at least one photovoltaic cell for collecting power from the at least one photovoltaic cell, wherein the high-frequency power circuit is arranged on a planar surface of the printed circuit board that is away from the transparent solar cover; arranging a thermally deformable polymer sheet on a side of the at least one photovoltaic cell opposite to the transparent solar cover, the thermally deformable polymer sheet The polymer sheet extends over the surface area of the transparent solar cover to form a compressed stack in a plane; the compressed stack is transferred to a vacuum oven; a vacuum is established in the vacuum oven to remove air between the layers of the compressed stack; the compressed stack is heated to a deformation temperature of the heat-deformable polymer sheet; pressure is applied to the stack perpendicular to the plane; an ambient air pressure is restored in the vacuum oven to bond the heat-deformable polymer sheet to the transparent solar cover and force the heat-deformable polymer sheet to conformally bond to the at least one photovoltaic cell and the high-frequency power module to form a packaged photovoltaic module array; and the packaged photovoltaic module array is mounted in a frame.

The method may further include placing a transparent heat-crosslinkable polymer sheet on the transparent solar cover before placing the at least one photovoltaic cell and the high-frequency power module on the transparent solar cover. Disposing the heat-deformable polymer sheet may include disposing a heat-deformable crosslinkable polymer sheet. Arranging the heat-deformable cross-linkable polymer sheet may include arranging a sheet comprising one or more layers of one or more of the following materials: polyethylene terephthalate, biaxially oriented polyethylene terephthalate, ethylene vinyl acetate, fluorinated polyester, polyvinyl fluoride, polyvinylidene fluoride, polyethylene vinyl acetate, polyethylene naphthalate, ethylene-tetrafluoroethylene, fluorovinyl ether, tetrafluoroethylene-hexafluoropropylene-vinylidene fluoride copolymer, polyamide, polypropylene, polyethylene and polyvinylidene fluoride short sugar palm fiber.

Mounting the packaged photovoltaic module array in a frame may include mounting the packaged photovoltaic module array in a frame carrying a receiver resonator and an aggregator, the aggregator configured to receive a power signal from the high frequency power circuit via the receiver resonator. Mounting the packaged photovoltaic module array in a frame may include mounting the packaged photovoltaic module array in a frame carrying an aggregator, the aggregator configured to receive a power signal from the high frequency power circuit via a wire.

If the solar panel system is considered without considering the packaging of the photovoltaic module, it can be described as a solar panel system for generating electricity and transmitting the electricity to an AC load, the system comprising: at least one photovoltaic cell, corresponding to each photovoltaic cell, a high-frequency power module in wired electrical communication with the corresponding at least one photovoltaic cell; and a frame carrying a single aggregator, the aggregator is arranged to receive power from the at least one high-frequency power module and to transmit the power to the AC load at an AC load line frequency. All of the at least one high-frequency power modules can be mutually phase-locked to the AC power signal in the AC load via a phase-locked loop. Each of the at least one high-frequency power module may include: a high-frequency switching signal generator, which can be phase-locked to a power signal in the AC load having the line frequency of the AC load; a first high-frequency switching mode power rectifier/amplifier and a second high-frequency switching mode power rectifier/amplifier, for providing a corresponding first high-frequency power signal and a second high-frequency power signal from power derived from the corresponding at least one photovoltaic cell, and the frequency difference between the corresponding first high-frequency power signal and the second high-frequency power signal is equal to twice the line frequency of the AC load. The aggregator of the solar panel system may include an expanded circuit arranged to receive power emitted from each of the at least one photovoltaic cell at twice the frequency of the AC load line frequency.

In certain embodiments, the aggregator of the solar panel system is configured to receive power from the at least one high frequency power module via wireless power transmission.

In certain embodiments, the aggregator of the solar panel system may be configured to receive power from at least one high frequency power module via bi-peak wireless power transfer. In these embodiments, each of the high frequency power modules includes a transmitter resonator in wired communication with a transmitter module, the transmitter resonator configured to receive power from the corresponding at least one photovoltaic cell. The solar power system also includes a single receiver resonator configured to receive power from the transmitter resonator corresponding to the at least one photovoltaic cell via bi-peak power transfer. The aggregator includes: a low frequency unfolded circuit; a switching mode rectifier; and a receiver module configured to receive power from the receiver resonator via wired communication. The receiver resonator may be mounted in the frame, and the aggregator may be mounted on the receiver resonator.

In another embodiment, the aggregator of the solar panel system can be configured to receive power from the at least one high-frequency power module via low-frequency wired power transmission. Each of the high-frequency power modules includes: a transmitter module configured to receive power from a corresponding at least one photovoltaic cell; a receiver module that communicates wired with the transmitter module to receive power from the transmitter module at a high frequency; and a switching mode rectifier that provides a low-frequency power signal. The aggregator includes an expanded circuit that is capable of receiving power from the high-frequency power module at a low frequency and transmitting the power to the AC load at the AC load line frequency.

In another embodiment, each of the high frequency power modules may include: a transmitter module configured to receive power from the corresponding at least one photovoltaic cell; a receiver module in wired communication with the transmitter module to receive power from the transmitter module at a high frequency; a switching mode rectifier providing a low frequency power signal; and a spreading circuit for spreading the low frequency signal from the switching mode rectifier. In this embodiment, the aggregator may be a device that collects all spread signals from each of the spreading circuits associated with each of the corresponding photovoltaic cells only at the AC load line frequency.

In the following detailed description, specific details are set forth to provide a more thorough understanding to those skilled in the art. However, well-known elements may not be shown or described in detail to avoid unnecessarily obscuring the present invention. Therefore, the present specification and drawings should be viewed in an illustrative rather than a restrictive sense.

One aspect of the invention provides a wireless power transmission system including a transmitter (also referred to as a primary side) and a receiver (also referred to as a secondary side). Another aspect provides a wireless power transmitter that can be used as part of other wireless power transmission systems. Another aspect provides a wireless power receiver that can be used as part of other wireless power transmission systems. A transmitter according to some embodiments may include a resonator configured to transmit power by inductive power transmission and/or by capacitive power transmission. Similarly, a receiver according to some embodiments may include a resonator configured to receive power by inductive power transmission and/or by capacitive power transmission.

1 is a simplified schematic diagram of a wireless power transmission (WPT) system 10 including a primary side 12 and a secondary side 14. The primary side 12 may also be referred to as a transmitter, and the secondary side 14 may also be referred to as a receiver. The primary side 12 includes: a transmitter module 20; and a transmitter resonator 30, and the secondary side 14 includes: a receiver module 40; and a receiver resonator 50.

The transmitter module 20 receives power including, for example, direct current (DC) power as input. Although not shown, the transmitter module 20 may include, for example, an inverter, a transmitter compensation network, and/or other components as further described herein. The transmitter module 20 delivers power including, for example, alternating current (AC) power as output to the transmitter resonator 30.

The transmitter resonator 30 receives power as input from the transmitter module 20 and can output a magnetic field 31A (e.g., a time-varying magnetic field) and/or an electric field 31B (e.g., a time-varying electric field). In some embodiments, the transmitter resonator 30 outputs the magnetic field 31A for the purpose of IPT. In some embodiments, the transmitter resonator 30 outputs the electric field 31B for the purpose of CPT. In some embodiments, the resonator 30 outputs both the magnetic field 31A and the electric field 31B for the purpose of transmitting power through both CPT and IPT. In some embodiments, the resonator 30 can switch between outputting the electric field 31B for the purpose of CPT, outputting the magnetic field 31A for the purpose of IPT, and outputting both the magnetic field 31A and the electric field 31B for the purpose of transmitting power through both CPT and IPT.

The adjective term "bimodal" is used herein to describe systems configured for both capacitive and inductive signaling.

In the presence of a magnetic field 31A, a current may be induced in the receiver resonator 50 for the purpose of IPT. In the presence of an electric field 31B, an AC potential may be induced on the receiver resonator 50 (or one or more of its antennas).

When a current is induced in the receiver resonator 50 by the magnetic field 31A, the current can be output to the receiver module 40. Similarly, when an AC potential is induced on the receiver resonator 50 by the electric field 31B, a current can be caused to flow into the receiver module 40 through the receiver resonator 50.

The receiver module 40 may receive power (e.g., AC power) as input from the receiver resonator 50 and may output power (e.g., DC power) to a load. The load may be a charge for an electrical storage device such as a battery or supercapacitor. By way of non-limiting example, the load may include or be a component of an electric bicycle (also known as an electric-assisted bicycle or electric-assisted bike) (such as an electric-assisted bike that is part of a shared bicycle fleet), a car, a boat, etc. Although not shown, the receiver module 40 may include, for example, a rectifier, a receiver compensation network, and/or other components as further discussed herein.

For various reasons, the WPT system 10 may be configured to adjust the ratio of power delivered from the transmitter module 20 to the receiver module 40 via CPT to the power delivered from the transmitter module 20 to the receiver module 40 via IPT (the "transmission mode ratio"). For example, the transmission mode ratio may be adjusted to: increase the ratio of power delivered by CPT as the distance between the transmitter resonator 30 and the receiver resonator 50 increases; increase the ratio of power delivered by IPT when a living being (e.g., a person or an animal) is near the WPT system 10; increase the ratio of power delivered by CPT when an object (e.g., a metal object) is near the WPT system 10; increase the ratio of power delivered by CPT when the alignment between the transmitter resonator 30 and the receiver resonator 50 deteriorates; and/or any combination of the foregoing.

In some embodiments, the transmit mode ratio may be adjusted based on maximum power point tracking techniques, such as, but not limited to, “observe and perturb” as sometimes used in wind turbines and solar panels (see, e.g., S. Dehghani, S. Abbasian, and T. Johnson, “Adjustable Load With Tracking Loop to Improve RF Rectifier Efficiency Under Variable RF Input Power Conditions,” IEEE Transactions on Microwave Theory and Techniques, Vol. 64, No. 2, pp. 343-352, February 2016). In some embodiments, the transmit mode ratio may be adjusted based on a machine learning algorithm. For example, in some embodiments, if the WPT system 10 determines that the WPT efficiency is unexpectedly low, the WPT system 10 may increase the proportion of power delivered by the CPT (or IPT). If the WPT efficiency is negatively affected by the increased trust in the CPT (or IPT), the WPT system 10 may reduce the trust in the CPT (or IPT). This process may be iteratively repeated until a desired/maximum WPT efficiency is achieved.

Each of the transmitter resonator 30 and the receiver resonator 50 may include a plurality of antennas 80 arranged in various configurations.

Antenna 80 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of creating both magnetic field 31A and electric field 31B (separately and/or simultaneously) for the purposes of CPT and IPT. FIGS. 2A, 2B, and 2C depict non-limiting examples of antennas 80, 180, 280. For purposes herein, "high self-inductance" is a self-inductance that is large enough to allow the antenna to create a magnetic field suitable for the purposes of IPT. Similarly, for purposes herein, "high self-capacitance" is a self-capacitance that is large enough to allow the antenna to create an electric field suitable for the purposes of CPT.

FIG. 2A depicts an antenna 80 according to certain embodiments. Antenna 80 may include any suitable conductive material. For example, antenna 80 may include copper, gold, silver, aluminum, other suitable materials, or combinations thereof. As can be seen from FIG. 2A , antenna 80 includes an elongated element 80A having a rectangular (e.g., square) cross-section that has been bent or formed into a generally planar rectangular (in the XY plane) coil shape such that adjacent wraps of elongated element 80A are separated by gaps 80B. Although gaps 80B are shown as being generally constant along the length of elongated element 80, this is not mandatory.

To increase the self-inductance of antenna 80, the size of gap 80B may be reduced. To increase the self-capacitance of antenna 80, the number of bends (e.g., bends 82A) of elongated element 80A may be increased, the number of corners and edges (e.g., edge 82B) of elongated element 80A may be increased, the length of elongated element 80A may be increased, and/or the thickness 80C of elongated element 80A may be increased.

FIG. 2B depicts another non-limiting example of an antenna 180 according to some embodiments. Antenna 180 is substantially similar to first antenna 80, except that elongated element 180A is not bent or formed into a generally planar rectangular coil shape, but is bent or formed into a generally planar sawtooth shape with square corners, as shown in FIG. 2B. As with antenna 80, adjacent sawtooths of elongated element 180A are separated by gaps 180B. Although gaps 180B are shown as being generally constant along the length of elongated element 180, this is not mandatory.

To increase the self-inductance of antenna 180, the size of gap 180B may be reduced. To increase the self-capacitance of antenna 180, the number of bends (e.g., bends 182A) of elongated element 180A may be increased, the number of corners and edges (e.g., edge 182B) of elongated element 180A may be increased, and/or the thickness 180C of elongated element 180A may be increased.

FIG. 2C depicts another non-limiting example of an antenna 280 according to some embodiments. Antenna 280 is substantially similar to first antenna 80, except that elongated element 280A is not bent or formed into a generally planar rectangular coil shape, but is bent or formed into a generally planar circular shape (in the XY plane) with hub element 280A, wherein fan-shaped elements 280C extend radially outward from hub element 280A. Adjacent fan-shaped elements 280C are separated from each other by gaps 280B.

To increase the self-inductance of antenna 280, the size of gap 280B may be reduced. To increase the self-capacitance of antenna 280, the number of sector elements 280C may be increased, the number of corners and edges (e.g., edge 280a) of hub element 280A and/or sector elements 280C may be increased, and/or the thickness 282C of elongated hub element 280A and/or sector elements 280C may be increased.

Although FIGS. 2A , 2B, and 2C depict exemplary non-limiting embodiments of antennas 80, 180, 280, it should be understood that many other shapes and configurations of antennas 80 may be employed in the resonators described herein. Non-limiting examples of changes that may be made to the antennas shown include: changing the cross-sectional shape of the elongated element 80A, 180A to a non-rectangular shape (e.g., triangular, circular, hexagonal, etc.); changing the 90° bend 82A, 182A to a non-90° or circular shape; changing the XY plane shape of the first transmitter antenna 80 to a non-rectangular or circular shape; using a non-repeating pattern of bends and corners, etc.

Although the antennas 80, 180, 280 are described and shown herein as being relatively flat or planar (e.g., having substantially no variation in thickness in the Z direction), this is not mandatory. In some embodiments, the antennas 80, 180, 280 may have a conical concave or conical convex shape as shown in FIGS. 3A and 3B. For example, the antennas herein may have a conical spiral shape (not shown). In some embodiments, the antenna 80 may have a rectangular conical spiral shape such that the inner windings of the antenna 80 are spaced apart from the outer windings of the antenna 80 in the Z direction. Such conical shapes may allow the resonator to be used for a wider range of resonant frequencies. In other embodiments, the thickness of the first transmitter antenna in the Z direction may vary in other ways.

For example, the antennas 80, 180, 280 may be arranged in a configuration similar to those of the panels in a CPT WPT system. For example, in a two-antenna WPT system according to certain embodiments, the transmitter resonator 30 may include a first transmitter antenna 32 configured in parallel with a first receiver antenna 52 of a receiver resonator 50, as shown in FIG. 4A. For the purpose of CPT, the mutual capacitance between the two antennas 32, 52 provides a path for current to flow forward to the receiver side, and the conductive path (e.g., land) will allow the current to flow back to the transmitter side. For the purpose of IPT, by driving current through the first transmitter antenna 32, a magnetic field 31A is generated that can induce current in the first receiver antenna 52. For the purpose of CPT, a voltage may be applied to the first transmitter antenna 32 to form a potential difference between the first transmitter antenna 32 and the first receiver antenna 52, thereby forming an electric field 31B.

The first transmitter antenna 32 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and/or simultaneously). For example, the first transmitter antenna may include one of antennas 80, 180, 280, or any other antenna described herein.

The first receiver antenna 52 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of inducing a current therein by the magnetic field 31A and having a potential difference thereon due to the electric field 31B (separately and/or simultaneously). In some embodiments, the first receiver antenna 52 may be substantially similar to the first transmitter antenna 32 (e.g., the first receiver antenna 52 may have the same characteristics of any antenna described or illustrated herein or otherwise). In some embodiments, the antennas 32, 52 may be different from one another (e.g., the first transmitter antenna 32 may include antenna 80, while the first receiver antenna 52 may include antenna 180).

In some embodiments, the XY plane area of the first transmitter antenna 32 is smaller than the XY plane area of the first receiver antenna 52 to improve coupling between the first transmitter antenna 32 and the first receiver antenna 52.

FIG. 4B shows another example of the configuration of antennas 80, 180, 280. In some embodiments, FIG. 4B shows a four-antenna stacked (or four-antenna vertical) WPT system. Each of the transmitter resonator 130 and the receiver resonator 150 includes two antennas. One antenna of the transmitter resonator 30 and one antenna of the receiver resonator 150 provide a forward path for power, while another antenna of the transmitter resonator 130 and another antenna of the receiver resonator 150 provide a return path for power.

For the purpose of IPT, a current is driven through the transmitter antennas 132, 134 to generate a magnetic field that can induce a current in the first receiver antenna 152 and the second receiver antenna 154. For the purpose of CPT, a potential difference can be applied between the first antenna 132 and the second antenna 134 to generate an electric field (31B shown in FIG. 1), thereby inducing a potential across the first receiver antenna 152 and the second receiver antenna 154.

As shown in FIG. 4B , the transmitter resonator 130 includes a first transmitter antenna 132 and a second transmitter antenna 134 separated in the Z direction by a spacer 138 .

The first transmitter antenna 132 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and/or simultaneously). For example, the first transmitter antenna may include one of antennas 80, 180, 280, or any other antenna described herein.

The spacer 138 may include any suitable material. For example, the spacer 138 may include air, a dielectric material, a ferrite, or some combination thereof. The spacer 138 may have a dielectric constant selected to change the electric field 31B and/or it may have a permeability selected to change the magnetic field 31A. The spacer 138 may include a high dielectric constant material that increases the capacitance of the transmitter resonator 130. The thickness and planar area of the spacer 138 may depend on the thickness and/or planar area of the first transmitter antenna 132 and the second transmitter antenna 134. In some embodiments, electrical isolation may be desirable and a low dielectric constant material may be used for the spacer 138 (e.g., for shielding).

The second transmitter antenna 134 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and/or simultaneously). In some embodiments, the second transmitter antenna 134 may be substantially similar to the first transmitter antenna 132 (e.g., the second transmitter antenna 134 may have the same characteristics of any antenna described or illustrated herein or otherwise). In some embodiments, the first transmitter antenna 132 and the second transmitter antenna 134 and the first receiver antenna 152 and the second receiver antenna 154 may be different from each other (e.g., the first transmitter antenna 132 and the second transmitter antenna 134 may be similar to antenna 80, and the first receiver antenna 152 and the second receiver antenna 154 may be similar to antenna 180).

In some embodiments, the size of the XY plane area of the second transmitter antenna 134 may be different from the XY plane area of the first transmitter antenna 132. In some embodiments, the XY plane area of the second transmitter antenna 134 may be smaller than the XY plane area of the first transmitter antenna 132 to ensure coupling between each pair of antennas. In some embodiments, the XY plane area of the second transmitter antenna 134 may be larger than the XY plane area of the first transmitter antenna 132.

In some embodiments, the second transmitter antenna 134 is substantially complementary to the first antenna 132 in size and/or shape, such that the first transmitter antenna 132 and the second transmitter antenna 134 do not substantially overlap in the Z direction. FIG5 depicts a schematic representation of an XZ plane cross-section of a portion of the transmitter resonator 130, wherein the first transmitter antenna 132 and the second transmitter antenna 134 are each substantially shaped similarly to the first transmitter antenna 180 of FIG2B. As can be seen, the portions 132A-1, 132A-2, 132A-3 of the elongated element 132A of the first transmitter antenna 132 overlap with the gaps 134B-1, 134B-2, 134B-3 of the second transmitter antenna 134 in the Z direction (e.g., a line oriented in the Z direction passing through the portion 132A-1 of the elongated element 132A of the first transmitter antenna 132 passes through the gaps 134B-1, 134B-2, 134B-3 of the second transmitter antenna 134). 1), and portions 134A-1, 134A-2, 134A-3 of the elongated element 134A of the second transmitter antenna 134 overlap with the gaps 132B-1, 132B-2, 132B-3 of the first transmitter antenna 132 in the Z direction (e.g., a line oriented in the Z direction passing through portion 134A-1 of the elongated element 134A of the second transmitter antenna 134 passes through the gap 132B-1 of the first transmitter antenna 132). The complementary shapes of the first transmitter antenna 132 and the second transmitter antenna 134 can reduce parasitic energy losses experienced by the transmitter resonator 130. In some embodiments, the first transmitter antenna 132 and the second transmitter antenna 134 may not be completely complementary, but may have one or more complementary portions.

The receiver resonator 150 includes a first receiver antenna 152 and a second receiver antenna 154 separated in the Z direction by a spacer 158. The first receiver antenna 152 can be substantially similar to the antennas 80, 180, 280, or any of the other antennas described herein. The second receiver antenna 154 can also be substantially similar to the antennas 80, 180, 280, or any of the other antennas described herein. Like the first transmitter antenna 132 and the second transmitter antenna 134, the first receiver antenna 152 and the second receiver antenna 154 can complement each other (or partially complement each other) in size and/or shape.

In some embodiments, as shown in FIG4B , the XY plane area of the first receiver antenna 152 and the second receiver antenna 154 is different from the XY plane area of the first transmitter antenna 132 and the second transmitter antenna 134 in order to adjust the self-inductance or self-capacitance of the receiver resonator 150. For example, in some embodiments, the XY plane area of the first receiver antenna 152 and the second receiver antenna 154 is larger than the XY plane area of the first transmitter antenna 132 and the second transmitter antenna 134, as shown in FIG2A . This XY plane area difference can improve the ability of the receiver resonator 150 to capture more magnetic fields 31A and/or electric fields 31B.

Spacer 158 may include any suitable spacer. Spacer 158 may include the same or similar material as spacer 138 or a different material than spacer 138. Spacer 138 may have a smaller Z-direction dimension than spacer 158 to achieve a desired self-capacitance and/or self-inductance. This may effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks may be used in both primary side 12 and secondary side 14 to accommodate these coupling coefficient and impedance changes.

Compared to the four-antenna parallel structure shown in FIG4C , the stacked configuration of FIG4B is more compact in the XY plane. In addition, since all antennas can be centrally aligned, the configuration is robust to angular misalignment. Specifically, when the antennas are circular in shape, angular rotation has no effect on the coupling capacitance. However, compared to the four-antenna parallel structure shown in FIG4C , the mutual conductance of the stacked configuration of FIG4B can be reduced due to the increased cross-coupling capacitance.

FIG. 4C depicts another example of the configuration of antennas 80, 180, 280. In some embodiments, FIG. 4C shows a four-antenna parallel (or four-antenna horizontal) WPT system. Each of the transmitter resonator 230 and the receiver resonator 250 includes two antennas. One antenna of the transmitter resonator 230 and one antenna of the receiver resonator 250 together provide a forward path for power, and another antenna of the transmitter resonator 230 and another antenna of the receiver resonator 250 together provide a return path for power.

For the purpose of IPT, a current is driven through the first transmitter antenna 232 and the second transmitter antenna 234 of the transmitter to generate a magnetic field that can induce a current in the first receiver antenna 252 and the second receiver antenna 254. For the purpose of CPT, a potential difference can be formed between the first transmitter antenna 232 and the second transmitter antenna 234 to generate an electric field 31B, thereby inducing a potential across the first receiver antenna 252 and the second receiver antenna 254.

Compared to the transmitter resonator 130 and the receiver resonator 150 shown in FIG. 4B , the transmitter resonator 230 and the receiver resonator 250 having a horizontal antenna arrangement may be desirable in applications where there are restrictions on the Z-direction size of the resonators.

The transmitter resonator 230 includes a first transmitter antenna 232 and a second transmitter antenna 234 separated in the X direction by a spacer 238. By separating the first transmitter antenna 232 from the second transmitter antenna 234 in the X direction, parasitic energy losses can be reduced. The first transmitter antenna 232 and the second transmitter antenna 234 can be substantially similar to the first transmitter antenna 132 and the second transmitter antenna 134, and the spacer 238 can be substantially similar to the spacer 138. As with the transmitter resonator 130, the first transmitter antenna 232 can have a larger XY plane area than the XY plane area of the second transmitter antenna 234 to improve the forward path for power transfer.

The spacer 238 may include any suitable material. For example, the spacer 238 may include air, a dielectric material, a ferrite, or a combination thereof. The spacer 238 may have a dielectric constant selected to change the electric field 31B and/or it may have a permeability selected to change the magnetic field 31A. The spacer 238 may include a high dielectric constant material that increases the capacitance of the transmitter resonator 230. The thickness and planar area of the spacer 238 may depend on the thickness and/or planar area of the first transmitter antenna 232 and the second transmitter antenna 234. In some embodiments, electrical insulation may be desirable and a low dielectric constant material may be used for the spacer 238 (e.g., for shielding).

The receiver resonator 250 includes a first receiver antenna 252 and a second receiver antenna 254 separated in the X direction by a spacer 258. By separating the first receiver antenna 252 from the second receiver antenna 254 in the X direction, parasitic energy losses can be reduced. The first receiver antenna 252 and the second receiver antenna 254 can be substantially similar to the first receiver antenna 152 and the second receiver antenna 154, and the spacer 258 can be substantially similar to the spacer 138. As with the receiver resonator 150, the first receiver antenna 252 can have a larger XY plane area than the XY plane area of the second receiver antenna 254.

Spacer 258 may include any suitable spacer. Spacer 258 may include the same or similar material as spacer 238 or a different material than spacer 238. Spacer 238 may have a smaller Z-direction dimension than spacer 258 to achieve a desired self-capacitance and/or self-inductance. This may effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks may be used in both primary side 12 and secondary side 14 to accommodate these coupling coefficient and impedance changes.

In some embodiments, the XY plane area of the spacer 258 can be different from the XY plane area of the spacer 238 to vary the self-inductance or self-capacitance of the transmitter resonator 230 or the receiver resonator 250. For example, the spacer 238 can have a smaller XY plane area than the spacer 258, as shown.

FIG. 4D depicts another example of a configuration of antennas 80, 180, 280. In some embodiments, FIG. 4D depicts a six-antenna WPT system combined with the stacked configuration of FIG. 4B and the parallel configuration of FIG. 4C. Each of the transmitter resonator 130 and the receiver resonator 150 includes three antennas. One of the first transmitter antenna 332 and the second transmitter antenna 334 together with one of the first receiver antenna 352 and the second receiver antenna 354 provides a forward path for power, while the other of the first transmitter antenna 332 and the second transmitter antenna 334 together with the other of the first receiver antenna 352 and the second receiver antenna 354 provides a return path for power. The third transmitter antenna 336 and the third receiver antenna 356 operate as auxiliary antennas to increase the equivalent self-capacitance and act as an electric field shield. In some embodiments, the third transmitter antenna 336 and the third receiver antenna 356 are passive (e.g., no potential difference is applied between the third transmitter antenna 336 and the third receiver antenna 356 and/or no current is driven through the third transmitter antenna 336 and the third receiver antenna 356). For the purpose of IPT, a magnetic field is generated that can induce current in the first receiver antenna 352, the second receiver antenna 354, and the third receiver antenna 356 by driving current through one or more of the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336 of the transmitter. For the purpose of CPT, a voltage may be applied to the first transmitter antenna 332, the second transmitter antenna 334 and/or the third transmitter antenna 336 to form a potential difference between any one of the first transmitter antenna 332, the second transmitter antenna 334 and the third transmitter antenna 336, thereby forming an electric field 31B.

The transmitter resonator 330 includes a first transmitter antenna 332 and a second transmitter antenna 334 separated in the X direction by a spacer 338; and a third transmitter antenna 336 separated from the first and second transmitter antennas and the spacer 338 by a second spacer 339. The third transmitter antenna 336 can provide electric field shielding to reduce undesired escape of electric fields from the transmitter resonator 330. The third transmitter antenna 336 can contain a ferrite sheet or surface to provide magnetic field shielding to reduce undesired escape of magnetic fields from the transmitter resonator 330. By varying the spacer 339, shielding or shaping of electric or magnetic fields is also possible.

The first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336 may be substantially similar to either of the first transmitter antenna 132 and the second transmitter antenna 134. The spacers 338, 339 may be substantially similar to the spacer 138. As with the transmitter resonator 130, the first transmitter antenna 332 may have a larger XY plane area than the XY plane area of the second transmitter antenna 334. The third transmitter antenna 336 may have a larger XY plane area than either of the first transmitter antenna 332 and the second transmitter antenna 334.

The spacers 338, 339 may include any suitable material. For example, the spacers 338, 339 may include air, a dielectric material, a ferrite, or a combination thereof. The spacers 338, 339 may have a dielectric constant selected to change the electric field 31B and/or they may have a permeability selected to change the magnetic field 31A. The spacers 338, 339 may include a high dielectric constant material to increase the capacitance of the transmitter resonator 230. The thickness and planar area of the spacers 338, 339 may depend on the thickness and/or planar area of the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336. In some embodiments, electrical isolation may be desirable and a low dielectric constant material may be used for the spacers 338, 339 (e.g., for shielding).

The receiver resonator 350 includes: a first receiver antenna 352 and a second receiver antenna 354 separated in the X direction by a spacer 358; and a third receiver antenna 356 separated from the first receiver antenna, the second receiver antenna, and the spacer 358 by a second spacer 359. The third receiver antenna 356 can provide electric field shielding to reduce the undesired escape of electric fields from the receiver resonator 350. The third receiver antenna 356 can contain a ferrite sheet or surface to provide magnetic field shielding to reduce the undesired escape of magnetic fields from the transmitter. By changing the spacer 359, shielding or shaping of electric or magnetic fields is also possible. The first receiver antenna 352, the second receiver antenna 354, and the third receiver antenna 356 can be substantially similar to any of the first receiver antenna 152 and the second receiver antenna 154. The spacers 358, 359 can be substantially similar to the spacer 158. As with the receiver resonator 150, the first receiver antenna 352 may have a larger XY plane area than the XY plane area of the second receiver antenna 354. The third receiver antenna 356 may have a larger XY plane area than either of the first receiver antenna 352 and the second receiver antenna 354.

Spacers 358, 359 may include any suitable spacers. Spacers 358, 359 may include the same or similar materials as spacers 338, 339 or different materials than spacers 338, 339. Spacers 338, 339 may have smaller Z-direction dimensions than spacers 358, 359 to achieve a desired self-capacitance and/or self-inductance. This may effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate these coupling coefficient and impedance changes.

In some embodiments, the XY plane area of spacer 358 can be different from the XY plane area of spacer 338 to vary the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350. For example, spacer 338 can have a smaller X-direction dimension than spacer 358. In some embodiments, the Z-direction dimension of spacer 359 can be different from the Z-direction dimension of spacer 339 to vary the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350. For example, spacer 339 can have a smaller Z-direction dimension than spacer 359. This can effectively change the coupling coefficient of the path between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate these coupling coefficient and impedance variations.

In some embodiments, a magnetic shield may be provided around one or more of the transmitter resonator 30 and the receiver resonator 50. For example, ferrite may be used as a magnetic shield and to reduce unwanted eddy currents in nearby metal objects. Ferrite (or another suitable material) may also be used to isolate the transmitter resonator 30 and/or the receiver resonator 50 from surrounding metal objects and may therefore be used to increase the self-inductance of the antenna and/or the mutual inductance of the resonators.

6 depicts a schematic diagram of the primary side 12 including the emitter module 20 and the emitter resonator 30 according to some embodiments. The emitter resonator 30 may include any of the emitter resonators 30, 130, 230, 330, or other emitter resonators described herein.

The transmitter module 20 includes a controller 22. The controller 22 is configured to receive various inputs from sensors 24 (e.g., load detector 24A, transmitter power sensor 24B, surrounding object detector 24C and/or distance detector 24D) and output control signals to various components 26 (e.g., oscillator 26A, power amplifier 26B, filter network 26C, matching network 26D, compensation network 26E and V/I tuner 26F).

The load detector 24A is configured to detect the presence of a load 70 (shown in FIG. 7 ) connected to the secondary side 14. For example, the load 70 may be a battery for an electric vehicle (such as an electric bicycle or electric car), or any other suitable item requiring power input. The load detector 24A may be implemented with a physical sensor (such as, without limitation, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor) and suitable software or firmware. For example, in some embodiments, power (e.g., current and voltage) at, for example, point 24E is measured to determine the power drawn by the transmitter resonator 30 (e.g., as measured by the transmitter power sensor 24B). If the amount of power drawn by the transmitter resonator 30 increases above the baseline, the load detector 24A may signal the controller 22 that a load 70 is present.

In other embodiments, the load detector 24A may be configured to measure the input impedance of the transmitter resonator 30 as experienced by the transmitter module 20 at point 24E. The presence of a resonant load in proximity to the transmitter resonator 30 (including, for example, the secondary side 14 configured to drive the load 70) will change the input impedance of the transmitter resonator 30. This change in impedance provided by the load detector 24A to the controller 22 may be used by the transmitter controller 22 to determine whether a cooperating receiver is in proximity to the transmitter resonator 30. The impedance changes induced in the transmitter resonator 30 by different receivers are different and characteristic, making it possible for the controller 22 to not only detect the presence or absence of a receiver in proximity to the transmitter resonator 30, but also to identify the type of receiver, such as, for example, different models of mobile phones or digital tablet computers, including without limitation.

The transmitter power sensor 24B can measure the power at point 24E (e.g., measure current and voltage) to determine how much power is being drawn by the transmitter resonator 30. This information can be used by the load detector 24A to determine whether there is a desirably efficient coupling between the transmitter resonator 30 and the receiver resonator 50, for example.

The surrounding object detector (SOD) 24C is configured to determine whether an object (e.g., a living being such as a person or animal, or such as a piece of metal or other static object) is in proximity to the transmitter resonator 30. The SOD 24C may be implemented with a physical sensor (e.g., without limitation, an optical sensor, a pressure sensor, an infrared sensor, a proximity sensor, a radar, or a lidar) or with the aid of suitable software or firmware. For example, if the power drawn by the transmitter resonator 30 (as measured by the transmitter power sensor 24B) drops during the IPT period, the software of the SOD may determine that a piece of metal (or any electrical conductor) is in proximity to the transmitter resonator 30 or the receiver resonator 50, and the SOD may provide a signal to the controller 22 indicating such presence. In some embodiments, the controller 22 may cause the transmitter module 20 to increase the proportion of power delivered by the CPT if a metal object is detected in proximity to the transmitter resonator 30 or the receiver resonator 50. In the event that the absence of a living being is detected by the SOD 24C, the controller 22 may be configured to increase the power feed to the transmitter resonator 30 (e.g., above the regulated level in the presence of a living being), or in the event that the proximity of a living being is detected by the SOD 24C, the controller 22 may be configured to reduce the power feed to the transmitter resonator 30 below the regulated level.

The distance detector 24D is configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50. The distance detector 24D may be implemented with a physical sensor (such as, without limitation, an optical sensor, an ultrasonic sensor, an infrared sensor, a proximity sensor, a radar, or a lidar) or by suitable software or firmware. For example, the distance detector 24D may be configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50 based on changes in the transmission power measured by the transmitter power sensor 24B.

In one embodiment, one or more temperature sensors may monitor the temperature at the transmitter resonator 30 or the receiver resonator 50. If the temperature exceeds a predetermined limit, the controller 22 may cause the transmitter module 20 to reduce the proportion of power delivered by the IPT, reduce the total power feed to the transmitter resonator 30, or shut down power to the transmitter resonator 30 to prevent a fire hazard or thermal runaway.

The oscillator 26A may be configured to control the frequency band and/or bandwidth and/or duty cycle (phase) (eg, 5% to 50%) of the current delivered to the transmitter resonator 30 in response to the signal from the controller 22 .

The power amplifier 26B may be employed to convert the DC power to AC power. The power amplifier 26B may be employed to adjust the power provided to the transmitter resonator 30 in response to a signal from the controller 22. In some embodiments, the controller 22 may send a signal to the power amplifier 26B to adjust the reflection coefficient of the power amplifier 26B. In some embodiments, the controller 22 may send a signal to the power amplifier 26B to turn off (or sleep) when the load detector 24A does not detect a load, or send a signal to turn on when the load detector 24A detects a load.

The power amplifier 26B may include a switching mode power amplifier (in a single-ended mode or differential configuration) that may be configured to receive a square wave (sine wave) from the self-oscillator 26A and generate a sine wave of a specific frequency desired to drive the transmitter resonator 30. FIG8 is a schematic diagram of an exemplary power amplifier 26B that can be used in the transmitter 30. The power amplifier 26B may be a differential switching mode amplifier. The power amplifier 26B has three inputs, namely: two input signals that drive the active devices (transistors) 127C, 127D at a frequency set at the resonant frequency and a DC voltage source 127E for controlling the output power and operating region of the active devices.

Different load terminals are used to improve performance (e.g., output power, power conversion efficiency) and reduce unnecessary harmonic levels. In some embodiments, the third harmonic terminal 127F is located in the series branch to shape the voltage waveform at the drain node 127G. The second harmonic terminal 127H is located in the parallel branch to shape the voltage waveform at the drain node 127G. The first harmonic terminal 127I is located in the series branch to shape the voltage waveform at the drain node 127G. The impact of the third harmonic terminal can be considered in the second harmonic terminal 127H and the first harmonic terminal 127I. The impact of the second harmonic terminal 127H can be considered in the first harmonic terminal 127I. For the differential configuration of the power amplifier 26B, the AC load 127J (which receives the output power) is placed in series. The charging rate of the AC load 127J can be a function of the alignment and position of the transmitter resonator 30, the receiver resonator 50, and/or the like. The power amplifier 26B can be configured to generate sufficient power for the transmitter resonator 30 so that an E field, or an H field, or any combination of E and H fields can be generated by the transmitter resonator 30 and captured by the receiver resonator 50.

The power amplifier 26B may include two phase shifters 127L in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifter 127L adjusts the appropriate phase difference between the AC signal overload 127J and the gate signal of the transistors 127C, 127D. The phase difference between the gate signal and the AC signal overload 127J can change the performance of the power amplifier, for example, the power conversion efficiency and operating region of the transistor. It can also change the output impedance of the transistors 127C and 127D and/or the optimal AC load 127J of the power amplifier 26B.

The power amplifier 26B may include two level shifters 127K in a differential configuration (but only one level shifter in a single-ended configuration). The level shifter 127K may adjust the appropriate amplitude of the gate signal of the transistors 127C, 127D. The amplitude level at the gate signal may change the performance of the amplifier (e.g., the power conversion efficiency and operating region of the transistor).

The power amplifier 26B may be reconfigurable to function as a rectifier, and in some embodiments as a self-synchronous rectifier. As part of this reconfiguration, the integrated phase shifter 127L and the integrated level shifter 127K (see FIG. 8 ) may be adjusted based on the inherent amplification and switching functions of the transistors 127C, 127D to allow the power amplifier 26B to function as a rectifier. This reconfigurability of the power amplifier 26B between operating as an amplifier and operating as a rectifier allows the transmitter module 20 to be controllably reconfigured between a transmitter mode and a receiver mode, respectively. The reconfiguration may occur under instructions from the controller 22. When the power amplifier 26B reconfigures from an amplifier to a rectifier, the AC load 127J changes to an AC source 127J. Accordingly, when the power amplifier 26B self-amplifier reconfigures as a rectifier, the DC source 127E reconfigures as a DC load. After explaining the secondary side 14 and its receiver module (both of which are shown in more detail in Figure 7), the application of the transmitter module 20 in its receiver mode will be discussed below.

The filter network 26C can adjust the frequency response, such as bandwidth, cutoff frequency, 3dB frequency, and gain provided to the transmitter resonator 30 in response to the signal from the controller 22. The filter network 26C can be configured to adjust the waveform shape of the power in the transmitter module 20 to increase the efficiency of the transmitter module 2.

Matching network 26D may be configured to adjust impedance to match the output of power amplifier 26B to transmitter resonator 30.

A compensation network 26E may be provided to drive the transmitter resonator 30 at a desired resonant frequency (e.g., the resonant frequency of the receiver resonator) to increase mutual flux, reduce heat generation, and improve power transfer efficiency. The compensation network 26E may include one or more capacitors for increasing capacitance and one or more inductors for increasing inductance. The compensation network 26E may be configured to increase capacitance (and/or decrease inductance) and increase inductance (and/or decrease capacitance) as desired. When the transmit mode ratio is 100% CPT, the compensation network 26E may function in a manner similar to any known CPT compensation network (e.g., the compensation network 26E may function to increase inductance). Similarly, when the transmission mode ratio is 100% IPT, the compensation network 26E may function in a manner similar to any known IPT compensation network (e.g., the compensation network 26E may function to increase capacitance). However, when the transmission mode is partial CPT and partial IPT, less compensation may be required because the capacitance of the transmitter resonator 30 will naturally provide compensation for the inductance of the transmitter resonator 30 and the inductance of the transmitter resonator 30 will naturally provide compensation for the capacitance of the transmitter resonator 30. For example, at approximately 50% IPT and 50% CPT (e.g., the transmission mode ratio is equal to 1), the compensation network may not be required at all or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10.

As another example, between approximately 40% to 60% IPT and 40% to 60% CPT, a compensation network may not be needed at all or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10. For this reason, the compensation network 26E may include fewer or smaller inductors and/or capacitors than a CPT WPT system and/or a pure IPT WPT system that requires significant compensation. In some embodiments, if the capacitance of the transmitter resonator 30 is significantly low, additional compensation may be provided by means of the compensation network 26E. Similarly, if the inductance of the transmitter resonator 30 is significantly low, additional compensation may be provided by means of the compensation network 26E. For example, the controller 22 may send a signal to the compensation network 26E regarding how much and what type of compensation is needed based on the transmit mode ratio, the distance between the transmitter resonator 30 and the receiver resonator 50, the amount of power drawn by the transmitter resonator 30, the power transmission efficiency, etc.

In certain embodiments, the amount of compensation (e.g., capacitance increase or inductance increase) performed by the compensation network 26E is proportional to the absolute value of the difference between the transfer mode ratio and 1. For example, if the transfer mode ratio is greater than 1, the compensation network 26E may act to increase the inductance, and the amount of increase in inductance may increase as the transfer mode ratio increases above 1. Similarly, if the transfer mode ratio is less than 1, the compensation network 26E may act to increase the capacitance, and the amount of increase in capacitance may increase as the transfer mode ratio decreases below 1.

In some embodiments, the compensation network 26E can be configured to modulate the signal provided to the transmitter resonator 30 with information and thereby can act as a source transfer modulator. The information used to modulate the signal provided to the transmitter resonator 30 can be provided to the compensation network 26E by the controller 22. The information can include control data that goes to the controller 42 of the receiver module 40 via the receiver resonator 50. The controller 42 is explained in more detail below with reference to Figure 7. In other embodiments, the power amplifier 26B can act as a source transfer modulator. In a further embodiment, the oscillator 26A can act as a source transfer modulator. The modulation employed by the selected source transfer modulator can be any of amplitude modulation, frequency modulation, and phase modulation. The information can be modulated onto the signal provided to the transmitter resonator 30 in digital form or in analog form. The information may be modulated by the source transfer modulator onto the resonant frequency of the power signal provided to the transmitter resonator 30. In other embodiments, the information may be modulated onto a frequency different from the frequency of the power transfer. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 30. In still further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 30 may be a harmonic of the frequency of the signal onto which the information is modulated. The V/I tuner 26F, described in more detail below, may be configured to transmit an information signal to the transmitter resonator 30 and thereby be transparent to the information being transmitted. The information transmitted in the manner described herein may include, without limitation, the operating mode of module 20, the number and type of receiver modules 40, surrounding object sensor information, and load status monitoring information including, for example, battery charge status, load voltage, and load current.

An embodiment of the V/I tuner 26F is shown in more detail in FIG. 10. The input signal of the V/I tuner 26F received from the matching network 26E (in FIG. 6) is split by a splitter 262 so as to have two mutually asymmetric paths 261A and 261B for the input signal. A first phase shifter 264A and a second phase shifter 264B form a phase difference between the input voltage and the input current of the transmitter resonator 30 (in FIG. 6). The first phase shifter 264A is controlled by the controller 22 (in FIG. 6) via a first phase splitter control line 263A, and the second phase shifter 264B is controlled by the controller 22 (see FIG. 6) via a second phase splitter control line 263B. The first active switch 266A and the second active switch 266B receive signals from the first phase shifter 264A and the second phase shifter 264B, respectively, and are controlled by the controller 22 via the first active switch control line 265A and the second active switch control line 265B, respectively. The first active switch 266A and the second active switch 266B are used to adjust the virtual part of the signal received from the first phase shifter 264A and the second phase shifter 264B, respectively. The passive signal shaping networks 268A and 268B receive the adjusted signals from the first active switch 266A and the second active switch 266B, respectively. Passive signal shaping networks 268A and 268B are used to fine tune the signals received from the first active switch 266A and the second active switch 266B, respectively, and in certain embodiments, to reduce any harmonics in those signals before passing them to the combiner 269. The signals provided along the two mutually asymmetric paths 261A and 261B are combined by the combiner 269 and provided to the transmitter resonator 30. In other embodiments, the first phase shifter 264A and the second phase shifter 264B may be combined into one phase shifter that receives the input signal to the V/I tuner 26F, and the combined phase shifter may have two separate outputs that serve the active switches 266A and 266B.

The V/I tuner 26F adjusts the transmit mode ratio by adjusting the phase difference between the input current and the input voltage to the transmitter resonator 30 in response to a signal from the controller 22. The real part of the impedance seen by the transmitter module 20 is adjusted by means of phase shifters 264A and 264B, and the imaginary part can be adjusted by switches 266A and 266B. For example, a 90 degree phase shift every 3 milliseconds out of every 10 milliseconds can result in 30% magnetic transmission and 70% electric transmission.

The V/I tuner 26F can be configured to adjust the current passing through each transmitter antenna (e.g., the first transmitter antenna 32, 132, 232, 332 and the second transmitter antenna 134, 234, 334 or the third transmitter antenna 336) and the potential applied to each transmitter antenna (e.g., the first transmitter antenna 32, 132, 232, 332 and the second transmitter antenna 134, 234, 334 or the third transmitter antenna 336).

If current is caused to pass through both the first transmitter antenna 132 and the second transmitter antenna 134, the transmitter antennas will each generate a magnetic field 31A for the purpose of IPT. If the current delivered to the second transmitter antenna 134 is reduced compared to the current delivered to the first transmitter antenna 132, a potential difference will be generated between the first transmitter antenna 132 and the second transmitter antenna 134 for the purpose of CPT and an electric field 31B will be generated. In order to modulate between CPT and IPT, the current delivered to the second antenna 134 can be modulated (e.g., when less current is allowed to pass through the second antenna 134, less IPT will occur, and when more current is allowed to pass through the second antenna, more CPT will occur). For example, when it is desired to transmit power via the IPT, the I/V tuner 26F can be configured to act as a short circuit connecting the first transmitter antenna and the second transmitter antenna together to thereby form a series LC resonator that allows current to flow therein. Conversely, when it is desired to transmit power via the CPT, the I/V tuner 26F can be configured to act as an open circuit that dumps current, thereby creating a potential difference between the first transmitter antenna and the second transmitter antenna. The I/V tuner 26F can thereby be configured to control whether the first transmitter antenna 132 and the second transmitter antenna 134 are effectively connected in series or in parallel.

Alternatively, when the first transmitter antenna 132 and the second transmitter antenna 134 are connected in parallel, the first transmitter antenna 132 and the second transmitter antenna 134 may be floating to cause the electric field 31B to be generated for the purpose of CPT without substantially generating the magnetic field 31A. To change the transmit mode ratio (e.g., to modulate between CPT and IPT), the I/V tuner 26F may be configured (via a multiplexer of the I/V tuner 26F, etc.) to alternate between: (1) floating the first transmitter antenna 132 and the second transmitter antenna 134 to cause CPT; and (2) driving current through the first transmitter antenna 132 and the second transmitter antenna 134 to cause IPT. The alternation may be performed in milliseconds or at a frequency between 10 Hz and 10 kHz. As more time is allocated to floating the first transmitter antenna 132 and the second transmitter antenna 134, the transmit mode ratio will be biased toward achieving more CPT, and as more time is allocated to driving current through the first transmitter antenna 132 and the second transmitter antenna 134, the transmit mode will be biased toward achieving more IPT.

In some embodiments, components 26 may be discrete components in transmitter module 20, while in other embodiments, one or more of components 26 may be part of an integrated circuit design.

FIG. 7 is a schematic depiction of a load 70 and the secondary side 14 (as shown in FIG. 1 ) including the receiver resonator 50 and the receiver module 40 according to certain embodiments.

The receiver resonator 50 may include any of the receiver resonators 50, 150, 250, 350, or other receiver resonators described herein. The receiver resonator 50 may be configured to capture power at a frequency set by an oscillating signal in the transmitter module 20 (e.g., without limitation, such as between 1 MHz and 1 GHz). In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is about 1 MHz to about 100 MHz, about 1 MHz to about 200 MHz, about 1 MHz to about 300 MHz, about 1 MHz to about 400 MHz, about 1 MHz to about 500 MHz, about 1 MHz to about 600 MHz, about 1 MHz to about 700 MHz, about 1 MHz to about 800 MHz, about 1 MHz to about 900 MHz, about 1 MHz to about 1 GHz, about 100 MHz to about 200 MHz, about 100 MHz to about 300 MHz, about 100 MHz to about 400 MHz, about 100 MHz to about 500 MHz, about 100 MHz to about 600 MHz, about 100 MHz to about 700 MHz, about 100 MHz to about 800 MHz, about 1 MHz to about 900 MHz, about 1 MHz to about 1 GHz, about 100 MHz to about 200 MHz, about 100 MHz to about 300 MHz, about 100 MHz to about 400 MHz, about 100 MHz to about 500 MHz, about 100 MHz to about 600 MHz, about 100 MHz to about 700 MHz, about 100 MHz to about 800 MHz, about 100 MHz to about 900 MHz, about 100 MHz to about 1 GHz, about 200 MHz to about 300 MHz, about 200 MHz to about 400 MHz, about 200 MHz to about 500 MHz, about 200 MHz to about 600 MHz, about 200 MHz to about 700 MHz, about 200 MHz to about 800 MHz, about 200 MHz to about 900 MHz, about 200 MHz to about 1 GHz, about 300 MHz to about 400 MHz, about 300 MHz to about 500 MHz, about 300 MHz to about 600 MHz, about 300 MHz to about 700 MHz, about 300 MHz to about 800 MHz, about 300 MHz to about 900 MHz, about 300 MHz to about 1 GHz, about 400 MHz to about 500 MHz, about 400 MHz to about MHz to about 600 MHz, about 400 MHz to about 700 MHz, about 400 MHz to about 800 MHz, about 400 MHz to about 900 MHz, about 400 MHz to about 1 GHz, about 500 MHz to about 600 MHz, about 500 MHz to about 700 MHz, about 500 MHz to about 800 MHz, about 500 MHz to about 900 MHz, about 500 MHz to about 1 GHz, about 600 MHz to about 700 MHz, about 600 MHz to about 800 MHz, about 600 MHz to about 900 MHz, about 600 MHz to about 1 GHz, about 700 MHz to about 800 MHz, about 700 MHz to about 900 MHz, about 700 MHz to about 1 GHz, about 800 MHz to about 900 MHz, about 800 MHz to about 1 GHz, or about 900 MHz to about 1 GHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at least about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, or about 900 MHz. In some embodiments, in some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at most about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz.

For some applications, frequencies in the Industrial, Scientific, and Medical (ISM) band may be preferred. For the purposes of this invention, the ISM band is understood to be 6.765 MHz to 6.795 MHz; 13.553 MHz to 13.567 MHz; 26.957 MHz to 27.283 MHz; 40.66 MHz to 40.70 MHz; 83.996 MHz to 84.004 MHz; 167.992 MHz to 168.008 MHz; 433.05 MHz to 434.79 MHz; and 886 MHz to 906 MHz. For other applications, frequencies in officially reserved application bands may be preferred, such as, without limitation, police communications or military bands. The receiver resonator 50 may be configured to capture electricity at that frequency from either the magnetic field 31A or the electric field 31B or any combination of the two fields.

The receiver module 40 includes a controller 42. The controller 42 is configured to receive various inputs from sensors 44 (e.g., receiver power sensor 44A and load detector 44B) and output control signals to various components 46 (e.g., compensation network 46A, matching network 46B, rectifier 46D, filter 46C, and load manager 46E).

The receiver power sensor 44A may measure the power at point 44C (eg, measure current and voltage) to determine how much power the receiver resonator 50 is receiving.

The load detector 44B is configured to detect the presence of the load 70. The load detector 44B may be implemented with a physical sensor (e.g., without limitation, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor) or with the aid of suitable software or firmware. For example, in some embodiments, the current and voltage at, for example, point 44D are measured by the load detector 44B to determine the power received by the load 70. If the amount of power measured at point 44D increases above a baseline, the load detector 44B signals the controller 42 that the load 70 is present.

The compensation network 46A may be configured to maintain a desired resonant frequency of the receiver resonator 50 in response to signals from the controller 42 to improve the efficiency of power transfer from the transmitter resonator 30 to the receiver resonator 50. The compensation network 46A may be similar to the compensation network 26E of the transmitter module 20 and may function substantially the same as the compensation network 26E of the transmitter module 20.

The matching network 26D may be configured to adjust the input impedance of the rectifier 46D to match the desired impedance of the transmitter resonator 30 to achieve maximum power transfer.

The rectifier 46D may be configured to convert AC power received by the receiver antenna 50 into DC power to be provided to the load 70.

Filter 46C can be configured to shape the waveform of the power output from rectifier 46D based on a signal from controller 42 so as to improve the overall power efficiency of receiver module 40.

Load manager 46E may be configured to provide appropriate voltage and current to load 70 and/or extract maximum power from rectifier 46D by adjusting its input impedance (eg, output impedance of rectifier 46D).

In some embodiments, the load manager 46E or another component may be configured to communicate (wirelessly or wired) with an external device (e.g., the load 70) to provide appropriate information for data analysis. For example, without limitation, this information may include: the presence of the load 70, the charge level of the load 70, the charge rate of the load 70, the state of the load 70, the current voltage, capacity, and/or the remaining time to charge the load 70. The load manager 46E may use this information (or relay this information to the controller 42 or controller 22) to adjust, for example, the transfer mode ratio to achieve optimal energy transfer between the primary side 12 and the secondary side 14. The load manager 46E may also provide this information to the user via a display. The display may be built into one or more of the primary side 12 and the secondary side 14 or may be accessed via software on a mobile device (e.g., an application on a mobile phone or tablet computer that communicates wirelessly (or wiredly) with the load manager 46E or the controller 22 or the controller 42).

In some embodiments, components 46 are discrete components in receiver module 40, while in other embodiments, one or more of components 46 are part of an integrated circuit design.

In some embodiments, the primary side 12 may include a plurality of transmitter resonators 30, and/or the secondary side 14 may include a plurality of receiver resonators 50. In such embodiments, each of the transmitter resonators 30 and/or the receiver resonators 50 may be controlled in a similar manner. In other embodiments, each of the transmitter resonators 30 and/or the receiver resonators 50 may be controlled individually. For example, in some embodiments, the primary side 12 may rely more heavily on transmitter resonators 30 that experience less interference (e.g., due to nearby metal objects), are not near a living being, or transmit power more efficiently and/or similarly, and the secondary side 14 may rely more heavily on receiver resonators 50 that experience less interference (e.g., due to nearby metal objects), are not near a living being, or receive power more efficiently. For example, such control may be provided or facilitated by the transmitter module 20 and the receiver module 40 and/or communications therebetween.

9 is a schematic depiction of a rectifier 46D having an integrated phase shifter. In some embodiments, the rectifier 46D includes a discrete phase shifter.

The rectifier 46D can be a switching mode self-synchronous rectifier (in single-ended mode or differential configuration) that can be configured to receive a sine wave (e.g., AC power) from the receiver resonator 50 at a specific resonant frequency. The rectifier 46D can be a differential switching mode self-synchronous rectifier. The rectifier 46D can capture enough power from the receiver resonator 50 so that the E field, or the H field, or any combination of the E field and the H field can be captured by the receiver resonator 50.

Rectifier 46D has an input 147A (e.g., AC power) that drives an active device 147B (e.g., a transistor) with a frequency set at the resonant frequency and has an output 147D (e.g., DC voltage) across a DC load (used to control the output power, input impedance, and operating region of the active device). In this design, different load terminals are used to improve performance (e.g., output power and power conversion efficiency). A third harmonic terminal 147D is located in the series branch to shape the voltage waveform at the drain node 147E. A second harmonic terminal 147F is located in the parallel branch to shape the voltage waveform at the drain node 147E. The first harmonic terminal 147G is located in the series branch to shape the voltage waveform at the drain node 147E. The influence of the third harmonic terminal 147D can be considered in the second harmonic terminal 147F and the first harmonic terminal 147G. The influence of the second harmonic terminal 147F can be considered in the first harmonic terminal 147G.

For a differential configuration, the AC source 147A is placed in series. The AC source 147A may be a function of the power received by the receiver resonator 50 and the alignment and position of the receiver resonator 50 relative to the transmitter resonator 30. The DC load 147C may be a single-ended load.

The rectifier 46D may include two phase shifters 147H in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifter 147H adjusts the appropriate phase difference between the AC source and the gate signal of the transistor 147B. The phase difference between the gate signal and the AC source 147A may change the performance of the self-synchronous rectifier (e.g., the power conversion efficiency and operating region of the transistor). It may also change the input impedance of the self-synchronous rectifier 46D and/or the optimal DC load 147C of the rectifier 46D.

Rectifier 46D may include two level shifters 147I in a differential configuration (but only one level shifter in a single-ended configuration). Level shifter 147I may adjust the appropriate amplitude of the gate signal of transistor 147B. The amplitude level at the gate signal may change the performance of the self-synchronous rectifier (e.g., the power conversion efficiency and operating region of the transistor).

The rectifier 46D can be reconfigurable to function as an amplifier. As part of this reconfiguration, the integrated phase shifter 147H and the integrated level shifter 147I (see FIG. 9 ) can be adjusted to allow the rectifier 46D to function as an amplifier based on the inherent amplification and switching functions of the transistor 147B. This reconfigurability of the rectifier 46D between operating as a rectifier and operating as an amplifier allows the receiver module 40 to be controllably reconfigured between a receiver mode and a transmitter mode, respectively. The reconfiguration can occur under instructions from the controller 42. When the rectifier 46D is reconfigured from the rectifier to an amplifier, the AC source 147A changes to the AC load 147A. Correspondingly, when the rectifier 46D is reconfigured from the rectifier to an amplifier, the DC load 147C is reconfigured to a DC source.

In some embodiments, when the receiver module 40 is in the transmitter mode, the compensation network 46A can be configured to modulate the signal provided to the resonator 50 with information and thereby act as a source transmission modulator. The information used to modulate the signal provided to the resonator 50 can be provided to the compensation network 46A by the controller 42. The information can include control data that is sent to the controller 22 of the transmitter module 20 via the transmitter resonator 30. In some embodiments, when the receiver module 40 is in the transmitter mode and the rectifier 46D is configured as an amplifier, the amplifier 46D can act as a modulator for the receiver module 40. The modulation used can be any of amplitude modulation, frequency modulation, phase modulation, and combinations thereof. The information can be modulated onto the signal provided to the transmitter resonator 50 in digital form or in analog form. The information may be modulated by the source transfer modulator onto the resonant frequency of the power signal provided to the transmitter resonator 50. In other embodiments, the information may be modulated onto a frequency different from the frequency of the power transfer. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 50. In yet further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 50 may be a harmonic of the frequency of the signal onto which the information is modulated. For example and without limitation, the information transmitted in the manner described herein may include: the presence of the load 70, the charge level of the load 70, the power transfer efficiency, the charge rate of the load 70, the state of the load 70, the current voltage, the charge capacity, and the remaining time to charge the load 70.

Having explained above how both the transmitter module 20 and the receiver module 40 can be reconfigured between operating in a transmitter mode and operating in a receiver mode, and having explained how the signals from both the transmitter module 20 and the receiver module 40 can be modulated, it is apparent that the system 10 of FIG. 1 can function as a full duplex transmit-receive system for transmitting information in both directions via the resonators 30 and 50. The system 10 of FIG. 1 can include additional secondary sides similar to the secondary side 14 of FIG. 1 and FIG. 7. When additional secondary sides are present, the configurations explained above allow information to be transmitted between the various secondary sides.

In some embodiments, the primary side 12 and the secondary side 14 may communicate via Bluetooth (e.g., 2.4 GHz) or a signal frequency similar to that of GPS (e.g., 10 GHz). In some embodiments, there may be an additional unit that detachably collects data and transmits data back and forth between the primary side 12 and/or the secondary side 14. In some embodiments, WiFi may be employed to upload data from the primary side 12 and/or the secondary side 14 to an online portal (e.g., a website or mobile application associated with the primary side 12 and/or the secondary side 14).

In some embodiments, it may be desirable to transfer power between two receiver modules 40 (e.g., peer-to-peer power transfer). For example, if a first electric bicycle having a first receiver is dead or low on power and a second electric bicycle having a second receiver and an at least partially charged battery is nearby, it may be desirable to transfer power from the second electric bicycle to the first electric bicycle. Such a situation may involve when, for example, there is no transmitter nearby. The facility of reconfiguring at least one of the two receiver modules 40 involved as a transmitter module enables this peer-to-peer power transfer. In general, this enables the forwarding of power between a plurality of secondary sides 14.

In other embodiments, it may be desirable to transfer power in the reverse direction (i.e., from the load side to the source side of FIGS. 1 , 6 , and 7 ) at certain times. The ability of both transmitter module 20 and receiver module 40 to reconfigure between operating in transmitter mode and in receiver mode allows such power transfer from receiver module 40 to transmitter module 20 in the “reverse” direction. The system thus allows bidirectional power transfer. In view of the fact that device 26B of FIG. 8 and device 46D of FIG. 9 can be reconfigured to function as an amplifier or a rectifier, respectively, these devices may be collectively referred to as “differential self-synchronous RF power amplifier/rectifiers.” In view of the bidirectional nature of the power transfer, both the transmitter resonator 30 and the receiver resonator 50 may be described as "transmitter-receiver resonators" and both the transmitter module 20 and the receiver module 40 may be referred to as "power transmit-receive modules." Such configurations are useful in electric vehicles where kinetic energy is converted during braking and needs to be transferred to a battery. For example, without limitation, other systems, conditions, and arrangements in which such altered direction of power transfer is applicable include a number of mobile phones that may have different levels of remaining battery charge, and such an arrangement may be used to at least partially recharge another mobile phone. More generally, when neither the transmitting system nor the receiving system has a permanent energy source (such as a power grid), then the bidirectional functionality may be employed to transfer energy in either direction.

In another embodiment described with respect to FIG. 31 , a near-field RF method [2200] for transmitting power via a power signal at a power signal frequency is provided, the method comprising: providing [2210] a dual-peak resonant near-field RF power transfer system comprising a plurality of power transmit-receive modules, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator configured to exchange power with at least another transmit-receive module of the plurality of power transmit-receive modules; and operating the power transfer system according to an adjustable transfer mode ratio [2220] for simultaneous capacitive power transfer and inductive power transfer.

Providing [2210] a power transmission system may include providing a first power transmission-receiving module among a plurality of power transmission-receiving modules having a power signal tuner module, and operating [2220] the power transmission system may include changing a transmission mode ratio by adjusting the power signal tuner module.

Providing [2210] a power transmission system may include providing at least one power transmit-receive module among a plurality of power transmit-receive modules that is in wired communication with an associated transmitter-receiver resonator and has a modulator, and operating [2220] the power transmission system may include: exchanging radio frequency signals between the associated transmitter-receiver resonator and a transmitter-receiver resonator in wired communication with at least another power transmit-receive module among the plurality of power transmit-receive modules; and modulating information onto the exchanged radio frequency signals. When a power load is present at the output of one of a plurality of power transmit-receive modules, for example, without limitation, the information modulated on the exchanged signals may include: one or more of: the presence of the power load, the charge level of the power load, the power transfer efficiency, the charge rate of the power load, the state of the power load, the presence of a voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

The information may be modulated onto the exchanged RF signal by amplitude modulation, frequency modulation, or phase modulation. The information may be modulated onto the exchanged RF signal by modulating digital information or analog information onto the exchanged RF signal.

Modulating the information onto the exchanged radio frequency signal may include modulating the information onto the power signal. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

Modulating the information onto the exchanged RF signal may include modulating a reflective property of an associated wire-connected transmitter-receiver resonator according to the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. Modulating the information onto the exchanged RF signal may include modulating a signal provided to the associated transmitter-receiver resonator according to the information.

The method [2200] may include operating a power signal tuner module of a first power transmit-receive module of a plurality of power transmit-receive modules to modulate information onto an exchanged radio frequency signal. Each of the provided power transmit-receive modules may include a compensation network, and the compensation network may include a modulator, thereby allowing the compensation network to be operated to modulate information onto the exchanged radio frequency signal. At least one of the power transmit-receive modules may include an radio frequency oscillator that provides a signal to the at least one power transmit-receive module at a power signal frequency, and the radio frequency oscillator may include a modulator, thereby allowing information to be modulated into the oscillator onto the exchanged radio frequency signal.

Each of the plurality of power transmit-receive modules provided may be reconfigurable between a power transmitter mode and a power receiver mode; and the method may further include reconfiguring at least two of the plurality of power transmit-receive modules between the power transmitter mode and the power receiver mode to reverse the power transmission direction between the at least two transmit-receive modules. Each of the power transmit-receive modules provided may include a differential self-synchronous radio frequency power amplifier/rectifier capable of reconfiguring between amplifier states and rectifier states corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively; and the method may include reconfiguring the differential self-synchronous radio frequency power amplifier/rectifier of the at least two transmit-receive modules between the amplifier state and the rectifier state. Each differential self-synchronous RF power amplifier/rectifier may include a phase shifter that is adjustable for reconfiguring the differential self-synchronous RF power amplifier/rectifier between an amplifier state and a rectifier state; and the method may include adjusting the phase shifter of each of the differential self-synchronous RF power amplifier/rectifiers in the at least two transmit-receive modules.

The WPT system 10 including the transmitter and/or the receiver described herein can be integrated into various applications, such as but not limited to electric vehicles, electric boats, electric planes, electric trucks, electric bicycles, electric motorcycles, electric skateboards, etc. An exemplary non-limiting application is a shared bicycle fleet, in which various portable computers are provided that integrate one or more transmitters (e.g., primary side 12), and electric bicycles including receivers (e.g., secondary side 14) and batteries (as loads 70) can be charged at the portable computer.

In some applications, the primary side 12 or the secondary side 14 can be configured to transmit power using other systems not described herein, and the transmission mode can be adjusted from CPT to IPT to provide compatibility with other CPT systems and/or IPT systems, even if the other systems are not specifically designed to work with the power transmission system described herein.

Although several exemplary aspects and embodiments have been discussed above, those skilled in the art will recognize certain modifications, permutations, additions, and sub-combinations thereof. It is therefore intended that the following appended claims and hereafter incorporated claims be interpreted as including all such modifications, permutations, additions, and sub-combinations consistent with the broadest interpretation of this specification as a whole.

In a first aspect, each of the systems described above and depicted in FIGS. 1 to 10 forms a dual-peak near-field resonant wireless power transfer system 10 configured for simultaneous capacitive power transfer and inductive power transfer at a variable resonant power signal oscillation frequency according to an adjustable transfer mode ratio, the system 10 comprising: a transmitter subsystem 12 including a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 and a power signal tuner module 26F, a tuner module 26F 6F is configured to adjust the transmit mode ratio by adjusting the power signal provided by the tuner module 26F to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336; and the receiver subsystem 14 includes a receiver antenna subsystem 52, 152, 252, 352, 154, 254, 354, 356 configured to receive power from the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 according to the transmit mode ratio.

The tuner module 26F may be configured to adjust the power signal by adjusting the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336. The transmitter subsystem 12 may further include: a controller 22; and at least one sensor 24, wherein the controller 22 is configured to receive sensor information from the at least one sensor 24 and automatically provide a tuning instruction to the tuner module 26F based on the sensor information, and the tuner module 26F is configured to adjust the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 according to the tuning instruction.

The system 10 resonates at a resonant frequency that is freely variable within a predetermined frequency band based on the degree of coupling between the transmitter subsystem 12 and the receiver subsystem 14. For example, without limitation, the predetermined frequency band may be an officially designed and reserved Industrial, Scientific and Medical (ISM) band or a user-specific frequency band. The quality factor (Q) of the system 10 may be reduced to a degree that allows the power signal oscillation frequency to vary within the opposite extremes of the predetermined frequency band. The reduced Q value allows the system 10 to adopt any of a number of different resonant frequencies within the predetermined frequency band during the power transfer process. The coupling between the transmitter subsystem 12 and the receiver subsystem 14 and the associated power absorption of the resonant receiver subsystem 14 ensure that less electromagnetic radiation is emitted into the far field when the system 10 is in operation. The arrangement as described herein with reference to Figures 1-10, together with the frequency profiles immediately above, makes the system 10 a dual peak near field resonant wireless power transfer system. It should be noted that in the wireless power transfer system 10, power is transferred from the primary subsystem to the secondary subsystem via capacitive coupling or inductive coupling, or both, and not to any substantial extent via electromagnetic radiation.

In another embodiment described with reference to the aforementioned figures and the flowchart in FIG. 11 , a near-field wireless method [1000] for transmitting power bimodally at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio is provided, the method comprising: providing [1010] a transmitter subsystem 12 including a power signal tuner module 26F and a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 configured to resonate at the resonant power signal oscillation frequency; providing [1020] a receiver antenna subsystem 52, 152, 252, 352, 154, 254, 354, 356 configured to resonate at the resonant power signal oscillation frequency. a receiver subsystem 14; providing [1030] a power signal self-tuner module 26F to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at a power signal oscillation resonance frequency; adjusting [1040] the transmit mode ratio by adjusting the power signal from the self-tuner module 26F to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336; and receiving [1050] the transmitted power according to the transmit mode ratio at the power signal oscillation resonance frequency in the receiver subsystem 14 via the receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356. Adjusting [1040] the transmit mode ratio may include adjusting the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336.

Providing [1010] the transmitter subsystem 12 may further include providing a controller 22 and at least one sensor 24, and the phase difference between the current and the voltage may be adjusted by a tuner module 26F based on sensor information received by the controller 22 from the at least one sensor 24 via a command of the controller 22. The controller 22 may automatically issue a command of the controller 22 to the tuner module 26F when the controller 22 receives the sensor information; and the tuner module 26F may automatically execute the command from the controller 22 to change the phase difference.

The method [1000] may further include allowing [1060] the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific and medical (ISM) band. Providing [1010] the transmitter subsystem may include providing a transmitter subsystem that demodulates to an extent that allows the resonant power signal oscillation frequency to vary within opposite limits of the predetermined frequency band.

In yet another embodiment described with reference to FIGS. 12, 13A, and 13B and with reference to FIGS. 1 to 10, a multi-transmitter dual-peak near-field resonant wireless power transfer system 10' is configured for simultaneous capacitive power transfer and inductive power transfer at a variable resonant power signal oscillation frequency according to an adjustable transfer mode ratio. The system 10' includes a multi-transmitter subsystem 12', which includes a plurality of transmitter resonators 30A' to 30I' each driven by a corresponding dedicated transmitter module 20A' to 20I', wherein each transmitter resonator and corresponding transmitter module (e.g., 30E' and 20E', respectively) may be consistent with the description set forth above with reference to FIGS. 1 to 10. FIG. 12 is a schematic representation of an embodiment of the system 10′ in which the transmitter resonators 30A′ to 30I′ are presented as nine resonators in a row but are not depicted in their formalized spatial positions. An embodiment of a spatial layout of the multiple transmitter subsystem 12′ is shown in FIGS. 13A and 13B and described below. In the system 10′, the resonant receiver subsystem 14 can be the same as or substantially similar to the resonant receiver system described above and referenced by FIGS. 1 to 10. In the embodiment shown in FIG. 12, the resonant receiver subsystem 14 can be implemented in a mobile phone or a digital “tablet”, for example, without limitation. For clarity, the resonant receiver subsystem 14 is depicted in FIG. 13A with a broken outline. In an embodiment, each operating emitter resonator 30A'-30I' and each corresponding emitter module 20A'-20I' can function the same as or in a substantially similar manner to the emitter resonator 30 and emitter module 20 described above and shown in Figures 1-10. An embodiment of a spatial layout of a multi-emitter subsystem 12' is illustrated in Figures 13A and 13B. Figure 13B is a view of the multi-emitter subsystem 12' in an opposite orientation relative to its orientation in Figure 13A.

In the exemplary embodiment of the system 10' shown in Figures 12, 13A and 13B, the multi-emitter subsystem 12' includes nine pairs of emitter resonators 30A' to 30I' and corresponding emitter modules 20A' to 20I' arranged in a square array. The emitter modules 20A' to 20I' are obscured by the grounded substrate 35' in Figure 13A but can be seen in Figure 13B. In more general embodiments, other numbers of pairs of resonators and emitter modules may be employed, and the resonator arrays need not be square or rectangular. By way of example and not limitation, the resonator arrays may have a hexagonal arrangement. In certain embodiments, it is preferred that the arrays be tightly packed within the confines of a grounded shielding mesh that separates and defines the emitter resonators 30A' to 30I'. The ground shield mesh 33' laterally confines the array of transmitter resonators 30A' to 30I'. The ground shield mesh 33' is disposed at a consistent distance 37' from the periphery of each of the transmitter resonators 30A' to 30I' to ensure consistent electric field behavior and associated capacitance between the transmitter resonators 30A' to 30I' and the ground shield mesh 33'. The term "shielding distance" is used herein to describe this distance between the transmitter resonators 30A' to 30I' and the ground shield mesh 33'.

In one embodiment, the ground shield mesh 33' ensures that the electric fields of the emitter resonators 30A' to 30I' will be completely spatially decoupled and thereby spatially independent. The emitter resonators 30A' to 30I' may have magnetic fields selected to be decoupled from each other by virtue of spatial positioning. In other embodiments, the ground shield mesh 33' may be formed of or coated with a highly conductive ferrite material in order to decouple the magnetic fields generated by the emitter resonators 30A' to 30I'.

As shown in FIGS. 13A and 13B , the emitter resonators 30A′ to 30I′ and their corresponding emitter modules 20A′ to 20I′ may be mounted substantially in a row with one another on opposite sides of a ground substrate 35′, wherein each emitter resonator (e.g., 30E′) is proximate to its corresponding emitter module (20E′). In other embodiments, there may be no fixed spatial relationship between the emitter resonators and their corresponding emitter modules. The array of emitter resonators 30A′ to 30I′ shares a common emitting surface defined by the collective upper surface of the emitter resonators 30A′ to 30I′ in FIG. 13A . For aesthetic and protective reasons, the array of emitter resonators 30A′ to 30I′ may be covered with a dielectric plate, not shown in FIG. 13A . A dielectric plate separates the receiver subsystem 14 from the transmitter resonators 30A' through 30I'.

In Figures 12 and 13A, an embodiment of a resonant receiver subsystem 14 is schematically shown as being overlaid with a subset of the plurality of transmitter resonators 30A' to 30I'. The overlaid transmitter resonators are shown as 30D', 30E', 30G', and 30H' according to Figures 12 and 13A. In Figure 13A, the resonant receiver subsystem 14 is shown as a dotted rectangle on the mutually adjacent transmitter resonators 30D', 30E', 30G', and 30H'. The controller of any of the transmitter modules 20A′ to 20I′ can determine the presence or absence of a resonant receiver subsystem 14 that is proximate to or overlaps with its corresponding transmitter resonator 30A′ to 30I′, and based on such detection, the controller can turn on or off the power signal to its corresponding transmitter resonator 30A′ to 30I′.

If the power amplifiers of transmitter modules 20A′ to 20I′ supply power signals to transmitter resonators 30A′ to 30I′ so that transmitter resonators 30A′ to 30I′ transmit power, and the controllers of transmitter modules 20A′, 20B′, 20C′, 20F′ and 20I′ determine that there are no resonant receivers close to transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′ within their frequency ranges, then their controllers may shut off the power signals to transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′.

If the power amplifiers of the transmitter modules 20A' to 20I' do not supply power signals to the transmitter resonators 30A' to 30I', the controllers for the transmitter resonators 30D', 30E', 30G', and 30H' can determine the presence of the resonant receiver subsystem 14 overlapping with and close to the resonators 30D', 30E', 30G', and 30H', and turn on the transmittable power provided by the transmitter modules 20D', 20E', 20G', and 20H' to the transmitter resonators 30D', 30E', 30G', and 30H'. This configuration ensures that only the transmitter resonators close to the resonant receiver subsystem 14 are drawing power and transmitting power to the resonant receiver subsystem 14.

The input impedance of the transmitter resonator 30A′ to 30I′ can be used to detect the presence or absence of a resonant receiver subsystem 14 in proximity to the transmitter resonator. The transmitter resonator input impedance varies with the presence or absence of a resonant receiver subsystem 14 in proximity to the transmitter resonator. As described above, with reference to FIG. 6 , the effect of a particular resonant receiver subsystem 14 is different so as to allow not only the presence and absence of a receiver to be detected, but also to detect characteristics such that the type of receiver can be identified by its effect on the transmitter resonator input impedance. In certain embodiments, the size of the receiver resonator has a significant effect on the input impedance of the transmitter resonator 30A′ to 30I′.

In an embodiment of the system 10′, the transmitter module 20E′ as shown in FIG. 12 and FIG. 13B is a transmitter module associated with one of the four transmitter resonators 30D′, 30E′, 30G′, and 30H′ overlapped by the resonant receiver subsystem 14. The detailed structure of each of the transmitter modules 20A′ to 20I′ is provided in FIG. 6 and FIG. 8. The process is started when the power amplifier 26B of the transmitter module 20A′ to 20I′ does not provide a power signal to the corresponding transmitter resonator 30A′ to 30I′.

Focusing now on the transmitter module 20E′, in this embodiment, its load detector 24A is configured to measure the input impedance of the transmitter resonator 30E′. The load detector 24A provides the input impedance measurement result to the controller 22. A default input impedance measurement value is stored in a register in the controller 22, which default input impedance measurement value represents the input impedance of the transmitter resonator 30E′ in the absence of any resonant receiver subsystem in proximity to the transmitter resonator 30E′. As shown in Figure 12, placing the resonant receiver subsystem 14 in proximity to the transmitter resonator 30E′ results in a new and different input impedance measurement being made by the load detector 24A, the results of which are provided to the controller 22 by the load detector 24A. The controller 22 compares the new input impedance measurement (referred to herein as the "first input transmitter resonator impedance change" or "primary transmitter resonator input impedance change") to a preset impedance measurement value stored in a register. Based on this first input impedance change, the controller 22 makes a determination as to whether a receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) is present proximate to the transmitter resonator 30E'. To make the determination as to the presence or absence of a receiver resonator proximate to the transmitter resonator 30E', the controller 22 may be pre-programmed with a minimum input impedance change that must be exceeded before the controller 22 deems a receiver resonator present.

If the controller 22 determines that there is a receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) proximate to the transmitter resonator 30E′, the controller 22 instructs the power amplifier to assume an “on” state. Power is thereby provided to the transmitter resonator 30E′ and, in turn, transfers power to the resonant receiver subsystem 14. If the controller 22 determines that there is no receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) proximate to the transmitter resonator 30E′, the controller 22 instructs the power amplifier to assume an “off” state. Power is thereby not provided to the transmitter resonator 30E′ and, in turn, not transfers power to the resonant receiver subsystem 14. The same procedure is performed independently by each transmitter module 20A′ to 20I′ with respect to its corresponding transmitter resonator 30A′ to 30I′. Therefore, the power amplifiers of the transmitter resonators 30D′, 30E′, 30G′ and 30H′ overlapped by the resonant receiver subsystem 14 are turned on and the power amplifiers of the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′ not overlapped by the resonant receiver subsystem 14 are turned off.

It should be noted that receiver resonators of different sizes present significantly different impedances at point 24A to the load detector 24A of the transmitter module 20. The impedance difference measured when a given receiver resonator partially overlaps a transmitter resonator compared to when it completely overlaps the transmitter resonator is not as significantly different as the impedance with different receiver resonator sizes. This allows the controller 22 of any transmitter module 20A′ to 20I′ to distinguish between a small receiver resonator and a large receiver resonator that is close to the corresponding transmitter resonator 30A′ to 30I′.

According to one embodiment, it is described herein that power signal frequency and phase are set between those transmitter resonators (e.g., 30D′, 30E′, 30G′, and 30H′) that are overlapped by a resonant receiver subsystem (e.g., resonant receiver subsystem 14). In order to maximize the efficiency of transferring power from the combination of transmitter resonators 30D′, 30E′, 30G′, and 30H′ that are receiving power, the power signals in the transmitter resonators 30D′, 30E′, 30G′, and 30H′ need to have the same frequency and also be in phase with each other. The frequencies of the power signals in a given transmitter resonator 30D′, 30E′, 30G′ and 30H′ may be different within an allowed frequency band, as previously described above and with reference to FIGS. 1 to 10 , the requirement in this current embodiment of FIGS. 12 , 13A and 13B is for the frequencies of the power signals in the transmitter resonators 30D′, 30E′, 30G′ and 30H′ to be the same and then for their phases to be locked together so that the power signals from the transmitter resonators 30D′, 30E′, 30G′ and 30H′ will be completely synchronized and in phase.

In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D', 30E', 30G' and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A' to 20I' all have the same frequency table selected within any given allowed frequency band, such as an ISM band. Within the ISM band, a number of discrete frequencies are selected for inclusion in the frequency table. Thus, the number of frequencies listed within the ISM band is finite and limited, and the frequencies of the list are spaced sufficiently wide that the various controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' can determine the power signal frequency based on the first impedance difference described above. Despite the small changes in those impedances, all controllers 22 of transmitter modules 20D', 20E', 20G' and 20H' select the same discrete frequency for the power signals of their corresponding oscillators 26A and power amplifiers 26B from among the frequencies allowed in the frequency band.

In one embodiment, to ensure that the transmitter resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency, but also the same phase, the following process steps are employed and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first independent controller among the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second independent controller of the other independent controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' will measure the input impedance of its corresponding transmitter resonator and detect the small secondary change in impedance due to the first transmitter resonator functioning by means of its corresponding load detector 24A. In effect, the second controller 22 experiences a reflection of the impedance of the first transmitter resonator through the interaction of the first transmitter resonator with the resonant receiver subsystem 14. The second controller 22 is programmed to conclude that the other controller has turned on its oscillator 26A and power amplifier 26B first based on the secondary impedance change. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of its power signal while measuring the power emitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then varies the phase of its oscillator and searches for the phase where maximum power transfer occurs and sets the phase of the oscillator to that value. The oscillator phase determined in this manner will ensure that the phase of the power signal transmitted by the second transmitter resonator is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14. In one embodiment, the setting of the oscillator phase is based on substantially maximizing power transfer rather than making the power signal phase absolutely equal.

In another embodiment, again based on the transmitter resonators 30D', 30E', 30G' and 30H' overlapped by the resonant receiver subsystem 14, the detection of the proximity of the resonant receiver subsystem 14 is based on the test signal power drawn through the transmitter resonators 30D', 30E', 30G' and 30H'. In this embodiment, a low amplitude power signal is initially maintained by the oscillators and power amplifiers corresponding to all transmitter resonators 30A' to 30I'. The controllers 22 of all transmitter modules 20A' to 20I' then sense the power drawn by their corresponding transmitter resonators 30 using their corresponding transmitter power sensors 24B. Using their corresponding transmitter power sensors 24B, the controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' sense that power is being drawn by their corresponding transmitter resonators 30D', 30E', 30G' and 30H'. Based on the detection of the drawn test signal power, the controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' turn on the full power of their corresponding power amplifiers 26B. The term "first test signal power draw" is used herein to describe the power drawn from the test signal via the transmitter resonators 30D', 30E', 30G' and 30H'. After a suitable test period, the test power signals to the power amplifiers 26B of the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′ that are not overlapped by the resonant receiver subsystem 14 may be turned off.

Equivalent to the impedance-based embodiment described above, the controller 22 of the transmitter modules 20D′, 20E′, 20G′ and 20H′ may require a threshold power draw in order to consider a resonant receiver subsystem 14 to be present proximate to its corresponding transmitter resonator 30D′, 30E′, 30G′ and 30H′.

In one embodiment, to ensure that the controllers 22 of overlapping transmitter resonators 30D', 30E', 30G' and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of transmitter modules 20A' to 20I' all have the same frequency table selected within any given allowed frequency band, such as an ISM band. Within the ISM band, a number of discrete frequencies are selected for inclusion in the frequency table. Thus, the number of frequencies listed within the ISM band is finite and limited, and the frequencies of the list are spaced sufficiently wide that the various controllers 22 of transmitter modules 20D', 20E', 20G' and 20H' can determine the power signal frequency based on the first test signal power draw described above. Despite the small variations in those power draw values, all controllers 22 of transmitter modules 20D', 20E', 20G' and 20H' select the same discrete frequency for the power signals of their corresponding oscillators 26A and power amplifiers 26B from among the frequencies allowed in the frequency band.

In one embodiment, to ensure that the transmitter resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency, but also the same phase, the following program steps are employed and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first independent controller among the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second independent controller of the other independent controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' will measure the power draw of its corresponding transmitter resonator and detect, by means of its corresponding transmitter power sensor 24B, the small secondary variation in power draw due to the first transmitter resonator functioning. In effect, the second controller 22 experiences a reflection of the impedance of the first transmitter resonator through its interaction with the resonant receiver subsystem 14. The second controller 22 is programmed to conclude that, based on the secondary power draw variation, the other controller has turned on its oscillator 26A and power amplifier 26B first. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of its power signal while measuring the power emitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then searches for the phase at which maximum power transfer occurs and sets the oscillator to that phase. The oscillator phase set in this manner ensures that the phase of the power signal transmitted by the second transmitter resonator to the resonant receiver subsystem 14 is equal to the phase of the power signal emitted by the first transmitter resonator to the resonant receiver subsystem 14. In an embodiment, the setting of the oscillator phase is based on substantially maximizing power transfer rather than making the power signal phase absolutely equal.

In one embodiment, when two different resonant receiver subsystems are proximate to the multi-transmitter subsystem 12' and overlap with different ones of the transmitter resonators 30A' to 30I' or combinations thereof, there is no a priori reason why the two different transmitter resonators or two different groups of transmitter resonators overlapped by the two resonant receiver systems should operate at the same frequency or phase, nor is there a requirement for them to do so. The grounded shielding mesh 33' ensures this multi-path independence by decoupling all of the individual transmitter resonators 30A' to 30I' from one another. However, the transmitter resonators overlapped by a particular resonant receiver subsystem need to have their corresponding power signal amplifiers actively synchronized by their controllers, as described above. This can result in two different transmitter resonators or two different groups of resonators operating at two specific different locking frequencies in a frequency band, with all signals in a particular group being in phase with each other.

In the foregoing, it has been explained how two transmitter resonators transmitting power to the same receiver resonator can be programmed to operate so as to ensure that the two transmitter resonators carry power signals that are in phase, thereby ensuring maximum power transfer. A different situation occurs when two adjacent transmitter resonators, such as 30A′ and 30B′ in FIG. 14 , are transmitting to two substantially similar corresponding receiver subsystems 14A and 14B. Both transmitter resonators 30A′ and 30B′ have fringing fields with field lines extending from, for example, transmitter resonator 30A′ to receiver subsystem 14B′ and from transmitter resonator 30B′ to receiver subsystem 14A. In general, there are no specific physical structures in system 10′ to prevent fields such as transmitter resonator 30A′ from interacting with receiver resonators of receiver subsystem 14B.

In one embodiment, when both transmitter resonators 30A′ and 30B′ serve the same large receiver resonator that overlaps the two transmitter resonators 30A′ and 30B′ (as in FIG. 13A ), fringing fields are not inherently a problem because the two transmitter resonators 30A′ and 30B′ will be running the same frequency power signal with the same phase. In the case shown in FIG. 14 , the requirement is to ensure that any fringing fields of a given transmitter resonator (e.g., 30A′) that interact with a receiver subsystem (e.g., 14B that is intended to receive power from a neighboring transmitter resonator 30B′) do not allow power to be parasitic from the transmitter resonator 30A′. One way to achieve this is to drive the two adjacent emitter resonators 30A′ and 30B′ 180° out of phase with each other so that the overlapping fringing fields from the emitter resonators 30A′ and 30B′ will largely cancel each other.

Since either of the transmitter resonators 30A′ and 30B′ treats the other of the transmitter resonators 30A′ and 30B′ as a parasitic when the power signals of the transmitter resonators are not 180⁰ out of phase, the controller 22 of each of the transmitter resonators 30A′ and 30B′ can increment the phase of the signal from each corresponding oscillator while measuring the power transmitted by the corresponding transmitter resonator 30A′, 30B′ using the corresponding transmitter power sensor 24B. The controller 22 can then search for the adjusted oscillator phase that provides the maximum transmitted power through the corresponding transmitter resonator 30A′, 30B′, and then set the phase of the oscillator to the corresponding phase.

The frequency and phase arrangement of each resonant receiver system, whether similar or different in size, as explained above, ensures that both resonant receiver systems receive maximum transferred power. In a general embodiment, there may be a large number of transmitter resonators and several different resonant receiver subsystems may be receiving power, each resonant receiver subsystem receiving power from its own corresponding individual group of transmitter resonators at a frequency and phase selected by the controller corresponding to the transmitter resonator in the group. As a result of maximizing power transfer to each of the adjacent transmitter resonators, adjacent transmitter resonators transferring power to different receiver subsystems may operate 180⁰ out of phase. The process of maximizing power transfer adjusts the oscillator phase. Due to the complex impedance of the various transmitter modules and the small variations in resistance, inductance, and capacitance, the phase angles of different oscillators at the point of maximum power transfer may not be exactly equal (or exactly 180⁰ different) while the power signals in the transmitter resonators are actually equal (or exactly 180⁰ different).

To the extent that system 10' includes a circuit having an air gap between the primary and secondary sides, any power transfer measured or maximized in the transmitter resonator (e.g., at point 24E in FIG. 6) based on the measurement by transmitter power sensor 24B may also be measured or maximized in the secondary circuit (e.g., at point 44C in FIG. 7) based on the measurement by receiver power sensor 44A. The measurement may be provided by transmitter power sensor 24B to controller 42 of receiver module 40, which in turn may communicate the measurement to controller 22 of transmitter module 20 by one of the means already described above.

The concept of a multi-transmitter near-field resonant wireless power transfer system has been explained above with reference to system 10′, which is configured for simultaneous capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency. In a more general embodiment, the multi-transmitter near-field resonant wireless power transfer system need not specifically be a bimodal system and can be a pure capacitive or pure inductive power transfer system.

In yet another aspect, as shown in the flow chart of FIG. 15 , a wireless near-field method [1100] for transmitting power from a multiple transmitter subsystem 12′ to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing [1110] a multiple transmitter subsystem 12′ including a plurality of mutually independent transmitter resonators 30A′ to 30I′, each of the transmitter resonators being driven by a corresponding transmitter module 20A′ to 20I′, each transmitter module 20A′ to 20I′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band. to 30I′ having a common emitting surface; setting [1120] a resonant receiver subsystem 14 close to the common emitting surface, the resonant receiver subsystem including a single receiver resonator 50 overlapping with two or more of the emitter resonators (30D′, 30E′, 30G′ and 30H in FIG. 13A); measuring [1130] the input impedance of each of the emitter resonators 30A′ to 30I′; and setting [1140] a power signal to each of the plurality of independent emitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator input impedance.

The method [1100] may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator (30D', 30E', 30G' and 30H' in Figure 13A) from among the plurality of preset power signal oscillation frequencies based on the input impedance measured for each of the active transmitter resonators (transmitter resonators 30D', 30E', 30G' and 30H in Figure 13A) [1150].

The method [1100] may further include setting [1160] the power signal of each active transmitter resonator (30D', 30E', 30G' and 30H' in Figure 13A) to a corresponding selected frequency.

The method [1100] may further include adjusting [1170] the phase of the power signal applied to each corresponding transmitter resonator (transmitter resonators 30D', 30E', 30G' and 30H in Figure 13A) to a phase at which power transfer through the transmitter resonator (30D', 30E', 30G' and 30H' in Figure 13A) is substantially maximum.

In yet another aspect, as shown in the flow chart of FIG. 16 , a wireless near-field method [1200] for transmitting power from a multiple transmitter subsystem 12′ to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing [1210] a multiple transmitter subsystem 12′ including a plurality of mutually independent transmitter resonators 30A′ to 30I′, each of the transmitter resonators being driven by a corresponding transmitter module 20A′ to 20I′, each transmitter module 20A′ to 20I′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band. ' having a common emitting surface; positioning [1220] a resonant receiver subsystem 14 proximate the common emitting surface, the resonant receiver subsystem comprising a single receiver resonator 50 overlapping with two or more of the emitter resonators (30D', 30E', 30G' and 30H' in FIG. 13A); measuring [1230] power drawn by each of the emitter resonators 30A' to 30I' from a test signal; and setting [1140] a power signal to each of the plurality of mutually independent emitter resonators 30A' to 30I' to one of an off state and an active state based on the corresponding measured resonator test power draw.

The method [1200] may further include selecting [1250] a power signal oscillation frequency for the corresponding transmitter resonator (30D′, 30E′, 30G′ and 30H in FIG. 13A) from the plurality of preset power signal oscillation frequencies based on a measured test power drawn by each of the active transmitter resonators (transmitter resonators 30D′, 30E′, 30G′ and 30H in FIG. 13A).

The method [1200] may further include setting [1260] the power signal of each active transmitter resonator (30D', 30E', 30G' and 30H in Figure 13A) to a corresponding selected frequency.

The method [1200] may further include adjusting [1270] the phase of the power signal applied to each corresponding transmitter resonator (transmitter resonators 30D′, 30E′, 30G′ and 30H in FIG. 13A) to a phase at which power transfer through the transmitter resonator (30D′, 30E′, 30G′ and 30H in FIG. 13A) is substantially maximum.

In yet another aspect, as shown in the flow chart of FIG. 17 , a method for transmitting power from a multi-transmitter subsystem 12′ to two or more receiver subsystems 14A, 14B (in FIG. 14 ) at a variable resonant power signal oscillation frequency is described below. The wireless near-field method [1300] comprises: providing [1310] a multi-transmitter subsystem 12' comprising a plurality of mutually independent transmitter resonators 30A' to 30I' (in FIG. 14), each of the transmitter resonators being driven by a corresponding transmitter module 20A' to 20I' (see FIG. 13B), each transmitter module 20A' to 20I' being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A' to 30I' having a common emitting surface; placing two or more resonant receivers Subsystems 14A, 14B are arranged [1320] close to a common transmitting surface, each resonant receiver subsystem includes a single receiver resonator overlapping one or more of the transmitter resonators (transmitter resonators 30A′, 30B′ in Figure 14); measuring [1330] the input impedance of each of the transmitter resonators 30A′, 30B′; and setting [1340] the power signal to each of the plurality of independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator input impedance.

The method [1300] may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator 30A′, 30B′ [1350] from among the plurality of preset power signal oscillation frequencies based on the input impedance measured for each of the active transmitter resonators (transmitter resonators 30A′, 30B′ in FIG. 14 ).

The method [1300] may further include setting [1360] the power signal of each active transmitter resonator 30A′, 30B′ to correspond to the selected frequency.

The method [1300] may further include adjusting [1370] the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to a phase at which power transfer through the transmitter resonator 30A', 30B' (in FIG. 14) is substantially maximum.

In yet another aspect, as shown in the flow chart of FIG. 18 , a wireless near-field method [1400] for transmitting power from a multiple transmitter subsystem 12′ to two or more receiver subsystems 14A, 14B (in FIG. 14 ) at a variable resonant power signal oscillation frequency includes: providing [1410] a plurality of mutually independent transmitter resonators 30A′ to 30I′ (in FIG. 14 ) A multi-transmitter subsystem 12′, each of the transmitter resonators is driven by a corresponding transmitter module 20A′ to 20I′ (see FIG. 13B ), each transmitter module 20A′ to 20I′ can be independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ have a common emitting surface; two or more resonant receiver subsystems 14A, 14B are arranged [1420] close to the common emitting surface, each resonant The receiver subsystem includes a single receiver resonator overlapped with one or more of the transmitter resonators (transmitter resonators 30A′, 30B′ in FIG. 13); measuring [1430] power drawn by each of the transmitter resonators 30A′ to 30I′ from a test signal; and setting [1440] a power signal to each of the plurality of mutually independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator test power draw.

The method [1400] may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator 30A′, 30B′ [1450] from among the plurality of preset power signal oscillation frequencies based on the input impedance measured for each of the active transmitter resonators (transmitter resonators 30A′, 30B′ in FIG. 14 ).

The method [1400] may further include setting [1460] the power signal of each active transmitter resonator 30A′, 30B′ to a corresponding selected frequency.

The method [1400] may further include adjusting [1470] the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to a phase at which power transfer through the transmitter resonator 30A', 30B' (in FIG. 14) is substantially maximum.

In yet another aspect described with reference to FIGS. 20A and 20B , FIGS. 21A and 21B , and FIGS. 22A and 22B and based on the systems of FIGS. 1 to 10 and 12 to 14 , a near-field resonant wireless power transfer system 10 ″ for wirelessly transferring power from a photovoltaic solar cell 420 to a power load 70 ″ is presented according to the schematic diagram of FIG. 19A . The markings on FIG. 19A use an accent numbering system so that the parallel relationship with FIGS. 13A and 13B is clear at a glance, and thereby the parallel relationship with FIGS. 6 and 7 is also clear at a glance. With this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20 ″ via the power conditioning unit (PCU) 430. In addition to converting DC voltage and DC current to levels that can be further transmitted by power amplifier 26B″, PCU 430 also provides appropriately regulated voltage and current levels to drive the rest of the system components in transmitter module 20″, including small signal electronic components. PCU 430 represents an adaptive load to solar cells 420 in order to adapt to the varying power provided by solar cells 420 and the varying output impedance presented by solar cells 420 to PCU 430. This allows PCU 430 to absorb power from solar cells 420 at the maximum possible rate at all times and temperatures, regardless of variations in power from solar cells 420.

Oscillator 26A" may be used to modulate power amplifier 26B" at a frequency suitable for wireless power transmission as described above. Power amplifier 26B" may be of the same design as amplifier 26B shown in FIG8, where DC power is supplied from PCU 430 rather than as DC voltage source 127E. In an alternative embodiment, power amplifier 26B" may be suitably provided with circuitry for maintaining oscillation itself, as is well known in the art of radio systems, thereby eliminating oscillator 26A".

Power may be delivered to the transmitter resonator 30" via a transmit tuning network 28", which in FIG19A is a merger of the signal conditioning and tuning components 26C, 26D, 26E and 26F of FIG6. The transmitter resonator 30" may have a surface area having an extension that may be at least a major portion of the extension of the active solar radiation receiving surface of the solar cell 420. All such components of the transmitter module 20" are under the control of the controller 22", just as the corresponding components of the transmitter module 20 in FIG6 are under the control of the controller 22. For clarity, not all components of the transmitter module 20" are shown in FIG19A. The sensors and detectors 24A, 24B, 24C and 24D of FIG. 6 may also be present in the transmitter module 20 ″ in an equivalent form and connected to the controller 22 ″, and may achieve the same effects as those described with reference to FIG. 6 .

Power may be wirelessly transferred from the transmitter module 20" to the receiver module 40" via the transmitter resonator 30" and the receiver resonator 50". The power may then be transferred from the receiver module 40" to the DC load 70". Power may be transferred between the transmitter resonator 30" and the receiver resonator 50" by means of near-field wireless transfer, as described above with reference to Figures 6-10. The near-field wireless power transfer according to Figure 19A is not limited to bimodal and may be purely capacitive or purely inductive.

The receiver module 40″ may have the same components as the receiver module 40 of FIG. 7 . For clarity, a reduced set of these components is shown in FIG. 19A . The sensor 44A and detector 44B of FIG. 7 are not shown in FIG. 19A in an equivalent form but may be present. The receiver tuning network 48″ in FIG. 19A may be a combination of the compensation network 46A, the matching network 46B, the rectifier 46D, and the filter 46C. Power may be transmitted from the receiver tuning network 48″ to a load manager 46E″, both of which may be under the control of the receiver controller 42″.

With respect to rectifier 46D, shown in more detail in FIG. 7 , the input impedance of the device is directly dependent on the load seen by the output of the device.

In operation, the near field resonant wireless power transfer system 10″ may function in the same manner as the near field resonant wireless power transfer system 10 of FIGS. 1 and 6 to 10 , with the difference being that the applied voltage VDD across each power amplifier 26B″ is replaced with a power signal from a power conditioning unit (PCU) 430, which in turn receives its power from an associated power source, in this embodiment a solar cell 420.

In another embodiment, the power conditioning unit 430 may be omitted from the system shown in FIG. 19A and instead the power transmission system 10″ is configured or operated to also function as a power conditioning system. This may be achieved by configuring the controller 22″ in software, for example, without limitation, to adjust the input DC equivalent resistance of the power amplifier 26B″ based on the power level measured by the transmitter power sensor 24B of FIG. 6 . The term “input DC equivalent resistance” is used herein to describe the ratio of the DC voltage to the DC current at the DC terminals of the power amplifier 26B. Although the controller 22″ will make adjustments based on the power measurements, it is expected that the maximum power point of the transmitted power will be achieved when the input impedance of the power amplifier 26B″ matches the output impedance of the solar cell 420. In this embodiment, the system 10″ acts as what is known in the industry as a “maximum power point tracker” and ensures that power is always delivered at a rate more appropriate to the power consuming load than would be obtained with an unregulated power supply. In another embodiment, the controller 22″ can be configured to measure the output impedance of the power source, which in this embodiment is the solar cell 420, and then adjust the input impedance of the power amplifier 26B″ based on the measured output impedance of the solar cell 420.

In addition to adjusting the input impedance of power amplifier 26B'', controller 22'' may also adjust one or more of the settings of transmit tuning network 28'' and the frequency of oscillator 26A''. In addition, transmitter controller 22'' may make the adjustments described above based on the measurements of load detector 24A shown in FIG6 , which provides more details about the circuitry of transmitter modules 20 and 20''. Load detector 24A senses the effect of load 70'' at point 24E of FIG6 .

The receiver controller 42″ may also adjust one or more of the settings of the receiver tuning network 48″ and the load management system 46E″ based on measurements from the receiver power sensor 44A and the load detector 44B (both shown in FIG. 7 ) to improve the efficiency of power transfer.

When considering the power conditioning functionality of the system 10″, it will be appreciated that there is no a priori reason why the power transfer functionality of the system should be limited to near-field wireless transmission across an air gap, as in FIG. 19A . Therefore, in another embodiment, a power conditioning unit 410 is shown in FIG. 19B based on the elements of the system 10″ of FIG. 19A . The transmit tuning network 28″ is in direct electrical communication with the receiver tuning network 48″ via a suitable non-air gap connection 60″. This communication is via an RF power signal and constitutes the power transferred in and by the system. Suitable reactive electronic components may be employed in a well-known configuration to decouple any DC voltage and current levels in the transmitter module 20″ from such levels in the receiver module 40″. The transmitter resonator 30" and the receiver resonator 50" are not present in this embodiment and are eliminated by the direct communication connection between the transmit tuning network 28" and the receiver tuning network 48".

The function of the power transfer system of FIGS. 19A and 19B as a power conditioning system may be better understood by considering FIG. 19B , wherein the simplified power conditioning concepts are absent from the transmitter resonator 30″ and the receiver resonator 50″, although such concepts apply equally to such resonators being present (as in FIG. 19A ). The system of FIGS. 19A and 19B has four independent control parameters that may be adjusted during operation to regulate the power delivered to the receiver module 40″ and thereby to the load 70″. Typical commercial power conditioning units are often referred to as “boost converters” by virtue of boosting their output voltage above that of the source voltage. Such devices have only two control parameters.

A first independent control parameter that may be adjusted during operation to regulate the power delivered to the receiver module 40″ and thereby to the load 70″ is the oscillation frequency of the power amplifier 26B″ which may be adjusted by the controller 22″ in the oscillator 26A″.

A second independent control parameter that may be adjusted during operation to regulate the power delivered to the receiver module 40' and thereby delivered to the load 70' is the output load on the rectifier 46D of the receiver module 40'. This output load in turn directly determines the input impedance of the rectifier 46D and thereby the input impedance of the receiver module 40'. This in turn is the load experienced by the transmitter module 20' and directly determines the input DC equivalent resistance of the power amplifier 26B'. Manipulation of the output load on the rectifier 46D is accomplished via the load management system 46E' of the receiver module 40' (see Figure 19A) under the control of the receiver controller 42'. This second independent control parameter is a property of the receiver module, but inherently controls the load experienced by the power supply. The control point for manipulating this parameter is the load management system 46E″ of the receiver module 40″.

The third and fourth independent control parameters that may be adjusted during operation to regulate the power delivered to the receiver module 40' and thereby delivered to the load 70' are properties of the rectifier 46D (see FIG. 7) and the power amplifier 26B' (FIG. 19A) of the receiver module 40' and are similar in nature but completely independent of each other. Both the rectifier 46D and the power amplifier 26B' comprise multi-terminal amplifying devices that rely on modulating the passage of current between two terminals of the multi-terminal device by a voltage signal applied to a third terminal of each device. The simplest multi-terminal amplifying device that may be used in each of the rectifier 46D and the power amplifier 26B' is a transistor. This allows a phase difference to exist between the voltage signal and the current signal generated by or in the device. The voltage-current phase difference is adjustable via the applied voltage. The rectifier 46D can be an adjustable phase RF rectifier, the voltage-current phase difference of which can be adjusted via the receiver controller 42''. In the case of the power amplifier 26B'', the voltage-current phase difference can be adjusted via the transmitter controller 22''. The rectifier 46D can effectively include a differential self-synchronous RF rectifier. The rectifier 46D can include a differential switching mode self-synchronous RF rectifier.

The examples of FIGS. 19A and 19B are based on delivering power from a solar cell or further from an array of solar cells, wherein the power delivered by the solar cell 420 may vary significantly down to zero depending on the sunlight. There are many other power sources that suffer from variable output in terms of power and in terms of the voltage produced. Such power sources include power turbines, wind turbines, and various batteries and storage batteries. Wind turbines can vary significantly in their power generation and various batteries can have a wide range of power consumption curves. In view of the power delivery efficiency of the system, either of the systems 10 ″ and 410 can be configured to receive power, for example, without restriction, from commercial batteries with a slow open circuit voltage decay curve. The load management system 46E′ can be configured to change the input DC equivalent resistance of the power amplifier 26B′ as described above, and the controllers 22′ and 42′ can be configured to provide the required voltage level to the load 70′ until this voltage can no longer be maintained by the transmitted power and the adjustability of the parameters of the systems 10′ and 410.

FIG. 19A and its associated description illustrate near-field wireless power transfer from a single solar cell 420 to a single load 70″ (typically a battery). In actual implementations of larger solar battery power systems, battery arrays are typically employed, allowing for a power transfer scheme similar to that described with reference to FIG. 12 , FIG. 13A , and FIG. 13B , with multiple transmitter subsystems and typically a single receiver subsystem. This is shown in FIGS. 20A and 20B , which are exploded front and rear views, respectively, of a solar panel 400 having a transparent solar cover 440 and one near-field wireless transmission subsystem per solar cell 420, and thereby by way of example including sixty near-field wireless power transmission subsystems 16, each transmission subsystem 16 including a transmitter resonator 30″, a transmitter module 20″, and a power conditioning unit 430, as described with reference to FIG. 19A . To avoid confusion, the transmission subsystems 16 are not labeled in FIG. 19A , but are pointed out and labeled in FIGS. 20B , 21B, and 22B , as further described below.

In one embodiment, coupling each individual solar cell of a solar panel composed of a plurality of solar cells to a power delivery and management system allows for cell-level power management. By providing power management at each individual cell, power collection can be optimized for each cell, resulting in improved efficiency of the entire solar panel system. In this embodiment, the effects caused by failure of an individual cell or poor connections between cells will be mitigated. Power collection at the individual cell level allows for maximum power harvest even in less than ideal conditions, such as rainfall, shadows, or when debris covers a portion of the solar panel.

To avoid confusion, only one near-field wireless power transmission subsystem 16 is labeled in FIG. 20B . In FIG. 20A and FIG. 20B , the transmitter resonator 30″ of each transmission subsystem 16 can be located on the back side of its corresponding solar cell 420. As seen from the front side of the board in FIG. 20A , the flat area of the solar cell represents the active solar radiation receiving and energy conversion semiconductor device itself and is correspondingly labeled as 420, while as seen from the back side in FIG. 20B , the flat area of the device represents the transmitter resonator and is correspondingly labeled as 30″. The transmitter resonator 30″ can have a surface area having an extension that can be at least a major part of the extension of the active solar radiation receiving surface of the solar cell 420. The transmitter module 20" and power conditioning unit 430 of each near-field wireless power transmission subsystem 16 are combined together in FIG. 20B and labeled 450. To avoid confusion, the combined assembly 450 is not labeled in FIG. 19A, but is indicated as a unit and labeled in FIG. 20B, FIG. 21B, and FIG. 22B, as further explained below. A single receiver resonator 50" may be assembled in a frame 460 of a solar panel 400. A single receiver module 40" may be mounted directly on the back of the receiver resonator 50".

In operation, the near field resonant wireless power transfer system 10″ may function in the same manner as the near field resonant wireless power transfer system 10 of FIGS. 12 , 13A, and 13B , with the difference being that the voltage VDD applied to each of the power amplifiers 26B″ is replaced with a power signal from a power conditioning unit (PCU) 430, which in turn receives its power from an associated solar cell 420.

20A and 20B, the frame 460 may be configured as a receiver resonator adapted to receive power from all transmitter resonators 30″, and the receiver module 40″ may be located on the frame 460. In this embodiment, the plate within the frame 460 is not a resonator but may be a simple flat sheet of non-conductive material.

In another embodiment, the solar panel 400' shown in the front view and rear view of Figures 21A and 21B, respectively, enables each near-field wireless power transmitting subsystem to transmit power to a near-field wireless power receiver subsystem. Although the frame 460 is shown as being filled by an opaque plate 470, the plate 470 may not be part of the near-field circuit or magnetic circuit. For clarity, the same component numbers as in Figures 20A and 20B are used on the transmitting side. On the receiving side, the numbering of Figure 19A is used. Again, to avoid confusion, only one receiving side device is labeled.

In operation, the solar panel arrangement 400' of Figures 21A and 21B can have individual transmitter modules 20" linked by hard wires (not shown) so that the transmitter modules can be in phase to minimize power loss in transmission. In other embodiments, the transmitter modules 20" can be independent and function as explained in Figures 14, 17 and 18.

In yet a further embodiment, shown as a solar panel arrangement 400" in the front view of FIG. 22A and the rear view of FIG. 22B, respectively, an array of twenty-five solar cells arranged, for example, in five rows, each row having five cells 420 is shown. Each solar cell 420 has at its rear a transmitter resonator 30' including its corresponding transmitter module 20" and a unit 450' including a power conditioning unit 430. At the bottom and top of the array and between every two rows of solar cells are receiver resonators 50" arranged in a plane substantially perpendicular to the plane of the solar cells 420, each receiver resonator 50" being in wired electrical communication with its corresponding receiver module 40". As with the previous solar panel embodiments, one example of each component is labeled. As with the embodiments shown in FIGS. 20A and 20B and 21A and 21B, in some embodiments, the solar panel arrangement 400" may also have a frame 460. For clarity, the frame 460 is not shown in FIGS. 22A and 22B.

In operation, the transmitter resonators 30″ of the solar cells 420 in a row of the system 400″ transmit power to the receiver resonators 50″ both above and below the transmitter resonators. In this embodiment, however, there is an additional mechanism for the various nearest neighbor receiver resonators 50″ to resonantly couple and share the collected power between the receiver resonators. The collected power gathered by all the receiver resonators 50″ of the array can thus be tapped via any one or more of the various receiver modules 40″. In some embodiments, the power collected by all the receiver modules 40″ can be tapped by way of example only via the bottom-most receiver module 40″. Any of the receiver modules 40″ on any receiver resonator 50″ can function as a receiver module to collect power from a row of solar cells 420 while also functioning as a transmitter module to transmit the collected power to another receiver resonator 50″ in close proximity to it via its associated receiver resonator 50″. This action can be repeated down the array to deliver power to the bottom-most receiver module 40″.

In another embodiment of the system of FIGS. 22A and 22B , a frame (similar to the frame 460 of FIGS. 20A and 20B ) surrounding the planar perimeter of the solar cell array of FIGS. 22A and 22B can be a receiver resonator that carries the receiver modules 40′ and can receive power from the various receiver resonators 50″. In this way, the total power generated by all solar cells 420 in the array can be received by the resonator frame 460 and tapped via the receiver modules 40″ for further electrical emission.

Power collection at the level of individual solar cells can be accomplished with a wired connection. However, the use of wireless transmission systems in solar panels allows a reduction in wiring and, therefore, a reduction in manufacturing costs.

In yet another embodiment described with reference to the flowchart in FIG. 23 , a method [1500] for transmitting power from a photovoltaic cell 420 to a power load 70″ is provided, the method comprising: converting [1510] power from the photovoltaic cell 420 into an oscillating power signal having an oscillating frequency in a transmitter module 20″; transmitting [1520] the power to a transmitter resonator 30′ that is in wired electrical communication with the transmitter module 20′ and is configured to resonate at the oscillating frequency; '; receiving [1530] power in a receiver resonator 50'' configured to resonate at the oscillation frequency and arranged to receive power from a transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction; receiving [1540] power in a receiver module 40'' in wired electrical communication with the receiver resonator 50''; and providing [1550] the received power in the form of direct current to a power load 70'' via wired electrical communication. The method may further include converting a voltage and a current of power from the photovoltaic cell 420 into a voltage and a current suitable for the transmitter module 20'' before converting the power into the oscillating power signal.

In yet another embodiment of the method described with reference to the flowchart in FIG. 19A and FIG. 24 , a method [1600] for transmitting power from an array 400 of photovoltaic cells 420 to an electrical load 70′′ is provided, the method comprising: in each of a first plurality of corresponding transmitter modules 20′′, converting [1610] power from each of the photovoltaic cells 420 in the array 400 into an oscillating power signal having an oscillation frequency; transmitting [1620] power in each of the transmitter modules 20′′ to a corresponding transmitter resonator 30′ in a second plurality of transmitter resonators; and [1630] power in a receiver resonator 50'', the receiver resonator being configured to resonate at the oscillation frequency and being arranged to receive power from the plurality of transmitter resonators 30'' via at least one of capacitive coupling and magnetic induction; receiving [1640] power in a receiver module 40'' in wired electrical communication with the receiver resonator 50''; and providing [1650] the received power in the form of direct current to a power load 70'' via wired electrical communication. The method may further include converting a voltage and a current of power from each photovoltaic cell 420 into a voltage and a current suitable for a corresponding transmitter module 20'' before converting the power into the oscillating power signal. Receiving [1630] power in a receiver resonator 50'' may include receiving power in a receiver resonator disposed around a planar perimeter of the array 400 of photovoltaic cells.

In yet another embodiment of the method described with reference to the flowchart in FIG. 19A and FIG. 25 , a method [1700] for transmitting power from an array 400′ of photovoltaic cells 420 to an electrical load 70″ is provided, the method comprising: converting [1710] power from each of the photovoltaic cells 420 in the array 400′ into an oscillating power signal having an oscillating frequency in each of a first plurality of corresponding transmitter modules 20″; transmitting [1720] power from each of the transmitter modules 20″ to a corresponding transmitter resonator 30″ in a second plurality of transmitter resonators 30″, wherein each transmitter resonator 30″ is a first plurality of corresponding transmitter modules 20″, wherein each transmitter resonator 30″ is a second ... '' is configured to resonate at an oscillation frequency; receiving [1730] power from each transmitter resonator 30'' in a corresponding receiver resonator 50'' configured to resonate at the oscillation frequency, wherein each receiver resonator 50'' is further configured and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction; receiving [1740] power from each receiver resonator 50'' in a corresponding receiver module 40'' that is in wired electrical communication with the receiver resonator 50''; and providing [1750] the received power in the form of direct current to a power load 70'' via wired electrical communication. The method may further include converting the voltage and current of the power from each photovoltaic cell 420 into a voltage and current suitable for the corresponding transmitting module 20 ″ before converting the power into the oscillating power signal.

In yet another embodiment described with reference to the flowchart in FIG. 19A and FIG. 26 , a method [1800] for transmitting power from an array 400″ of photovoltaic cells 420 to an electrical load 70″ (in FIG. 19A ) is provided, the method comprising: in each of a first plurality of corresponding transmitter modules 20″, converting [1810] power from each of the photovoltaic cells 420 in the array 400″ into an oscillating power signal having an oscillation frequency; transmitting [1820] power from each of the transmitter modules 20″ to a transmitter resonator 30″ in a second plurality of transmitter resonators 30″, wherein each transmitter resonator 30″ is configured to resonate at the oscillation frequency; and transmitting [1821] power from each of the transmitter modules 20″ to a transmitter resonator 30″ in a third plurality of receiver resonators 30″. receiving [1830] power from each transmitter resonator 30'' in any proximal receiver resonator 50'' of the resonator 50'', the receiver resonators being configured to resonate at the oscillation frequency, wherein each receiver resonator 50'' is further configured and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction; sharing [1840] the received power among a third plurality of receiver resonators 50''; and providing [1850] the received power in the form of direct current to a power load 70'' via wired electrical communication, the received power coming from one or more of the third plurality of receiver resonators 50'' via corresponding one or more receiver modules 40''. The method may further include converting the voltage and current of the power from each photovoltaic cell 420 into a voltage and current suitable for the corresponding transmitting module 20 ″ before converting the power into the oscillating power signal.

FIG. 27A shows a representative portion 500 of an expanded near-field wireless power distribution system in an electric vehicle having a conductive chassis 510. In this embodiment of the general system 10″ of FIG. 19A, the power source is a rechargeable battery 520 rather than a solar cell 420, and the load 70″ is an electric motor 530 rather than a battery as in FIG. 19A. The system shown in FIG. 14A may include a power conditioning unit 430 as in FIG. 19A. In other embodiments, the transmitter modules may act in conjunction to provide power conditioning as described above with reference to FIG. 19B.

The system shown in FIG. 27A and described in more detail below can operate by capacitive power transfer, inductive power transfer, or by bimodal power transfer. Referring to FIGS. 4B and 19A , the transmitter resonator 30 ″ includes a dielectric element 138 clamped between conductive antennas 132 and 134. Referring to FIGS. 4B and 19A , the receiver resonator 50 ″ includes a dielectric element 158 clamped between conductive antennas 152 and 154. The transmitter module 20 ″ is shown mounted directly to the antenna 132, which also serves as a frame or support for the battery 520. The transmitter module 20 ″ can be electrically connected between the battery 520 and the transmitter resonator 30 ″. The receiver module 40 ″ is shown mounted directly to the electric motor 530. The receiver module 40 ″ may be electrically connected between the receiver resonator 50 ″ and the electric motor 530 .

FIG27B shows a representative portion 500 of an expanded near-field wireless power distribution system in an electric vehicle having a conductive chassis 510. In an embodiment of the general system 10″ of FIG19A, again as in FIG27A, the power source is a rechargeable battery 520 instead of a solar cell 420, and the load 70″ is an electric motor 530 instead of a battery as in FIG19A. The system shown in FIG27B may include a power conditioning unit 430 as in FIG19A. In other embodiments, the transmitter module 20″ and the receiver module 40″ may act in conjunction to provide power conditioning as described above with reference to FIG19B.

The system shown in FIG. 27B and described in more detail below may operate by capacitive power transfer, inductive power transfer, or by bimodal power transfer. Referring to FIGS. 4B and 19A , the transmitter resonator 30 ″ includes a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to FIGS. 4B and 19A , the receiver resonator 50 ′′′ includes the dielectric element 158 of FIG. 27A and conductive antennas 152 and 154, with the receiver resonator 50 ′′′ not being present in this embodiment. The transmitter module 20 ′′ is shown mounted directly to the antenna 132, which also serves as a frame or support for the battery 520. The transmitter module 20 ′′ may be electrically connected between the battery 520 and the transmitter resonator 30 ′′. The receiver module 40" is shown mounted directly to the electric motor 530. In this embodiment, the receiver module 40" may be electrically connected between the electric motor 530 and the chassis 510. In this arrangement, there is sufficient coupling between the chassis 510 and the antenna 152 for power transfer to proceed with suitable efficiency. The conductive mechanical components of the system (i.e., components having, for example, a load bearing structure function in the system) may hereby form part of the resonant structure of the power transfer system.

In the embodiment shown in Figures 27A and 27B, specifically, the focus is on power supplied to the electric motor 530 to drive one of the wheels of the vehicle, but an equivalent arrangement can be implemented for any electrical subsystem on the vehicle using a plurality of suitably adapted receiver modules 40'', with the transmitter module 20'' providing power to all receiver modules.

The arrangement of FIG. 27A and FIG. 27B for delivering power from a battery to the electrical subsystem of a vehicle largely avoids the extremely complex automotive wiring harness that is difficult and a source of considerable manufacturing cost during vehicle manufacture. The embodiment in FIG. 27A and FIG. 27B , together with its extension to other electrical subsystems of a vehicle, may be described as an "extended near-field wireless power distribution system."

In addition to the other wheels of the electric vehicle, the arrangement can be extended to headlights and other vehicle accessories, including without limitation interior lights, dashboard displays, measuring instruments, digital electronics, navigation systems, warning systems, etc. The application is not limited to electric vehicles. It can be applied to hybrid or internal combustion vehicles to distribute power as needed and when needed. It can be similarly applied to other vehicles that employ any electrical system that requires power. Examples include without limitation motorized or non-motorized bicycles, aircraft, boats, and other vehicles that employ on-board power. The battery or power source need not be limited to the vehicle. The principles described with respect to FIGS. 1-11 , 19A and 19B, and 27A and 27B also apply to fixed and vehicle-mounted systems that require power from an earth-stationary source (e.g., fixed orbits that are not limited to supplying power to mobile vehicles).

FIG. 28A shows another embodiment of the general system 10″ of FIG. 19A in a power supply system 600 for supplying power to a computer monitor 610 located on a tabletop 620 with power from a suitable source via the primary side 12 according to FIG. 1 and more specifically according to FIG. 6 . In the system 600, both the transmitter module 20″ and the transmitter resonator 30″ of FIG. 19A are incorporated into the primary side 12. In the arrangement of the system 600, the receiver resonator 50″ according to FIG. 19A forms the base of the monitor 610. The receiver module 40″ of FIG. 19A can be incorporated into the base of the monitor 610. Alternatively, the receiver module 40" of Figure 19A may be incorporated into the monitor 610 itself. Referring to Figure 4B, the antenna 152 forms the bottom of the base of the monitor 610 and is separated from the antenna 154 by a dielectric element 158.

The housing and structural frame 630 of the monitor 610 may be at least partially conductive and serve as one continuous conductor to electrically supply the power signal from the antenna 154 via the receiver module 40″ (see FIG. 19A ) to the circuitry of the monitor 610 representing the load resonator 70″ of FIG. 19A . Other electrical connectors from the antenna 152 to the circuitry of the monitor 610 extend upward from the antenna 152 along the base of the monitor 610. In other embodiments, the housing and structural frame 630 of the monitor 610 may be a non-conductive polymer and a separate conductor extends from the antenna 154 to the circuitry of the monitor 610 representing the load resonator 70″ of FIG. 19A .

As shown in another embodiment of a power supply system 600' for supplying power to a computer monitor 610 in FIG. 28B, the base of the monitor 610 may include only the antenna 152 and the dielectric element 158. In this embodiment, the metal conductive portion of the monitor housing or frame 630 acts as the antenna instead of the antenna 154, and the housing or frame 630 has sufficient coupling with the antenna 152 under the dielectric element 158 to provide sufficiently efficient power transfer. The receiver module 40'' of FIG. 19A can be incorporated into the base of the monitor 610. Alternatively, the receiver module 40'' of FIG. 19A can be incorporated into the monitor 610 itself. The housing and structural frame 630 of the monitor 610 can act as a continuous electrical conductor to supply a power signal via the receiver module 40″ to the circuit of the monitor 610 representing the load resonator 70″ of Figure 19A.

The system 600 may include a power conditioning unit 430 as shown in FIG19A. In some embodiments, the transmitter module 20" and the receiver module 40" may work in conjunction to provide power conditioning as described with reference to FIG19A using near-field wireless power transfer. The near-field wireless power transfer system of FIG28A removes the need for cumbersome cables to supply power to the monitor 610 and employs the mechanical structural elements of the system as integral electrical/electronic components in the power transfer arrangement.

As described with reference to the flowchart in FIG. 29 and the systems of FIGS. 19A and 19B, a method [2000] for transmitting power from a DC power source 420 to a power load 70'' is provided, the method comprising: providing [2010] a power transmission system 10'', 410 in wired communication with the power source 420, the power transmission system 10'', 410 comprising: an oscillator 26A'' capable of oscillating at an oscillation frequency, a power amplifier 26B'' and a transmitter tuning network 28'' both under the control of a transmitter controller 22'', and a receiver tuning network 48'' and a load management system 46E'' both under the control of a receiver controller 42'', wherein the load management system 46E'' is in wired communication with the power load 70'' signal; in the power amplifier 26B'', the power from the power source 420 is converted [2020] into an oscillating power signal having an oscillation frequency; under the control of the transmitter controller 22'', the power signal is transmitted [2030] from the power amplifier 26B'' to the load management system 46E'' via the transmitter tuning network 28'' and the receiver tuning network 48''; the [20 40] oscillation frequency, the input DC equivalent resistance of the power amplifier 26B'', the transmitter tuning network 28'', the receiver tuning network 48'' and at least one of the load management system 46E'' to change the rate at which power is transmitted; and the power received by the load management system 46E'' is provided [2050] to the power load 70'' in the form of direct current via wired electrical communication.

Transmitting [2030] the power signal via the transmitter tuning network 28'' and the receiver tuning network 48'' may include transmitting power by wired communication or by wireless communication. Transmitting power by wireless communication may include transmitting power by near field wireless communication. Transmitting power by near field wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling. Transmitting power from a DC power source 420 may include transmitting power from at least one solar cell 420. Transmitting power from a DC power source may include transmitting power from at least one battery. Transmitting power from a DC power source may include transmitting power from a power source having a varying voltage.

In another embodiment described with reference to the flow chart in FIG. 30 and with further consideration of the system of FIGS. 19A and 19B , a method [2100] for transmitting power from a DC power source 420 to an electrical load 70″ is provided, the method comprising: providing [2110] a power transmission system 10″, 410 in wired electrical communication with the power source 420, the power transmission system 10″, 410 comprising an RF rectifier 46D (see FIG. 7 ) in radio frequency communication with an adjustable phase RF rectifier 46D. The invention relates to a radio frequency power amplifier 26B'' for communication, wherein the adjustable phase radio frequency rectifier is in wired electrical contact with the power load 70''; converting [2120] power from a DC power source 420 into a radio frequency oscillating power signal in the power amplifier 26B''; converting [2130] the radio frequency oscillating power signal into a DC power signal in the rectifier 46D; and adjusting [2140] the efficiency of power transmission by adjusting the current-voltage phase characteristic of the rectifier 46D. Providing an adjustable phase radio frequency rectifier can include providing a differential self-synchronous radio frequency rectifier 46D.

The method [2100] may further include adjusting the efficiency of the power transmission by adjusting the DC equivalent input resistance of the power amplifier 26B''. Providing [2110] the power transmission system 10'', 410 may include providing a load management system 46E'' for wired communication between the rectifier 46D and the load 70''. Adjusting the DC equivalent input resistance of the power amplifier 26B'' may include adjusting the input impedance of the rectifier 46D by adjusting the load management system 46E''. Adjusting the load management system 46E'' may include automatically adjusting the load management system 46E''.

The method [2100] may further include adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B''. Providing [2110] the power transmission system 10'', 410 may include providing a transmitter controller 22'' that communicates with the power amplifier 26B'' to control the power amplifier 26B''. Adjusting the current-voltage phase characteristic of the power amplifier 26B'' may be performed by the transmitter controller 22''. Adjusting the current-voltage phase characteristic of the power amplifier 26B'' may be performed automatically by the transmitter controller 22''.

The method [2100] may further include adjusting the efficiency of power transfer by changing the oscillation frequency of the power amplifier 26B″.

Providing [2110] the power transmission system 10'', 410 may include providing a receiver controller 42'' in communication with the rectifier 46D to control the rectifier 46D. Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed by the receiver controller 42''. Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed automatically by the receiver controller 42''.

Providing [2110] the power delivery system 10'', 410 may include providing a power amplifier 26B'' for direct wired RF communication with the adjustable phase RF rectifier 46D (via connection 60'' of Figure 19B). Providing [2110] the power delivery system 10'', 410 may include providing a power amplifier 26B'' for wireless near-field RF communication with the adjustable phase RF rectifier 46D.

Providing [2110] a power transmission system 10'', 410 may include providing a transmitter resonator 30'' in wired radio frequency communication with a power amplifier 26B' and a receiver resonator 50'' in wired radio frequency communication with an radio frequency rectifier 46D. The method [2100] may further include operating the transmitter resonator 30'' and the receiver resonator 50'' in wireless near-field radio frequency communication with each other. Providing [2110] a power transmission system 10'', 410 may include providing a power amplifier 26B'' in at least one of capacitive near-field wireless radio frequency communication and inductive near-field wireless radio frequency communication with the rectifier 46D. Providing [2110] a power transmission system 10'', 410 may include providing a power amplifier 26B'' in bi-peak wireless near-field communication with the rectifier 46D.

The method [2100] may further include: providing a power regulating unit 430 electrically disposed between the power source 420 and the power transmission system 10''; and adjusting the power regulating unit 430 to adjust at least one of the current and voltage from the power source 420 to improve the efficiency of power transmission.

Based on a more in-depth consideration of the systems of FIG. 19A and FIG. 19B and referring to FIG. 7 , a universal power transmission system 10″, 410 for supplying power from a DC power source 420 to a power load 70″ includes: a radio frequency power amplifier 26B″, which is in wired electrical communication with the power source 420 and is configured to convert the DC voltage from the power source 420 into an AC voltage signal having an oscillating frequency; an adjustable phase radio frequency rectifier , which is in wired electrical contact with the power load 70'' and in radio frequency communication with the power amplifier, the rectifier is configured to receive power transmitted from the power amplifier 26B''; and a receiver controller 42'', which is in communication with the rectifier 46D, the receiver controller is configured to adjust the efficiency of the power transmission from the power amplifier 26B'' to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D. The receiver controller 42'' can be configured to automatically adjust the current-voltage phase characteristic of the rectifier 46D. The rectifier can be a differential self-synchronous radio frequency rectifier.

The power transmission system 10″, 410 may further include a load management system 46E″ in wired communication with the load 70″ and disposed between the load 70″ and the rectifier 46D in a power signal manner, the load management system 46E″ configured to increase the efficiency of the power transmission by adjusting the input impedance of the rectifier 46D. The load management system 46E″ may be configured to automatically adjust the input impedance of the rectifier 46D.

The power transmission system 10″, 410 may further include a transmitter controller 22″ in communication with the power amplifier 26B″, the transmitter controller 22″ configured to increase the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B″. The transmitter controller 22″ may be configured to automatically adjust the current-voltage phase characteristic of the power amplifier 26B″ to increase the efficiency of the power transmission.

The power transmission system 10", 410 may further include an oscillator 26A" in communication with the power amplifier 26B" and the transmitter controller 22". The transmitter controller 22" may be configured to adjust the oscillation frequency via the oscillator 26A".

The power amplifier 26B″ may be in direct wired RF communication with the adjustable phase RF rectifier 46D (via connection 60″ of FIG. 19B ). The power amplifier 26B″ may be in wireless near-field RF communication with the adjustable phase RF rectifier 46D. The power transmission system 10″, 410 may include a transmitter resonator 30″ in wired RF communication with the power amplifier 26B″ and a receiver resonator 50″ in wired RF communication with the rectifier 46D. The transmitter resonator 30″ and the receiver resonator 50″ may be in wireless near-field RF communication with each other. The power amplifier 26B″ may be in at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier 46D. The power amplifier 26B'' can communicate with the rectifier 46D in a dual peak near field wireless RF manner.

The power transmission system may further include a power conditioning unit 430 electrically disposed between the power source 420 and the power amplifier 26B″, the power conditioning unit 430 being configured to regulate at least one of the current and the voltage from the power source 420 to improve the efficiency of the power transmission.

In another embodiment described with reference to Figures 19A, 19B, 27A and 27B, and 28A and 28B, an electric system includes: a mechanical load carrying structure 510, 630 having a conductive first portion; a power load; and a power transfer system 10'', 410, including at least one radio frequency resonator 30'', 50'' configured for near-field wireless power transfer, wherein the resonator at least partially includes the conductive first portion. The electric system may further include a rechargeable battery 520, and the power load may include an electric motor 530. The electric system may be an electric vehicle 500, 500', and the mechanical load carrying structure may include a chassis 510 of the vehicle. The electric system may be a display monitor 610 and the mechanical load bearing structure may be at least one of a frame 630 and a base of the monitor.

The electric power system may further include a power source. The power transmission system may include: a radio frequency power amplifier 26B'', which is in wired electrical communication with the power source and is configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase radio frequency rectifier 46D, which is in wired electrical contact with the power load 70'' and in radio frequency communication with the power amplifier 26B''; a rectifier 46D, configured to receive power transmitted from the power amplifier 26B''; and a receiver controller 42'', which is in communication with the rectifier 46D, the receiver controller 42'' being configured to adjust the efficiency of power transmission from the power amplifier 26B'' to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D.

In another embodiment, as described in FIGS. 19A and 19B, 27A and 27B, and 28A and 28B, an apparatus includes: a mechanical load bearing structure 510, 630 having a conductive first portion; a power source; an electrical load 70'', 530, 610; and an electrical power transmission system 10'', 410, including: an RF power amplifier 26B'' in wired electrical communication with the power source and configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier 46D, which is coupled to the electrical load 70' ' is in wired electrical contact and in radio frequency communication with the power amplifier 26B''; a rectifier 46D, configured to receive power transmitted from the power amplifier 26B''; and a receiver controller 42'', which communicates with the rectifier 46D, and the receiver controller 42'' is configured to adjust the efficiency of power transmission from the power amplifier 26B'' to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D; wherein the conductive first portion is configured to carry at least one of the radio frequency signal from the power amplifier 26B'' and the radio frequency signal to the rectifier 46D.

The device may further include a load management system 46E″ in wired communication with the load 70″ and disposed between the load 70″ and the rectifier 46D in a power signal manner, the load management system 46E″ configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier 46D. The device may further include a transmitter controller 22″ in communication with the power amplifier 26B″, the transmitter controller 22″ configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B″. The apparatus may further include an oscillator 26A" in communication with the power amplifier 26B" and a transmitter controller 22", wherein the transmitter controller 22" is configured to adjust the oscillation frequency via the oscillator 26A".

The power amplifier 26B″ may be in direct wired RF communication with the rectifier 46D via the conductive first portion. The power amplifier 26B″ may be in wireless near-field RF communication with the rectifier 46D. The power transmission system 10″, 410 may include a transmitter resonator 30″ in wired RF communication with the power amplifier 26B″ and a receiver resonator 50″ in wired RF communication with the rectifier 46D, and one of the transmitter resonator 30″ and the receiver resonator 50″ may include the conductive first portion. The transmitter resonator 30″ and the receiver resonator 50″ may be in wireless near-field RF communication with each other. The power amplifier 26B″ may be in at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier 46D. The power amplifier 26B″ can communicate with the rectifier 46D in a dual peak near field wireless radio frequency. The DC power source can include a rechargeable battery 520, and the load can include an electric motor 530.

In yet another embodiment schematically shown in FIG. 32 and based on FIG. 6 , FIG. 7 , FIG. 8 and FIG. 9 , a sealed bidirectional power transmission circuit device 800 is provided, the device having a plurality of terminals configured to communicate electrically with a device outside the sealed device 800, the sealed device 800 including within its sealed interior: a multi-terminal power switching (MPS) device 810 having at least one DC terminal, at least one AC terminal and at least one control terminal, the MPS device 810 being adjustable between an amplifying state and a rectifying state, and being configured to bidirectionally transmit a DC voltage and a DC current via at least one DC terminal, and to communicate via at least one AC terminal. The controller 880 is provided with a phase, frequency and duty cycle adjustment (PFDCA) circuit 820, which is in wired data communication with the controller 880, and the PFDCA circuit is in wired electrical communication with the MPS device 810 via at least one control terminal, and the PFDCA circuit 820 is configured to establish an RF oscillation signal having the frequency and phase of the RF power signal at at least one control terminal of the MPS device 810, and adjust the MPS device 810 between an amplification state and a rectification state by adjusting the phase of the RF oscillation signal under the command of the controller 880. The PFDCA circuit 820 can be further configured to establish a duty cycle of the RF oscillation signal. The PDFCA circuit 820 may include an RF oscillator for generating an RF oscillation signal under instructions from the controller 880. The term "multi-terminal power switching device" is used herein to describe a device having at least three terminals and capable of switching or modulating a current flowing between at least two terminals of the device based on a signal applied to at least a third terminal of the device. Suitable MPS devices 810 include, but are not limited to, mechanical relay switches, solid-state switches, electro-optical switches (also known as optical switches), gate currents, waveguide switches, transistors (including, for example, MOSFETs, MESFETs, III-V group semiconductor transistor devices, and BJT devices), and power tube devices (including, for example, triodes and pentodes).

In some embodiments, a circuit is sealed with a polymeric coating or mold to form a seal or sealed device. In some embodiments, the sealed device protects components disposed on the interior of the device. In some embodiments, the seal of the device provides electrical insulation to prevent electrostatic discharge, short circuits, or other harmful discharges that can damage components of the device. In some embodiments, the sealed device protects internal components from oxidation. In some embodiments, the seal can form a waterproof barrier or a water vapor barrier. In some embodiments, the seal provides for facilitating electrical connection to the device by providing access to one or more terminals on the exterior of the sealed device.

The sealed power transmission circuit device 800 may further include a tuning network 830 in wired data communication with the controller 880 within the seal, the tuning network being in wired electrical communication with the MPS device 810 via at least one AC terminal, the tuning network 830 being configured to adjust the RF power signal to a tuned RF power signal from the tuning network 830 under instructions from the controller 880 when the MPS device 810 is in the amplification state. The tuning network 830 may include a harmonic termination network circuit of the type shown in FIGS. 8 and 9, the harmonic termination network circuit being configured to suppress harmonics of the RF oscillation signal in the RF power signal. As shown in FIGS. 8 and 9 , the harmonic terminal network may include one or more inductors and one or more of the first harmonic terminal 127I, 147G, the second harmonic terminal 127H, 147F, and the third harmonic terminal 127F, 147D.

The sealed power transmission circuit device 800 may include an amplitude/frequency/phase detector (AFPD) 840 in wired data communication with a controller 880 within the seal, the amplitude/frequency/phase detector being arranged to communicate with the tuning network by wire and configured to determine the amplitude, frequency and phase of any RF power signal transmitted between the tuning network and an AC load/source external to the sealed device. To this end, according to FIG. 32 , the AFPD 840 measures the amplitude, frequency and phase of the signal at the output of the tuning network 830 derived from the device 800. The PFDCA circuit 820 is configured to receive instructions from the controller 880 based on the measurement data transmitted to the controller 880 by the AFPD 840. In other embodiments not shown in FIG. 32 , the PFDCA circuit 820 is configured to adjust the RF oscillation signal and/or at least one of the DC current and DC voltage based on a feedback signal received directly from the AFPD 840.

The tuning network 830 may include a voltage-current tuner for adjusting the phase difference between the voltage and current of the tuned RF signal based on the measurement data from the AFPD 840 when the power switching device is in the amplification state. A suitable voltage-current tuner is explained in more detail with reference to FIG6. According to FIG32, the voltage-current tuner of the tuning network 830 is applied to the signal connected to the signal derived from the device 800. When the power is emitted downward in FIG32, the voltage-current tuner thereby acts as a tuner. The voltage-current tuner can be transparent to power transmitted in the opposite upward direction through the device 800 in FIG. 32, and the power transmission circuit device 800 is bidirectional. In some embodiments, the tuning network 830 can transmit a tuned RF power signal to the AC load/source 900, which can be the transmitter resonator 30 and 30", as described with reference to FIG. 6 and FIGS. 19A, 27A, and 27B. When the AC load/source 900 is this double-peak transmitter resonator, the voltage-current tuner can be used to adjust the ratio of the electric field to the magnetic field, as described with reference to FIG. 6.

The sealed power transmission circuit device 800 may further include a power management (PM) circuit 860 in wired data communication with the controller 880 inside the seal and in wired electrical communication between the MPS 810 and a DC source/load 700 outside the sealed device 800, the power management (PM) circuit being configured to impedance match the MPS 810 with the external DC source/load 700 and to adjust the DC power transmitted between the MPS 810 and the DC source/load 700 based on the measurement data transmitted to the controller by the AFPD 840. In other embodiments not shown in FIG. 32, the PM circuit 860 may be configured to adjust the DC power transmitted between the MPS 810 and the DC source/load 700 based on feedback signals received directly from the AFPD 840 and/or the VID 850.

It should be noted again that DC power can be transferred in both directions via the PM circuit 860 between the MPS 810 and the DC source/load 700. It should also be noted that a convention is maintained herein whereby the DC source/load 700 is described as a "source/load" and the external AC load/source 900 that delivers AC power to the tuning network is described as a "load/source," thereby emphasizing the point that when the DC source/load 700 functions as a DC power source, the AC load/source 900 functions as a load of that power for conversion to AC power, and vice versa. When the MPS 810 is in either of its amplifying state and rectifying state, the arrows depicted in FIG32 as being proximate to and parallel to the connector indicate the path and direction of the power transfer circuit device 800. When the MPS 810 is in the amplifying state, the power flow is downward through FIG32; when the MPS 810 is in the rectifying state, the power flow is upward through FIG32.

The sealed power delivery circuit device 800 may further include a voltage/current detector (VID) 850 in wired data communication with the controller 880 within the seal, the voltage/current detector being configured to determine the DC voltage and DC current transmitted between the MPS 810 and the PM circuit 860. When the MPS 810 is in the amplification state, the power delivery circuit device 800 may be adjusted based on the measurement result of the VID 850 so that the device 800 presents an equivalent DC load to the DC source/load 700, thereby allowing maximum power to be extracted from the DC source/load 700. The DC voltage at at least one DC terminal of the MPS device 810 is thereby adjusted. When the MPS 810 is in a rectifying state, the power transmission circuit device 800 can be adjusted based on the measurement result of the VID 850 so that the device 800 presents an equivalent DC source impedance to the DC source/load 700, thereby allowing maximum power transmission from the device 800 to the DC source/load 700. The DC voltage at the wired connection between the device 800 and the DC source/load 700 is thereby adjusted.

The sealed power transmission circuit device 800 may further include a memory 870 in wired data communication with the controller 880, AFPD 840 and VID 850 inside the seal, wherein the memory 870 is configured to receive and store signal data from the two detectors 840 and 850 and provide signal data from the two detectors 840 and 850 to the controller 880. The memory 870 is capable of storing the complete state of the device 800 for a series of continuous instantaneous times.

The tuning network may further include one or more of a compensation network, a matching network, and a filter. The compensation network 26E, the matching network 26D, and the filter 26C of FIG6 are suitable for this purpose, and the selection is not limited to the device of FIG6.

The sealed power transmission circuit device 800 may include a controller 880 within the sealed interior. In other embodiments, the sealed power transmission circuit device 800 may employ an external controller having suitable input/output facilities to communicate data with the various circuits incorporated within the sealed interior of the device 800, and suitable software or firmware may be programmed into the controller to perform all of the control program steps described above.

The sealed power delivery circuit device 800 may further include at least one communication circuit 890 that operates on one or more of Bluetooth, WiFi, Zigbee, and cellular technologies to bidirectionally transmit information between the controller 880 and devices external to the sealed power delivery circuit device 800. The at least one communication circuit 890 may be in bidirectional wired communication with one or more suitable antennas 894. Although the one or more antennas 894 may be disposed within the sealed interior of the device 800, it is typically more efficient for such antennas to be disposed outside the device 800. One or more of the external devices may be other power delivery circuit devices, including, for example, other devices 800, and one or more of the other devices may form part of a collective power delivery system as described above in other embodiments (e.g., FIG. 1 ).

The PFDCA circuit can be arranged to adjust the duty cycle of the RF oscillation signal based on the measurements made by the AFPD 840 and the VID 850. In some embodiments, information about the measurements can be transmitted to the controller 880 and from the controller to the PFDCA circuit 820, which then adjusts the duty cycle of the RF oscillation signal based on the information received. In other embodiments not shown in FIG. 32, feedback signals can be directly transmitted from the AFPD 840 and the VID 850 to the PFDCA circuit 820, which then adjusts the duty cycle of the RF oscillation signal based on the received feedback signals. By changing the duty cycle of the RF oscillation signal, the PFDCA circuit 820 can adjust the direction of power flow through the device 800. As power flows from the DC source/load 700 through the device 800 to the AC load/source 900, the PFDCA circuit 820 can thereby regulate the DC power delivered by the source/load 700 to the device 800 and the AC power delivered from the device 800 to the AC load/source 900. As power flows from the AC load/source 900 through the device 800 to the DC source/load 700, the PFDCA circuit 820 can thereby regulate the AC power delivered by the C load/source 900 to the device 800 and the power delivered by the device 800 to the DC source/load 700.

The controller 880 can perform two-way wired communication with external devices and circuits 898 (labeled as Ext. in FIG. 32 ) disposed outside the sealed interior of the device 800. For example, without limitation, such wired communication can be used to exchange data with a system in which the device 800 can be incorporated or to supply a system clock synchronization signal to the controller 880.

6 and 7, sensors and detectors 24A, 24B, 24C and 24D may be effectively disposed outside of the sealed interior of device 800.

The bidirectional power transmission circuit device 800 can also be effectively used to transmit and/or receive information via a power channel passing through the device 800 by the mechanism already explained above with reference to FIGS. 6 and 7. The power channel physically extends from the wired connection between the DC source/load 700 and the PM circuit 860 through the PM circuit 860, the VID 850, the MPS device 810 and the tuning network 830 to the AC load/source 900. Along the physical power channel, the PM circuit 860, the MPS device 810 and the tuning network 830 are all under the control of the controller 880, which controls the MPS device 810 via the PFDCA circuit 820. The controller can modulate the RF power signal in the tuning network 830 and/or in the MPS device 810 itself. The controller can also be configured to sense modulation of the DC voltage between the PM circuit 860 and the DC source/load 700. This allows information to be modulated onto the RF power signal, the tuned RF power signal, and/or the aforementioned DC voltage, and thereby transmitted to other devices external to the device 800. Such other devices may include other bidirectional power transmission circuit devices 800. Information can be modulated onto the RF power signal, the tuned RF power signal, and/or the aforementioned DC voltage in digital form or in analog form. In other embodiments, the information can be modulated onto a frequency different from the frequency of the power transmission. In other embodiments, the information can be modulated onto a harmonic of the frequency of the power signal. In yet a further embodiment, the frequency of the RF power signal may be a harmonic of the frequency of the signal onto which the information is modulated. In the foregoing, it has been explained how the tuning network 830 subsystem may be used as a suitable modulator.

Having explained above how the device 800 can be reconfigured between operating in a transmitter mode and operating in a rectifier mode, and having explained how the power channel can be modulated, it is apparent that the device 800 can be used as a full duplex transmit-receive system that transmits information in both directions. When two devices 800 are employed in the transmitter module 20 and the receiver module 40 of FIG. 1 , the system 10 of FIG. 1 can include additional secondary sides similar to the secondary side 14 of FIG. 1 . When additional secondary sides 14 are present, the arrangement explained above allows information to be transmitted between the various secondary sides 14 and thereby to the primary side 12. By using the device 800 of Fig. 32, the transmitter module 20" and the receiver module 40" used in the system of Figs. 19A and 19B can have the same full-duplex transmit-receive configuration. The same is true for the systems shown in Figs. 20A to 22B and Figs. 27A to 28B.

The information transmitted in the manner described herein may include, without limitation, the operating mode of the MPS device 810, the number and type of other devices 810, surrounding object sensor information, and load status monitoring information including, for example, battery charge status, load voltage, and load current.

The electronic circuitry of the sealed bidirectional power delivery circuit device 800 can be implemented in a variety of device fabrication technologies, including without limitation as multiple discrete devices suitable for a circuit board, as a hybrid circuit in which devices fabricated in different individual sections of semiconductor material can be bonded or mounted to a suitable substrate material, as a flip chip configuration with an active face down bonded to one or more individual devices on a silicon-based circuit, or as a single monolithic integrated circuit device. FIG33 illustrates a flip chip arrangement in which the bidirectional power delivery circuit device 800 of FIG32 includes a multi-terminal power switch (MPS) device 810 implemented in a separate semiconductor die and then flip chip mounted via solder bumps on pads 808. For example, without limitation, the MPS device 810 may be fabricated as a discrete higher power device in a wide bandgap semiconductor crystal. Pads 808 are formed on silicon wafer 801, which also contains the balance of the subsystems of the device 800 of FIG. 32, all monolithically integrated into silicon wafer 801. Two pads 806 are used for connection to the DC source/load 700 and AC load/source 900 shown in FIG. 32. Pads 802 are used to connect the controller 880 and communications circuitry 890 to devices and antennas external to the device 800.

In one particular embodiment as shown in FIG. 34A , the electronic circuitry of a sealed bidirectional power transfer circuit device 800 may be implemented within a single silicon single crystal wafer 812 in conjunction with at least one photovoltaic cell 814 used as the DC source/load 700 of FIG. 32 .

In yet another embodiment further explained with reference to FIG. 34B , as described above, the electronic circuitry of the sealed bidirectional power transmission circuit device 800 can be implemented in conjunction with at least one photovoltaic cell 814 used as the DC source/load 700 of FIG. 32 , and a resonator structure 180′ of the type described with reference to FIG. 2B and described in more detail with reference to FIGS. 2A to 5 (used as an AC load/source 900 on one surface of the silicon single crystal wafer 812). An antenna 894 for Bluetooth, WiFi, Zigbee, and cellular technologies can also be integrated on the same single silicon single crystal wafer. The antenna 894 is not shown in FIG. 34B . In Figures 34A and 34B, connection 818 connects resonator 180' and tuning network 830 of device 800. Resonator 180' can be used as a heat sink or heat dissipator for heat generated in device 800 or absorbed by photovoltaic cell 814. To this end, resonator 180' can use air as a dielectric and as a coolant fluid at the same time.

In other embodiments, the DC load 70" of FIGS. 19A and 19B may be replaced with an AC load 70"" in both cases, as shown in FIGS. 35A and 35B, respectively. The remainder of the systems 10" and 410 of FIGS. 35A and 35B may be the same as the systems 10" and 410 of FIGS. 19A and 19B. The oscillator 26A" of FIGS. 19A and 19B may be set to the desired frequency and phase of the AC load 70"" of FIGS. 19A and 19B. In other embodiments, the transmitter controller 22" may be programmed to set the oscillator 26A" to the desired frequency and phase of the AC load 70""

In yet other embodiments of the system of FIGS. 35A and 35B , the AC load 70 ′″ may be a power grid to which the system of FIGS. 35A and 35B is configured to deliver power. In this power grid supply configuration, it is important to control the frequency, phase, and voltage level of the signal fed back from the system of FIGS. 35A and 35B to the power grid 70 ′″ in question. To this end, the information feedback mechanism described above may be used to transmit information about the frequency, phase, and voltage level required by the power grid back to the transmitter controller 22 ′′. This information may be in digital form or in analog form. In certain embodiments of the wired system of FIG. 35B , an additional signal line (not shown to avoid confusion) may be connected from the AC grid 70′″ to the transmitter controller 22″ or directly to the oscillator 26A″ to allow the transmitter module 20″ to directly track the frequency and phase of the AC load 70′″ and thereby impose the constraints required by the grid 70′″ on the output signal of the system of FIG. 35B . Such constraints may include modulating the output signal of the load management system 46E″ to meet the requirements of the grid 70′″. The modulation may be performed at a frequency equal to that of the grid and at a phase and voltage level at which power is delivered to the grid 70′″.

FIG36 shows an embodiment of the system of FIG32 in which the AC load/source 900 of FIG32 is an AC grid 900′. In this embodiment, as with the systems of FIG35A and FIG35B, information regarding the frequency, phase, and voltage level required by the grid may be transmitted back to the controller 880. This allows the controller 880 to adjust the signal at the control terminals of the MPS device 810 via the phase, frequency, and duty cycle adjustment (PFDCA) circuit 820 to meet the power delivery requirements imposed by the grid 900′. Such requirements may include modulating the output signal of the tuning network 830 to meet the requirements of the grid 70′″. The modulation may be performed at a frequency equal to that of the grid and at a phase and voltage level that delivers power to the grid 70′″. Although inherently bidirectional, the system of Figure 3 can be used in this arrangement as a means of delivering power to the AC grid.

Returning now to FIGS. 20A and 20B, 21A and 21B, and 22A and 22B, each solar cell 420 may be provided with a sensor to determine the operating state of the solar cell 420. The operating state may include, without limitation, power levels, voltage levels, current levels, temperature, and other performance parameters. This information about the operating state may be transmitted to the receiver module 40" via the transmitter module 20" associated with the solar cell 420. The operating state of the transmitter module 20" may similarly be sensed and transmitted to the receiver module 40" via the transmitter module 20". 33 and 34A and 34B, suitable sensors may also sense performance parameters of the sealed bidirectional power transfer circuit device 800 and the multi-terminal power switching (MPS) device 810. It has been described that load information is transmitted via the MPS device 810. Information regarding performance parameters of the devices 800 and 810 may similarly be transmitted through the system.

37A and 37B illustrate two configurable bidirectional power transfer systems for transferring power from a DC source according to certain embodiments. FIG. 37C and FIG. 37D illustrate multiple different embodiments of configurable power transfer systems for transferring power between a DC source and a variable load. The variable load may be an AC load (in the case of both FIG. 37A and FIG. 37B ), a DC load ( FIG. 37B ), or a load carrying a mixture of AC and DC power ( FIG. 37B ).

FIG. 37A shows a system 950 for transmitting power between a DC source 1028 and an AC load/source 1070, the system being used to transmit power from the DC source to an AC grid operating at a typical line frequency of about 50 Hz or about 60 Hz. The system 950 can also be configured to transmit power in the opposite direction. As with FIGS. 19A , 19B , 35A , and 35B , the system 950 of FIG. 37A is based on the controlled functionality of self-synchronous RF rectifiers/amplifiers 1025A and 1025B, which can be reconfigured between amplifier mode and rectifier mode. These devices 1025A and 1025B can be the same or similar to the self-synchronous RF rectifier/amplifier 26B of FIGS. 6 and 8 and the rectifier 46D of FIGS. 7 and 9 . Devices 1025A and 1025B may include switched-mode self-synchronous RF rectifier/amplifiers.

In a first embodiment, a central controller 1080 is employed. The controller 1080 may include protection circuitry for the system. In other embodiments, distributed controllers may be used for the same purpose. When power is delivered from the DC source/load 1028, the devices 1025A and 1025B are placed in an amplification mode, and their switching action is driven by a switching signal provided by a high-frequency switching signal generator 1024. The high-frequency switching signal generator 1024 provides the switching signal frequency that drives the devices 1025A and 1025B, controls the switching duty cycle of the devices 1025A and 1025B, and ensures that the switching modes of the devices 1025A and 1025B have a controlled mutual phase and pulse width relationship.

In the systems of Figures 37A and 37B, a high frequency switching signal generator 1024 supplies a switching signal to each of devices 1025A and 1025B. In more general systems (such as those described below with respect to Figures 37C and 37D), a high frequency switching signal generator similar to high frequency switching signal generator 1024 can provide switching signals to multiple pairs of self-synchronous RF rectifiers/amplifiers. The number of high frequency switching signal generators used in any embodiment can vary. For example, a high frequency switching signal generator can provide a switching signal to a pair of self-synchronous RF rectifiers/amplifiers. A high frequency switching signal generator can provide a switching signal to a plurality of pairs of self-synchronous RF rectifiers/amplifiers.

The high frequency switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous RF rectifier/amplifier 1025A (in amplifier mode) with a first switching signal having a first frequency of f _A. At the same time, the high frequency switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous RF rectifier/amplifier 1025B (in amplifier mode) with a second switching signal having a second frequency of f _B , wherein: f _B = f _A + ∆f … (Equation 1), In equation 1, the difference frequency ∆f between the frequencies of the second switching signal and the first switching signal is twice the frequency at which the power to be delivered is to be supplied to the AC load/source 1070.

In embodiments where the AC load/source 1070 does not carry a power signal in the absence of the system 950, the frequencies _fB and _fA , and thereby the difference frequency ∆f, may simply be set in or by the high frequency switching signal generator 1024. The frequencies _fB and _fA may differ from each other by a difference frequency ∆f that is twice as large as the frequency of the power signal intended to be injected into the AC load/source 1070. In certain embodiments, the frequencies _fB and _fA may be set in the high frequency switching signal generator 1024 by the controller 1080 based on design choice.

In other embodiments where there is an existing AC power signal in the AC load/source 1070 (such as in a residential electrical grid), the frequencies f _B and f _A of the switching signals can be set in the high frequency switching signal generator 1024 by sensing the operating frequency f _L of the AC load/source 1070, and a reference signal of frequency f _L is transmitted to the high frequency switching signal generator 1024 via an optional isolator system 1090 and a phase-locked loop 1095. In this specification, the term "load information circuit" is used to describe a section of the circuit. To distinguish this additional circuit portion from the circuit portion used when there is no existing power signal in the AC load/source 1070, this load information circuit and its components are shown in dashed lines in Figure 37A. The direction of reference signal flow in this circuit is given by the arrows in Figure 37A. In some cases, an optional isolator system 1090 may be included for certain areas. When the load is not carrying a power signal, certain areas may need to be isolated from the AC load/source 1070 by conditioning. The optional isolator system 1090 may include an air gap. Those skilled in the art will recognize how to use isolators to provide data and timing signals, and the details are not explained herein. In other embodiments, instead of using a reference signal, information about at least one of the DC level, frequency, and phase of the power signal in the load may be transmitted to the high frequency switching signal generator 1024.

The high frequency switching signal generator 1024 may multiply the sensed frequency f _L to determine the desired difference frequency ∆f between the frequencies f _B and f _A and apply the switching signal to the devices 1025A and 1025B at the resulting frequencies f _B and f _A. In this embodiment, the process of sensing the operating frequency f _L of the AC load/source 1070, transmitting the signal to the high frequency switching signal generator 1024, and multiplying the operating frequency f _L may all be performed under the control of the controller 1080. To avoid cluttering FIG. 37A, the control lines extending from the controller 1080 to the devices it senses or controls (including the devices 1025A and 1025B) are not shown. It should be noted that the frequencies f _B and f _A of the switching signals only need to differ by ∆f = 2f _L . The difference frequency ∆f can be obtained according to the above equation 1. Two suitable frequencies f _B and f _A which differ from each other by ∆f=2f _L can be determined in the high frequency switching signal generator 1024. The arrangement described herein helps the power supplied from the DC source 1028 to be in phase with the grid load, thereby allowing efficient power transmission.

In some embodiments, the switching signals driving devices 1025A and 1025B can be selected to be in the range between 1 MHz and 1 GHz. In some embodiments, the first switching signal and the second switching signal of system 950 can be selected to be in the range between 100 kHz and 1 GHz. In some embodiments, the signals can be selected to be in the ISM band previously described in the present invention. The term "high frequency" (high frequency) is used herein to describe frequencies between approximately 100 Hz and 1 Hz. Devices 1025B and 1025A can transmit any power drawn from the DC source/load 1028 at frequencies f _B and f _A , respectively, to the switching mode rectifier 1067 via the high frequency power link system 1065. The operation of the rectifier 1067 can be controlled by the controller 1080 using control lines, which are not shown in Figure 37A for clarity.

The high frequency power link system 1065 can be wired or wireless. In some embodiments, the high frequency power link system 1065 can be a near field wireless link. In some embodiments, the high frequency power link system 1065 can be a near field dual peak wireless link. Such various high frequency links have been previously described in the present invention. The near field dual peak wireless link is described in detail with reference to Figures 1 to 10, Figures 19A and 19B, and Figures 32 to 36. In view of the intentionally lower quality factor Q of the bimodal link described above, the power signals emitted from devices 1025B and 1025A at frequencies f _B and f _A , respectively, can be transmitted simultaneously in a near-field bimodal wireless link.

Internally, the high frequency power link system 1065 may include a single high frequency wireless receiver module of the type described with reference to FIG. 7 that communicates with one or more high frequency wireless transmitter modules of the type described in FIG. 6 . In some embodiments, the high frequency power link system 1065 may include a single receiver module of the type described with reference to FIG. 19B that is configured to receive power transmitted by wires from one or more transmitter modules of the type described in FIG. 19B . In some embodiments, the high frequency power link system 1065 may have a single transmitter module and a single receiver module as required by the system described in FIG. 37A . Even though there may be only a single transmitter module in the high frequency power link system 1065, the transmitter module can be driven differentially by the two self-synchronous RF rectifier/amplifiers 1025A and 1025B. In particular, in photovoltaic systems, it can be useful to employ multiple transmitter modules to transmit power to a single receiver, as has been described with reference to FIGS. 20A and 20B.

The system of FIG. 37A requires only one pair of self-synchronous RF rectifier/amplifiers 1025A and 1025B. Each of devices 1025A and 1025B is shown as having one signal line entering the high frequency power link system 1065. In other embodiments to be discussed later below, there may be other pairs of self-synchronous RF rectifier/amplifiers. These devices may operate at the same or different frequencies as the devices 1025A and 1025B of FIG. 37A. It will be clear to practitioners in the art that feeding two signals of the same frequency and phase from two self-synchronous RF rectifier/amplifiers will not require a separate wiring to enter the high frequency power link system 1065, and the same physical wiring may be used. To reduce the number and complexity of the drawings in this specification, a separate wiring for each self-synchronous RF rectifier/amplifier will be shown, even though the signals from two separate self-synchronous RF rectifier/amplifiers can be the same.

The high frequency power link system 1065 of FIG37A mixes two high frequency signals of frequencies f _B and f _A on its receiving side to produce a transmitted power signal modulated at frequency ∆f/2, which is transmitted together with various overtone frequencies resulting from nonlinearity, noise, and other non-sinusoidal factors in the components including devices 1025B and 1025A. Since the high frequency power link system 1065 is a tuned system, all of these signals except the carrier signal modulated at the difference frequency ∆f can be filtered on the receiving side of the high frequency power link system 1065. The rectifier 1067 and expansion circuit 1069 also further ensure that only modulation at the difference frequency ∆f passes through the system 950 to reach the load/source 1070.

FIG38 shows a waveform of a signal generated by the rectifier 1067 of the system 950 in FIG37A for transmission to the AC load/source 1070. The rectified power signal generated by the rectifier 1067 is in the form of a series of adjacent half-waves 1048 having the same polarity and a frequency equal to the difference frequency ∆f. The rectified power signal is received by the spreading circuit 1069, and each second half-wave is inverted to form a substantially sinusoidal spread output power signal 1049 at a frequency of ∆f/2. The action of the spreading circuit 1069 can be controlled by the controller 1080 via control lines, which are not shown in FIG37A to avoid clutter. The term "spread output power signal" is used to describe the power signal provided by the spreading circuit 1069 to the AC load/source 1070.

In the event that the AC load/source 1070 is not carrying an existing power signal in the absence of the system 950, the high frequency switching signal generator 1024 can trigger the operation of the development circuit 1069 to ensure that its development operation is synchronized with the power signal from the rectifier device 1067.

In the event that a power signal is present in AC load/source 1070 in the absence of system 950, a reference signal from AC load/source 1070 at operating frequency f _L is optionally routed directly from AC load/source 1070 and used to trigger operation of deployment circuit 1069 to ensure that its deployment operation is synchronized with the power signal from device 1067. In FIG. 37A , the dashed line extending directly from AC load/source 1070 back toward deployment circuit 1069 represents this route of the reference signal from AC load/source 1070 toward deployment circuit 1069. The term “power signal conversion circuit” is used to describe the combination of devices 1067 and 1069.

It has been explained in the previous section of this document how a power transfer system of the general type discussed herein can be employed to transfer power in a direction opposite to that which has been explained directly above. For this operation, devices 1025A and 1025B are set to their rectifier mode and switching mode, and rectifier 1067 is switched to a normally open mode, wherein the input of device 1067 is directly connected to its output. This mode setting can be performed by controller 1080 via control lines to those devices. It has been explained how a link of devices 1065 of this type can transfer power in a direction opposite to that explained above. The same is true for devices 1025A and 1025B. The net effect is to transfer power from AC load/source 1070 to DC load/source 1028.

Furthermore, as has been explained previously in this document, information about the source side and the load side can be transmitted directly between the source and the load on the actual power signal, or can be obtained by the controller 1080 for the purpose of controlling the system. In certain embodiments where the transmit side and the receive side of the system 950 are physically separated and housed, the transmission of information via the power signal can be important. This can be useful when the high frequency power link system 1065 is a wireless link.

The use of high frequency to transfer power between a DC source and an AC grid results in the use of relatively small high frequency switching devices and creates the opportunity to integrate much of the circuitry into a semiconductor integrated circuit. The implementation of these circuits follows the same lines as presented with respect to FIG. 33 and FIG. 34A and FIG. 34B. Furthermore, in this configuration, total harmonic distortion, such as that resulting from signal conversion, can be controlled and minimized.

FIG. 37B shows another configurable bidirectional power transfer system 950′ for transferring power between a DC source/load 1028 and a load/source 1070′, which in this embodiment can be DC or AC. Elements in FIG. 37B with the same reference numerals as in FIG. 37A are the same as the corresponding elements in FIG. 37A. The system 950′ can also be configured to transfer power in the opposite direction. As with the system described with reference to FIG. 37A, the system 950′ of FIG. 37B is based on the controlled functionality of the self-synchronous RF rectifier/amplifiers 1025A and 1025B that have been described in the preceding text.

In certain embodiments shown in FIG. 37B , a central controller 1080 is employed. The controller 1080 may include protection circuitry for the system. In certain embodiments, a distributed controller may be used for the same purpose. When power is delivered from the DC source/load 1028 , the devices 1025A and 1025B are placed in an amplification mode. The high frequency switching signal generator 1024 provides a common switching frequency f _C for the devices 1025A and 1025B and controls the switching duty cycle of the devices 1025A and 1025B and ensures that the switching patterns of the devices 1025A and 1025B have a controlled mutual phase and pulse width relationship. In some embodiments, the high frequency switching signal generator 1024 may be used to adjust the relative phase difference between the two switching signals supplied to the devices 1025A and 1025B.

The high-frequency switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous RF rectifier/amplifier 1025A (in amplifier mode) with a first switching signal having a frequency of f _C and a first phase of ɸ1. Simultaneously or substantially simultaneously, the high-frequency switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous RF rectifier/amplifier 1025A (in amplifier mode) with a second switching signal having the same frequency f _C but a different second phase, which is given by the following equation: ɸ2 = ɸ1 + ∆ɸ … (Equation 2), where ∆ɸ is the mutual phase difference between the first switching signal and the second switching signal.

The frequency f _C of the first switching signal and the second switching signal may be set in the high frequency switching signal generator 1024. In some embodiments, the frequency f _C may be set in the high frequency switching signal generator 1024 based on design choice. In some embodiments, the frequency f _C may be set in the high frequency switching signal generator 1024 to a frequency f _C that is preferred for the high frequency power link system 1065. However, in the case of the system 950 shown in FIG37A, the frequencies f _A and f _B are at least partially related to the load frequency via their difference frequency ∆f, and the frequency f _C of the system 950′ of FIG37B is not based on the frequency of any signal in the AC/DC load/source 1070′. In contrast, in the case of system 950′ of FIG. 37B , the high frequency switching signal generator 1024 imposes a mutual phase difference ∆ɸ on the first switching signal and the second switching signal based on information obtained from the load/source 1070′.

Power is extracted from a DC source/load 1028 at a frequency f _C by differential self-synchronous RF rectifiers/amplifiers 1025A and 1025B to generate two independent high-frequency power signals whose frequencies f _C and phases differ by an adjustable mutual phase difference ∆ɸ. The high-frequency power link system 1065 mixes the two high-frequency power signals from the differential self-synchronous RF rectifiers/amplifiers 1025A and 1025B at its receiving side during its operation to generate a transmitted power signal. Under the control of the high-frequency switching signal generator 1024, the transmitted power signal at a frequency f _C has an amplitude determined by the phase difference ∆ɸ between the first switching signal and the second switching signal. In the frequency domain, it further includes various overtone frequencies resulting from nonlinearity, noise, and other non-sinusoidal factors in the components including devices 1025B and 1025A. Since high frequency power link system 1065 is a tuned system, it can filter out all signals except the power signal transmitted at frequency _fC .

If the phase difference ∆ɸ is not adjusted, a transmitted power signal having a fixed amplitude at frequency f _C is generated. By adjusting the phase difference ∆ɸ between the first switching signal and the second switching signal, the amplitude of the signal generated by the high frequency power link system 1065 described with reference to FIG. 37A can be adjusted. The high frequency switching signal generator 1024 can be configured to adjust the phase difference based on the type of load and its instantaneous charge level to provide a charging signal to the load. This charging level can be set and controlled via the controller 1080. To this end, the controller may provide coarse settings appropriate for the type or technology of load/source 1070′ (e.g., Ni—Cd, lithium ion, etc.), as well as fine settings to control the charging process for the selected load type based on, for example, the percentage of charge depleted in the load.

In the case where the load/source 1070′ is an AC load, the same system 950′ can be operated to deliver power to the load/source 1070′ in AC form. By modulating the phase difference ∆ɸ at a predetermined phase modulation frequency f _M in the high-frequency switching signal generator 1024, the AC power can be delivered to the load/source 1070′. Thus, in general, by appropriately controlling the phase difference ∆ɸ via the high-frequency switching signal generator 1024, power can be delivered from the DC source/load 1028 to the load/source 1070′ as a DC and/or AC power signal with adjustable magnitude and polarity.

Next, consider the modulation of the phase difference ∆ɸ between the first switching signal and the second switching signal and the pre-determination of the phase modulation frequency f _M. In embodiments where an existing AC power signal is present in the AC/DC load/source 1070′ (such as in a residential power grid), the pre-determined phase modulation frequency f _M can be set in the high-frequency switching signal generator 1024 by sensing the operating frequency f _L of the load/source 1070′ and transmitting a reference signal having a frequency f _L to the high-frequency switching signal generator 1024 via the optional isolator system 1090 and the phase-locked loop 1095. In this specification, the term “load information circuit” is used to describe this section of the circuit. In order to distinguish this additional circuit portion from the circuit portion used when there is no existing AC power signal in the load/source 1070', this load information circuit and its components are shown in dashed lines in Figure 37B. The direction of reference signal flow in this circuit is given by the arrows in Figure 37B. In some cases, such as without limitation, when the load/source 1070' is a DC load/source, an optional isolator system 1090 may be included. When the load does not carry a power signal, certain areas may also specifically need to be isolated from the AC load/source 1070 by conditioning. The optional isolator system 1090 may include an air gap. Methods for providing data and timing signals via isolators are well known in the art and will not be expanded upon herein.

The high frequency switching signal generator 1024 can determine the phase modulation frequency f _M based on the sensed operating frequency f _L of the AC/DC load/source 1070 ′ and apply this modulation to the phase difference ∆ɸ between the first switching signal and the second switching signal supplied to the devices 1025A and 1025B, respectively. In some embodiments, the process of sensing the operating frequency f _L of the AC load/source 1070 ′, transmitting the signal to the high frequency switching signal generator 1024, and determining the phase modulation frequency f _M can all be performed under the control of the controller 1080. To avoid cluttering FIG. 37B , control lines extending from the controller 1080 to the devices it senses or controls (including devices 1025A and 1025B) are not shown. The power supplied from the DC source 1028 can be kept in phase with the power signal in the AC/DC load/source 1070', thereby allowing efficient power transfer. This will be further explained below.

The first switching signal and the second switching signal of the system 950' for driving the devices 1025A and 1025B can be selected to be in the range between 1 MHz and 1 GHz. In some embodiments, the first switching signal and the second switching signal of the system 950' can be selected to be in the range between 100 kHz and 1 GHz. In some embodiments, the signals can be selected to be in the ISM band previously described in the present invention. The devices 1025B and 1025A can transmit any power they extract from the DC source/load 1028 at a frequency f _C to the switching mode rectifier 1067 via the high frequency power link system 1065. The switching mode rectifier 1067 can have an arrangement that is the same or similar to the arrangement shown in FIG. 37A. The operation of the rectifier 1067 may be controlled by the controller 1080 using control lines which are not shown in FIG. 37B for clarity.

The high frequency power link system 1065 can be wired or wireless. In some embodiments, the high frequency power link system 1065 can be a near field wireless link. In some embodiments, the high frequency power link system 1065 can be a near field dual peak wireless link. Such various high frequency links have been previously described in the present invention. The near field dual peak wireless link is described in detail with reference to Figures 1 to 10, Figures 19A and 19B, and Figures 32 to 36. In view of the intentionally lower quality factor Q of the dual-peak link described above, power signals with phases ɸ1 and ɸ2 emitted from devices 1025A and 1025B, respectively, at frequency f _C can be transmitted simultaneously in a near-field dual-peak wireless link.

As previously stated, the high frequency power link system 1065 may internally include a single high frequency receiver module of the type described with respect to Figures 7 and 19B, which communicates with one or more high frequency transmitter modules of the type described in Figures 6 and 19B. As with Figure 37A, the high frequency power link system 1065 of Figure 37B may have a single high frequency receiver module and a single transmitter module differentially driven by devices 1025A and 1025B.

In the case of the system 950' of FIG. 37B, as with the system 950 of FIG. 37A, the rectified power signal produced by the rectifier 1067 can be in the form of a series of adjacent half-waves of the same polarity. The rectified power signal is received by the spreading circuit 1069, and each second half-wave is inverted to form a substantially sinusoidal spread output power signal at the frequency of the signal in the load (if present). As with the system 950, the term "spread output power signal" is used to describe the power signal provided by the spreading circuit 1069 to the AC load/source 1070.

In the absence of a load/source 1070′ in the system 950′ and without carrying an existing power signal, the high frequency switching signal generator 1024 can trigger the operation of the development circuit 1069 to ensure that its development operation is synchronized with the power signal from the rectifier device 1067.

In the event that a power signal is present in load/source 1070′ in the absence of system 950′, a reference signal from load/source 1070′ at operating frequency f _L is optionally routed directly from load/source 1070′ and used to trigger operation of deployment circuit 1069 to ensure that its deployment operation is synchronized with the power signal from device 1067. In FIG. 37B , the dashed line extending directly back from load/source 1070′ toward deployment circuit 1069 represents the route of the reference signal from load/source 1070′ toward deployment circuit 1069. The term “power signal conversion circuit” is used to describe the combination of devices 1067 and 1069.

It has been explained in the previous section of this document how a power transmission system of the general type discussed herein can be employed to transmit power in a direction opposite to that which has been explained above. For this operation, devices 1025A and 1025B are set to their rectifier mode and switching mode, with rectifier 1067 switched to a normally open mode. This mode setting can be performed by controller 1080 via control lines to those devices. In certain embodiments, it has been explained how a link of devices 1065 of the type described herein can transmit power in a direction opposite to that which has been explained above. The same is true for devices 1025A and 1025B. The net effect is that power is transmitted from load/source 1070′ to DC source/load 1028.

Furthermore, as has been explained previously in this document, information about the source side and the load side can be transmitted directly between the source and the load on the actual power signal, or can be obtained by the controller 1080 for the purpose of controlling the system. In those embodiments where the transmit side and the receive side of the system 950' are physically separated and accommodated, the information transmission via the power signal can be important. This can be useful when the high frequency power link system 1065 is a wireless link.

The use of high frequencies to transfer power between a DC source and an AC grid results in a requirement for a smaller size of the high frequency switching device and creates an opportunity to integrate most of the circuitry into a semiconductor integrated circuit. The implementation of these circuits follows the same lines as already presented with respect to FIG. 33 and FIG. 34A and FIG. 34B. Furthermore, in this arrangement, the total harmonic distortion resulting, for example, from the signal conversion can be controlled and minimized.

37A and 37B present power transfer systems 950, 950' for transferring power between a DC source 1028 and a variable load 1070, 1070'. The systems 950 and 950' are identical in structure, but differ in the two embodiments as to how they are functionally applied, as to the nature of the signals generated and applied, and whether the power is transferred to an AC load or a DC load. A first self-synchronous RF rectifier/amplifier 1025A and a second self-synchronous RF rectifier/amplifier 1025B are configured to extract a first high frequency (HF) power signal and a second high frequency (HF) power signal from a DC source 1028 at a first high frequency frequency and a second high frequency frequency, respectively. The high frequency power link system 1065 is configured to receive and mix the first high frequency power signal and the second high frequency power signal to generate a transmitted power signal. The power signal conversion circuit in communication with the high frequency power link system 1065 and the variable load 1070, 1070' is configured to generate an output power signal from the transmitted power signal and supply the output power signal to the variable load 1070, 1070'.

The power transmission system 950, 950' further includes a high-frequency switching signal generator 1024, which is configured to supply a first switching signal and a second switching signal to a first rectifier/amplifier 1025A and a second rectifier/amplifier 1025B at respective first high-frequency frequencies and second high-frequency frequencies, and to establish and control a mutual phase relationship between the first switching signal and the second switching signal.

The power signal conversion circuit includes: a switching mode rectifier 1067, configured to receive a transmitted power signal from a high-frequency power link system 1065, and to rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit 1069, configured to receive the rectified power signal from the switching mode rectifier and to expand the rectified power signal to generate an output power signal.

The first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B can be configured to operate in a rectification mode, and the switching mode rectifier 1067 can be configured to operate in a normally open mode, thereby allowing power to be extracted from the variable load 1070, 1070' and transmitted to the DC source 1028 via the power signal conversion circuit (element 1067 and element 1069) and the high-frequency power link system 1065.

The spreading circuit may be configured to receive a reference signal from the variable load 1070, 1070' to spread a rectified power signal synchronized with the signal in the variable load 1070, 1070'. The power signal conversion circuit (element 1067 and element 1069), the high frequency power link system 1065, and the plurality of pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B may be configured to transmit control information from the rest of the system 950, 950' to the high frequency switching signal generator 1024. The system 950, 950' may further include one or more controllers 1080 in data communication with the plurality of components of the system 950, 950' and configured to control the plurality of components. The system 950, 950' may further include an isolable load information circuit configured to communicate information about at least one of a DC level, a frequency, and a phase of a power signal in the variable load 1070, 1070' to the high frequency switching signal generator 1024. The load information circuit may include a phase locked loop 1095. The load information circuit may further include an isolator system 1090, and the isolator system 1090 may include an air gap.

The high frequency power link system 1065 of the system 950, 950' may include a wireless power link system. The wireless high frequency power link system 1065 may include a dual peak wireless high frequency power link system. The high frequency power link system 1065 may include a wired power link system.

In two phase difference based implementations of the power transmission system 950′ specific to FIG. 37B , the first high frequency and the second high frequency are the same frequency; and the first switching signal and the second switching signal have a mutual phase difference that can be adjusted by the high frequency switching signal generator 1024.

In the first phase difference based implementation, the high frequency switching signal generator 1024 is configured to adjust the mutual phase difference between the first switching signal and the second switching signal based on the DC level in the variable load 1070′, thereby generating the transmitted power signal from the high frequency power link system 1065 as a DC signal correspondingly adjusted in amplitude.

In a second phase difference based implementation, the high frequency switching signal generator 1024 is configured to modulate the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load 1070′, thereby generating a transmitted power signal from the high frequency power link system 1065 as an AC power signal modulated at the frequency of the power signal in the variable load 1070′. The modulation can be based at least in part on a modulation function at the phase modulation frequency, the modulation function including, for example, a sawtooth function.

In a frequency difference based implementation of the power transmission system 950 specific to FIG. 37A , the first high frequency frequency and the second high frequency frequency differ by a difference frequency ∆f. In this implementation, the high frequency switching signal generator 1024 is configured to determine the first high frequency frequency and the second high frequency frequency, and set the difference frequency ∆f to multiply the frequency of the power signal in the variable load 1070. The high frequency power link system 1065 is configured to generate the transmitted power signal at the difference frequency ∆f, and the power signal conversion circuit (components 1067 and 1069) is configured to supply the output power signal to the variable load 1070 at the frequency of the power signal in the variable load 1070.

Referring to FIG. 39 , a method [2300] for transmitting power between a DC source 1028 and a variable load 1070, 1070′ is provided, the method comprising: [2310] extracting a corresponding first high frequency (HF) power signal and a second high frequency (HF) power signal from the DC source 1028 at a first high frequency and a second high frequency via a corresponding first self-synchronous RF rectifier/amplifier 1025A and a second self-synchronous RF rectifier/amplifier 1025B; [2320] transmitting a corresponding first high frequency (HF) power signal and a second high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2321] transmitting a corresponding first high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency via a corresponding first self-synchronous RF rectifier/amplifier 1025A and a second self-synchronous RF rectifier/amplifier 1025B; [2322] transmitting a corresponding first high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2323] transmitting a corresponding second high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2324] transmitting a corresponding first high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2325] transmitting a corresponding first high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2326] transmitting a corresponding first high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2327] transmitting a corresponding second high frequency (HF) power signal to the DC source 1028 at a first high frequency and a second high frequency; [2330] transmitting a corresponding first high frequency (HF) 5 receives and mixes the first high frequency power signal and the second high frequency power signal to generate a transmitted power signal; generates an output power signal from the transmitted power signal in a power signal conversion circuit (components 1067 and 1069 in Figures 37A and 37B) that communicates with the high frequency power link system 1065 and the variable loads 1070, 1070'; and supplies the output power signal to the variable loads 1070, 1070' (see steps [2334], [2339] and [2344] in Figure 39).

The method may further include: generating a first switching signal and a second switching signal in a high-frequency switching signal generator 1024, and transmitting the first switching signal and the second switching signal to a first rectifier/amplifier 1025A and a second rectifier/amplifier 1025B at respective first high-frequency frequencies and second high-frequency frequencies; and establishing and controlling a mutual phase relationship between the first switching signal and the second switching signal in the high-frequency switching signal generator 1024.

The method may further include: receiving a transmitted power signal from the high-frequency power link system 1065 and rectifying the transmitted power signal in a switching mode rectifier 1067 of the power signal conversion circuit; and receiving a rectified power signal from the switching mode rectifier 1067 and expanding the rectified power signal in an expansion circuit 1069 of the power signal conversion circuit.

The method may further include: setting the first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B to rectification mode; setting the switching mode rectifier 1067 to normally open mode; extracting power from the variable load 1070, 1070'; and transmitting the extracted power to the DC source 1028 via the power signal conversion circuit (element 1067 and element 1069) and the high-frequency power link system 1065.

The method may further include: developing a rectified power signal synchronized with the signal in the variable load 1070, 1070' based on a reference signal from the variable load 1070, 1070'; transmitting the control information from the system to the other components via the power signal conversion circuit (components 1067 and 1069), the high frequency power link system 1065, and the first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B. the remainder is transmitted to the high frequency switching signal generator 1024; multiple components of the system are controlled by one or more controllers 1080 that communicate data with the multiple components; and at least one of the DC level, frequency and phase of the power signal in the variable load 1070, 1070' is transmitted to the high frequency switching signal generator 1024 using an isolable load information circuit including a phase-locked loop 1095 and an optional isolator system 1090.

Transmitting the power signal in the high frequency power link system 1065 may include wirelessly transmitting the power signal. Transmitting the power signal in the high frequency power link system 1065 may include wirelessly transmitting the power signal with a double peak. Transmitting the power signal in the high frequency power link system 1065 may include wirelessly transmitting the power signal with a wire.

Two methods for transmitting power from the DC source 1028 of FIG. 37B to the variable load 1070′ are represented by branch [2330] of FIG. 39 , wherein the power transmission system 950′ employs a phase difference between switching signals. In these embodiments, the first high frequency frequency and the second high frequency frequency of the first switching signal and the second switching signal have the same frequency; and the first switching signal and the second switching signal have a mutual phase difference that can be adjusted by the high frequency switching signal generator 1024.

The first of the two methods includes: adjusting [2332] the mutual phase difference between the first switching signal and the second switching signal based on the DC level in the variable load 1070', thereby generating the transmitted power signal from the high frequency power link system 1065 as a DC signal that is correspondingly adjusted [2334] in amplitude.

The second of the two methods includes modulating [2335] the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load 1070', thereby generating the transmitted power signal from the high frequency power link system 1065 as an AC power signal modulated at the frequency of the power signal in the variable load 1070'. (See steps [2337] and [2339] of Figure 39).

A method for a frequency difference based implementation represented by branch [2340] of FIG. 39 includes: determining a first high frequency and a second high frequency corresponding to a first switching signal and a second switching signal; and setting [2340] a difference frequency ∆f equal to twice the frequency f _L of the power signal in the variable load 1070. The method further includes: generating [2342] a transmitted power signal from the high frequency power link system 1065 at the difference frequency; and supplying [2344] the output power signal to the variable load 1070 at the frequency of the power signal in the variable load.

A series of embodiments using one or more pairs of first and second self-synchronous RF rectifier/amplifiers of the type in Figures 37A and 37B are described below with reference to Figures 37C and 37D. These embodiments differ based on whether the power (i) is delivered from a single DC source or (ii) multiple DC sources or based on whether the embodiment employs (i) a single high frequency switching signal generator or (ii) multiple high frequency switching signal generators of the type described with reference to Figures 37A and 37B. Implementations also differ based on whether they rely on (i) a frequency difference between a first self-synchronous RF rectifier/amplifier and a second self-synchronous RF rectifier/amplifier in a pair, or (ii) a phase difference therebetween (whether modulated, simply adjusted, or not adjusted at all). These implementations are applicable to extracting power from multiple sources to a single variable load in various ways and extracting power from a single source to a single variable load through multiple channels to maintain greater power delivery. These implementations also differ in that some deliver AC power, others deliver DC power, and still others deliver a mixture of AC and DC power to a variable load, which can be an AC load, a DC load, or a load carrying a mixture of AC and DC power. The various implementations can ultimately be reduced to two circuit topologies, namely the circuit topology of FIG37C and the circuit topology of FIG37D. It should be noted that all the self-synchronous RF rectifiers/amplifiers 1025A, 1025B in FIG37C and FIG37D can be the same, and only the switching signals that trigger the self-synchronous RF rectifiers/amplifiers are different between the embodiments.

In Figure 37C, multiple pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B transfer power between a single DC source 1028 and a single variable load 1070'. The actual transfer mechanism and the requirements it imposes on the switching signals to the various self-synchronous RF rectifier/amplifiers 1025A and 1025B in each pair vary between embodiments, as described below.

In FIG37D , multiple pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B transfer power between multiple DC sources 1028 and a single variable load 1070′, with one pair of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B associated with each DC source 1028. The actual transfer mechanism and the requirements imposed on the switching signals to the various self-synchronous RF rectifier/amplifiers 1025A and 1025B in each pair vary between embodiments, as described below.

First, a general description is provided that applies to all implementations associated with both Figures 37C and 37D. The description then proceeds to delve into more specific implementations, first focusing on implementations having the topology of Figure 37C, and then focusing on implementations having the topology of Figure 37D.

37C and 37D, a power transmission system 950C, 950D for transmitting power between at least one DC source 1028 and a variable load 1070' is provided, the system 950C, 950D comprising: at least one pair of first self-synchronous radio frequency rectifier/amplifier 1025A and second self-synchronous radio frequency rectifier/amplifier 1025B, each pair of rectifier/amplifiers configured to transmit power from at least one DC source 1028 at a corresponding first high frequency and a second high frequency, respectively. 28, respectively extracting a pair of corresponding first high frequency (HF) power signals and second high frequency (HF) power signals; a high frequency power link system 1065, configured to receive at least one pair of the first high frequency power signal and the second high frequency power signal and mix the power signals together to generate a transmitted power signal; and a power signal conversion circuit, communicating with the high frequency power link system 1065 and the variable load 1070' (combining element 1067 and element 1069). The power signal conversion circuit is configured to generate an output power signal from the transmitted power signal and supply the output power signal to the variable load 1070'.

The system further includes: one or more high frequency switching signal generators 1024, wherein each of at least one pair of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B is configured to receive a corresponding first high frequency frequency and a second high frequency frequency from a single high frequency switching signal generator in the one or more high frequency switching signal generators 1024. A switching signal and a second switching signal; and each of the one or more high-frequency switching signal generators 1024 is configured to: supply multiple pairs of first switching signals and second switching signals to one or more pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B; and establish and control the mutual phase relationship between the first switching signal and the second switching signal in each pair of switching signals.

It should be noted that, unless otherwise specified, the first switching signals in the plurality of pairs of high-frequency switching signals do not necessarily have the same frequency, and the corresponding first high-frequency power signals in the plurality of pairs of high-frequency power signals do not necessarily have the same frequency. This situation is applicable to the second switching signal in the plurality of pairs of switching signals and the corresponding second high-frequency power signal in the plurality of pairs of high-frequency power signals separately.

As shown in FIG. 37C , in certain embodiments (in this case system 950C), at least one DC source 1028 may be a single DC source 1028; at least one pair of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B may be a plurality of self-synchronous RF rectifier/amplifiers 1025A, 1025B (two pairs in the example of FIG. 37C ) that all communicate with the single DC source 1028; and one or more high-frequency switching signal generators 1024 may be a single high-frequency switching signal generator configured to provide corresponding pairs of first switching signals and second switching signals to a plurality of pairs of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B. In FIG. 37C , the switching signal pair (ψA, ψB) is shown as being provided to a first pair of self-synchronous RF rectifier/amplifiers 1025A, 1025B, and the switching signal pair (ψA′, ψB′) is shown as being provided to a second pair of self-synchronous RF rectifier/amplifiers 1025A, 1025B. The high-frequency power link system 1065 mixes multiple pairs of high-frequency power signals from multiple pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B. The multiple detailed embodiments described below are consistent with the circuit topology described herein with reference to FIG. 37C .

As shown in FIG. 37D , in some embodiments (in this case, system 950D), at least one DC source 1028 may be a plurality of DC sources 1028; at least one pair of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B may be a corresponding plurality of pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B, each pair being connected to the plurality of DC sources. / load 1028 to communicate with the corresponding DC source; and one or more high-frequency switching signal generators 1024 can be a plurality of high-frequency switching signal generators 1024, each of which is configured to provide a corresponding first switching signal and a second switching signal to a corresponding pair of a plurality of pairs of first self-synchronous RF rectifiers/amplifiers 1025A and second self-synchronous RF rectifiers/amplifiers 1025B. In FIG37D, as in FIG37C, the switching signal pair (ψA, ψB) is shown as being provided to the first pair of self-synchronous RF rectifiers/amplifiers 1025A, 1025B, and the switching signal pair (ψA', ψB') is shown as being provided to the second pair of self-synchronous RF rectifiers/amplifiers 1025A, 1025B. The high frequency power link system 1065 mixes a pair of switching signals (ψA, ψB) from the first pair of self-synchronous RF rectifier/amplifiers 1025A, 1025B, and mixes a pair of switching signals (ψA′, ψB′) from the second pair of self-synchronous RF rectifier/amplifiers 1025A, 1025B. When there are additional pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B that output additional pairs of switching signals, each of the additional pairs of switching signals can be mixed by the high frequency power link system 1065 and output separately as power signals transmitted to the expansion circuit 1069. For example, the first pair of switching signals can be mixed (without mixing other pairs of switching signals) to generate a first power signal, the second pair of switching signals can be mixed to generate a second power signal, and so on. The detailed embodiments described below are consistent with the circuit topology described herein with reference to FIG. 37D. This topology circuit configuration is particularly suitable for photovoltaic array panel systems, such as described with reference to FIG. 20A and FIG. 20B.

The power signal conversion circuits 950C and 950D of Figures 37C and 37D may include a switching mode rectifier 1067, configured to receive a transmitted power signal from a high-frequency power link system 1065 and rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit 1069, configured to receive the rectified power signal from the switching mode rectifier and expand the rectified power signal to generate an output power signal.

The first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B in each pair in Figures 37C and 37D can be configured to operate in a rectification mode, and the switching mode rectifier 1067 can be configured to operate in a normally open mode, thereby allowing power to be extracted from the variable load 1070' and transmitted to the DC source 1028 via the power signal conversion circuit (element 1067 and element 1069) and the high frequency power link system 1065.

The expansion circuits (components 1067 and 1069) in FIG. 37C and FIG. 37D can be configured to receive a reference signal from a variable load 1070′ to expand a rectified power signal that is synchronized with the signal in the variable load 1070′. The power signal conversion circuits (components 1067 and 1069), the high frequency power link system 1065, and the plurality of pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B can be configured to transmit control information from the rest of the system 950C, 950D to the at least one high frequency switching signal generator 1024. The system 950C, 950D can further include one or more controllers 1080 that are in data communication with the plurality of components of the system 950C, 950D and are configured to control the plurality of components. The system 950C, 950D may further include an isolable load information circuit configured to communicate information about at least one of a DC level, a frequency, and a phase of a power signal in the variable load 1070′ to the at least one high frequency switching signal generator 1024. The load information circuit may include a phase locked loop 1095. The load information circuit may further include an isolator system 1090. The isolator system 1090 may include an air gap.

The high frequency power link system 1065 of the systems 950C and 950D of FIG. 37C and FIG. 37D may include a wireless power link system. The wireless high frequency power link system 1065 may include a dual peak wireless high frequency power link system. The high frequency power link system 1065 may include a wired power link system.

In the three phase difference based implementations described directly below, the first high frequency frequency and the second high frequency frequency in each pair of high frequency frequencies can be the same frequency, and the first switching signal and the second switching signal in each pair of switching signals can have a mutual phase difference ∆Φ that can be adjusted by the corresponding high frequency switching signal generator. It should be noted that the first switching signals in the plurality of pairs of switching signals do not have to have the same phase, and the corresponding first high frequency power signals in the corresponding plurality of pairs of high frequency power signals do not have to have the same frequency. It should also be noted that all three implementations are applicable to the topology of Figure 37C and the topology of Figure 37D.

In a first phase difference-based implementation, at least one of the high-frequency switching signal generators 1024 can be configured to adjust the relative phase difference between the first switching signal and the second switching signal within at least one corresponding switching signal pair based on the DC level in the variable load 1070′, thereby generating a transmitted power signal from the high-frequency power link system 1065 as a DC signal correspondingly adjusted in amplitude.

In a second phase difference based implementation, all high frequency switching signal generators 1024 may be configured to modulate the mutual phase difference between the first switching signal and the second switching signal within each pair of switching signals at a phase modulation frequency derived from the frequency of the power signal in the variable load 1070′, thereby generating a transmitted power signal from the high frequency power link system 1065 as an AC power signal modulated at the frequency of the power signal in the variable load 1070′.

In a third phase difference-based implementation, at least one of the one or more high-frequency switching signal generators 1024 can be configured to modulate the mutual phase difference between the first switching signal and the second switching signal within at least one pair of the multiple pairs of switching signals at a phase modulation frequency obtained from the frequency of the power signal in the variable load 1070′, thereby generating a transmitted power signal from the high-frequency power link system as a DC power signal that is a portion of the signal modulated at the frequency of the power signal in the variable load 1070′.

In a frequency difference based implementation, the first high frequency frequency and the second high frequency frequency in each pair of high frequency frequencies may differ by a difference frequency ∆f. At least one high frequency switching signal generator 1024 may be configured to determine the first high frequency frequency and the second high frequency frequency in each pair of switching signals, and set the difference frequency ∆f in each pair to multiply the frequency of the power signal in the variable load 1070′. The high frequency power link system 1065 may be configured to generate a transmitted power signal at the difference frequency ∆f, and the power signal conversion circuit (components 1067 and 1069) may be configured to supply the output power signal to the variable load 1070′ at the frequency of the power signal in the variable load 1070′.

Referring to the systems 950C and 950D of FIG. 37C and FIG. 37D , a method for transmitting power between at least one DC source 1028 and a variable load 1070′ is provided, the method comprising: extracting at least a pair of first high frequency power from each of the at least one DC source 1028 at a pair of first high frequency and second high frequency using a pair of first self-synchronous RF rectifiers 1025A/amplifiers and a second self-synchronous RF rectifier/amplifier 1025B, respectively. The invention relates to a first self-synchronous RF rectifier/amplifier 1025A and a second self-synchronous RF rectifier/amplifier 1025B. The first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B are configured to extract a corresponding pair of the first high frequency power signal and the second high frequency power signal from a single DC source of at least one DC source 1028.

The method further includes: supplying a plurality of pairs of first high-frequency switching signals and second high-frequency switching signals from one or more high-frequency switching signal generators 1024 to one or more pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B at corresponding pairs of first high-frequency frequencies and second high-frequency frequencies, respectively; and establishing and controlling the mutual phase relationship between the first switching signal and the second switching signal in each pair in one or more high-frequency switching signal generators 1024. Each of at least one pair of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B is configured to receive a pair of corresponding first switching signals and second switching signals from a single high frequency switching signal generator in one or more high frequency switching signal generators 1024 at a pair of corresponding first high frequency frequencies and second high frequency frequencies, respectively.

It should be noted that, unless otherwise specified, the first switching signals in the plurality of pairs of high-frequency switching signals do not necessarily have the same frequency, and the corresponding first high-frequency power signals in the plurality of pairs of high-frequency power signals do not necessarily have the same frequency. This situation is applicable to the second switching signal in the plurality of pairs of switching signals and the corresponding second high-frequency power signal in the plurality of pairs of high-frequency power signals separately.

In the method of the embodiment described above and with reference to FIG. 37C , at least one DC source 1028 may be a single DC source 1028; at least one pair of first self-synchronous RF rectifier/amplifier 1025A and second self-synchronous RF rectifier/amplifier 1025B may be a plurality of self-synchronous RF rectifier/amplifiers 1025A, 1025B that all communicate with the single DC source 1028; and one or more high-frequency switching signal generators 1024 may be a single high-frequency switching signal generator 1024 that is configured to provide corresponding first switching signals and second switching signals to a plurality of pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B.

In the method of the embodiment described above and with reference to FIG. 37D , at least one DC source 1028 may be a plurality of DC sources 1028; at least one pair of a first self-synchronous RF rectifier/amplifier 1025A and a second self-synchronous RF rectifier/amplifier 1025B may be a plurality of pairs of self-synchronous RF rectifier/amplifiers 1025A, 1025B, each pair communicating with a corresponding DC source in the plurality of DC sources 1028; and one or more high-frequency switching signal generators 1024 may be a plurality of high-frequency switching signal generators 1024, each high-frequency switching signal generator being configured to provide a corresponding pair of first switching signals and second switching signals to a corresponding pair in the plurality of pairs of first self-synchronous RF rectifier/amplifiers 1025A and second self-synchronous RF rectifier/amplifiers 1025B.

Returning to the method regarding Figures 37C and 37D, the method may further include: receiving a transmitted power signal from the high-frequency power link system 1065 and rectifying the transmitted power signal in the switching mode rectifier 1067 of the power signal conversion circuit; and receiving the rectified power signal from the switching mode rectifier 1067 and expanding the rectified power signal in the expansion circuit 1069 of the power signal conversion circuit to generate an output power signal.

The method may further include: setting the first self-synchronous RF rectifier/amplifier 1025A and the second self-synchronous RF rectifier/amplifier 1025B in each pair to rectification mode; setting the switching mode rectifier 1067 to normally-on mode; extracting power from the variable load 1070′; and transmitting the extracted power to at least one DC source 1028 via the power signal conversion circuit (element 1067 and element 106 in Figures 37C and 37D) and the high-frequency power link system 1065.

The method may further include developing a rectified power signal synchronized with the signal in the variable load 1070' based on a reference signal from the variable load 1070'; transmitting control information from the rest of the system to at least one high frequency switching signal generator via the power signal conversion circuit (components 1067 and 1069), the high frequency power link system 1065, and the plurality of pairs of first self-synchronous RF rectifier/amplifiers 1025A, 1025B. generator 1024; controlling a plurality of components of the systems 950C, 950D by means of one or more controllers 1080 in data communication with the plurality of components; and transmitting information about at least one of the DC level, frequency, and phase of the power signal in the variable load 1070′ to at least one high frequency switching signal generator 1024 using an isolable load information circuit including a phase-locked loop 1095 and an optional isolator system 1090.

Transmitting a power signal in a high frequency power link system may include wirelessly transmitting the power signal; transmitting a power signal in a high frequency power link system wirelessly may include bi-peak wirelessly transmitting the power signal; and transmitting a power signal in a high frequency power link system may include wiredly transmitting the power signal.

In the three phase difference based implementations described directly below with reference to FIG. 37C and FIG. 37D , the first high frequency frequency and the second high frequency frequency in each pair of high frequency frequencies can be the same frequency, and the first switching signal and the second switching signal in each pair of switching signals can have a mutual phase difference that can be adjusted by the corresponding high frequency switching signal generator. It should be noted that the first switching signals in the plurality of pairs of switching signals do not have to have the same phase, and the corresponding first high frequency power signals in the corresponding plurality of pairs of high frequency power signals do not have to have the same frequency.

The method for the first phase difference based implementation includes adjusting a mutual phase difference between a first switching signal and a second switching signal within at least one corresponding switching signal pair based on a DC level in the variable load 1070′ to generate a transmitted power signal from the high frequency power link system 1065 as a DC signal correspondingly adjusted in amplitude. The mutual phase difference is adjusted by at least one of the high frequency switching signal generators 1024.

The method for the second phase difference based implementation includes modulating the mutual phase difference between the first switching signal and the second switching signal in each pair of switching signals at a phase modulation frequency derived from the frequency of the power signal in the variable load 1070′ to generate the transmitted power signal from the high frequency power link system 1065 as an AC power signal modulated at the frequency of the power signal in the variable load 1070′. The mutual phase difference is adjusted by all high frequency switching signal generators 1024.

The method for the third phase difference based implementation includes modulating a mutual phase difference between a first switching signal and a second switching signal within at least one of the plurality of pairs of switching signals at a phase modulation frequency derived from the frequency of the power signal in the variable load 1070′ to generate a transmitted power signal from the high frequency power link system 1065 as a DC power signal that carries a portion of the signal modulated at the frequency of the power signal in the variable load 1070′. The mutual phase difference is adjusted by at least one of the high frequency switching signal generators 1024.

In a frequency difference based implementation, the first high frequency and the second high frequency in each pair of high frequency frequencies may differ by a difference frequency ∆f. The method includes: determining the first high frequency and the second high frequency in each pair of corresponding first switching signals and second switching signals; setting the difference frequency ∆f in each pair to double the frequency of the power signal in the variable load 1070′; generating a transmitted power signal from the high frequency power link system 1065 at the difference frequency ∆f; and supplying the output power signal to the variable load 1070′ at the frequency of the power signal in the variable load 1070.

FIG40A shows a rear view of a photovoltaic module 3220, which includes a photovoltaic cell 3420 and a high-frequency power module 3019 close to the photovoltaic cell 3420. The high-frequency power module 3019 includes a high-frequency power circuit 3016 on a printed circuit board 3024. The view in FIG40A is exploded along axis 3018, which shows a protective cap 3017 for the high-frequency power module 3019 separated from the high-frequency power module 3019. Sunlight shines on the front surface of the photovoltaic cell 3420 in the direction of arrow 3010. The rear surface metallized strip 3424 and the front surface metallized connector 3428 extend across the photovoltaic cell 3420 and connect to the high frequency power circuit 3016 via the metal strip 3020 using electrical contacts on the PC board fingers 3026. In operation, the photovoltaic cell 3420 transmits DC power to the high frequency power circuit 3016 for conversion to a high frequency power signal.

Various power transmission systems that use wireless links or wired links to transmit power have been discussed above. Power transmission systems dedicated to photovoltaic cells have been previously discussed with reference to Figures 35A and 35B. The high-frequency power circuit 3016 of Figure 40A is used in a power transmission system that incorporates a wireless link, as indicated in Figure 41A. The high-frequency power circuit 3016' of Figure 40B is used in a power transmission system that incorporates a wired link, as indicated in Figure 41B, and will be discussed further below.

FIG41A is a reproduction of FIG37D, wherein the DC source/load 1028 of FIG37D may be one of a plurality of photovoltaic cells 3420, and wherein the high frequency power link system 1065 of FIG37D is shown in more detail based on FIG35A. The high frequency power circuit 3016 of FIG40A includes: a high frequency switching signal generator 1024; and the high frequency switching mode power rectifier/amplifier 1025A and 1025B described with reference to FIG37D and the transmitter module 20″ and transmitter resonator 30″ of FIG35A. It should be noted that the photovoltaic cell 3420 is not part of the high frequency power circuit 3016, but is only connected to the high frequency power circuit according to FIG40A. In FIG. 41A , photovoltaic cell 3420 represents a single DC source in DC source 1028 as shown in FIG. 37D .

The receiver resonator 3050 functions the same as the receiver resonator 50″ of FIG. 35A, but is labeled differently in FIG. 41A for clarity. As shown in FIG. 41A, the aggregator 3040 (see also FIG. 42A) includes: the receiver module 40″ of FIG. 35A; and the switch-mode rectifier 1067 and expansion circuit 1069 described with reference to FIG. 37D. The aggregator 3040 may also include any electromagnetic interference filters, wiring junctions, and other components not required to illustrate the function of the system in FIG. 41A. In some embodiments, the aggregator 3040 may also include a controller 1080. The aggregator 3040 may be wired to a variable load 1070′. The components of the high frequency power circuit 3016 can be phase locked to the variable load 1070' using an isolable load information circuit, which includes the phase locked loop 1095 and optional isolator system 1090 in Figure 41A. Alternatively, the information required for the high frequency signal generator 1024 to provide the appropriate switching signals φ _A and φ _B to the high frequency switch mode power rectifier/amplifiers 1025A and 1025B can be directed in an actual implementation to the high frequency switching signal generator 1024 in the opposite direction along the power transmission path via the expansion circuit 1069, the switch mode rectifier 1067, the high frequency power link system 1065′ and the high frequency switch mode power amplifiers 1025A and 1025B. The ability of the high frequency power link system 1065 to perform this information transmission has been described herein with reference to FIG. 7 and FIG. 1. Since this can be done in phase for all individual photovoltaic cells 3420 in the plurality of photovoltaic cells 3420, the power signals from the plurality of photovoltaic cells 3420 can be aggregated in phase by the aggregator 3040. As shown in FIG37D, the high frequency power link system 1065 can be a high frequency dual peak near field wireless link configured for dual peak wireless power transmission.

40B shows a photovoltaic module 3220′ including a photovoltaic cell 3420 and a high-frequency power module 3019′, and a high-frequency power module 3019′ including a high-frequency power circuit 3016′ on a printed circuit board 3024. The high-frequency power circuit 3016′ of FIG40B is used in a power transmission system and is incorporated into the wired link shown in FIG35B.

As shown in FIG41B, where the DC source/load 1028 of FIG37D can be one of a plurality of photovoltaic cells 3420, the high-frequency power circuit 3016′ of FIG40B includes the high-frequency switching signal generator 1024 of FIG37D, high-frequency switching mode power rectifiers/amplifiers 1025A and 1025B, a high-frequency power link system 1065″, and a switching mode rectifier 1067. The wired nature of power transmission excludes any transmitter resonator or receiver resonator (see also FIG35B, compared to FIG35A), so that the high-frequency power link system 1065″ includes the transmitter module 20″ and the receiver module 40″ of FIG35B. It should be noted that the photovoltaic cell 3420 is not part of the high frequency power circuit 3016 here either, but is only connected to the high frequency power circuit according to Figure 40B. Other embodiments of the system of Figure 41B can be similarly described based on Figure 37D and its association in the text, because Figure 41B is largely a description of how the elements of Figure 37D are grouped in an actual photovoltaic system.

For this wired implementation, the aggregator 3040′ (see also FIG. 42B ) includes the expanded circuit 1069 of FIG. 37D . It may also include any electromagnetic interference filters, wiring junctions, and other components not required to illustrate the function of the system in FIG. 41B . In some embodiments, the aggregator 3040 may also include a controller 1080 . The expanded circuit 1069 of the aggregator 3040′ may collect low frequency power signals via wired connections from a plurality of high frequency power circuits 3016′ wired to a corresponding plurality of photovoltaic cells 3420 . The term “low frequency” is used here to describe the frequency of the frequency order of the AC signal in the variable load 1070′, in contrast to the high frequency employed within the high frequency power link system 1065″. Aggregator 3040' may be connected to variable load 1070'. Elements of high frequency power circuit 3016' may be phase locked to variable load 1070' using an isolable load information circuit comprising phase locked loop 1095 and optional isolator 1090 in FIG. 41B. Alternatively, the desired information may also be transmitted via a power transmission circuit as described with reference to the embodiment of FIG. 41A. Since this may be done in phase for all individual photovoltaic cells 3420 in a plurality of photovoltaic cells 3420, the power signals originating from a plurality of photovoltaic cells 3420 may be aggregated in phase by aggregator 3040'.

As described with reference to FIG. 41A , the phase and frequency information from the variable load 1070′, as shown in both FIG. 41A and FIG. 41B , can be sent to the high frequency switching signal generator 1024 via the phase-locked loop 1095 and the optional isolator 1090, and in an actual implementation can be directed in the opposite direction along the power transmission path to the high frequency switching signal generator 1024. In some embodiments, the controller and protection circuit 1080 of FIG. 41A and FIG. 41B can be implemented in the aggregator 3040 and the aggregator 3040′, respectively. It will be noted that in both the wireless and wired embodiments shown in FIGS. 41A and 41B , respectively, the aggregators 3040, 3040′ include an expansion circuit 1069 configured to receive transmitted power from each of at least one photovoltaic cell 3420 at a frequency twice the AC load line frequency when present in a variable load 1070′ and then expand the signal to the AC load line frequency.

In yet another embodiment shown in FIG. 41C , the expanded circuit 1069 of FIG. 41B may be incorporated into each high frequency power circuit 3016″, and thus the aggregator may be a device that collects only all expanded signals or DC signals from each of the expanded circuits 1069 associated with each of the corresponding photovoltaic cells 3420. The aggregator may also include any electromagnetic interference filters, wiring junctions, etc. In certain embodiments, the aggregator may also include a controller 1080. As in FIG. 37D , the high frequency power link system 1065 may be wired or wireless. As in other embodiments described above, the elements of the high frequency power circuit 3016″ may be phase locked to the variable load 1070′. The same means can be used to transmit information about the variable load 1070', as described with reference to Figures 41A and 41B. Since this can be done in phase for all individual photovoltaic cells 3420 in the plurality of photovoltaic cells 3420, the power signals originating from the plurality of photovoltaic cells 3420 can be aggregated in phase by the aggregator.

In one set of embodiments of the system of FIG. 41C , the high frequency power link system 1065 of FIG. 41C may be a wireless high frequency power link system, just as the high frequency power link system 1065′ of FIG. 41A . In some embodiments, the high frequency power link system 1065 may be a dual peak wireless high frequency power link that transmits power locally within the high frequency power circuit 3016″. In this embodiment, the high frequency power link system 1065 may be physically located near a photovoltaic cell (e.g., the photovoltaic cell 3420 of FIG. 40A ). This local power transfer can be between components on a single printed circuit board, such as printed circuit board 3024 of FIG. 40A , or across different layers of one printed circuit board 3024, or even between separate high frequency power circuits 3016′ on different printed circuit boards 3024. As in other embodiments described above, the elements of the high frequency power circuit can be phase locked to any signal that may be present in the variable load 1070′. The same means can be used to transfer information about the variable load 1070′, as described with reference to FIGS. 41A and 41B .

FIG42A is an exploded schematic rear view of a solar panel 3400 based on an array of photovoltaic modules 3220. The high frequency power module 3019 obtains power from the photovoltaic cells 3420, and the protective cap 3017 shown in FIG40A and FIG40B is omitted from the photovoltaic module 3220. The solar panel 3400 further includes: a transparent solar cover 3440; and a frame 3460. For wireless implementations of power transmission according to FIG35A and FIG41A, the aggregator 3040 can be disposed on the frame 3460 or on the receiver resonator 3050. Although the receiver resonator 3050 is shown as a single large panel in FIG43A, in other embodiments, the receiver resonator 3050 can be implemented as a mesh or wire structure. This arrangement is useful in bifacial solar panels, where the solar panel is illuminated from the back in addition to the front.

For wired power transmission as shown in Figures 41B and 42B, the high frequency power module 3019' of the solar panel 3400' based on the array of photovoltaic modules 3220' can be wired to the concentrator 3040' located on the frame 3460 or on a protective sheet 3062 of appropriate size that fills the frame 3460.

It is worth pointing out that the conceptual implementation described with respect to FIG. 37D and the physical arrangement shown in FIG. 42A and FIG. 42B implemented for photovoltaic "solar" panels according to FIG. 41A, FIG. 41B and FIG. 41C provide photovoltaic solar panels that are inherently capable of providing AC power at residential and industrial line frequencies, and in certain embodiments, do so at the PC board level from the high frequency power circuits 3016, 3016' located with the photovoltaic cells 3420, as shown in FIG. 40A and FIG. 40B. In addition, the use of such systems eliminates the need for inverters, which are characteristic of residential photovoltaic systems of the prior art. By shifting the task of generating AC power from a central heavy inverter to each generating point, each panel or each battery can utilize lighter weight, lower unit cost power components, which helps reduce the cost of generating photovoltaic power. In addition, the ability to switch these systems in ∆φ mode as a selection within the high frequency switching signal generator 1024 makes it possible to employ the exact same panels in a DC generation configuration with an existing inverter-based AC power supply system.

The groupings 3410 and 3410' of components in Figures 42A and 42B, respectively, are components used in the packaging of the arrays of photovoltaic modules 3220 and 3220' in Figures 42A and 42B, respectively. Although the electronics incorporated into the photovoltaic modules 3220 and 3220' differ for the wireless or wired embodiments, the packaging proceeds in the same manner. Therefore, the packaging will only be explained with reference to the wireless embodiment and the wired embodiment proceeds in the same manner, except that in the wired case, the wiring from the photovoltaic module 3220' is routed to the aggregator 3040'. The grouping 3410 in FIG. 42A , also referred to hereinafter as a “laminated stack,” includes: an encapsulation layer 3150 ; an array of photovoltaic modules 3220 prior to conformal application of the encapsulation layer 3150 ; an optional additional optically transparent polymer layer 3154 ; and a transparent solar cover 3440 .

FIG43A shows a schematic side view (not shown to scale) of a portion of the photovoltaic module 3220 of FIG40A, which includes a photovoltaic cell 3420 and a high frequency power module 3019. The front solar radiation receiving surface of the photovoltaic cell 3420 is disposed on a transparent solar cover 3440. The transparent solar cover 3440 may be composed of a suitable solar radiation transparent glass. The printed circuit board 3024 of the high frequency power module 3019 is similarly mounted on the transparent solar cover 3440 close to the photovoltaic cell 3420, wherein the high frequency power circuit 3016 is located on the side of the printed circuit board 3024 opposite to the transparent solar cover 3440. For the sake of clarity, the relative sizes of the components in FIG43A have been exaggerated. The photovoltaic module 3220 is encapsulated beneath a conformal encapsulation layer 3150 disposed on the back side of the photovoltaic module 3220 and extending onto the transparent solar cover 3440. As described further below, the conformal encapsulation layer 3150 is applied by thermal vacuum sealing so that any encapsulation gaps, such as gap 3160, are at a pressure lower than the ambient air pressure.

In certain embodiments shown in FIG. 43B , the surface of the transparent solar cover 3440 facing the photovoltaic module 3220 may include an optional additional optically transparent polymer layer 3154. For example, without limitation, the material of the layer 3154 may include ethylene vinyl acetate (EVA). The optional additional optically transparent polymer layer 3154 may enhance the bonding of the photovoltaic module 3220 and the conformal encapsulation layer 3150 to the transparent solar cover 3440 while still allowing the passage of solar radiation.

In certain embodiments, a method of producing a solar panel 3400 is described herein based on the elements of Figures 42A and 43A and the wireless implementation of Figure 41A. The fabrication of a solar panel 3400' based on the elements of Figure 42B and the wired implementation of Figure 41B proceeds in the same manner, except that in the wired case, the wiring from the photovoltaic module 3220' is routed to the concentrator 3040'. An encapsulation layer 3150 of the form shown in Figure 43A can be conformally applied by heat vacuum sealing the heat deformable polymeric sheet 3150 of Figure 42A to the transparent solar cover 3440 above the photovoltaic module array 3220 using a heat vacuum laminating press. This general type of machine is also configured to apply mechanical pressure to the arrangement or stack of encapsulated sheets and solar cells while heating under vacuum. The active solar radiation receiving "front" surface of the photovoltaic module array 3220 can be laid on the transparent solar cover 3440, and the heat deformable polymer sheet 3150 is laid on the back of the photovoltaic module array 3220 to produce the laminated stack 3410 before insertion into the laminating press. Air is exhausted from the laminating press and heat is applied. During heating, mechanical pressure can be applied normal to the plane of the stack of sheets and solar cells. Under the pressure of the ambient air returning to the laminating press, the heat deformable polymer sheet 3150 is pressed against the transparent solar cover 3440 to conformally encapsulate the array of photovoltaic modules 3220, thereby producing the conformal encapsulation layer 3150 shown in Figures 43A and 43B. Due to the vacuum sealing method described above, any encapsulation gap (such as gap 3160 in Figures 43A and 43B) is at a pressure lower than the ambient air pressure. In some embodiments, an additional optically transparent polymer sheet 3154 shown in Figures 43B and 42A can be placed between the transparent solar cover 3440 and the photovoltaic module 3220 prior to the laminating process.

In some embodiments, a protective cap 3017 (see FIG. 40A and FIG. 40B ) may be placed on the high-frequency power module 3019, 3019′ of the photovoltaic module 3220, 3220′. The protective cap 3017 may include one or more polymers, including but not limited to: polyamide, polyphenylene oxide, polyphenylene sulfide, polylactic acid, polyetheretherketone, acrylonitrile-butadiene-styrene, polycarbonate, polyethylene terephthalate, acrylonitrile-styrene-acrylate, polyethylene, polypropylene, polyoxymethylene, polybenzimidazole, polyethersulfone, polyetherimide, polyvinylidene fluoride, polytetrafluoroethylene. The cap formed by any one or more of these compounds can provide suitable protection for the high-frequency power module 3019, 3019′. The protective cap 3017 can be placed on the high frequency power module 3019, 3019' before or after encapsulation. The protective cap 3017 can be encapsulated as an outer shell under the conformal encapsulation layer 3150.

In some embodiments, the protective cap 3017 may protrude through the conformal encapsulation layer 3150. In some embodiments shown in FIG. 44, the protective cap 3017 shields the high frequency power module 3019 or 3019'. The laminated stack 3410' for an embodiment of a solar panel 3400'' includes a heat deformable polymeric sheet 3150'. Prior to lamination, suitable holes 3152 may be formed in the heat deformable polymeric sheet 3150' above the protective cap 3017, the holes having a lateral dimension smaller than the lateral dimension of the protective cap 3017 to maintain the integrity of the composite seal between the encapsulation layer 3150' and the cap 3017.

The conformal encapsulation layer 3150 is used to protect the photovoltaic module 3220 or 3220'. The conformal encapsulation layer 3150 may include one or more layers of cross-linkable and thermoformable polymeric materials, including but not limited to: polyethylene terephthalate, biaxially oriented polyethylene terephthalate, ethylene vinyl acetate, fluorinated coatings, fluorinated polyesters, polyvinyl fluoride; polyvinylidene fluoride, polyethylene vinyl acetate, polyethylene naphthalate, ethylene-tetrafluoroethylene, fluorovinyl ether, tetrafluoroethylene-hexafluoropropylene-vinylidene fluoride copolymer, polyamide, polypropylene, polyethylene, polyvinylidene fluoride short sugar palm fiber.

Although several exemplary aspects and embodiments have been discussed above, those skilled in the art will also recognize certain modifications, arrangements, additions, and sub-combinations thereof. Therefore, it is intended that the following attached patent scope and the patent scope introduced hereafter be interpreted as including all such modifications, arrangements, additions, and sub-combinations consistent with the broadest interpretation of this specification as a whole. [Term Explanation]

Unless the context clearly requires otherwise, throughout this specification and patent application:

“Include,” “comprise,” “comprising,” and the like are to be construed in an inclusive sense as opposed to an exclusive or exhaustive sense; that is, in the sense of “including but not limited to.”

"Connected", "coupled" or any variation thereof means any direct or indirect connection or coupling between two or more elements; the coupling or connection between elements may be physical, logical or a combination thereof; elements formed as one may be considered to be connected or coupled.

"Wired," "wired connection," or any variation thereof, means any physical connection that allows electrical current to flow between, through, or across components of a system through a conductive medium, intermediate circuits, or other means.

"Electrical communication," "power communication," or any variation thereof, means any connection, coupling, interface, or other communication means, hardwired, wireless, or a combination thereof, suitable for transmitting electrical signals between, through, or across components of a system.

"Herein," "above," "below," and words of similar meaning when used in describing this specification shall refer to this specification as a whole rather than any specific part of this specification.

When the term "or" is used with reference to a list of two or more items, the term includes all of the following interpretations of the term: any one of the items in the list, all of the items in the list, and any combination of the items in the list.

The singular forms “a”, “an” and “the” are intended to include any appropriate plural forms.

"Simultaneously" and variations thereof may include simultaneously, substantially simultaneously, and/or occurring simultaneously.

The directional terms used in this specification and any accompanying claims (if any) (e.g., "vertical," "lateral," "horizontal," "upward," "downward," "forward," "backward," "inward," "outward," "vertical," "lateral," "left," "right," "front," "back," "top," "bottom," "below," "above," "below," etc.) depend on the particular orientation of the device described and illustrated. The subject matter described herein can be employed in a variety of alternative orientations. Accordingly, such directional terms are not strictly defined and should not be construed narrowly.

Embodiments include various operations described herein. Such operations can be performed by hardware components, software, firmware, or a combination thereof.

Certain embodiments may be implemented as a computer program product that may include instructions stored on a machine-readable medium. Such instructions may be used to program a general or special processor to perform the operations described. Machine-readable media include any mechanism for storing information in a form (e.g., software or processing application) that is readable by a machine (e.g., a computer). The machine-readable medium may include, but is not limited to, magnetic storage media (e.g., floppy disks), optical storage media (e.g., CD-ROMs), magneto-optical storage media, read-only memory (ROM), random access memory (RAM), erasable programmable memory (e.g., EPROM and EEPROM), flash memory, or another type of media suitable for storing electronic instructions.

In addition, some embodiments may be practiced in a distributed computing environment, where the machine-readable medium is stored on and/or executed by more than one computer system. In addition, information transmitted between computer systems may be pulled or pushed across the communication media connecting the computer systems.

The computer processing components used in the implementation of various embodiments include one or more general-purpose processing devices, such as a microprocessor or central processing unit, a controller, a graphics processing unit (GPU), a mobile computer, etc. Alternatively, the digital processing component may include one or more special-purpose processing devices, such as a digital signal processor (DSP), a special application integrated circuit (ASIC), a field programmable gate array (FPGA), etc. In some embodiments, for example, the digital processing device may be a network processor having multiple processors including a core unit and multiple microengines. In addition, the digital processing device may include any combination of a general-purpose processing device and a special-purpose processing device.

Although the operations of the methods herein are shown and described in a particular order, the order of operations of each method may be changed so that certain operations may be performed in reverse order, or certain operations may be performed at least partially simultaneously with other operations. In another embodiment, instructions or sub-operations of different operations may be performed in an intermittent and/or alternating manner.

In the case of components mentioned above (e.g., software modules, processors, assemblies, devices, circuits, etc.), unless otherwise indicated, references to such components (including references to "means") should be interpreted as including any components that perform the function of the described components (i.e., functional equivalents), including components that are not structurally equivalent to the disclosed structures that perform the functions in the described exemplary embodiments.

For illustrative purposes, specific examples of systems, methods, and apparatus have been described herein. These are merely examples. The techniques provided herein may be applied to systems other than the example systems described above. In the practice of the invention, many changes, modifications, additions, omissions, and arrangements are possible. The invention includes variations of the described embodiments that are obvious to one skilled in the art, including variations obtained by: replacing features, elements, and/or actions with equivalent features, elements, and/or actions; mixing and matching features, elements, and/or actions from different embodiments; combining features, elements, and/or actions of the embodiments described herein with features, elements, and/or actions of other technologies; and/or omitting to combine features, elements, and/or actions from the described embodiments.

This application claims the benefit of U.S. Application No. 63/320,590 filed on March 16, 2022, U.S. Application No. 63/379,547 filed on October 14, 2022, U.S. Application No. 63/476,781 filed on December 22, 2022, and PCT/IB2023/000167 filed on March 15, 2023, the contents of each of which are incorporated herein by reference in their entirety for all purposes.

10: Wireless power transmission system (WPT system) 10′: Multi-transmitter dual-peak near-field resonance wireless power transmission system 10′′: Near-field resonance wireless power transmission system 12: Primary side, transmitter subsystem 12′: Multi-transmitter subsystem 14: Secondary side, resonance receiver subsystem 14A: Receiver subsystem 14B: Receiver subsystem 16: Transmitter subsystem 20, 20′′, 20A′, 20B′, 20C′, 20D′, 20E′, 20F′, 20G′, 20H′, 20I′: Transmitter module 22, 22′′: Controller 24: Sensor 24A: Load detector 24B: Transmitter power sensor 24C: Surrounding object detector (SOD) 24D: distance detector 24E: point 26: component 26A, 26A'': oscillator 26B: power amplifier, self-synchronous RF rectifier/amplifier 26B'': RF power amplifier, power amplifier 26C: filter network, filter, tuning component 26D: matching network, tuning component 26E: compensation network, tuning component 26F: V/I tuning Harmonizer, tuning component 28'': transmission tuning network, transmitter tuning network 30: transmitter resonator, resonator 30A', 30B', 30C', 30D', 30E', 30F', 30G', 30H', 30I', 30'': transmitter resonator 32: first transmitter antenna, antenna, transmitter antenna subsystem 31A: magnetic field 31B : electric field 33': ground shield 35': ground substrate 40, 40'': receiver module 42: controller 42'': receiver controller 44: sensor 44A: receiver power sensor 44B: load detector 44C, 44D: point 46: component, assembly 46A: compensation network 46B: matching network 46C: filter 46D: rectifier 46E: load manager 46E'': load management 48'': receiver tuning network 50: receiver resonator, resonator, receiver antenna, transmitter resonator 50'', 50''': receiver resonator 52: first receiver antenna, antenna, receiver antenna subsystem 60'': non-air gap connection, connection 70: load 70'': load (battery) 70''': AC load, power grid 80: antenna, elongated element, first transmitter antenna 80A: elongated element 80B: gap 80C: thickness of elongated element 82A: bent portion 82B: edge 127C, 127D: active device, transistor 127E: DC source, DC voltage source 127F: third harmonic terminal 127G: drain node 127H : Second harmonic terminal 127I: First harmonic terminal 127J: AC load, AC source, AC signal overload 127K: Level shifter 127L: Phase shifter 130: Transmitter resonator 132: Antenna, first transmitter antenna, transmitter antenna subsystem 132A: Elongated element 132A-1, 132A-2, 132A-3: Part of the elongated element 132B-1, 132B-2, 132B-3: gap 134: antenna, second transmitter antenna, transmitter antenna subsystem 134A: extension element 134A-1, 134A-2, 134A-3: portion of extension element 134B-1, 134B-2, 134B-3: gap 138: spacer, dielectric element 147A: input, AC power, AC source, AC load 147B: active device, transistor 147C: DC load 147D: third harmonic terminal, output 147E: drain node 147F: second harmonic terminal 147G: first harmonic terminal 147H: phase shifter 147I: level shifter 150: receiver resonator 152: first receiver antenna, receiver antenna subsystem system, antenna 154: second receiver antenna, receiver antenna subsystem, antenna 158: spacer, dielectric element 180: antenna 180A: extension element 180B: gap 182A: bend 182B: edge 230: transmitter resonator 232: first transmitter antenna, transmitter antenna subsystem 234: second transmitter antenna, transmitter antenna subsystem 238: spacer 250: receiver resonator 252: first receiver antenna, receiver antenna subsystem 254: second receiver antenna, receiver antenna subsystem 258: spacer 261A, 261B: path 262: splitter 263A: first phase splitter control line 263B: second phase splitter control line 264A: first phase shifter 264B: second Second phase shifter 265A: first active switch control line 265B: second active switch control line 266A: first active switch 266B: second active switch 268A, 268B: passive signal shaping network 269: combiner 280: antenna 280A: extension element, hub element 280a: edge 280B: gap 280C: sector element 282C: thickness of sector element 330: transmitter resonator 332: first transmitter antenna, transmitter antenna subsystem 334: second transmitter antenna, transmitter antenna subsystem 336: third transmitter, transmitter antenna subsystem 338: spacer 339: second spacer, spacer 350: receiver resonator 352: first receiver antenna, receiver antenna subsystem, 354: second receiver antenna, receiver antenna subsystem 356: third receiver antenna, receiver antenna subsystem 358: spacer 359: second spacer, spacer 400, 400': solar panel, array 400'': solar panel arrangement, system, array 410: power conditioning unit, system, power transmission system 420: solar cell, power supply 430: power conditioning unit (PCU) 440: Transparent solar cover 450: Combined assembly 460: Frame 470: Plate 500, 500′: Electric vehicle 510: Chassis, mechanical load bearing structure 520: Battery 530: Electric motor 600, 600′: Power supply system 610: Computer monitor, monitor 620: Desktop 630: Housing, frame 700: DC source/load 700′: AC source/load 800: Power transmission circuit device 801: Silicon wafer 802, 806, 808: Pad 810: Multi-terminal power switching device (MPS device) 812: Silicon single crystal wafer 814: Photovoltaic cell 818: Connection 820: Phase, frequency and duty cycle adjustment circuit (PFDCA circuit) 830: Tuning network 840: Amplitude/frequency/phase detector (AFPD) 850: Voltage/current detector (VID) 860: PM circuit 870: memory 880: controller 890: communication circuit 894: antenna 898: external device and circuit 900: AC load/source 900′: power grid 950, 950′: power transmission system, system 950C, 950D: power transmission system, power signal conversion circuit, system 1024: high frequency switching signal generator 1025A: high frequency switching mode power rectifier/amplifier, self-synchronous RF rectifier/amplifier 102 5B: High frequency switching mode power rectifier/amplifier, self-synchronous RF rectifier/amplifier 1028: DC source/load, DC source 1048: adjacent half-wave 1049: output power signal 1065, 1065′, 1065′′: high frequency power link system 1067: rectifier 1069: unfolded circuit 1070: AC load/source 1070′: AC/DC load/source, variable load 1080: controller and protection circuit, controller 1090: Isolator system 1095: phase-locked loop 3010: arrows 3016, 3016′, 3016′′: high-frequency power circuit 3017: protective cap 3018: axis 3019, 3019′: high-frequency power module 3020: metal strip 3024: printed circuit board 3026: PC board fingers 3040, 3040′: polymerizer 3050: receiver resonator 3062: protective sheet 3150: thermally deformable polymer sheet, encapsulation layer 3150 ′: thermally deformable polymer sheet 3160: gap 3152: hole 3154: optically transparent polymer layer, optically transparent polymer sheet 3220, 3220′: photovoltaic module 3400, 3400′, 3400′′: solar panel 3410, 3410′, 3410′′: lamination, grouping 3420: photovoltaic cell 3424: rear surface metallized strip 3428: front surface metallized connector 3440: transparent solar cover 3460: frame f _A, f _B : frequency f _L : operating frequency ∆f: difference frequency ψ _A ′, ψ _A, ψ _B, ψ _B ': switching signal 1000, 1100, 1200, 1300, 1400, 1500, 1600, 1700, 1800, 2000, 2100, 2200, 2300: method 1010-1060: step 1110-1170: step 1210-1270: step 1310- 1370: Steps 1410 to 1470: Steps 1510 to 1550: Steps 1610 to 1650: Steps 1710 to 1750: Steps 1810 to 1850: Steps 2010 to 2050: Steps 2110 to 2140: Steps 2210, 2220: Steps 2310 to 2344: Steps

Illustrative embodiments are illustrated in the referenced drawings. The embodiments and drawings disclosed herein are intended to be illustrative and not restrictive. In particular: FIG. 1 is a schematic diagram of a wireless power transmission system according to an exemplary embodiment. FIG. 2A , FIG. 2B , and FIG . 2C depict antennas that may be used in various exemplary embodiments, either alone or in combination with other disclosed elements. FIG. 3A and FIG . 3B depict side profile views of antennas that may be used in various exemplary embodiments, either alone or in combination with other disclosed elements. FIG. 4A , FIG. 4B , FIG. 4C , and FIG. 4D depict side profile views of exemplary resonators that may be used in various exemplary embodiments, either alone or in combination with other disclosed elements. FIG. 5 depicts a cross-section of an exemplary resonator that may be used in various exemplary embodiments, either alone or in combination with other disclosed elements. FIG . 6 is a schematic diagram of a primary side of a wireless power transmission system according to an example embodiment. FIG. 7 is a schematic diagram of a secondary side of a wireless power transmission system according to an example embodiment. FIG. 8 is a schematic diagram of an exemplary power amplifier that may be used in various example embodiments, either alone or in combination with other disclosed components. FIG. 9 is a schematic diagram of an exemplary self-synchronous rectifier that may be used in various example embodiments, either alone or in combination with other disclosed components. FIG. 10 shows a more detailed schematic diagram of a V/I tuner for adjusting a power signal to a transmitter resonator according to FIG. 6 according to an example. FIG. 11 shows a flow chart of a near field resonant wireless method for transmitting power bimodally according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency according to an example embodiment. FIG12 is a schematic representation of a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem. FIG13A and FIG13B depict a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem. FIG14 depicts a multi-transmitter near-field resonant wireless power transfer system for transferring power to more than one receiver subsystem. FIG15 shows a flow chart of a wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency. FIG16 shows a flow chart of another wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency. FIG . 17 shows a flow chart of a wireless near-field method for transferring power from a multiple transmitter subsystem to one or more resonant receiver subsystems at a variable resonant power signal oscillation frequency. FIG. 18 shows a flow chart of another wireless near-field method for transferring power from a multiple transmitter subsystem to one or more resonant receiver subsystems at a variable resonant power signal oscillation frequency. FIG . 19A shows a near-field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to a power load. FIG. 19B shows a power transfer system for transferring power from a photovoltaic solar cell to a power load. FIG. 20A and FIG . 20B show front and rear views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG. 19A in a many-to-one configuration. FIG21A and FIG21B show front and rear views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG19A in a one-to-one configuration. FIG22A and FIG22B show front and rear views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG19A in a row-based configuration. FIG23 shows a diagram of a flow chart of a method for wirelessly transferring power from a photovoltaic solar cell to a power load. FIG24 shows a flow chart of another method for wirelessly transferring power from a photovoltaic solar cell array to a power load. FIG25 shows a flow chart of another method for wirelessly transferring power from a photovoltaic solar cell array to a power load. FIG26 illustrates a flow chart of another method for wirelessly transmitting power from a photovoltaic solar cell array to an electrical load. FIG27A illustrates a diagram of a portion of an electric vehicle using an embodiment of a power transmission system. FIG27B illustrates another diagram of a portion of an electric vehicle using an embodiment of a power transmission system. FIG28A illustrates a diagram of a computer monitor using an embodiment of a power transmission system. FIG28B illustrates a computer monitor using another embodiment of a power transmission system. FIG29 illustrates a flow chart of a method for transmitting power from a DC power source to an electrical load. FIG30 illustrates a flow chart of yet another method for transmitting power from a DC power source to an electrical load. FIG . 31 shows a flow chart of a method for transferring power between transmit-receive modules in a dual peak resonant near field RF power transfer system. FIG . 32 shows a schematic diagram of a bidirectional power transfer circuit device. FIG. 33 shows an embodiment of a bidirectional power transfer circuit device. FIG . 34 shows an embodiment of a bidirectional power transfer circuit device implemented in the same silicon wafer as a photovoltaic cell. FIG. 34B shows a combined device of FIG. 34A with a resonator on the surface of a silicon wafer. FIG . 35A shows a near field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to an AC power load. FIG. 35B shows a power transfer system for transferring power from a photovoltaic solar cell to an AC power load. FIG36 shows a schematic diagram of a bidirectional power transmission circuit device. FIG37A shows a schematic diagram of a bidirectional power transmission system for transmitting power between a DC power source and an AC power load using the frequency difference of two high frequency signals. FIG37B shows a schematic diagram of a bidirectional power transmission system for transmitting power, which may be AC or DC, between a DC power source and a variable power load using the phase difference of two high frequency signals. FIG37C shows a schematic diagram of a bidirectional power transmission system for transmitting power, which may be AC or DC, between a DC power source and a variable power load using the phase difference of two high frequency signals and multiple pairs of rectifiers/amplifiers. FIG37D shows a schematic diagram of a bidirectional power transmission system for transmitting power, which may be AC or DC, between multiple DC power sources and variable power loads using a phase difference of two high frequency signals and multiple high frequency switching signal generators and multiple pairs of rectifiers/amplifiers. FIG38 shows the result of the rectified power signal and the expanded power signal in the form of a series of half waves. FIG39 shows a flow chart of a method for transmitting power, which may be AC or DC, between a DC power source and a variable power load. FIG40A shows an exploded view of a photovoltaic module for wirelessly transmitting power, including a photovoltaic cell and a high frequency power module. FIG40B shows an exploded view of a photovoltaic module for wired power transmission, including a photovoltaic cell and a high frequency power module. FIG41A shows a power transmission system for wirelessly transmitting power, which may be AC or DC, from a photovoltaic cell to a variable power load. FIG41B shows a power transmission system for wirelessly transmitting power, which may be AC or DC, from a photovoltaic cell to a variable power load. FIG41C shows a power transmission system for wirelessly transmitting power, which may be AC or DC, from a photovoltaic cell to a variable power load. FIG42A is a schematic exploded rear view of a solar panel for wirelessly transmitting power based on a photovoltaic module array prior to conformal application of an encapsulation layer. FIG42B is a schematic exploded rear view of a solar panel for wired transmission of power based on a photovoltaic module array prior to conformal application of an encapsulation layer. FIG43A shows a schematic side view of a photovoltaic module encapsulated under a conformal encapsulation layer. Figure 43B shows a schematic side view of yet another embodiment of a photovoltaic module encapsulated under a conformal encapsulation layer. Figure 44 is a schematic exploded rear view of a solar panel for wirelessly transmitting power based on a photovoltaic module array including a protective cap prior to conformal application of an encapsulation layer. Figure 45 shows a flow chart of a method for making a solar panel.

10: Wireless power transmission system (WPT system)

12: Primary side, transmitter subsystem

14: Secondary side, resonant receiver subsystem

20: Transmitter module

30: Transmitter Resonator

31A: Magnetic field

31B: Electric field

40: Receiver module

50: Receiver resonator, resonator, receiver antenna, transmitter resonator

Claims (61)

A power transmission system for transmitting power between a direct current (DC) source and a variable load, the system comprising: a first self-synchronous radio frequency rectifier/amplifier and a second self-synchronous radio frequency rectifier/amplifier, configured to extract a first high frequency power signal and a second high frequency power signal from the DC source at a first frequency and a second frequency, respectively; a high frequency power link system, configured to receive and mix the first high frequency power signal and the second high frequency power signal to generate a transmitted power signal; and a power signal conversion circuit, which communicates with the high frequency power link system and the variable load and is configured to generate an output power signal based at least in part on the transmitted power signal, and supply the output power signal to the variable load. The power transmission system as described in claim 1 further includes: a high-frequency switching signal generator, configured to supply a first switching signal and a second switching signal to the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier at the respective first frequency and the second frequency, and to establish and control a mutual phase relationship between the first switching signal and the second switching signal. The power transmission system as described in claim 2, wherein the power signal conversion circuit includes: a switching mode rectifier configured to receive the transmitted power signal from the high-frequency power link system and rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit configured to receive the rectified power signal from the switching mode rectifier and expand the rectified power signal to generate the output power signal. A power transmission system as described in claim 3, wherein the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier are configured to operate in a rectification mode, and the switching mode rectifier is configured to operate in a normally-on mode, thereby allowing power to be extracted from the variable load and transmitted to the DC source via the power signal conversion circuit and the high-frequency power link system. A power transmission system as described in claim 2, wherein: the first frequency and the second frequency are the same frequency; and the first switching signal and the second switching signal have a mutual phase difference that can be adjusted by the high-frequency switching signal generator. A power transmission system as described in claim 5, wherein the high-frequency switching signal generator is configured to adjust the mutual phase difference between the first switching signal and the second switching signal based on a DC level in the variable load, thereby generating the transmitted power signal from the high-frequency power link system as a DC signal correspondingly adjusted in amplitude. A power transmission system as described in claim 5, wherein the high-frequency switching signal generator is configured to modulate the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from a frequency of a power signal in the variable load based at least in part on a modulation function, thereby generating the transmitted power signal from the high-frequency power link system as an alternating current (AC) power signal modulated at the frequency of the power signal in the variable load. A power transmission system as described in claim 2, wherein the first frequency and the second frequency differ by a differential frequency. The power transmission system of claim 8, wherein the high frequency switching signal generator is configured to determine the first frequency and the second frequency and set the difference frequency to double the frequency of the power signal in the variable load. A power transmission system as described in claim 8, wherein: the high frequency power link system is configured to generate the transmitted power signal at the difference frequency; and the power signal conversion circuit is configured to supply the output power signal to the variable load at the frequency of the power signal in the variable load. A power transmission system as described in claim 1, wherein the high frequency power link system includes a wireless power link. A power transmission system as described in claim 11, wherein the wireless high-frequency power link system includes a dual-peak wireless high-frequency power link system. A power transmission system as described in claim 1, wherein the high-frequency power link system includes a wired high-frequency power link. A method for transmitting power between a direct current (DC) source and a variable load, the method comprising: extracting a corresponding first high frequency power signal and a second high frequency power signal from the DC source at a first high frequency frequency and a second high frequency frequency via a corresponding first self-synchronous radio frequency rectifier/amplifier and a second self-synchronous radio frequency rectifier/amplifier; receiving and mixing the first high frequency power signal and the second high frequency power signal in a high frequency power link system to generate a transmitted power signal; generating an output power signal based at least in part on the transmitted power signal in a power signal conversion circuit that communicates with the high frequency power link system and the variable load; and supplying the output power signal to the variable load. The method as claimed in claim 14 further comprises: generating a first switching signal and a second switching signal at the first high frequency and the second high frequency in a high frequency switching signal generator communicating with the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier; and establishing and controlling a mutual phase relationship between the first switching signal and the second switching signal in the high frequency switching signal generator. The method of claim 14 further comprises: receiving the transmitted power signal from the high frequency power link system and rectifying the transmitted power signal in a switching mode rectifier of the power signal conversion circuit; and receiving the rectified power signal from the switching mode rectifier and expanding the rectified power signal in an expansion circuit of the power signal conversion circuit. The method as described in claim 16 further includes: Setting the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier to a rectification mode; Setting the switching mode rectifier to a normally open mode, extracting power from the variable load; and transmitting the extracted power to the DC source via the power signal conversion circuit and the high-frequency power link system. The method of claim 15, wherein transmitting the power signal in the high frequency power link system comprises transmitting the power signal wirelessly. The method of claim 18, wherein wirelessly transmitting the power signal in the high frequency power link system comprises bimodally and wirelessly transmitting the power signal. The method of claim 15, wherein transmitting the power signal in the high frequency power link system comprises transmitting the power signal via a wired connection. A method according to claim 15, wherein the first high frequency and the second high frequency of the first switching signal and the second switching signal are the same frequency; and the first switching signal and the second switching signal have a mutual phase difference that can be adjusted by the high frequency switching signal generator. The method as described in claim 21 further includes: adjusting the mutual phase difference between the first switching signal and the second switching signal based on a DC level in the variable load to generate the transmitted power signal from the high-frequency power link system as a DC signal correspondingly adjusted in amplitude. The method as described in claim 21 further includes modulating the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from a frequency of a power signal in the variable load at least in part based on a modulation function to generate the transmitted power signal from the high-frequency power link system as an alternating current (AC) power signal modulated at the frequency of the power signal in the variable load. The method as claimed in claim 15 further comprises: determining the first high frequency and the second high frequency of the corresponding first switching signal and the second switching signal; and setting the difference frequency to be equal to twice the frequency of the power signal in the variable load. The method of claim 24 further comprises: generating the transmitted power signal from the high frequency power link system at the difference frequency; and supplying the output power signal to the variable load at the frequency of the power signal in the variable load. A power transmission system for transmitting power between at least one direct current (DC) source and a variable load, the system comprising: At least one pair of first self-synchronous radio frequency rectifier/amplifier and second self-synchronous radio frequency rectifier/amplifier, wherein each of the at least one pair of first self-synchronous radio frequency rectifier/amplifier and second self-synchronous radio frequency rectifier/amplifier is configured to extract a corresponding first high frequency power signal and a second high frequency power signal from one of the at least one DC source, and the corresponding first high frequency power signal and the second high frequency power signal have a corresponding first frequency and a second frequency; A high frequency power link system configured to receive and mix the first high frequency power signal and the second high frequency power signal of the corresponding first high frequency power signal and the second power signal to generate a transmitted power signal; and A power signal conversion circuit communicates with the high-frequency power link system and the variable load, wherein the power signal conversion circuit is configured to generate an output power signal based at least in part on the transmitted power signal and supply the output power signal to the variable load. The power transmission system as described in claim 26 further includes: one or more high-frequency switching signal generators, configured to output one or more pairs of first switching signals and second switching signals, wherein: Each of the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier is configured to receive a corresponding pair of the one or more pairs of first switching signals and second switching signals, and the corresponding first switching signals and second switching signals have a corresponding first frequency and second frequency; and Each of the one or more high-frequency switching signal generators is configured to: Supply at least one pair of the one or more pairs of first switching signals and second switching signals to the corresponding one or more pairs of the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier; and Establishing and controlling a mutual phase relationship between the first switching signal and the second switching signal in one corresponding pair of the one or more pairs of the first switching signal and the second switching signal. A power transmission system as described in claim 27, wherein the at least one DC source comprises a single DC source, wherein all pairs of the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier communicate with the single DC source; and wherein the one or more high-frequency switching signal generators comprise a single high-frequency switching signal generator. A power transmission system as described in claim 27, wherein the at least one DC source includes a plurality of DC sources; wherein the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier includes a plurality of pairs of self-synchronous RF rectifier/amplifiers, each pair communicating with a corresponding DC source in the plurality of DC sources; and wherein the one or more high-frequency switching signal generators include a plurality of high-frequency switching signal generators, each of the plurality of high-frequency switching signal generators being configured to provide one of the one or more pairs of first switching signals and second switching signals to a corresponding pair of the plurality of pairs of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier. A power transmission system as described in claim 27, wherein all of the first switching signals in the one or more pairs of first switching signals and second switching signals have the same frequency, and all of the corresponding first high-frequency power signals in the one or more pairs of first high-frequency power signals and second high-frequency power signals have the same frequency. The power transmission system as claimed in claim 26, wherein the power signal conversion circuit comprises: a switching mode rectifier configured to receive the transmitted power signal from the high frequency power link system and rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit configured to receive the rectified power signal from the switching mode rectifier and expand the rectified power signal to generate the output power signal. A power transmission system as described in claim 31, wherein the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier in each pair of the at least one pair of the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier are configured to operate in a rectification mode, and the switching mode rectifier is configured to operate in a normally-on mode, thereby allowing power to be extracted from the variable load and transmitted to the at least one DC source via the power signal conversion circuit and the high-frequency power link system. A power transmission system as described in claim 26, wherein the high frequency power link system includes a wireless power link system. A power transmission system as described in claim 33, wherein the wireless high frequency power link system includes a dual-peak wireless high frequency power link system. A power transmission system as described in claim 26, wherein the high-frequency power link system includes a wired power link system. A power transmission system as claimed in claim 27, wherein the first frequency and the second frequency in each pair of the first frequency and the second frequency are the same; and wherein there is a mutual phase difference between the first switching signal and the second switching signal in each pair of the first switching signal and the second switching signal, and the mutual phase difference can be adjusted by the corresponding one of the one or more high-frequency switching signal generators. A power transmission system as described in claim 36, wherein at least one of the one or more high-frequency switching signal generators is configured to adjust the mutual phase difference between the first switching signal and the second switching signal within at least one corresponding switching signal pair based on a DC voltage level in the variable load, thereby generating the transmitted power signal from the high-frequency power link system as a DC signal that is correspondingly adjusted in amplitude. A power transmission system as described in claim 36, wherein all of the one or more high-frequency switching signal generators are configured to modulate the mutual phase difference between the first switching signal and the second switching signal within each pair of switching signals at a phase modulation frequency derived from the frequency of a power signal in the variable load based at least in part on a modulation function, thereby generating the transmitted power signal from the high-frequency power link system as an AC power signal modulated at the frequency of the power signal in the variable load. A power transmission system as described in claim 36, wherein at least one of the one or more high-frequency switching signal generators is configured to modulate the mutual phase difference between the first switching signal and the second switching signal within at least one pair of the plurality of pairs of switching signals at a phase modulation frequency derived from the frequency of the power signal in the variable load based at least in part on a modulation function, thereby generating the transmitted power signal from the high-frequency power link system as a DC power signal that is a portion of a signal modulated at the frequency of the power signal carried in the variable load. A power transmission system as described in claim 36, wherein all of the first switching signals in the one or more pairs of first switching signals and second switching signals have the same phase, and all of the corresponding first high-frequency power signals in the one or more pairs of high-frequency power signals have the same phase. A power transmission system as described in claim 27, wherein the first frequency and the second frequency in each pair of frequencies differ by a difference frequency. A power transmission system as described in claim 41, wherein each of the one or more high-frequency switching signal generators is configured to determine the first frequency and the second frequency in each pair of frequencies and set the difference frequency in each pair of frequencies to double the frequency of the power signal in the variable load. A power transmission system as described in claim 41, wherein: the high frequency power link system is configured to generate the transmitted power signal at the difference frequency; and the power signal conversion circuit is configured to supply the output power signal to the variable load at the frequency of the power signal in the variable load. A method for transmitting power between at least one direct current (DC) source and a variable load, the method comprising: extracting a corresponding first high-frequency power signal and a second high-frequency power signal from one of the at least one DC source by at least one pair of first self-synchronous radio frequency rectifier/amplifier and second self-synchronous radio frequency rectifier/amplifier, the corresponding first high-frequency power signal and the second high-frequency power signal having a corresponding first frequency and a second frequency; receiving the corresponding first high-frequency power signal and the second high-frequency power signal by a high-frequency power link system; mixing the first high-frequency power signal and the second high-frequency power signal in the high-frequency power link system to generate a transmitted power signal; A power signal conversion circuit in communication with the high frequency power link system and the variable load generates an output power signal based at least in part on the transmitted power signal; and The output power signal is supplied to the variable load. The method as described in claim 44 further includes: Outputting one or more pairs of first switching signals and second switching signals from one or more high-frequency switching signal generators; Receiving a corresponding pair of the one or more pairs of first switching signals and second switching signals by each of the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier, the corresponding first switching signal and second switching signal having a corresponding first frequency and second frequency; Supplying at least one pair of the one or more pairs of first high-frequency switching signals and second high-frequency switching signals from each of the one or more high-frequency switching signal generators to a corresponding pair or pairs of the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier; and A mutual phase relationship between the first switching signal and the second switching signal in a corresponding pair of the one or more pairs of the first switching signal and the second switching signal is established and controlled by each of the one or more high-frequency switching signal generators. A method as described in claim 45, wherein the at least one DC source includes a single DC source, the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier includes a plurality of self-synchronous RF rectifier/amplifiers all communicating with the single DC source, and wherein the one or more high-frequency switching signal generators include a single high-frequency switching signal generator. A method as described in claim 45, wherein the at least one DC source includes a plurality of DC sources, the at least one pair of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier includes a plurality of pairs of self-synchronous RF rectifier/amplifiers, each pair of the plurality of pairs of self-synchronous RF rectifier/amplifiers communicates with a DC source corresponding to one of the plurality of DC sources; and wherein the one or more high-frequency switching signal generators include a plurality of high-frequency switching signal generators, each of the plurality of high-frequency switching signal generators being configured to provide one pair of the one or more pairs of first switching signals and second switching signals to a corresponding pair of the plurality of pairs of first self-synchronous RF rectifier/amplifier and second self-synchronous RF rectifier/amplifier. A method as described in claim 45, wherein all of the first switching signals in the plurality of pairs of first switching signals and second switching signals have the same frequency, and all of the corresponding first high-frequency power signals in the plurality of pairs of first high-frequency power signals and second high-frequency power signals have the same frequency. The method as claimed in claim 44 further comprises: receiving the transmitted power signal and rectifying the transmitted power signal by a switching mode rectifier of the power signal conversion circuit at least partially based on the high frequency power link system; and receiving the rectified power signal from the switching mode rectifier and expanding the rectified power signal in an expansion circuit of the power signal conversion circuit to generate the output power signal. The method as described in claim 49 further includes: Setting the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier in the at least one pair of the first self-synchronous RF rectifier/amplifier and the second self-synchronous RF rectifier/amplifier to a rectification mode; Setting the switching mode rectifier to a normally open mode; Extracting power from the variable load; and Transmitting the extracted power to the at least one DC source via the power signal conversion circuit and the high-frequency power link system. A method as claimed in claim 45, wherein: the first frequency and the second frequency in each pair of the first frequency and the second frequency are the same; and the first switching signal and the second switching signal in each pair of the first switching signal and the second switching signal have a mutual phase difference, and the mutual phase difference can be adjusted by a corresponding one of the one or more high-frequency switching signal generators. The method of claim 51 further comprises: adjusting the mutual phase difference between the first switching signal and the second switching signal in at least one corresponding switching signal pair based at least in part on a DC voltage level in the variable load to generate the transmitted power signal from the high frequency power link system as a DC signal correspondingly adjusted in amplitude, wherein the mutual phase difference is adjusted by at least one of the high frequency switching signal generators. The method of claim 51 further comprises: modulating the mutual phase difference between the first switching signal and the second switching signal in each pair of switching signals at a phase modulation frequency derived from the frequency of a power signal in the variable load at least partially based on a modulation function to generate the transmitted power signal from the high frequency power link system as an alternating current (AC) power signal modulated at the frequency of the power signal in the variable load, wherein the mutual phase difference is adjusted by all of the one or more high frequency switching signal generators. The method of claim 51 further comprises: modulating the mutual phase difference between the first switching signal and the second switching signal in at least one of the plurality of pairs of switching signals at a phase modulation frequency derived from the frequency of the power signal in the variable load based at least in part on a modulation function to generate a DC power signal from the high frequency power link system as a portion of a signal modulated at the frequency of the power signal carried in the variable load, wherein the mutual phase difference is adjusted by at least one of the one or more high frequency switching signal generators. A method as described in claim 51, wherein all of the first switching signals in the plurality of pairs of first switching signals and second switching signals have the same phase, and all of the corresponding first high-frequency power signals in the plurality of pairs of high-frequency power signals have the same phase. A method as described in claim 45, wherein the first frequency and the second frequency in each pair of the first frequency and the second frequency differ by a difference frequency. The method as described in claim 56 further includes: Determining the first frequency and the second frequency in each pair of the corresponding first switching signals and the second switching signals; and Setting the difference frequency in each pair of frequencies to double the frequency of the power signal in the variable load. The method of claim 56 further comprises: generating the transmitted power signal from the high frequency power link system at the difference frequency; and supplying the output power signal to the variable load at the frequency of the power signal in the variable load. A method as described in claim 44, wherein transmitting the power signal in the high frequency power link system includes transmitting the power signal wirelessly. A method as described in claim 59, wherein wirelessly transmitting the power signal in the high frequency power link system includes transmitting the power signal bimodally and wirelessly. A method as described in claim 44, wherein transmitting the power signal in the high frequency power link system includes transmitting the power signal via a wired connection.